WO2018188202A1 - 一种新型无线电能传输磁路耦合机构 - Google Patents

一种新型无线电能传输磁路耦合机构 Download PDF

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Publication number
WO2018188202A1
WO2018188202A1 PCT/CN2017/091608 CN2017091608W WO2018188202A1 WO 2018188202 A1 WO2018188202 A1 WO 2018188202A1 CN 2017091608 W CN2017091608 W CN 2017091608W WO 2018188202 A1 WO2018188202 A1 WO 2018188202A1
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Prior art keywords
side energy
coupling mechanism
magnetic circuit
layer
coil
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PCT/CN2017/091608
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English (en)
French (fr)
Inventor
夏晨阳
任思源
郑凯
刘利民
朱从
朱文婷
陈锐
马念
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China University of Mining and Technology CUMT
China University of Mining and Technology Beijing CUMTB
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China University of Mining and Technology CUMT
China University of Mining and Technology Beijing CUMTB
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Priority to CA3031438A priority Critical patent/CA3031438C/en
Publication of WO2018188202A1 publication Critical patent/WO2018188202A1/zh
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F38/00—Adaptations of transformers or inductances for specific applications or functions
    • H01F38/14—Inductive couplings
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F27/00—Details of transformers or inductances, in general
    • H01F27/28—Coils; Windings; Conductive connections
    • H01F27/2871—Pancake coils
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F17/00—Fixed inductances of the signal type
    • H01F17/0006—Printed inductances
    • H01F2017/0066—Printed inductances with a magnetic layer
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F27/00—Details of transformers or inductances, in general
    • H01F27/28—Coils; Windings; Conductive connections
    • H01F27/2804—Printed windings
    • H01F2027/2809—Printed windings on stacked layers
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F38/00—Adaptations of transformers or inductances for specific applications or functions
    • H01F38/14—Inductive couplings
    • H01F2038/143—Inductive couplings for signals

Definitions

  • the present invention relates to the field of radio energy transmission technologies, and in particular, to a novel radio energy transmission magnetic circuit coupling mechanism.
  • the wireless energy transmission technology is a new power access mode that realizes the transmission of electrical energy from a source device to a powered device under full electrical isolation by means of a space invisible soft medium (such as a magnetic field, an electric field, a laser, a microwave, etc.).
  • This technology fundamentally eliminates the problems of device wear, poor contact, and contact spark caused by the traditional "socket + connector" power supply mode. It is a clean, safe and flexible new power supply mode. It is published by the US Technical Review. Selected as one of the top ten research directions in the future.
  • the wireless energy transmission magnetic circuit coupling mechanism is the key to the difference between the wireless energy transmission technology and the traditional wired power transmission form. Its performance also indicates the advantages and disadvantages of the radio transmission system, so the wireless energy transmission magnetic circuit coupling mechanism Research becomes very important.
  • the most important indicator to measure the performance of the wireless energy transmission magnetic coupling mechanism is the coupling coefficient k, which can consider the coupling degree of a magnetic circuit mechanism. In practice, it is generally between 0.01 and 0.5. The larger the k value, the closer the magnetic circuit mechanism is coupled. The magnetic circuit coupling mechanism is more efficient.
  • the relative position of the magnetic circuit coupling mechanism with a wider offset tolerance range is more practical.
  • the offset direction is used to study the anti-offset characteristics of the magnetic circuit coupling mechanism, and the arbitrary displacement of the magnetic circuit coupling mechanism can be realized by superimposing the above three offset directions.
  • a larger coupling coefficient k can provide a wider range of offset tolerance.
  • the DD type magnetic circuit coupling mechanism is developed by a "magnetic tube” type magnetic circuit coupling mechanism, but compared with the latter, the former provides only a single side magnetic flux path in the air, and the other side magnetic flux path is matched.
  • the ferrite strips form a closed path, so they have a large coupling coefficient in the case of the same gap.
  • the DD-type magnetic circuit coupling mechanism has a good offset tolerance in the direction of its ferrite strip, and its tolerance in the direction parallel to its ferrite bar and rotation around the center of the mechanism is poor.
  • the object of the present invention is to provide a novel radio energy transmission magnetic circuit coupling mechanism which not only has a higher coupling coefficient, but also can rotate in two mutually perpendicular horizontal directions and around the central axis of the mechanism. Provides a wider range of offset tolerance in the direction.
  • a novel radio energy transmission magnetic circuit coupling mechanism comprising: a primary side energy emitting pad and a secondary side energy picking pad, the primary side energy emitting pad and the secondary side energy picking pad are oppositely arranged and parallel to each other; primary side energy emission
  • the pad and the secondary energy pick-up pad are of a two-layer structure, one of which is a coil layer wound by a Litz wire, and the other layer is a core layer; the coil layer and the core layer are both centrally symmetric;
  • the coil layer is composed of two identical rectangular coils stacked orthogonally, and the core layer is a nine-grid grid layer composed of eight ferrite strips of equal length; the primary side energy emitting pad and the secondary side energy picking pad
  • the coil layers are opposite, and the opposite sides of the primary side energy emitting pad and the secondary side energy picking pad are mirror symmetrical with each other.
  • the length of the ferrite strip is equal to the length of the rectangular coil.
  • the ratio of the width to the length of the rectangular coil is 0.7.
  • the novel radio energy transmission magnetic circuit coupling mechanism of the present invention is an excellent magnetic circuit coupling structure, which has a higher coupling coefficient than the related art, and can simultaneously be in two mutually perpendicular horizontal directions and Provides a wider offset tolerance range in three directions, such as the rotation of the central axis of the mechanism, and provides a more diverse selection of magnetic circuit coupling mechanisms for the selection of the magnetic path coupling mechanism of the wireless energy transmission system.
  • Embodiment 1 is a schematic structural view of Embodiment 1;
  • FIG. 2 is a schematic diagram of a winding mode and key parameters of a primary side energy emitting pad in Embodiment 1;
  • FIG. 3 is a model diagram of a magnetic circuit coupling mechanism in the prior art
  • Figure 5 is a comparison diagram of the tolerance characteristics of the center rotation angle under the same conditions of the DD type and the cross type coupling mechanism of the first embodiment
  • FIG. 6 is a comparison diagram of the horizontal offset distance tolerance characteristics of the DD type and the cross type coupling mechanism of the first embodiment under the same conditions;
  • FIG. 7 is a schematic structural view of a ferrite core layer of the cross-type magnetic circuit coupling mechanism according to Embodiment 1 in five different schemes;
  • FIG. 10 is a schematic view showing the structure and parameters of a ferrite core layer in Embodiment 2;
  • Fig. 15 is a configuration diagram of the third embodiment.
  • 101 a first coil layer, 102, a first core layer 201, a second coil layer, 203, and a second core layer.
  • FIG. 1 is a structural diagram of Embodiment 1 of the present invention, including: a primary side energy emitting pad and a secondary side energy picking pad; wherein the primary side energy emitting pad includes a first coil layer 101 and a first magnetic layer The core layer 102, the first coil layer 101 is placed over the first core layer 102; the secondary side energy pickup pad comprises a second coil layer 201 and a second core layer 202, and the second coil layer 202 is placed on the second core layer Below 202.
  • the first coil 101 and the second coil 201 are each composed of two identical rectangular coils stacked in an orthogonal manner. Rectangular coil They are all wound by the Litz wire.
  • the first core layer 102 and the second core layer 202 are each composed of eight ferrite strips arranged vertically and horizontally, and the first core layer 102 and the second core layer 202 are entirely centrally symmetric.
  • the outer length of the first/second core layer 102/202 is equal to the length of the first/second coil 101/201.
  • the primary side energy transmitting pad of the novel wireless energy transmission magnetic circuit coupling mechanism of Embodiment 1 has the same structure as the secondary side energy picking pad, and the winding method is also the same.
  • the winding mode and key parameters are as shown in FIG. 2: the first coil 101 and the first core layer 102 are formed, and the overall structure is center-symmetrical.
  • the first coil 101 is composed of two identical rectangular coils stacked in an orthogonal manner. Therefore, the magnetic circuit coupling mechanism of the present invention is also referred to as a cross-type magnetic circuit coupling mechanism, and the winding manner is as shown by an arrow in FIG.
  • the side length of the ferrite core layer and the length of the rectangular coil are defined as a, and the width of the rectangular coil is defined as b, the number of turns is n, and the core layer ferrite
  • the strip is made of a MnZn ferrite strip material having a width of 30 mm and a thickness of 20 mm.
  • the outer margin of the middle ferrite strip is defined as w.
  • the ratio of b to a is defined as q
  • the ratio of w to a is c.
  • FIG. 3 shows a magnetic circuit coupling mechanism which is relatively common in the prior art and has excellent performance. It is generally referred to as a DD type magnetic circuit coupling mechanism, and is a cross type magnetic circuit coupling mechanism and a DD type magnetic circuit coupling mechanism in Comparative Example 1. Performance, making a cross-type magnetic circuit coupling mechanism of the same size (600*600mm), the same Litz wire length (65.6m), and the same rectangular coil turns (10 ⁇ ) as the DD type magnetic circuit coupling mechanism shown in Fig. 3. As shown in Figure 1. In Fig.
  • the DD type magnetic circuit coupling mechanism uses a 5760 cm 3 volume ferrite material, and the coupling coefficient is 0.21 under an air gap of 200 mm, and the cross type magnetic circuit coupling mechanism uses only a ferrite material of 5184 cm 3 volume. The coupling coefficient reached 0.2439 at an air gap of 200 mm.
  • FIG. 4 to FIG. 6 are further comparison diagrams of the tolerance of the cross-type magnetic circuit coupling mechanism and the DD-type magnetic circuit coupling mechanism under the above conditions, wherein FIG. 4, FIG. 5 and FIG. A comparison of the three coupling characteristics of the coupling coefficient of the path coupling mechanism to the air gap distance, the central rotation angle, and the horizontal offset distance.
  • the curve (1) and the curve (2) in Fig. 4 are the relationship between the coupling coefficient k and the breath distance of the cross-type magnetic circuit coupling mechanism and the DD-type magnetic circuit coupling mechanism, respectively, and it can be clearly seen that the breath is in the range of 100 mm to 250 mm.
  • the cross-type magnetic circuit coupling mechanism in the range is more advantageous than the DD-type magnetic circuit coupling mechanism.
  • the curve (3) and the curve (4) in Fig. 5 are the relationship between the coupling coefficient k and the central rotation offset angle of the cross-type magnetic circuit coupling mechanism and the DD-type magnetic circuit coupling mechanism at a breath distance of 200 mm, respectively.
  • the coupling coefficient k of the DD type magnetic circuit coupling mechanism fluctuates greatly with the increase of the central rotation angle. Especially at 0° and 180°, the k value takes the maximum value and approaches the 0 at 90° and 270°. This brings stability to the entire wireless energy transmission system.
  • a great problem is that, in comparison, the coupling coefficient of the cross-type magnetic circuit coupling mechanism is basically unchanged when the central rotation offset occurs, and its stability value is greater than the coupling coefficient of the DD-type magnetic circuit coupling mechanism.
  • the curve (5) in Fig. 6 shows the coupling coefficient curve of the cross-type magnetic circuit coupling mechanism horizontally offset in the cross or y direction. Since the cross-type magnetic circuit coupling mechanism is centrally symmetrical, the horizontal offset tolerance characteristic in the cross or y direction Similarly, there is only one curve (5) in Fig. 6, and for the DD type magnetic circuit coupling mechanism, the horizontal offset tolerance characteristics in the cross and y directions are different, so they are represented by curves (6) and (7), respectively.
  • the offset tolerance characteristic of the DD type magnetic circuit coupling mechanism in the cross direction is earlier than that in the y direction, and a blind spot (a point where k is 0) occurs when the cross direction is shifted by 220 mm, and the cross type
  • the horizontal offset tolerance characteristic of the magnetic circuit coupling mechanism in the cross or y direction is better than the offset tolerance characteristic of the DD type magnetic circuit coupling mechanism in the cross direction, and the cross type magnetic circuit is shifted in the y direction by a distance of 0-135 mm.
  • the coupling coefficient of the coupling mechanism is larger than the DD type magnetic circuit coupling mechanism. When the offset distance in the y direction is greater than 135 mm, the coupling coefficient of the DD type magnetic circuit coupling mechanism is larger than that of the cross type magnetic circuit coupling mechanism.
  • the cross-type magnetic circuit coupling mechanism of the present invention is an excellent magnetic circuit coupling structure, which has a higher coupling coefficient than the related art, and can be simultaneously perpendicular to each other.
  • a wider offset tolerance range is provided in three directions, such as the horizontal direction and the rotation of the central axis of the mechanism, which provides a more diverse selection of magnetic circuit coupling mechanisms for the selection of the magnetic circuit coupling mechanism of the wireless energy transmission system.
  • the cross-type magnetic circuit coupling mechanism described above is only an original model for convenience of explanation, and is not an optimized result.
  • the following uses the control variable method to further optimize the cross-type magnetic circuit coupling mechanism in combination with the parameters shown in FIG.
  • Figure 7 (a), (b), (c), (d), (e) are ferrite magnets of five different schemes.
  • the core layer in the case of replacing only the ferrite core layer and other conditions are the same, the coupling coefficient and ferrite volume comparison results are shown in Table 1:
  • the ferrite in Figure 7(a)-(e) The amount of bulk material used is decreasing in turn.
  • the ferrite material used in the ferrite core layer in scheme (e) is at least 2592cm 3 , which is only 9/25 of the scheme (a) with the most ferrite material usage, but except Under the 100mm breath, the coupling coefficient of scheme (e) is slightly smaller than that of scheme (a), and the coupling coefficient of scheme (e) is higher than other schemes in other cases.
  • the option (e) is used as the ferrite core layer structure of the cross-type magnetic circuit coupling mechanism of the present invention, and the specific structural parameters under the scheme are optimized below.
  • the ferrite core layer obtained by the cross-type magnetic circuit coupling mechanism as described above is formed by the average longitudinal and transverse cross-distribution of eight ferrite strips, but this is not the optimal structure.
  • the following is combined with the ferrite defined above.
  • the side length of the core layer and the length a of the rectangular coil, the width b of the rectangular coil, the number of turns of the rectangular coil n, the outer margin of the middle ferrite strip is defined as w, and the ratio of b to a is q, w and a
  • the ratio is c and other parameters to further optimize the structure shown in scheme (e).
  • Embodiment 2 Through a large number of experiments, it can be known that under the premise of unsaturated, the width and thickness of the ferrite strip reach a certain value and do not have much influence on the coupling coefficient of the cross-type magnetic circuit coupling mechanism, so for the convenience of analysis,
  • This embodiment uses a relatively easily obtained manganese-zinc ferrite strip material having a width of 30 mm and a thickness of 20 mm. The position of the middle two ferrite strips is the key to optimization.
  • the shape of the cross-type magnetic circuit coupling mechanism is further optimized under the premise of using the optimized ferrite core layer structure as shown in FIG. 10, mainly for the side length of the ferrite core layer and the length of the rectangular coil. a, the width b of the rectangular coil is optimized.
  • the relationship between the coupling coefficient k and q when a takes different values is shown in Fig. 11.
  • the larger the a value is, the higher the coupling coefficient k is, and the coupling coefficient k always takes the maximum value at q 0.7 regardless of the value of a.
  • the k-c curve of the case can be obtained from the figure.
  • the number of turns is independent of the ratio q, which has general applicability in a cross-type magnetic circuit coupling mechanism.
  • first and second are used for descriptive purposes only and are not to be construed as indicating or implying a relative importance or implicitly indicating the number of technical features indicated.
  • features defining “first” or “second” may include at least one of the features, either explicitly or implicitly.
  • the meaning of "a plurality” is at least two, such as two, three, etc., unless specifically defined otherwise.
  • the terms “installation”, “connected”, “connected”, “fixed” and the like shall be understood broadly, and may be either a fixed connection or a detachable connection, unless explicitly stated and defined otherwise. , or integrated; can be mechanical or electrical connection; can be directly connected, or indirectly connected through an intermediate medium, can be the internal communication of two elements or the interaction of two elements, unless otherwise specified Limited.
  • the specific meanings of the above terms in the present invention can be understood on a case-by-case basis.
  • the first feature "on” or “under” the second feature may be a direct contact of the first and second features, or the first and second features may be indirectly through an intermediate medium, unless otherwise explicitly stated and defined. contact.
  • the first A feature “above”, “above” and “above” the second feature may be that the first feature is directly above or above the second feature, or merely that the first feature level is higher than the second feature.
  • the first feature “below”, “below” and “below” the second feature may be that the first feature is directly below or obliquely below the second feature, or merely that the first feature level is less than the second feature.

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Abstract

本发明提出一种新型无线电能传输磁路耦合机构，包括：相对设置且相互平行的原边能量发射垫和副边能量拾取垫；原边能量发射垫和副边能量拾取垫均为双层结构，其中一层为由利兹线绕制而成的线圈层，另一层为磁芯层；线圈层和磁芯层均为中心对称结构；其中，线圈层由两个完全相同矩形线圈正交叠放组成，磁芯层为由8根长度相等的铁氧体条组成的九宫格形状的网格层；铁氧体条的长度与矩形线圈的长相等；原边能量发射垫和副边能量拾取垫的线圈层相对，且原边能量发射垫和副边能量拾取垫相对的一面互为镜像对称。该机构具有更高的耦合系数，且能够同时在两个相互垂直的水平方向以及绕机构中心轴旋转等三个方向上提供更宽的偏移容忍范围。

Description

一种新型无线电能传输磁路耦合机构 技术领域
本发明涉及无线电能传输技术领域，特别涉及一种新型无线电能传输磁路耦合机构。
背景技术
无线电能传输技术是一种借助于空间无形软介质(如磁场、电场、激光、微波等)，实现完全电气隔离条件下电能由源设备传递至受电设备的全新电能接入模式。该技术从根本上杜绝了传统“插座+接线器”供电模式带来的器件磨损、接触不良、接触火花等问题，是一种洁净、安全、灵活的新型供电模式，被美国《技术评论》杂志评选为未来十大科研方向之一。
其中，无线电能传输磁路耦合机构作为无线电能传输技术与传统有线电能传输形式本质区别的关键，其性能的好坏也表征了无线电传输系统的优劣，所以对无线电能传输磁路耦合机构的研究就变得十分重要。衡量无线电能传输磁路耦合机构性能最关键的指标就是耦合系数k，它可以考量一个磁路机构的耦合程度，实际中一般在0.01-0.5之间，k值越大表明磁路机构耦合越紧密，磁路耦合机构效率越高。由于无线电能传输磁路耦合机构的原边能量发射垫与副边能量拾取垫之间为实现非接触而存在较大空气间隙，所以副边能量拾取垫与原边能量发射垫很难正对，其相对位置难免发生一些偏移，所以具有更宽的偏移容忍范围的磁路耦合机构才更具实用性。原边能量发射垫与副边能量拾取垫可能存在的偏移位置有很多，所以为研究方便一般选取与副边能量拾取垫共面的两个互相垂直的水平方向以及绕其中心轴旋转这三个偏移方向来研究磁路耦合机构的抗偏移特性，通过上述三个偏移方向的叠加即可实现磁路耦合机构任意偏移情况。特别地，更大的耦合系数k就能够提供更宽的偏移容忍范围。
关于无线电能传输磁路耦合机构的研究很多，但在相关技术中奥克兰大学提出的DD型磁路耦合机构由于其本身良好特性而被广泛应用。DD型磁路耦合机构是由“磁管”型磁路耦合机构发展而来，但与后者相较，前者在空气中仅提供单侧磁通路径，而另一侧的磁通路径经过搭配的铁氧体条形成闭合路径，所以在相同间隙情况下具有较大耦合系数。同时，DD型磁路耦合机构在垂直其铁氧体条方向具有较好的偏移容忍度，而在平行其铁氧体条方向以及绕机构中心旋转偏移容忍度较差
发明内容
发明目的：本发明的目的在于提出一种新型无线电能传输磁路耦合机构，该机构不但具有更高的耦合系数，而且能够同时在两个相互垂直的水平方向以及绕机构中心轴旋转等三个方向上提供更宽的偏移容忍范围。
技术方案：为实现上述技术效果，本发明提出以下技术方案：
一种新型无线电能传输磁路耦合机构，其特征在于，包括：原边能量发射垫和副边能量拾取垫，原边能量发射垫和副边能量拾取垫相对设置且相互平行；原边能量发射垫和副边能量拾取垫均为双层结构，其中一层为由利兹线绕制而成的线圈层，另一层为磁芯层；线圈层和磁芯层均为中心对称结构；其中，线圈层由两个完全相同矩形线圈正交叠放组成，磁芯层为由8根长度相等的铁氧体条组成的九宫格形状的网格层；原边能量发射垫和副边能量拾取垫的线圈层相对，且原边能量发射垫和副边能量拾取垫相对的一面互为镜像对称。
进一步的，所述铁氧体条的长度与矩形线圈的长相等。
进一步的，所述磁芯层中间的4根铁氧体条中，任意两根相互平行的铁氧体条的位置满足以下条件：
w＝0.2a
式中，w表示两根相互平行的铁氧体条的外边距；a表示矩形线圈的长。
进一步的，所述矩形线圈的宽度与长度之比为0.7。
有益效果：与现有技术相比，本发明具有以下优势：
本发明所述的新型无线电能传输磁路耦合机构是一种性能优良的磁路耦合结构，与相关技术相比，其具有更高的耦合系数，而且能够同时在两个相互垂直的水平方向以及绕机构中心轴旋转等三个方向上提供更宽的偏移容忍范围，为无线电能传输系统磁路耦合机构选取提供了更多样化的磁路耦合机构选择。
附图说明
图1是实施例1的结构示意图；
图2是实施例1中原边能量发射垫的绕线方式以及关键参数示意图；
图3是现有技术中的磁路耦合机构模型图；
图4是DD型和实施例1所述十字型路耦合机构在同等条件下对气隙距离容忍特性的对比图；
图5是DD型和实施例1所述十字型路耦合机构在同等条件下对中心旋转角度容忍特性的对比图；
图6是DD型和实施例1所述十字型路耦合机构在同等条件下对水平偏移距离容忍特性的对比图；
图7是五种不同方案下的实施例1所述十字型磁路耦合机构铁氧体磁芯层结构示意图；
图8是在200mm气息距离并且n＝10匝条件下，当a不同而q＝0.5时，实施例1所述十字型磁路耦合机构耦合系数k与c的关系曲线对比图；
图9是在200mm气息距离并且n＝10匝条件下，当q不同而a＝600mm时，实施例1所述十字型磁路耦合机构耦合系数k与c的关系曲线对比图；
图10是实施例2中铁氧体磁芯层结构及参数示意图；
图11是实施例2所述十字型路耦合机构在n＝10匝、气息距离为200mm条件下，当a取不同值时，耦合系数k与q的关系曲线图；
图12是实施例2所述十字型路耦合机构在n＝10匝、a＝600mm条件下，当气息距离取不同值时，耦合系数k与q的关系曲线图；
图13是实施例2所述十字型路耦合机构在a＝600mm、气息距离为200mm条件下，q以0.01为步长从0.5到1变化以及矩形线圈匝数以10为步长从10匝到30匝变化而形成的30种情况的k随c变化曲线；
图14是采用图16所示最优铁氧铁磁芯层结构并且在a＝600mm、Air gap＝200mm前提下，矩形线圈匝数n分别为10匝、20匝、30匝三种情况下k随q变化曲线；
图15是实施例3的结构图。
图中：101、第一线圈层，102、第一磁芯层，201、第二线圈层，203、第二磁芯层。
具体实施方式
下面结合附图对本发明作更进一步的说明。
实施例1：如图1所示为本发明实施例1的结构图，包括：原边能量发射垫和副边能量拾取垫；其中，原边能量发射垫包括第一线圈层101和第一磁芯层102，第一线圈层101放置在第一磁芯层102上方；副边能量拾取垫包括第二线圈层201和第二磁芯层202，第二线圈层202放置在第二磁芯层202下方。
第一线圈101与第二线圈201均由两个完全相同矩形线圈正交叠放组成。矩形线圈 均由利兹线绕制而成。
第一磁芯层102和第二磁芯层202均由8个铁氧体条纵横交叉排列组成，第一磁芯层102和第二磁芯层202整体呈中心对称。
第一/二磁芯层102/202的外边长与第一/二线圈101/201的长相等。
实施例1中的新型无线电能传输磁路耦合机构的原边能量发射垫与副边能量拾取垫的结构相同，绕线方式也相同。以原边能量发射垫为例，其绕线方式及关键参数如图2所示：由第一线圈101与第一磁芯层102组成，整体结构呈中心对称。第一线圈101又由两个完全相同的矩形线圈正交叠放组成，所以也称本发明磁路耦合机构为十字型磁路耦合机构，其绕制方式如图2中箭头所示。为方便进一步说明磁路耦合机构的优化构成，将铁氧体磁芯层的边长以及矩形线圈的长定义为a，定义矩形线圈的宽为b，匝数为n，磁芯层铁氧体条采用宽为30mm，厚度为20mm的锰锌铁氧体条材料，中间铁氧体条的外边距定义为w，同时，定义b与a的比值为q，以及w与a的比值为c。
图3所示为现有技术中较为常见且性能优良的磁路耦合机构，一般称为DD型磁路耦合机构，为对比实施例1中十字型磁路耦合机构与DD型磁路耦合机构的性能，制作与图3所示DD型磁路耦合机构相同尺寸(600*600mm)、相同利兹线线长(65.6m)、相同矩形线圈匝数(10匝)条件下的十字型磁路耦合机构如图1所示。图3中，DD型磁路耦合机构使用5760cm3体积的铁氧体材料，在200mm的空气间隙下耦合系数为0.21，而十字型磁路耦合机构仅使用5184cm3体积的铁氧体材料，其耦合系数就在200mm的空气间隙下达到了0.2439。
图4至图6为十字型磁路耦合机构与DD型磁路耦合机构在上述条件下对发生偏移情况容忍度的进一步对比图，其中，图4、图5和图6分别是两种磁路耦合机构耦合系数对气隙距离、中心旋转角度以及水平偏移距离三个容忍特性的对比图。
图4中的曲线(1)和曲线(2)分别是十字型磁路耦合机构和DD型磁路耦合机构的耦合系数k与气息距离之间的关系曲线，明显可以看出在100mm到250mm气息范围内十字型磁路耦合机构比DD型磁路耦合机构更有优势。
图5中曲线(3)、曲线(4)分别是十字型磁路耦合机构和DD型磁路耦合机构在200mm气息间距下的耦合系数k与中心旋转偏移角度的关系曲线，由图可知，DD型磁路耦合机构耦合系数k随着中心旋转角度的增大，起伏很大，尤其在0°和180°时k值取到极大值点而在90°与270°时趋近为0，这对整个无线电能传输系统的稳定工作带来 了极大的困扰，相较而言，十字型磁路耦合机构在发生中心旋转偏移时，其耦合系数基本不变且其稳定值大于DD型磁路耦合机构的耦合系数。
图6中曲线(5)表示十字型磁路耦合机构沿十字或y方向水平偏移下的耦合系数曲线，由于十字型磁路耦合机构呈中心对称，所以在十字或y方向水平偏移容忍特性相同，图6中仅有一条曲线(5)表示，而对于DD型磁路耦合机构，其在十字与y方向水平偏移容忍特性不同，所以分别由曲线(6)、(7)表示，从图中可以得到，DD型磁路耦合机构在十字方向上的偏移容忍特性要比其早在y方向上差，并且在十字方向偏移220mm时出现盲点(k为0的点)，十字型磁路耦合机构沿十字或y方向的水平偏移容忍特性要优于DD型磁路耦合机构在十字方向上的偏移容忍特性，而在y方向偏移0-135mm距离时，十字型磁路耦合机构耦合系数大于DD型磁路耦合机构，当在y方向偏移距离大于135mm后，DD型磁路耦合机构耦合系数要大于十字型磁路耦合机构。
综上所述，本发明所述的十字型磁路耦合机构是一种性能优良的磁路耦合结构，与相关技术相比，其具有更高的耦合系数，而且能够同时在两个相互垂直的水平方向以及绕机构中心轴旋转等三个方向上提供更宽的偏移容忍范围，为无线电能传输系统磁路耦合机构选取提供了更多样化的磁路耦合机构选择。
上文所述的十字型磁路耦合机构只是便于说明的原始模型，而不是最优化的结果，下面结合图2所示参数，运用控制变量法对十字型磁路耦合机构做进一步优化分析。
首先对十字型磁路耦合机构的铁氧体磁芯层进行优化设计，图7(a)、(b)、(c)、(d)、(e)为五种不同方案的铁氧体磁芯层，在仅替换铁氧体磁芯层而其他条件不变情况下的耦合系数与铁氧体体积对比结果如表1所示：
表1
Figure PCTCN2017091608-appb-000001
从表1中可以得到，随着气息距离的增大，耦合系数会越来越小但并不是使用铁氧 体材料越多，效果越好，图7(a)-(e)中的铁氧体材料使用量依次递减，方案(e)中铁氧体磁芯层的铁氧体材料使用量最少为2592cm3，仅为铁氧体材料使用量最多的方案(a)的9/25，但是除在100mm气息下，方案(e)的耦合系数略小于方案(a)，其余情况下方案(e)的耦合系数都高于其他方案。综上所述，选择方案(e)作为本发明十字型磁路耦合机构铁氧体磁芯层结构，下面对该方案下的具体结构参数进行优化。
前文所出现的十字型磁路耦合机构得铁氧体磁芯层是由8个铁氧体条平均纵横交叉分布形成网格状，但这并不是最优结构，下面结合前文定义的铁氧体磁芯层的边长以及矩形线圈的长a，矩形线圈的宽b，矩形线圈匝数n，中间铁氧体条的外边距定义为w，以及b与a的比值为q，w与a的比值为c等参数对方案(e)所示结构做进一步优化。
实施例2：通过大量实验可以知道在未饱和前提下，铁氧体条的宽度与厚度到达一定值后对十字型磁路耦合机构的耦合系数并不会有太大影响，所以为方便分析，本实施例使用较易获得的宽为30mm，厚度为20mm的锰锌铁氧体条材料。中间两个铁氧体条的位置是优化的关键，图8至图9所示曲线均为在200mm气息距离并且n＝10匝条件下十字型磁路耦合机构耦合系数k随w与a的比值为c的关系曲线。
其中图8表示仅当a不同而q＝0.5时k与c的关系曲线；而图9为仅当q不同而a＝600mm时k与c的关系曲线。从图8和9可得，在不同的a与q条件下，十字型磁路耦合机构的耦合系数k都在c＝0.2处取得最大值(Max)，所以可以得到最优铁氧体磁芯层结构如图10所示，即当中间两个铁氧体条的外边距w＝0.2a时为最优结构。
下面在采用如图10所示优化后的铁氧体磁芯层结构前提下，对十字型磁路耦合机构的形状进一步优化，主要是对铁氧体磁芯层的边长以及矩形线圈的长a，矩形线圈的宽b，进行优化。为方便分析先假设n＝10匝、气息距离为200mm条件下，当a取不同值时耦合系数k与q的关系曲线如图11所示。由图11中曲线可知，a值越大耦合系数k越高，而无论a取何值时，耦合系数k总在q＝0.7处取得最大值。图12为n＝10匝、a＝600mm条件下，当气息距离(Air gap)去不同值时耦合系数k与q的关系曲线，由图中可以看出，气息距离越小耦合系数k越高，同样的，无论气息距离为多少，耦合系数k总在q＝0.7处取得最大值。综上所述，矩形线圈的宽b与长a的比值q存在最优解，即在同一条件下，当q＝0.7时十字型磁路耦合机构的耦合系数k最大。
为了分析某一特性参数对十字型磁路耦合机构，前文诸多优化分析都是建立在矩形线圈匝数为10匝条件下，虽然这种做法有利于优化分析过程，但其特殊化的分析过程 也会使其结论不具有普遍性，为使优化结果更具普遍性，现在改变矩形线圈匝数n条件下，验证前文优化分析结果是否依然成立。
图13所示为在a＝600mm、Air gap＝200mm前提下，q以0.01为步长从0.5到1变化以及矩形线圈匝数以10为步长从10匝到30匝变化而形成的30种情况的k随c变化曲线，从图中可以得到，30条曲线同时在c＝0.2处取得最大值(Max)点，因此可以验证图10所示铁氧铁磁芯层最优结构与矩形线圈匝数和比值q无关，其在十字型磁路耦合机构中具有普遍适用性。图13为使用图15所示最优铁氧铁磁芯层结构并且在a＝600mm、Air gap＝200mm前提下，矩形线圈匝数n分别为10匝、20匝、30匝三种情况下k随q变化曲线，由图可知，3条曲线同时在q＝0.7取得最大值点，所以最优矩形线圈的宽b与长a的比值q为0.7，其与矩形线圈匝数n无关，具有普遍性。
由上述可得，十字型磁路耦合机构的原边能量发射垫或副边能量拾取垫优化结构示意图如图15所示，图15即为实施例3的结构图，其中q＝0.7，w＝0.2a。
在本发明的描述中，需要理解的是，术语“中心”、“纵向”、“横向”、“长度”、“宽度”、“厚度”、“上”、“下”、“前”、“后”、“左”、“右”、“竖直”、“水平”、“顶”、“底”“内”、“外”、“顺时针”、“逆时针”、“轴向”、“径向”、“周向”等指示的方位或位置关系为基于附图所示的方位或位置关系，仅是为了便于描述本发明和简化描述，而不是指示或暗示所指的装置或元件必须具有特定的方位、以特定的方位构造和操作，因此不能理解为对本发明的限制。
此外，术语“第一”、“第二”仅用于描述目的，而不能理解为指示或暗示相对重要性或者隐含指明所指示的技术特征的数量。由此，限定有“第一”、“第二”的特征可以明示或者隐含地包括至少一个该特征。在本发明的描述中，“多个”的含义是至少两个，例如两个，三个等，除非另有明确具体的限定。
在本发明中，除非另有明确的规定和限定，术语“安装”、“相连”、“连接”、“固定”等术语应做广义理解，例如，可以是固定连接，也可以是可拆卸连接，或成一体；可以是机械连接，也可以是电连接；可以是直接相连，也可以通过中间媒介间接相连，可以是两个元件内部的连通或两个元件的相互作用关系，除非另有明确的限定。对于本领域的普通技术人员而言，可以根据具体情况理解上述术语在本发明中的具体含义。
在本发明中，除非另有明确的规定和限定，第一特征在第二特征“上”或“下”可以是第一和第二特征直接接触，或第一和第二特征通过中间媒介间接接触。而且，第 一特征在第二特征“之上”、“上方”和“上面”可是第一特征在第二特征正上方或斜上方，或仅仅表示第一特征水平高度高于第二特征。第一特征在第二特征“之下”、“下方”和“下面”可以是第一特征在第二特征正下方或斜下方，或仅仅表示第一特征水平高度小于第二特征。
在本说明书的描述中，参考术语“一个实施例”、“一些实施例”、“示例”、“具体示例”、或“一些示例”等的描述意指结合该实施例或示例描述的具体特征、结构、材料或者特点包含于本发明的至少一个实施例或示例中。在本说明书中，对上述术语的示意性表述不必须针对的是相同的实施例或示例。而且，描述的具体特征、结构、材料或者特点可以在任一个或多个实施例或示例中以合适的方式结合。此外，在不相互矛盾的情况下，本领域的技术人员可以将本说明书中描述的不同实施例或示例以及不同实施例或示例的特征进行结合和组合。
以上所述仅是本发明的优选实施方式，应当指出：对于本技术领域的普通技术人员来说，在不脱离本发明原理的前提下，还可以做出若干改进和润饰，这些改进和润饰也应视为本发明的保护范围。

Claims (4)

  1. 一种新型无线电能传输磁路耦合机构，其特征在于，包括：原边能量发射垫和副边能量拾取垫，原边能量发射垫和副边能量拾取垫相对设置且相互平行；原边能量发射垫和副边能量拾取垫均为双层结构，其中一层为由利兹线绕制而成的线圈层，另一层为磁芯层；线圈层和磁芯层均为中心对称结构；其中，线圈层由两个完全相同矩形线圈正交叠放组成，磁芯层为由8根长度相等的铁氧体条组成的九宫格形状的网格层；原边能量发射垫和副边能量拾取垫的线圈层相对，且原边能量发射垫和副边能量拾取垫相对的一面互为镜像对称。
  2. 根据权利要求1所述的一种新型无线电能传输磁路耦合机构，其特征在于，所述铁氧体条的长度与矩形线圈的长相等。
  3. 根据权利要求2所述的一种新型无线电能传输磁路耦合机构，其特征在于，所述磁芯层中间的4根铁氧体条中，任意两根相互平行的铁氧体条的位置满足以下条件：
    w＝0.2a
    式中，w表示两根相互平行的铁氧体条的外边距；a表示矩形线圈的长。
  4. 根据权利要求3所述的一种新型无线电能传输磁路耦合机构，其特征在于，所述矩形线圈的宽度与长度之比为0.7。
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CN114429851A (zh) * 2022-01-25 2022-05-03 哈尔滨工业大学 一种绕组线圈及其绕制方法及无线电能传输装置
CN114974853A (zh) * 2022-05-05 2022-08-30 重庆大学 四方交叠式无线电能传输耦合线圈结构

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CN108448738B (zh) * 2018-04-17 2020-10-02 中国矿业大学 一种三相感应式无线电能传输系统的电磁耦合机构
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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2005109195A (ja) * 2003-09-30 2005-04-21 Murata Mfg Co Ltd 積層コイル部品
CN102946154A (zh) * 2012-11-17 2013-02-27 福州大学 一种无线电能传输磁耦合结构及其电路
CN204481546U (zh) * 2015-04-09 2015-07-15 浙江大学 一种偏移敏感度低的汽车用无线充电装置
CN106230124A (zh) * 2016-08-19 2016-12-14 武汉理工大学 一种磁耦合无线能量传输装置的双面不对称线圈

Family Cites Families (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2012018268A1 (en) * 2010-08-05 2012-02-09 Auckland Uniservices Limited Inductive power transfer apparatus
CN103733460B (zh) * 2011-07-08 2019-07-23 奥克兰联合服务有限公司 用于感应功率传输系统的磁结构的互操作性
CN103400682B (zh) * 2013-08-14 2016-08-24 广西电网公司电力科学研究院 一种磁芯结构以及基于该磁芯结构的电磁耦合装置
CA2957903A1 (en) * 2014-08-12 2016-02-18 Powerbyproxi Limited System and method for power transfer
CN104347257A (zh) * 2014-10-24 2015-02-11 天津榕丰科技有限公司 一种用于无线充电和无线供电的中空磁芯装置

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2005109195A (ja) * 2003-09-30 2005-04-21 Murata Mfg Co Ltd 積層コイル部品
CN102946154A (zh) * 2012-11-17 2013-02-27 福州大学 一种无线电能传输磁耦合结构及其电路
CN204481546U (zh) * 2015-04-09 2015-07-15 浙江大学 一种偏移敏感度低的汽车用无线充电装置
CN106230124A (zh) * 2016-08-19 2016-12-14 武汉理工大学 一种磁耦合无线能量传输装置的双面不对称线圈

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114429851A (zh) * 2022-01-25 2022-05-03 哈尔滨工业大学 一种绕组线圈及其绕制方法及无线电能传输装置
CN114974853A (zh) * 2022-05-05 2022-08-30 重庆大学 四方交叠式无线电能传输耦合线圈结构
CN114974853B (zh) * 2022-05-05 2023-09-15 重庆大学 四方交叠式无线电能传输耦合线圈结构

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