WO2017188591A1 - 무선 통신 시스템에서 위상 잡음 추정을 위한 신호 전송 방법 - Google Patents
무선 통신 시스템에서 위상 잡음 추정을 위한 신호 전송 방법 Download PDFInfo
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/003—Arrangements for allocating sub-channels of the transmission path
- H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2602—Signal structure
- H04L27/261—Details of reference signals
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/01—Reducing phase shift
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
- H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
- H04B7/0617—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal for beam forming
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
- H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
- H04B7/0619—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side
- H04B7/0621—Feedback content
- H04B7/0626—Channel coefficients, e.g. channel state information [CSI]
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04J—MULTIPLEX COMMUNICATION
- H04J13/00—Code division multiplex systems
- H04J13/0007—Code type
- H04J13/0055—ZCZ [zero correlation zone]
- H04J13/0059—CAZAC [constant-amplitude and zero auto-correlation]
- H04J13/0062—Zadoff-Chu
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/0202—Channel estimation
- H04L25/0224—Channel estimation using sounding signals
- H04L25/0228—Channel estimation using sounding signals with direct estimation from sounding signals
- H04L25/023—Channel estimation using sounding signals with direct estimation from sounding signals with extension to other symbols
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2647—Arrangements specific to the receiver only
- H04L27/2655—Synchronisation arrangements
- H04L27/2668—Details of algorithms
- H04L27/2673—Details of algorithms characterised by synchronisation parameters
- H04L27/2675—Pilot or known symbols
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/0001—Arrangements for dividing the transmission path
- H04L5/0014—Three-dimensional division
- H04L5/0023—Time-frequency-space
- H04L5/0025—Spatial division following the spatial signature of the channel
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/0001—Arrangements for dividing the transmission path
- H04L5/0003—Two-dimensional division
- H04L5/0005—Time-frequency
- H04L5/0007—Time-frequency the frequencies being orthogonal, e.g. OFDM(A), DMT
Definitions
- the following description relates to a wireless communication system, and more particularly, to a method and apparatus for transmitting a signal for phase noise estimation in a WLAN system.
- Ultra-high frequency wireless communication systems using millimeter wave are configured such that the center frequency operates at a few GHz to several tens of GHz. Due to the characteristics of the center frequency, path loss may be prominent in the shadow area in the mmWave communication system. Considering that the synchronization signal should be stably transmitted to all terminals located within the coverage of the base station, the mmWave communication system designs and transmits the synchronization signal in consideration of the potential deep-null phenomenon that may occur due to the characteristics of the ultra-high frequency band described above. Should be.
- the present invention has been made to solve the above problems, and an object of the present invention is to enable accurate decoding of a received signal by improving a phase noise estimation process of a terminal in a wireless communication system.
- Another object of the present invention is to define a reference signal capable of channel correction with phase noise estimation.
- a method of generating a phase tracking reference signal (PTRS) used for estimating phase noise in a downlink signal may include generating a PTRS on a region where a data channel is mapped in a downlink resource region. Mapping the symbols to predetermined Orthogonal Frequency Division Multiplexing (OFDM) symbol intervals, and transmitting the PTRS to the UE.
- OFDM Orthogonal Frequency Division Multiplexing
- 2 or 4 OFDM symbol intervals may be applied to the predetermined OFDM symbol interval.
- the PTRS of a specific antenna port may be mapped onto a subcarrier on which a DeModulation Reference Signal (DMRS) of a specific antenna port is disposed.
- DMRS DeModulation Reference Signal
- PTRSs of the same antenna port may be mapped on the same OFDM symbol.
- PTRSs of the same antenna port mapped on different subcarriers may be mapped on different OFDM symbols.
- the OFDM symbol to which the PTRS is mapped may be determined from a location where a control channel E or a channel state information reference signal (CSI-RS) and a sounding reference signal (SRS) transmitted in the downlink resource region are mapped.
- CSI-RS channel state information reference signal
- SRS sounding reference signal
- the PTRS may be mapped to an OFDM symbol except where a control channel is mapped.
- the PTRS may be mapped to an OFDM symbol except for a location where the CSI-RS and the SRS are mapped.
- the base station for solving the technical problem includes a transmitter, a receiver, and a processor operating in connection with the transmitter and the receiver, the processor, a phase tracking reference signal (PTRS) used to estimate the phase noise in the downlink signal Generates PT, maps the PTRS to a predetermined Orthogonal Frequency Division Multiplexing (OFDM) symbol interval on the region where the data channel is mapped in the downlink resource region, and transmits the PTRS to the terminal.
- PTRS phase tracking reference signal
- OFDM Orthogonal Frequency Division Multiplexing
- phase noise estimation process of the terminal in the wireless communication system is improved to enable accurate decoding of the received signal.
- the overhead of the signal transmitted by the base station can be minimized while the phase noise estimation performance of the terminal is improved.
- the terminal can perform channel correction while estimating phase noise, thereby improving communication efficiency.
- 1 is a diagram illustrating a Doppler spectrum.
- FIG. 2 is a diagram illustrating narrow beamforming according to the invention.
- 3 is a diagram illustrating Doppler spectra when narrow beamforming is performed.
- FIG. 4 is a diagram illustrating an example of a synchronization signal service zone of a base station.
- 5 is an example of a frame structure proposed in a communication environment using mmWave.
- OVSF Orthogonal Variable Spreading Factor
- FIG. 7 is a diagram illustrating an example of an arrangement of terminals.
- FIG. 8 is a diagram illustrating a resource area structure used in a communication system using mmWave.
- FIGS 9 to 11 are diagrams illustrating methods of mapping a phase tracking reference signal (PTRS) to a resource region according to a proposed embodiment.
- PTRS phase tracking reference signal
- FIG. 14 is a flowchart illustrating a method of transmitting PTRS according to an exemplary embodiment.
- 15 is a diagram illustrating a configuration of a terminal and a base station related to the proposed embodiment.
- each component or feature may be considered to be optional unless otherwise stated.
- Each component or feature may be embodied in a form that is not combined with other components or features.
- some of the components and / or features may be combined to form an embodiment of the present invention.
- the order of the operations described in the embodiments of the present invention may be changed. Some components or features of one embodiment may be included in another embodiment, or may be replaced with corresponding components or features of another embodiment.
- the base station is meant as a terminal node of a network that directly communicates with a mobile station.
- the specific operation described as performed by the base station in this document may be performed by an upper node of the base station in some cases.
- various operations performed for communication with a mobile station in a network consisting of a plurality of network nodes including a base station may be performed by the base station or network nodes other than the base station.
- the 'base station' may be replaced by terms such as a fixed station, a Node B, an eNode B (eNB), an advanced base station (ABS), or an access point.
- a 'mobile station (MS)' may be a user equipment (UE), a subscriber station (SS), a mobile subscriber station (MSS), a mobile terminal, an advanced mobile station (AMS), a terminal. (Terminal) or a station (STAtion, STA) and the like can be replaced.
- UE user equipment
- SS subscriber station
- MSS mobile subscriber station
- AMS advanced mobile station
- Terminal or a station (STAtion, STA) and the like can be replaced.
- the transmitting end refers to a fixed and / or mobile node that provides a data service or a voice service
- the receiving end refers to a fixed and / or mobile node that receives a data service or a voice service. Therefore, in uplink, a mobile station may be a transmitting end and a base station may be a receiving end. Similarly, in downlink, a mobile station may be a receiving end and a base station may be a transmitting end.
- the description that the device communicates with the 'cell' may mean that the device transmits and receives a signal with the base station of the cell. That is, a substantial target for the device to transmit and receive a signal may be a specific base station, but for convenience of description, it may be described as transmitting and receiving a signal with a cell formed by a specific base station.
- the description of 'macro cell' and / or 'small cell' may not only mean specific coverage, but also 'macro base station supporting macro cell' and / or 'small cell supporting small cell', respectively. It may mean 'base station'.
- Embodiments of the present invention may be supported by standard documents disclosed in at least one of the wireless access systems IEEE 802.xx system, 3GPP system, 3GPP LTE system and 3GPP2 system. That is, obvious steps or parts which are not described among the embodiments of the present invention may be described with reference to the above documents.
- the error value of the oscillator of the terminal and the base station is defined as a requirement, and is described as follows.
- the UE modulated carrier frequency shall be accurate to within ⁇ 0.1 PPM observed over a period of one time slot (0.5 ms) compared to the carrier frequency received from the E-UTRA Node B
- Frequency error is the measure of the difference between the actual BS transmit frequency and the assigned frequency.
- the maximum difference of the oscillator between the base station and the terminal is ⁇ 0.1ppm, and when an error occurs in one direction, a maximum offset value of 0.2 ppm may occur.
- This offset value is multiplied by the center frequency and converted into Hz units for each center frequency.
- the CFO value is differently represented by subcarrier spacing, and in general, even when a large CFO value is large, the effect of the OFDM system with a sufficiently large subcarrier spacing is relatively small. Therefore, the actual CFO value (absolute value) needs to be expressed as a relative value affecting the OFDM system, which is called a normalized CFO.
- the normalized CFO is expressed by dividing the CFO value by the subcarrier spacing. Table 2 below shows the CFO and normalized CFO for each center frequency and oscillator error value.
- Center frequency (subcarrier spacing) Oscillator offset ⁇ 0.05 ppm ⁇ 0.1 ppm ⁇ 10 ppm ⁇ 20 ppm 2 GHz (15 kHz) ⁇ 100 Hz ( ⁇ 0.0067) ⁇ 200 Hz ( ⁇ 0.0133) ⁇ 20 kHz ( ⁇ 1.3) ⁇ 40 kHz ( ⁇ 2.7) 30 GHz (104.25 kHz) ⁇ 1.5 kHz ( ⁇ 0.014) ⁇ 3 kHz ( ⁇ 0.029) ⁇ 300 kHz ( ⁇ 2.9) ⁇ 600 kHz ( ⁇ 5.8) 60 GHz (104.25 kHz) ⁇ 3 kHz ( ⁇ 0.029) ⁇ 6 kHz ( ⁇ 0.058) ⁇ 600 kHz ( ⁇ 5.8) ⁇ 1.2 MHz ( ⁇ 11.5)
- a subcarrier spacing (15 kHz) is assumed for a center frequency of 2 GHz (for example, LTE Rel-8 / 9/10), and a subcarrier spacing of 104.25 kHz for a center frequency of 30 GHz or 60 GHz. This prevents performance degradation considering the Doppler effect for each center frequency.
- Table 2 above is a simple example and it is apparent that other subcarrier spacings may be used for the center frequency.
- Doppler dispersion causes dispersion in the frequency domain, resulting in distortion of the received signal at the receiver's point of view.
- Doppler dispersion It can be expressed as.
- v is the moving speed of the terminal
- ⁇ means the wavelength of the center frequency of the transmitted radio waves.
- ⁇ means the angle between the received radio wave and the moving direction of the terminal. In the following description, it is assumed that 0 is 0.
- the coherence time is in inverse proportion to the Doppler variance. If the coherence time is defined as a time interval in which the correlation value of the channel response in the time domain is 50% or more, It is expressed as In a wireless communication system, Equation 1 below, which represents a geometric mean between a formula for Doppler variance and a formula for coherence time, is mainly used.
- 1 is a diagram illustrating a Doppler spectrum.
- the Doppler spectrum or Doppler power spectrum density, which represents a change in the Doppler value according to the frequency change, may have various shapes according to a communication environment.
- a communication environment such as downtown
- the Doppler spectrum appears in the U-shape as shown in FIG. 1 shows the center frequency
- the maximum Doppler variance U-shaped Doppler spectra are shown.
- FIG. 2 is a diagram showing narrow beamforming according to the present invention
- FIG. 3 is a diagram showing Doppler spectrum when narrow beamforming is performed.
- an antenna array including a plurality of antennas may be installed in a small space with a small antenna. This feature enables pin-point beamforming, pencil beamforming, narrow beamforming, or thin beamforming using tens to hundreds of antennas. This narrow beamforming means that the received signal is received only at a certain angle, not in the same direction.
- FIG. 2A illustrates a case where the Doppler spectrum is U-shaped according to a signal received in an equal direction
- FIG. 2B illustrates a case where narrow beamforming using a plurality of antennas is performed.
- the Doppler spectrum also appears narrower than the U-shape due to the reduced angular spread.
- FIG. 3 it can be seen that Doppler variance appears only in a certain band when the narrow beamforming is performed.
- the center frequency operates in the band of several GHz to several tens of GHz. This characteristic of the center frequency makes the influence of the CFO due to the Doppler effect or the oscillator difference between the transmitter / receiver caused by the movement of the terminal more serious.
- FIG. 4 is a diagram illustrating an example of a synchronization signal service zone of a base station.
- the terminal performs synchronization with the base station by using a downlink (DL) synchronization signal transmitted by the base station.
- DL downlink
- timing and frequency are synchronized between the base station and the terminal.
- the base station transmits the synchronization signal by configuring the beam width as wide as possible so that terminals in a specific cell can receive and use the synchronization signal.
- path loss is greater than that of a low frequency band in synchronizing signal transmission. That is, in the case of a system using a high frequency band, a cell radius that can be supported compared to a conventional cellular system (for example, LTE / LTE-A) using a relatively low frequency band (for example, 6 GHz or less). This is greatly toned.
- a conventional cellular system for example, LTE / LTE-A
- a relatively low frequency band for example, 6 GHz or less
- a synchronization signal transmission method using beamforming may be used.
- the cell radius is increased, but the beam width is reduced. Equation 2 below shows the change in the received signal SINR according to the beam width.
- Equation 2 is the beam width according to the beamforming If received decreases, the received SINR is Fold improvement.
- Another method for solving the reduction of the cell radius may be considered to repeatedly transmit the same sync signal. This method requires additional resource allocation on the time axis, but has the advantage of increasing the cell radius without reducing the beam width.
- the base station allocates resources to each terminal by scheduling frequency resources and time resources located in a specific area.
- this specific zone is defined as a sector.
- A1, A2, A3, and A4 represent sectors having a radius of 0 to 200 m and widths of 0 to 15 ', 15 to 30', 30 to 45 ', and 45 to 60', respectively.
- B1, B2, B3, and B4 represent sectors having a radius of 200 to 500 m and widths of 0 to 15 ', 15 to 30', 30 to 45 ', and 45 to 60', respectively.
- sector 1 is defined as ⁇ A1, A2, A3, A4 ⁇
- sector 2 is defined as ⁇ A1, A2, A3, A4, B1, B2, B3, B4 ⁇ .
- the synchronization signal service area of the current base station is sector 1, it is assumed that an additional power of 6 dB or more is required for transmission of the synchronization signal in order for the base station to service the synchronization signal in sector 2.
- the base station can obtain an additional gain of 6 dB using the beamforming technique to serve sector 2.
- the service radius can be increased from A1 to B1.
- A2, A3, and A4 cannot be serviced at the same time. Therefore, when beamforming is performed, a synchronization signal should be separately transmitted to the A2 to B2, A3 to B3, and A4 to B4 sectors. In other words, the base station must transmit a synchronization signal four times beamforming to serve sector 2.
- the base station can transmit the synchronization signal to all sectors 2, but must transmit the synchronization signal four times on the time axis.
- the resources required to service sector 2 are the same for both beamforming and iterative transmission.
- the beam width is narrow, it is difficult for a terminal moving at a high speed or a terminal at the boundary of a sector to stably receive a synchronization signal. Instead, if the ID of the beam in which the terminal is located can be distinguished, there is an advantage that the terminal can determine its own position through a synchronization signal.
- the repetitive transmission scheme since the beam width is wide, it is very unlikely that the terminal misses the synchronization signal. Instead, the terminal cannot determine its location.
- 5 is an example of a frame structure proposed in a communication environment using mmWave.
- one frame consists of Q subframes and one subframe consists of P slots.
- One slot consists of T OFDM symbols.
- the first subframe in the frame uses the 0 th slot (slot indicated by 'S') for synchronization purposes.
- the 0 th slot is composed of A OFDM symbols for timing and frequency synchronization, B OFDM symbols for beam scanning, and C OFDM symbols for informing the UE of system information. The remaining D OFDM symbols are used for data transmission to each terminal.
- Q, P, T, S, A, B, C, and D may each be arbitrary values and may be values set by a user or automatically set on a system.
- Equation (3) Denotes the length of an OFDM symbol, the length of a cyclic prefix (CP), and the index of an OFDM symbol, respectively. Denotes a vector of the received signal at the receiver. At this time, Cold reception signal vector of From the first Vector defined by the first element.
- the algorithm of Equation 3 operates under the condition that two adjacent OFDM received signals in time are the same.
- Such an algorithm can use a sliding window method, which can be implemented with low complexity, and has a strong characteristic of frequency offset.
- Equation 4 represents an algorithm for performing timing synchronization by using a correlation between a received signal and a signal transmitted by a base station.
- Equation 4 denotes a signal transmitted by the base station and is a signal vector previously promised between the terminal and the base station. Equation 4 may produce better performance than Equation 3, but may not be implemented as a sliding window method, and thus requires high complexity. It also has a feature that is vulnerable to frequency offset.
- Beam scanning refers to the operation of the transmitter and / or receiver to find the direction of the beam that maximizes the receiver's received SINR.
- the base station determines the direction of the beam through beam scanning before transmitting data to the terminal.
- FIG. 4 illustrates a sector served by one base station divided into eight regions.
- the base station transmits beams in the areas (A1 + B1), (A2 + B2), (A3 + B3), and (A4 + B4), respectively, and the terminal can distinguish beams transmitted by the base station.
- the beam scanning process can be embodied in four processes. First, i) the base station transmits a beam in four areas in sequence. ii) The terminal determines the beam that is determined to be the most suitable among the beams in view of the received SINR. iii) The terminal feeds back information on the selected beam to the base station. iv) The base station transmits data using the beam having the feedback direction. Through the above beam scanning process, the UE can receive downlink data through the beam with optimized reception SINR.
- the Zadoff-Chu sequence is called a chu sequence or ZC sequence and is defined by Equation 5 below.
- N is the length of the sequence
- r is the root value
- a characteristic of the ZC sequence is that all elements have the same size (constant amplitude).
- the DFT results of the ZC sequence also appear the same for all elements.
- Equation 6 the ZC sequence and the cyclic shifted version of the ZC sequence have a correlation as shown in Equation 6.
- the ZC sequence also has a zero auto-correlation property, it is also expressed as having a constant Amplitude Zero Auto Correlation (CAZAC).
- Hadamard matrix is defined as Equation 8 below.
- Equation (8) Denotes the size of the matrix.
- Equation 9 It can be seen from Equation 9 that the columns are orthogonal to each other.
- the OVSF code is generated based on the Hadamard matrix and has a specific rule.
- the first code when branching to the right side of the OVSF code (lower branch), the first code repeats the upper code on the left side twice (mother code), and the second code repeats the high code code once and inverts it once. Is generated. 6 shows a tree structure of the OVSF code.
- All of these OVSF codes are orthogonal except for the relationship between adjacent higher and lower codes on the code tree.
- the code [1 -1 1 -1] is orthogonal to [1 1], [1 1 1 1], and [1 1 -1 -1].
- the OVSF code has the same length as the code length. That is, in FIG. 6, it can be seen that the length of a specific code is equal to the total number of branches to which the corresponding code belongs.
- RACH random access channel
- the base station defines a parameter called 'preambleInitialReceivedTargetPower', and broadcasts the parameter to all terminals in the cell through SIB (System Information Block) 2.
- SIB System Information Block
- the UE calculates a path loss using a reference signal, and determines the transmission power of the RACH signal by using the calculated path loss and the 'preambleInitialReceivedTargetPower' parameter as shown in Equation 10 below.
- P_PRACH_Initial, P_CMAX, and PL represent the transmission power of the RACH signal, the maximum transmission power of the terminal, and the path loss, respectively.
- Equation 10 it is assumed that the maximum transmit power of the terminal is 23 dBm and the RACH reception power of the base station is -104 dBm. In addition, it is assumed that the terminal is arranged as shown in FIG.
- the terminal calculates a path loss using the received synchronization signal and the beam scanning signal, and determines the transmission power based on this.
- Table 3 shows the path loss of the terminal and its transmission power.
- the RACH signal must be transmitted with a very small power (-44 dBm) to match the RACH reception power.
- the path loss is large, but the required transmission power is 6 dBm.
- phase noise related to the present invention Jitter occurring on the time axis appears as phase noise on the frequency axis. This phase noise randomly changes the phase of the received signal on the time axis as shown in Equation 11 below.
- Equation (11) The parameters represent the phase rotation values due to the received signal, time axis signal, frequency axis signal, and phase noise, respectively.
- Equation 12 Equation 12 below is derived.
- Equation (12) The parameters represent Common Phase Error (CPE) and Inter Cell Interference (ICI), respectively. At this time, the larger the correlation between phase noise, the larger the CPE of Equation 12.
- CPE is a kind of carrier frequency offset (CFO) in a WLAN system, but from the viewpoint of the terminal, the CPE and the CFO can be similarly interpreted.
- the UE removes the CPE / CFO, which is the phase noise on the frequency axis by estimating the CPE / CFO, and the process of estimating the CPE / CFO for the received signal is a process that must be preceded for accurate decoding of the received signal.
- the base station can transmit a predetermined signal to the terminal so that the terminal can accurately estimate the CPE / CFO, this signal may be a pilot signal previously shared between the terminal and the base station as a signal for estimating the phase noise And the data signal may be a changed or duplicated signal.
- phase compensation reference signal PCRS
- PNRS phase noise reference signal
- PTRS phase tracking reference signal
- FIG. 8 is a diagram illustrating a resource area structure used in the mmWave communication system.
- a communication system using an ultra high frequency band such as mmWave uses a frequency band different in physical properties from the conventional LTE / LTE-A communication system. Accordingly, in a communication system using an ultra high frequency band, a resource structure of a form different from that of the resource region used in the conventional communication system is being discussed. 8 shows an example of a downlink resource structure of a new communication system.
- the first two (or three) OFDM symbols 810 is assigned to a control channel (eg, a physical downlink control channel (PDCCH)) similarly to the prior art, the next one OFDM symbol 820 is assigned a DeModulation Reference Signal (DMRS), and the remaining OFDM symbols ( 830 may be assigned a data channel (eg, a Physical Downlink Shared Channel (PDSCH)).
- a control channel eg, a physical downlink control channel (PDCCH)
- DMRS DeModulation Reference Signal
- PDSCH Physical Downlink Shared Channel
- the PCRS or PNRS or PTRS for CPE (or CFO) estimation described above may be carried on a part of a resource element (RE) of the region 830 to which the data channel is allocated and transmitted to the terminal.
- This signal is a signal for estimating phase noise, and may be a pilot signal or a signal whose data signal is changed or duplicated as described above.
- the base station transmits a PTRS (or PCRS or PNRS) to the terminal so that the terminal can remove the phase noise of the received signal.
- a PTRS or PCRS or PNRS
- the PTRS is a pilot signal shared between the base station and the terminal and is a reference signal defined to compensate for phase noise.
- 9 to 11 are diagrams illustrating various embodiments in which a base station arranges (or maps) a PTRS in a resource region.
- the horizontal axis represents an OFDM symbol and the vertical axis represents a subcarrier.
- 9 to 11 show DMRS and PTRS structures of antenna port 7, respectively, and the right diagrams show DMRS and PTRS structures of antenna port 8, respectively.
- the embodiment of FIG. 9 will be described first.
- the base station may arrange the PCRSs at positions on the frequency axis where the DMRSs of the specific antenna ports are arranged. Accordingly, since each antenna port has a different position on the frequency axis (for example, a subcarrier index) at which the DMRS is disposed, PTRSs of different antenna ports are disposed at different positions on the frequency axis.
- 9 (a) shows the DMRS and PTRS arrangement of antenna port 7.
- PTRSs disposed at positions (ie, subcarriers) on the frequency axis where DMRSs are arranged may be arranged at predetermined intervals on the time axis, rather than every OFDM symbol.
- 9 (a) shows an embodiment in which PTRSs are arranged at one OFDM symbol interval, but is not limited thereto. Integers (eg, 0, 1, 2, PTRS) arranged on one subcarrier are shown in FIG. ..., 3, etc.) may be arranged at intervals of the OFDM symbol.
- the structure in which the PTRSs are arranged at regular intervals on the time axis may be referred to as a comb type structure.
- the comb structured PTRS has an advantage of reducing the overall overhead of the PTRS. For example, when the PTRS is defined for all OFDM symbols and the OFDM symbol positioned with a spacing of 2 OFDM symbols, the overhead of PTRS is about two times different. However, when the PTRS is configured as a comb structure as described above, there is a disadvantage in that the estimation performance decreases when the CPE changes rapidly on the time axis.
- 9 (b) shows a DMRS and PTRS arrangement of antenna port 8.
- the PTRSs may be disposed on a frequency axis different from the illustrated embodiment as long as the DMRSs are on the frequency axis on which the DMRSs are arranged.
- FIGS. 10 (a) and 10 (b) the number of PTRSs arranged in the same resource region is twice as high on the frequency axis as compared with FIGS. 9A and 9B.
- the embodiment of FIG. 10 has a form in which the density on the frequency axis of the PTRS is doubled compared to the embodiment of FIG. 9.
- This arrangement structure enables the terminal to estimate the CPE as well as channel estimation along the frequency axis. That is, PTRS can be used not only for removing phase noise through CPE estimation but also for channel estimation in the frequency domain. This channel estimation can compensate for the deteriorated channel estimation result when the channel changes rapidly on the time axis.
- FIGS. 11A and 11B the number of REs in which PTRSs are arranged in an RB pair is the same as in FIGS. 10 (a) and 10 (b).
- the start OFDM symbols of the PTRSs are different for each frequency axis.
- the OFDM symbol at which the PTRS is started may be different for each subcarrier in which the PTRS is arranged, which may be said to be arranged when the PTRS is hopping on the time axis with respect to the subcarriers.
- the scheme of FIG. 11 has an advantage in that PTRS is continuously defined on the time axis, and when the channel is rapidly changed, the terminal requires the channel estimation value for every OFDM symbol. There is this.
- PTRSs of each antenna port are positioned on the same subcarrier as the DMRS of the corresponding antenna port.
- the present invention is not limited to this embodiment, and the PTRSs of each antenna port may be located on a subcarrier in which a DMRS is not disposed.
- FIG. 12 and 13 illustrate mapping positions of PTRSs in subframes in relation to a proposed embodiment.
- the horizontal axis shows OFDM symbol indexes in subframes
- the vertical axis shows different subframe configurations.
- the UE determines the position of an OFDM symbol in which a PDCCH is arranged in a subframe through a control channel (eg, a physical control format indicator channel (PCFICH) or signaling).
- a control channel eg, a physical control format indicator channel (PCFICH) or signaling.
- the UE may know up to which OFDM symbol the PDCCH is arranged in a subframe through a PCFICH or signaling from a base station, and according to the conventional LTE / LTE-A standard, the PDCCH is up to the third from the first OFDM symbol in the subframe. Up to OFDM symbols may be arranged.
- a precoding different from a data channel for example, PDSCH
- a control channel such as a PDCCH. Accordingly, the PTRS is not defined in the region where the control channel is arranged in the resource region.
- the base station may not explicitly inform the terminal of the OFDM symbol in which the PTRS is disposed in the subframe. Even if the terminal does not explicitly indicate the location of the PTRS, as described above, the terminal may receive the PTRS in the region excluding the OFDM symbol in which the control channel is disposed in the subframe. For example, the UE may determine that the PTRS is arranged from the next OFDM symbol of the OFDM symbol in which the PDCCH is transmitted in the subframe.
- the PDCCH when the subframe configuration is 0, the PDCCH is disposed at the position where the OFDM symbol index is 0 ('DL control').
- the UE may know that data is arranged in the OFDM symbol indexes 1 to 13 ('DL data'), and accordingly, the PTRS may be determined to be arranged in the OFDM symbol indexes 1 to 13.
- FIG. 13 illustrates a process of determining the position of the PTRS in consideration of the arrangement of the channel state information (RS-RS) and the sounding RS (SRS).
- RS-RS channel state information
- SRS sounding RS
- the UE determines that the OFDM symbol corresponding to the SRS and the GP is not also transmitted in the PTRS.
- an OFDM symbol composed of 'UL control' in FIG. 13 may refer to a self-contained model according to new Radio Access Technology (RAT). That is, when downlink and uplink transmissions are simultaneously performed in one subframe, the UE may determine that PTRS is not transmitted even in the corresponding OFDM symbol of the downlink subframe.
- RAT Radio Access Technology
- the base station may also inform the terminal where the PTRS is placed through a method of notifying the last OFDM symbol in which the data channel is transmitted.
- the base station generates a PTRS (or PCRS or PNRS) (S1410).
- a PTRS or PCRS or PNRS
- the PTRS is a signal used by the UE to estimate the CPE to estimate phase noise, and may be a pilot signal previously shared between the UE and the base station.
- the base station maps the PTRS to the resource region (S1420), and the PTRS of a specific antenna port may be mapped onto one or more subcarriers to which DMRSs of the same antenna port are mapped.
- the PTRS may be mapped at a constant OFDM symbol interval on one subcarrier, and when the PTRS is mapped on two or more subcarriers in one RB pair, the OFDM symbol at which the PTRS placement starts in each subcarrier may be different. have.
- the base station transmits the PTRS mapped on the resource region to the terminal (S1430), and the terminal estimates the CPE (or CFO) using the PTRS (S1440).
- the terminal removes the phase noise from the received signal by removing the influence of the estimated CPE (S1450).
- the terminal 100 and the base station 200 may include radio frequency (RF) units 110 and 210, processors 120 and 220, and memories 130 and 230, respectively.
- RF radio frequency
- FIG. 15 only the 1: 1 communication environment between the terminal 100 and the base station 200 is illustrated, but a communication environment may be established between a plurality of terminals and a plurality of base stations.
- the base station 200 illustrated in FIG. 15 may be applied to both the macro cell base station and the small cell base station.
- Each RF unit 110, 210 may include a transmitter 112, 212 and a receiver 114, 214, respectively.
- the transmitting unit 112 and the receiving unit 114 of the terminal 100 are configured to transmit and receive signals with the base station 200 and other terminals, and the processor 120 is functionally connected with the transmitting unit 112 and the receiving unit 114.
- the transmitter 112 and the receiver 114 may be configured to control a process of transmitting and receiving signals with other devices.
- the processor 120 performs various processes on the signal to be transmitted and transmits the signal to the transmitter 112, and performs the process on the signal received by the receiver 114.
- the processor 120 may store information included in the exchanged message in the memory 130.
- the terminal 100 can perform the method of various embodiments of the present invention described above.
- the transmitter 212 and the receiver 214 of the base station 200 are configured to transmit and receive signals with other base stations and terminals, and the processor 220 is functionally connected to the transmitter 212 and the receiver 214 to transmit the signal. 212 and the receiver 214 may be configured to control the process of transmitting and receiving signals with other devices.
- the processor 220 may perform various processing on the signal to be transmitted, transmit the signal to the transmitter 212, and may perform processing on the signal received by the receiver 214. If necessary, the processor 220 may store information included in the exchanged message in the memory 230. With such a structure, the base station 200 may perform the method of the various embodiments described above.
- Processors 120 and 220 of the terminal 100 and the base station 200 respectively instruct (eg, control, coordinate, manage, etc.) the operation in the terminal 100 and the base station 200.
- Respective processors 120 and 220 may be connected to memories 130 and 230 that store program codes and data.
- the memories 130 and 230 are coupled to the processors 120 and 220 to store operating systems, applications, and general files.
- the processor 120 or 220 of the present invention may also be referred to as a controller, a microcontroller, a microprocessor, a microcomputer, or the like.
- the processors 120 and 220 may be implemented by hardware or firmware, software, or a combination thereof.
- ASICs application specific integrated circuits
- DSPs digital signal processors
- DSPDs digital signal processing devices
- PLDs programmable logic devices
- FPGAs Field programmable gate arrays
- the above-described method may be written as a program executable on a computer, and may be implemented in a general-purpose digital computer which operates the program using a computer readable medium.
- the structure of the data used in the above-described method can be recorded on the computer-readable medium through various means.
- Program storage devices that may be used to describe storage devices that include executable computer code for performing the various methods of the present invention should not be understood to include transient objects, such as carrier waves or signals. do.
- the computer readable medium includes a storage medium such as a magnetic storage medium (eg, a ROM, a floppy disk, a hard disk, etc.), an optical reading medium (eg, a CD-ROM, a DVD, etc.).
- the above description can be applied to various wireless communication systems including not only 3GPP LTE and LTE-A systems, but also IEEE 802.16x and 802.11x systems. Furthermore, the proposed method can be applied to mmWave communication system using ultra high frequency band.
Abstract
Description
BS class | Accuracy |
Wide Area BS | ±0.05 ppm |
Local Area BS | ±0.1 ppm |
Home BS | ±0.05 ppm |
Center frequency(subcarrier spacing) | Oscillator Offset | ||||
±0.05 ppm | ±0.1 ppm | ±10 ppm | ±20 ppm | ||
2GHz (15kHz) | ±100Hz(±0.0067) | ±200Hz(±0.0133) | ±20kHz(±1.3) | ±40kHz(±2.7) | |
30GHz (104.25kHz) | ±1.5kHz(±0.014) | ±3kHz(±0.029) | ±300kHz(±2.9) | ±600kHz(±5.8) | |
60GHz (104.25kHz) | ±3kHz(±0.029) | ±6kHz(±0.058) | ±600kHz(±5.8) | ±1.2MHz(±11.5) |
단말 | preambleInitialReceived TargetPower | 경로 손실 | 필요한 송신파워 | 송신 파워 | 추가 필요 파워 |
K1 | -104dBm | 60dB | -44dBm | -44dBm | 0dBm |
K2 | -104dBm | 110dB | 6dBm | 6dBm | 0dBm |
K3 | -104dBm | 130dB | 26dBm | 23dMb | 3dBm |
Claims (16)
- mmWave 통신 시스템에서 기지국이 위상 잡음을 추정하기 위한 신호를 전송하는 방법에 있어서,하향링크 신호에서 위상 잡음을 추정하기 위해 이용되는 PTRS(Phase Tracking Reference Signal)를 생성하는 단계;하향링크 자원 영역에서 데이터 채널이 매핑되는 영역 상에 상기 PTRS를 소정의 OFDM(Orthogonal Frequency Division Multiplexing) 심볼 간격으로 매핑하는 단계; 및상기 PTRS를 단말로 전송하는 단계를 포함하는, 신호 전송 방법.
- 제1항에 있어서,상기 소정의 OFDM 심볼 간격은 2 또는 4 OFDM 심볼 간격인, 신호 전송 방법.
- 제1항에 있어서,특정 안테나 포트의 PTRS는 상기 특정 안테나 포트의 DMRS(DeModulation Reference Signal)가 배치되는 서브캐리어 상에 매핑되는 것인, 신호 전송 방법.
- 제3항에 있어서,동일 안테나 포트의 PTRS들은 동일한 OFDM 심볼상에 매핑되는 것인, 신호 정송 방법.
- 제3항에 있어서,서로 다른 서브캐리어 상에 매핑되는 동일 안테나 포트의 PTRS들은 서로 다른 OFDM 심볼상에 매핑되는 것인, 신호 전송 방법.
- 제1항에 있어서,상기 PTRS가 매핑되는 OFDM 심볼은 상기 하향링크 자원 영역에서 전송되는 제어 채널 또는 CSI-RS (Channel State Information - Reference Signal) 및 SRS (Sounding Reference Signal)이 매핑되는 위치로부터 결정되는 것인, 신호 전송 방법.
- 제6항에 있어서,상기 PTRS는 상기 제어 채널이 매핑되는 위치를 제외한 OFDM 심볼에 매핑되는 것인, 신호 전송 방법.
- 제6항에 있어서,상기 PTRS는 상기 CSI-RS 및 SRS가 매핑되는 위치를 제외한 OFDM 심볼에 매핑되는 것인, 신호 전송 방법.
- mmWave 통신 시스템에서 위상 잡음을 추정하기 위한 신호를 전송하는 기지국에 있어서,송신부;수신부; 및상기 송신부 및 상기 수신부와 연결되어 동작하는 프로세서를 포함하되,상기 프로세서는,하향링크 신호에서 위상 잡음을 추정하기 위해 이용되는 PTRS(Phase Tracking Reference Signal)를 생성하고,하향링크 자원 영역에서 데이터 채널이 매핑되는 영역 상에 상기 PTRS를 소정의 OFDM(Orthogonal Frequency Division Multiplexing) 심볼 간격으로 매핑하고,상기 PTRS를 단말로 전송하는 것인, 기지국.
- 제9항에 있어서,상기 소정의 OFDM 심볼 간격은 2 또는 4 OFDM 심볼 간격인, 기지국.
- 제9항에 있어서,특정 안테나 포트의 PTRS는 상기 특정 안테나 포트의 DMRS(DeModulation Reference Signal)가 배치되는 서브캐리어 상에 매핑되는 것인, 기지국.
- 제11항에 있어서,동일 안테나 포트의 PTRS들은 동일한 OFDM 심볼상에 매핑되는 것인, 기지국.
- 제11항에 있어서,서로 다른 서브캐리어 상에 매핑되는 동일 안테나 포트의 PTRS들은 서로 다른 OFDM 심볼상에 매핑되는 것인, 기지국.
- 제9항에 있어서,상기 PTRS가 매핑되는 OFDM 심볼은 상기 하향링크 자원 영역에서 전송되는 제어 채널 또는 CSI-RS (Channel State Information - Reference Signal) 및 SRS (Sounding Reference Signal)이 매핑되는 위치로부터 결정되는 것인, 기지국.
- 제14항에 있어서,상기 PTRS는 상기 제어 채널이 매핑되는 위치를 제외한 OFDM 심볼에 매핑되는 것인, 기지국.
- 제14항에 있어서,상기 PTRS는 상기 CSI-RS 및 SRS가 매핑되는 위치를 제외한 OFDM 심볼에 매핑되는 것인, 기지국.
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EP17789776.6A EP3451601B1 (en) | 2016-04-25 | 2017-03-09 | Signal transmission method for estimating phase noise in wireless communication system |
CN201780037238.3A CN109314686B (zh) | 2016-04-25 | 2017-03-09 | 无线通信系统中估计相位噪声的信号传输方法 |
US16/064,977 US10587446B2 (en) | 2016-04-25 | 2017-03-09 | Signal transmission method for estimating phase noise in wireless communication system |
KR1020187013765A KR101966131B1 (ko) | 2016-04-25 | 2017-03-09 | 무선 통신 시스템에서 위상 잡음 추정을 위한 신호 전송 방법 |
KR1020197007928A KR102044704B1 (ko) | 2016-04-25 | 2017-03-09 | 무선 통신 시스템에서 위상 잡음 추정을 위한 신호 송수신 방법 및 이를 지원하는 장치 |
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US16/738,515 US10938616B2 (en) | 2016-04-25 | 2020-01-09 | Signal transmission method for estimating phase noise in wireless communication system |
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Cited By (16)
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US20220166565A1 (en) * | 2017-04-28 | 2022-05-26 | Panasonic Intellectual Property Corporation Of America | Measurement apparatus and measurement method |
US11456905B2 (en) | 2018-03-12 | 2022-09-27 | Vivo Mobile Communication Co., Ltd. | Method for transmitting phase tracking reference signal (PTRS), terminal and network device |
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Publication number | Priority date | Publication date | Assignee | Title |
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US10554359B2 (en) * | 2017-03-25 | 2020-02-04 | Lg Electronics Inc. | Method of receiving phase tracking reference signal by user equipment in wireless communication system and device for supporting same |
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WO2018230900A1 (en) * | 2017-06-15 | 2018-12-20 | Samsung Electronics Co., Ltd. | Method and apparatus for allocating ptrs in next generation communication system |
US20210211257A1 (en) | 2017-06-16 | 2021-07-08 | Telefonaktiebolaget Lm Ericsson (Publ) | Joint resource map design of dm-rs and pt-rs |
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CN111034139B (zh) * | 2017-08-12 | 2022-11-04 | 日本电气株式会社 | 用于确定相位跟踪参考信号配置参数的方法和装置 |
US11343804B2 (en) * | 2018-02-14 | 2022-05-24 | Qualcomm Incorporated | Phase-tracking reference signal mapping |
US11160055B2 (en) | 2018-04-10 | 2021-10-26 | Qualcomm Incorporated | Communication of direct current (DC) tone location |
EP3993529A1 (en) * | 2019-06-26 | 2022-05-04 | Ntt Docomo, Inc. | Terminal |
CN114902774A (zh) * | 2019-12-27 | 2022-08-12 | 华为技术有限公司 | 一种确定参考信号的方法及装置 |
CN114374483A (zh) * | 2020-10-14 | 2022-04-19 | 夏普株式会社 | 由用户设备执行的方法以及用户设备 |
Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20150098535A1 (en) * | 2013-10-08 | 2015-04-09 | Blackberry Limited | Phase noise mitigation for wireless communications |
US20150282171A1 (en) * | 2012-09-24 | 2015-10-01 | Shirish Nagaraj | Frequency Error Correction for LTE Uplink CoMP |
US20150311986A1 (en) * | 2014-04-23 | 2015-10-29 | Nokia Solutions And Networks Oy | Phase Noise Tracking and Reduction |
US20160006594A1 (en) * | 2013-03-28 | 2016-01-07 | Telefonaktiebolaget L M Ericsson (Publ) | A phase reference symbol format for ofdm phase synchronization |
WO2016048074A1 (ko) * | 2014-09-24 | 2016-03-31 | 엘지전자 주식회사 | 무선 통신 시스템에서 참조 신호를 송수신하는 방법 및 이를 위한 장치 |
Family Cites Families (12)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US8565194B2 (en) * | 2005-10-27 | 2013-10-22 | Qualcomm Incorporated | Puncturing signaling channel for a wireless communication system |
KR101357923B1 (ko) * | 2008-10-23 | 2014-02-03 | 에릭슨 엘지 주식회사 | 자기간섭 제거 장치 및 방법과 그를 위한 릴레이 시스템 |
US20110040666A1 (en) * | 2009-08-17 | 2011-02-17 | Jason Crabtree | Dynamic pricing system and method for complex energy securities |
KR101241916B1 (ko) * | 2010-02-07 | 2013-03-11 | 엘지전자 주식회사 | 다중 안테나를 지원하는 무선 통신 시스템에서 하향링크 참조신호를 전송하는 방법 및 장치 |
US8331506B2 (en) * | 2010-03-12 | 2012-12-11 | Telefonaktiebolaget L M Ericsson (Publ) | Frequency-dependent IQ imbalance estimation |
US8963751B2 (en) * | 2010-11-29 | 2015-02-24 | Yissum Research Development Company Of The Hebrew University Of Jerusalem Ltd | System and method for photonically assisted analog to digital signal conversion |
JP5663700B2 (ja) * | 2011-06-30 | 2015-02-04 | エルジー エレクトロニクス インコーポレイティド | 無線通信システムにおけるダウンリンク制御チャネル割当方法及び装置 |
EP2761780A1 (en) * | 2011-09-30 | 2014-08-06 | Interdigital Patent Holdings, Inc. | Multipoint transmission in wireless communication |
JP5893999B2 (ja) * | 2012-04-27 | 2016-03-23 | 株式会社Nttドコモ | 無線通信システム、基地局装置、ユーザ端末、及び無線通信方法 |
WO2014019181A1 (zh) * | 2012-08-01 | 2014-02-06 | 华为技术有限公司 | 一种控制信道传输方法及装置 |
KR102039535B1 (ko) * | 2013-10-22 | 2019-11-01 | 삼성전자 주식회사 | 무선 자원 할당 방법 및 장치 |
ES2898647T3 (es) * | 2016-02-09 | 2022-03-08 | Ericsson Telefon Ab L M | Aparatos y métodos para la generación de secuencias de señales de referencia de seguimiento del ruido de fase usando señales de referencia de demodulación |
-
2017
- 2017-03-09 KR KR1020197032812A patent/KR102235180B1/ko active IP Right Grant
- 2017-03-09 CN CN201780037238.3A patent/CN109314686B/zh active Active
- 2017-03-09 KR KR1020197007928A patent/KR102044704B1/ko active Application Filing
- 2017-03-09 US US16/064,977 patent/US10587446B2/en active Active
- 2017-03-09 EP EP17789776.6A patent/EP3451601B1/en active Active
- 2017-03-09 KR KR1020187013765A patent/KR101966131B1/ko active IP Right Grant
- 2017-03-09 WO PCT/KR2017/002570 patent/WO2017188591A1/ko active Application Filing
-
2020
- 2020-01-09 US US16/738,515 patent/US10938616B2/en active Active
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20150282171A1 (en) * | 2012-09-24 | 2015-10-01 | Shirish Nagaraj | Frequency Error Correction for LTE Uplink CoMP |
US20160006594A1 (en) * | 2013-03-28 | 2016-01-07 | Telefonaktiebolaget L M Ericsson (Publ) | A phase reference symbol format for ofdm phase synchronization |
US20150098535A1 (en) * | 2013-10-08 | 2015-04-09 | Blackberry Limited | Phase noise mitigation for wireless communications |
US20150311986A1 (en) * | 2014-04-23 | 2015-10-29 | Nokia Solutions And Networks Oy | Phase Noise Tracking and Reduction |
WO2016048074A1 (ko) * | 2014-09-24 | 2016-03-31 | 엘지전자 주식회사 | 무선 통신 시스템에서 참조 신호를 송수신하는 방법 및 이를 위한 장치 |
Non-Patent Citations (1)
Title |
---|
See also references of EP3451601A4 * |
Cited By (37)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20220166565A1 (en) * | 2017-04-28 | 2022-05-26 | Panasonic Intellectual Property Corporation Of America | Measurement apparatus and measurement method |
US11711178B2 (en) * | 2017-04-28 | 2023-07-25 | Panasonic Intellectual Property Corporation Of America | Measurement apparatus and measurement method |
AU2018283592B2 (en) * | 2017-06-15 | 2022-10-13 | Samsung Electronics Co., Ltd. | Method and apparatus for allocating PTRS in next generation communication system |
US11882072B2 (en) | 2017-11-15 | 2024-01-23 | Interdigital Patent Holdings, Inc. | Phase tracking reference signal transmission |
TWI698110B (zh) * | 2017-11-15 | 2020-07-01 | 美商Idac控股公司 | 相位追蹤參考信號傳輸方法及裝置 |
CN109802777B (zh) * | 2017-11-16 | 2020-07-21 | 维沃移动通信有限公司 | Ptrs的映射方法和通信设备 |
CN109802777A (zh) * | 2017-11-16 | 2019-05-24 | 维沃移动通信有限公司 | Ptrs的映射方法和通信设备 |
RU2754431C1 (ru) * | 2017-11-17 | 2021-09-02 | Телефонактиеболагет Лм Эрикссон (Пабл) | Методика для конфигурирования опорного сигнала отслеживания фазы |
CN111630820A (zh) * | 2017-11-17 | 2020-09-04 | 华为技术有限公司 | 用于确定相位跟踪参考信号资源位置的方法、装置和设备 |
US11902205B2 (en) | 2017-11-17 | 2024-02-13 | Telefonaktiebolaget Lm Ericsson (Publ) | Technique for configuring a phase tracking reference signal |
CN108900286A (zh) * | 2017-11-17 | 2018-11-27 | 华为技术有限公司 | 参考信号的传输方法和传输装置 |
CN109802796B (zh) * | 2017-11-17 | 2023-10-20 | 华为技术有限公司 | 参考信号的传输方法和传输装置 |
JP2020511814A (ja) * | 2017-11-17 | 2020-04-16 | 華為技術有限公司Huawei Technologies Co.,Ltd. | 参照信号送信方法及び送信機器 |
US10637691B2 (en) | 2017-11-17 | 2020-04-28 | Huawei Technologies Co., Ltd. | Reference signal transmission method and transmission apparatus |
CN110176981B (zh) * | 2017-11-17 | 2020-06-26 | 华为技术有限公司 | 参考信号的传输方法和传输装置 |
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CN109802796A (zh) * | 2017-11-17 | 2019-05-24 | 华为技术有限公司 | 参考信号的传输方法和传输装置 |
CN111630820B (zh) * | 2017-11-17 | 2022-04-05 | 华为技术有限公司 | 用于确定相位跟踪参考信号资源位置的方法、装置和设备 |
CN110176981A (zh) * | 2017-11-17 | 2019-08-27 | 华为技术有限公司 | 参考信号的传输方法和传输装置 |
US10972320B2 (en) | 2017-11-17 | 2021-04-06 | Huawei Technologies Co., Ltd. | Reference signal transmission method and transmission apparatus |
WO2019095828A1 (zh) * | 2017-11-17 | 2019-05-23 | 华为技术有限公司 | 参考信号的传输方法和传输装置 |
CN108900286B (zh) * | 2017-11-17 | 2019-04-23 | 华为技术有限公司 | 参考信号的传输方法和传输装置 |
US11277291B2 (en) | 2017-11-17 | 2022-03-15 | Huawei Technologies Co., Ltd. | Method, apparatus, and device for determining phase tracking reference signal resource location |
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US11570775B2 (en) | 2017-12-01 | 2023-01-31 | Samsung Electronics Co., Ltd. | Method and apparatus for improving in and relating to integrated access and backhaul and non terrestrial networks |
WO2019107961A1 (en) * | 2017-12-01 | 2019-06-06 | Samsung Electronics Co., Ltd. | Method and apparatus for improving in and relating to integrated access and backhaul and non terrestrial networks |
US11569956B2 (en) | 2018-02-08 | 2023-01-31 | Nec Corporation | Methods and apparatuses for phase tracking reference signal configuration |
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US11456905B2 (en) | 2018-03-12 | 2022-09-27 | Vivo Mobile Communication Co., Ltd. | Method for transmitting phase tracking reference signal (PTRS), terminal and network device |
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US11469846B2 (en) | 2018-04-05 | 2022-10-11 | Samsung Electronics Co., Ltd. | Method and device for decoding data in wireless communication system |
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US10938616B2 (en) | 2021-03-02 |
US20190081844A1 (en) | 2019-03-14 |
CN109314686A (zh) | 2019-02-05 |
KR102235180B1 (ko) | 2021-04-02 |
EP3451601B1 (en) | 2021-10-06 |
KR101966131B1 (ko) | 2019-04-05 |
KR20180071301A (ko) | 2018-06-27 |
US20200153673A1 (en) | 2020-05-14 |
EP3451601A1 (en) | 2019-03-06 |
EP3451601A4 (en) | 2019-11-27 |
US10587446B2 (en) | 2020-03-10 |
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