WO2017157218A1 - 一种天线 - Google Patents

一种天线 Download PDF

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Publication number
WO2017157218A1
WO2017157218A1 PCT/CN2017/076109 CN2017076109W WO2017157218A1 WO 2017157218 A1 WO2017157218 A1 WO 2017157218A1 CN 2017076109 W CN2017076109 W CN 2017076109W WO 2017157218 A1 WO2017157218 A1 WO 2017157218A1
Authority
WO
WIPO (PCT)
Prior art keywords
absorbing material
antenna
layer
radome
material layer
Prior art date
Application number
PCT/CN2017/076109
Other languages
English (en)
French (fr)
Inventor
刘若鹏
周添
李木森
魏栋
Original Assignee
深圳光启高等理工研究院
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 深圳光启高等理工研究院 filed Critical 深圳光启高等理工研究院
Priority to EP17765760.8A priority Critical patent/EP3432422B1/en
Publication of WO2017157218A1 publication Critical patent/WO2017157218A1/zh
Priority to US16/121,662 priority patent/US10784574B2/en

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q17/00—Devices for absorbing waves radiated from an antenna; Combinations of such devices with active antenna elements or systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/528—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the re-radiation of a support structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/42—Housings not intimately mechanically associated with radiating elements, e.g. radome
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
    • H01Q15/0086—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices having materials with a synthesized negative refractive index, e.g. metamaterials or left-handed materials
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q17/00—Devices for absorbing waves radiated from an antenna; Combinations of such devices with active antenna elements or systems
    • H01Q17/001—Devices for absorbing waves radiated from an antenna; Combinations of such devices with active antenna elements or systems for modifying the directional characteristic of an aerial
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q17/00—Devices for absorbing waves radiated from an antenna; Combinations of such devices with active antenna elements or systems
    • H01Q17/004—Devices for absorbing waves radiated from an antenna; Combinations of such devices with active antenna elements or systems using non-directional dissipative particles, e.g. ferrite powders
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H01Q19/12—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces wherein the surfaces are concave
    • H01Q19/17—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces wherein the surfaces are concave the primary radiating source comprising two or more radiating elements
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/061—Two dimensional planar arrays
    • H01Q21/065—Patch antenna array
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q25/00—Antennas or antenna systems providing at least two radiating patterns
    • H01Q25/001—Crossed polarisation dual antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/241—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM
    • H01Q1/246—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for base stations

Definitions

  • the present invention relates to the field of antennas, and more particularly to an antenna with improved electrical performance.
  • the front-to-back ratio of the antenna is the ratio of the power flux density of the maximum radiation direction of the main lobe in the antenna pattern (specified as 0°) to the maximum power flux density in the vicinity of the opposite direction (specified in the range of 180° ⁇ 20°). It shows that the antenna suppresses the back lobes, and the low front and rear of the antenna will cause interference in the back area of the antenna.
  • the cross polarization of an antenna means that there is a component in the direction orthogonal to the main polarization direction of the electric field vector of the far field of the antenna radiation.
  • the reflector is modified, such as increasing the area of the reflector, increasing the complexity of the edge of the reflector, and the like.
  • increasing the size of the reflector increases the cross-sectional area of the antenna, and increasing the complexity of the edge of the reflector increases the processing difficulty and product cost.
  • the technical problem to be solved by the present invention is to provide an antenna which can improve front-to-back ratio and cross-polarization isolation without changing the structure of the reflecting plate.
  • the technical solution adopted by the present invention to solve the above technical problem is an antenna, including an antenna element, a reflector, the antenna element is disposed on the reflector, the antenna further includes a layer of absorbing material, and the absorbing material The layer is disposed on a side of the reflector facing away from the outer surface of the antenna element.
  • the absorbing material layer is attached to the outer surface of the reflector opposite to the antenna element, or the absorbing material layer gap is disposed on the antenna facing away from the antenna.
  • the outer surface of the vibrator is attached to the outer surface of the reflector opposite to the antenna element, or the absorbing material layer gap is disposed on the antenna facing away from the antenna.
  • the antenna further includes a radome, the antenna element and the reflector are disposed in the radome, and the absorbing material layer is disposed between the radome and the reflector.
  • the reflector has a bottom plate, a first side plate and a second side plate, the first side
  • the antenna is disposed on the bottom plate
  • the antenna cover is disposed on the bottom plate
  • the radome at least surrounding the bottom plate
  • the absorbing material layer is disposed at least on the radome And between the first side panel and between the radome and the second side panel.
  • the absorbing material layer is attached to an outer surface of the first side plate facing the radome and an outer surface of the second side plate facing the radome Or the layer of absorbing material is applied to the inner surface of the radome facing the first side panel and the second side panel.
  • the layer of absorbing material is further disposed between the radome and the bottom plate.
  • the layer of absorbing material is applied to the outer surface of the bottom plate facing the radome
  • the layer of absorbing material is applied to the inner surface of the radome facing the bottom plate.
  • the layer of absorbing material is bonded to a metal layer disposed on an inner surface of the antenna cover facing the first side panel and the second side panel.
  • the metal layer is further disposed on an inner surface of the radome facing the bottom plate.
  • the number of the antenna elements is plural and forms an array of vibrators covering the outer surface of the region of the reflector on the corresponding array of vibrators, and the layer of the absorber material The arrangement is centered on the array of vibrators.
  • the absorbing material layer comprises a magnetic electromagnetic absorbing material layer and a conductive geometric layer combined with the magnetic electromagnetic absorbing material layer; the conductive geometric layer is sequentially arranged
  • the plurality of conductive geometric units are composed of a non-closed annular conductive geometric structure, and the annular conductive geometric structure is provided with two strip structures which are relatively parallel.
  • the annular conductive geometry is provided with more than one of the openings.
  • the annular conductive geometry is circular, elliptical, triangular or polygonal.
  • the layer of absorbing material has a dielectric constant of 5-30 and a magnetic permeability of 1-7.
  • the electrically conductive geometric units are arranged in a periodic array.
  • the magnetic electromagnetic wave absorbing material layer is provided with a metal layer on the surface thereof.
  • the magnetic electromagnetic absorbing material layer is a absorbing patch material.
  • the conductive geometric unit is attached to or embedded in the layer of magnetic electromagnetic absorbing material.
  • the magnetic electromagnetic wave absorbing material layer includes a substrate and an absorber bonded to the substrate.
  • the conductive geometric unit is in the shape of a circumscribed circle having a diameter of 1/20 to 1/5 of the electromagnetic wavelength of the free space in the operating frequency band.
  • the absorbing material layer has an operating frequency in the frequency range of 0.8-2.7 GHz, and the thickness of the conductive geometric unit is greater than the trend of the conductive geometric unit corresponding to the operating frequency band. Skin depth.
  • the absorbing material layer has an operating frequency in a frequency range of 0.8-2.7 GHz, and the thickness of the metal layer is greater than a skin depth of the metal layer corresponding to the working frequency band.
  • the line width of the annular conductive geometry and the strip structure is W, 0.1m m ⁇ W ⁇ lmm.
  • the thickness of the annular conductive geometry and the strip structure is H, 0.005 mm ⁇ H ⁇ 0.05 mm.
  • the present invention adopts the above technical solution, and can improve the electrical education of the antenna compared with the prior art, and the specific performance is as follows: the absorbing material layer disposed on the side of the reflector facing away from the outer surface of the antenna element It can absorb electromagnetic waves diffracted from the edge of the reflector on the antenna to the backward direction, thereby improving the front-to-back ratio and cross-polarization isolation of the antenna. And the absorbing material does not add significantly to the raw material cost, and the antenna is easy to install and does not add difficulty to the antenna assembly.
  • the layer of absorbing material comprises a magnetic electromagnetic absorbing material layer and a conductive geometric layer combined with the magnetic electromagnetic absorbing material layer, and the conductive geometric layer may be a absorbing material layer Electromagnetic waves in the working frequency are required to be concentratedly absorbed, which facilitates absorption of the magnetic electromagnetic absorbing material layer disposed below.
  • the additional metal layer reflects the absorbed electromagnetic waves to the magnetic electromagnetic absorbing material layer for secondary absorption, achieving better absorbing effect.
  • FIG. 1 is a perspective structural view of an antenna according to a first embodiment of the present invention.
  • Fig. 2 is a perspective structural view of an antenna according to a second embodiment of the present invention.
  • Fig. 3 is a perspective structural view of an antenna according to a third embodiment of the present invention.
  • Fig. 4 is a comparison of the pattern of the antenna with the absorbing material and the antenna without the absorbing material in the embodiment of the present invention at 1710 MHz.
  • Fig. 5 is a view showing the orientation of the antenna with the absorbing material and the antenna without the absorbing material in the embodiment of the present invention at 1990 MHz.
  • Fig. 6 is a comparison of the pattern of the antenna with the absorbing material and the antenna without the absorbing material in the embodiment of the present invention at 2170 MHz.
  • Figure 7 is a comparison of the pattern of an antenna with a absorbing wave metamaterial and an antenna without an absorbing wave material in a preferred embodiment of the present invention at 1710 MHz.
  • Figure 8 is a comparison of the orientation of an antenna with a wave absorbing metamaterial and an antenna without an absorbing wave material in 1990 MHz on a preferred embodiment of the present invention.
  • Figure 9 is a comparison of the pattern of an antenna with a absorbing wave metamaterial and an existing antenna without absorbing supermaterial at 2170 MHz in accordance with a preferred embodiment of the present invention.
  • FIG. 10 is a schematic diagram of a unit of an electromagnetic wave absorbing super material according to a first preferred embodiment of the present invention
  • FIG. 11 is a layout of a plurality of units of electromagnetic wave absorbing super material according to a first preferred embodiment of the present invention
  • FIG. 13 is a graph showing the reflectance of the electromagnetic wave absorbing supermaterial in the TM mode in the first preferred embodiment of the present invention
  • FIG. 14 is a diagram showing an arrangement of a plurality of cells of an electromagnetic wave absorbing supermaterial according to a second preferred embodiment of the present invention.
  • FIG. 15 is an electromagnetic wave absorbing supermaterial according to a second preferred embodiment of the present invention.
  • FIG. 16 is a reflectance curve of the electromagnetic wave absorbing super material in the TM mode according to the second preferred embodiment of the present invention.
  • 17 is a schematic view showing an arrangement rule of a plurality of cells of an electromagnetic wave absorbing supermaterial in a third preferred embodiment of the present invention.
  • FIG. 18 is a graph showing reflectance of an electromagnetic wave absorbing material in TE mode according to a third preferred embodiment of the present invention.
  • FIG. 19 is a graph showing reflectance of an electromagnetic wave absorbing metamaterial in a TM mode according to a third preferred embodiment of the present invention. [0050] FIG.
  • 20 is a graph showing the reflectance of the electromagnetic wave absorbing super material in the TE mode according to the fourth preferred embodiment of the present invention.
  • 21 is a graph showing the reflectance of the electromagnetic wave absorbing metamaterial in the TM mode in the fourth preferred embodiment of the present invention.
  • Embodiments of the present invention describe an antenna that can improve performance such as front-to-back ratio and cross-polarization, improve backward interference for applied systems, mitigate transmission and reception interference, and improve communication capacity.
  • an absorbing material is introduced into the antenna to absorb electromagnetic waves that are diffracted from the edge of the antenna reflector to the rear, thereby avoiding structural changes to the antenna reflector.
  • the antenna 10 of the present embodiment includes an antenna element 11, a reflector 12, a radome 13, and a layer 14 of absorbing material.
  • the reflector 12 has a bottom plate 12a, a first side plate 12b, and a second side plate 12c.
  • the first side plate 12b and the second side plate 12c are opposed to each other.
  • the reflecting plate 12 may also have a third side plate and a fourth side plate (not shown).
  • the third side panel is opposite to the fourth side panel.
  • the third side panel is adjacent to the first side panel 12b and the second side panel 12c, and the fourth side panel is also adjacent to the first side panel 12b and the second side panel 12c.
  • the first side panel 12b and the second side panel 12c may be in a regular moment.
  • the third side plate and the fourth side plate form a chamfer on a rectangular basis. For example, one or more corners of a rectangle are cut away and become a hypotenuse.
  • the antenna element 11 is disposed above the bottom plate 12a.
  • the form of the antenna element 11 and the manner of bonding with the bottom plate 12a are not limited in this embodiment.
  • the radome 13 surrounds at least the bottom plate 12a of the reflecting plate 12, the first side plate 12b, and the second side plate 12c. Part of the radome is removed in Fig. 1 to make the structure of the reflecting plate 12 visible. As can be seen, the radome 13 is not in contact with the reflector 12 but has a gap with the entire reflector 12. It will be appreciated that the radome arrangement is optional and the antenna 10 may not include a radome.
  • the absorbing material layer 14 can theoretically be disposed on the outer surface of the reflecting plate 12 facing away from the antenna element 11. In the embodiment in which the radome 13 is provided, the absorbing material layer 14 is disposed between the radome 13 and the first side plate 12b of the reflecting plate 12 and between the radome 13 and the second side plate 12c to achieve the desired The absorbing properties.
  • the absorbing material layer 14 is applied to the outer surface of the first side plate 12b facing the radome 13 and to the outer surface of the second side plate 12c facing the radome 13.
  • the manner in which the absorbing material layer 14 is coupled to the reflecting plate may include bonding and riveting.
  • Absorbing materials are an important functional composite that was first applied to the military and can reduce the radar cross section of military targets.
  • electronic components are increasingly integrated, miniaturized and high-frequency, and absorbing materials are widely used in the civilian field, such as microwave chamber materials, micro-attenuator components and microwave molding processing technology. Wait.
  • the absorbing material is usually a composite material obtained by mixing a matrix material and a absorbing agent.
  • the base materials mainly include coating type, ceramic type, rubber type and plastic type, and the absorbing agent mainly includes inorganic ferromagnetic and ferrite magnetic substances, conductive polymers and carbon-based materials.
  • the absorbing material may be the absorbing wave metamaterial described in the first to fourth preferred embodiments.
  • the parameters of the absorbing material are:
  • the normal incidence reflectance R is at lGH fR ⁇ -ldB, at 2
  • the absorbing material layer 14 may cover the outer surface of the region of the reflector comprising the array of transducers, and the arrangement of the absorbing material layer 14 is centered on the array of transducers.
  • the line 20 includes an antenna element 21, a reflector 22, a radome 23, and a layer of absorbing material 24.
  • the reflecting plate 22 has a bottom plate 22a, a first side plate 22b, and a second side plate 22c.
  • the first side plate 22b and the second side plate 22c are opposed to each other.
  • the reflecting plate 22 may also have a third side plate and a fourth side plate (not shown).
  • the third side panel is opposite to the fourth side panel.
  • the third side panel is adjacent to the first side panel 22b and the second side panel 22c, and the fourth side panel is also adjacent to the first side panel 22b and the second side panel 22c.
  • the first side panel 22b and the second side panel 22c may have a regular rectangular shape, and the third side panel and the fourth side panel may form a chamfer on a rectangular basis.
  • the antenna element 21 is disposed above the bottom plate 22a.
  • the form of the antenna element 21 and the manner of bonding with the bottom plate 22a are not limited in this embodiment.
  • the radome 23 surrounds at least the bottom plate 22a of the reflecting plate 22, the first side plate 22b, and the second side plate 22c. Part of the radome is removed in Fig. 2 to make the structure of the reflecting plate 22 visible. As can be seen, the radome 23 is not in contact with the reflecting plate 22, but has a gap with the entire reflecting plate 22. It will be appreciated that the radome arrangement is optional and the antenna 20 may not include a radome.
  • the absorbing material layer 24 can theoretically be disposed on the outer surface of the reflecting plate 22 facing away from the antenna element 21. In the embodiment in which the radome 23 is provided, the absorbing material layer 24 is disposed between the radome 23 and the first side plate 22b of the reflecting plate 22 and between the radome 23 and the second side plate 22c to achieve the desired The absorbing properties.
  • the absorbing material layer 24 is attached to the radome 23 and is located on the inner surface of the radome 23 facing the first side panel 22b and the second side panel 22c. In order to achieve a better effect, the absorbing material layer 24 is also located on the inner surface of the radome 23 facing the bottom plate 22a.
  • the manner in which the absorbing material layer 24 is attached to the radome 23 may include bonding or riveting.
  • the radome 33 may be metallized with the surface of the bonding portion of the absorbing material layer 34 and then bonded to the absorbing material layer 34.
  • the radome 23 has a built-in recess for placing the absorbing material.
  • the absorbing material may be the absorbing wave metamaterial described in the first to fourth preferred embodiments.
  • the parameters of the absorbing material are: normal incidence reflectance R at lGH fR ⁇ -ldB, R ⁇ -3dB at 2 GHz, dielectric constant 5-30, permeability 1- 7.
  • the absorbing material layer 24 may cover the outer surface of the region of the reflector comprising the array of transducers, and the arrangement of the absorbing material layer 24 is centered on the array of transducers.
  • the antenna 30 of the present embodiment includes an antenna element 31, a reflector 32, a radome 33, and a absorbing material layer 34.
  • the reflecting plate 32 has a bottom plate 32a, a first side plate 32b, and a second side plate 32c. The first side plate 32b and the second side plate 32c are opposed to each other.
  • the reflecting plate 32 may also have a third side plate and a fourth side plate (not shown).
  • the third side panel is opposite to the fourth side panel.
  • the third side panel is adjacent to the first side panel 32b and the second side panel 32c, and the fourth side panel is also adjacent to the first side panel 32b and the second side panel 32c.
  • the first side panel 32b and the second side panel 32c may have a regular rectangular shape, and the third side panel and the fourth side panel may form a chamfer on a rectangular basis.
  • the antenna element 31 is disposed above the bottom plate 32a.
  • the form of the antenna element 31 and the manner of bonding with the bottom plate 32a are not limited in this embodiment.
  • the radome 33 surrounds at least the bottom plate 32a of the reflecting plate 32, the first side plate 32b, and the second side plate 32c. Part of the radome is removed in Fig. 3 to make the structure of the reflecting plate 22 visible. As can be seen, the radome 33 is not in contact with the reflecting plate 32, but has a gap with the entire reflecting plate 32. It will be appreciated that the radome arrangement is optional and the antenna 30 may not include a radome.
  • the absorbing material layer 34 can theoretically be disposed on the outer surface of the reflecting plate 32 facing away from the antenna element 31. In the embodiment in which the radome 33 is provided, the absorbing material layer 34 is disposed between the radome 33 and the first side plate 32b of the reflecting plate 32 and between the radome 33 and the second side plate 32c to achieve the desired The absorbing properties.
  • the absorbing material layer 34 is bonded to a metal layer 35 which is located on the inner surface of the radome 33 facing the first side plate 32b and the second side plate 32c.
  • the metal layer 35 is also located on the inner surface of the antenna cover 23 facing the bottom plate 32a.
  • the manner in which the absorbing material layer 34 and the metal layer 35 are joined may include bonding and riveting.
  • the manner in which the metal layer 35 is coupled to the radome 33 may include bonding and riveting. Grooves may be provided in the radome 33 for placing the metal layer 35 and the absorbing material layer 34.
  • the metal layer can be, for example, a copper foil.
  • the absorbing material may be the absorbing wave metamaterial described in the first to fourth preferred embodiments.
  • the parameters of the absorbing material are: normal incidence reflectance R at lGH fR ⁇ -ldB, R ⁇ -3dB at 2 GHz, dielectric constant 5-30, permeability 1- 7.
  • the absorbing material layer 34 may cover the outer surface of the region of the reflector comprising the array of transducers, and the arrangement of the absorbing material layer 34 is centered on the array of transducers.
  • the grid is a node with the center of the conductive geometric unit, and a connection between adjacent nodes is formed, which is used to describe the arrangement rule of the conductive geometric unit.
  • the absorbing wave metamaterial includes a magnetic electromagnetic absorbing material layer 2 and a magnetic electromagnetic absorbing material Layer 2 combines conductive geometry unit 1.
  • the magnetic electromagnetic absorbing material layer 2 may be a rubber-based combined electromagnetic wave absorbing agent, and the electromagnetic wave absorbing agent may be a granular ferrite or a micro/submicron metal particle absorbent or a magnetic fiber absorbent or a nano magnetic absorbent, which can pass A miscellaneous or proportionate combination is incorporated into the rubber matrix.
  • the magnetic electromagnetic absorbing material layer 2 may be a absorbing patch material, has a small thickness and can be automated.
  • the thickness and electromagnetic parameters of the magnetic electromagnetic absorbing material layer 2 can be set according to the working frequency band of the absorbing wave metamaterial, the working frequency range is 0.8-2.7 GHz, and the dielectric constant of the absorbing wave metamaterial is 5-30, magnetic permeability.
  • the vertical incident reflectance R is R ⁇ -ldB at 1 GHz and R ⁇ -3d B at 2 GHz.
  • the conductive geometric unit 1 has a circular shape with two openings, and a parallel metal strip la is provided at the cornice. As shown in FIG.
  • the arrangement rule of the conductive geometric structure unit 1 is a periodic rule, and the periodic law is periodically arranged in two directions perpendicular to each other in the plane, extending in a square mesh form, but the arrangement law is not limited Therefore, it may be a misaligned arrangement or a disordered arrangement or an uneven arrangement.
  • a metal layer 3 may also be disposed on the back side of the magnetic electromagnetic wave absorbing material layer 2. The metal layer 3 is selectively disposed, and in some applications, the metal layer 3 may be omitted. For example, in the third embodiment, since the absorbing material layer has been attached to the metal layer, no metal layer is provided inside the absorbing material layer.
  • the material of the conductive geometric unit 1 may be copper, silver or gold.
  • the thickness of the conductive geometry unit 1 is greater than the skin depth of the working frequency segment.
  • the conductive geometric unit 1 and its metal strip la have a line width of W and a thickness of H, which can be set to 0.1 mm ⁇ W ⁇ 1 mm, 0.005 mm ⁇ H ⁇ 0.05 mm, and the conductive geometry in the size range
  • the structural unit 1 has a good absorbing effect.
  • the conductive geometric unit 1 has a shape of a circumscribed circle, and the diameter of the circumscribed circle can be set to 1/20 to 1/5 of the electromagnetic wavelength of the free space in the working frequency band.
  • the circumscribed circle of the conductive geometry unit 1 is a circular shape defined by itself. In other embodiments, the circumscribed circle may be a circle defined by the outermost endpoint.
  • the thickness of the metal layer 3 can be set to be greater than the skin depth of the corresponding operating frequency band.
  • the skin depth is such that when a very high frequency current passes through the conductor, it can be considered that the current flows only in a very thin layer on the surface of the conductor, the thickness of which is the skin depth.
  • the thickness of the metal layer 3 is set with reference to the skin depth, the material of the central portion of the conductor can be omitted.
  • the conductive geometric unit 1 may be fixed to the magnetic electromagnetic wave absorbing material layer 2 by a film or a patch, or may be embedded in the magnetic electromagnetic wave absorbing material layer 2.
  • the magnetic electromagnetic absorbing material layer 2 can be bonded or otherwise fixed to the metal layer 3.
  • the TE wave is a transverse wave in the electromagnetic wave, as shown in FIG. 12, the reflectance in the TE mode is increased by the conductivity
  • the vertical incident reflectance of the material after the structural unit is decreased.
  • the diameter lm of the conductive geometric unit 1 is 3 micrometers
  • the reflectivity of the absorbing supermaterial shown in Fig. 11 is relative to the magnetic electromagnetic absorbing wave without the conductive geometric unit.
  • the material layer has a lower reflectivity.
  • the diameter lm of the conductive geometric unit 1 is 3.5 ⁇ m, the reflectance of the absorbing wave metamaterial is further lowered.
  • the diameter lm of the conductive geometric unit is 4 micrometers, the absorption of the superabsorbent metamaterial is the lowest.
  • the operating frequency range shown in Figure 12 is 0.8-2.7 GHz.
  • the TM wave is a longitudinal wave in the electromagnetic wave, as shown in FIG. 13, the reflectance in the TM mode decreases after the increase of the conductive geometry unit, and the diameter lm of the conductive geometric unit 1 is At 3 micron ⁇ , the reflectivity of the absorbing supermaterial shown in Figure 11 is lower than that of the magnetic electromagnetic absorbing material layer without conductive geometrical elements.
  • the diameter lm of the conductive geometric unit 1 is 3.5 ⁇ m, the reflectance of the absorbing supermaterial is further lowered.
  • the diameter of the conductive geometry unit is lm 4 ⁇ m, the absorption of the superabsorbent material is the lowest.
  • the operating frequency range shown in Figure 13 is 0.8-2.7 GHz. It is worth mentioning that the embodiment according to the invention is not limited to a specific operating frequency, but the electromagnetic microstructure can be correspondingly designed according to the set operating frequency and the absorbing material used.
  • the present embodiment has the same reference numerals and the same elements as those of the foregoing embodiments, and the same reference numerals are used to denote the same or similar elements, and the description of the same technical content is selectively omitted.
  • the description of the omitted portions reference may be made to the foregoing embodiments, and the detailed description is not repeated herein.
  • the conductive geometric unit 4 has an octagonal shape of the cornice, and a parallel metal strip 40 is disposed at the cornice.
  • the arrangement rule of the conductive geometric unit 4 is a periodic rule, and the periodic law is periodically arranged in two directions perpendicular to each other in the plane, extending in a square mesh form, but the arrangement law is not limited Therefore, it may be a misaligned arrangement or a disordered arrangement or an uneven arrangement.
  • Conductive Geometry Unit 4 The diameter of the circumscribed circle can be set to 1/20 ⁇ 1/5 of the free space electromagnetic wavelength of the working frequency band.
  • the reflectance in the TE mode decreases as the vertical incidence reflectance of the material increases after the conductive geometric unit is increased, when the diameter lm of the conductive geometric unit 4 is 3 micrometers, as shown in FIG.
  • the reflectivity of the absorbing supermaterial is lower than that of the magnetic electromagnetic absorbing material layer without the conductive geometric unit.
  • the diameter lm of the conductive geometric unit 4 is 3.5 ⁇ m, the reflectance of the absorbing wave metamaterial is further lowered.
  • the diameter lm of the conductive geometric unit is 4 micrometers, the absorption of the superabsorbent metamaterial is the lowest.
  • Figure 15 The operating frequency range shown is 0.8-2.7 GHz.
  • the reflectance in the TM mode decreases as the vertical incidence reflectance of the material increases after the conductive geometric unit, when the diameter lm of the conductive geometric unit 4 is 3 micrometers, as shown in FIG.
  • the reflectivity of the absorbing supermaterial is lower than that of the magnetic electromagnetic absorbing material layer without the conductive geometric unit.
  • the diameter lm of the conductive geometric unit 4 is 3.5 ⁇ m, the reflectance of the absorbing supermaterial is further lowered.
  • the diameter lm of the conductive geometric unit 4 is 4 ⁇ m, the absorption of the superabsorbent material is the lowest.
  • the operating frequency range shown in Figure 16 is 0.8-2.7 GHz.
  • the conductive geometric unit 5 has a quadrangular shape of a cornice, and a parallel metal strip 50 is disposed at the cornice, and the side of the cornice is located. The center is displaced into the quadrilateral.
  • the arrangement rule of the conductive geometric unit 5 is a periodic rule, and the periodic law is periodically arranged in two directions perpendicular to each other in the plane, and extends in a square grid form, but the arrangement rule is not limited. Therefore, it may be a misaligned arrangement or a disordered arrangement or an uneven arrangement.
  • Conductive Geometry Unit 5 The diameter of the circumscribed circle can be set to 1/20 ⁇ 1/5 of the free-space electromagnetic wavelength of the working frequency band.
  • the reflectance in the TE mode decreases as the normal incidence reflectance of the material increases after the conductive geometric unit, when the diameter lm of the conductive geometric unit 5 is 3 micrometers, as shown in FIG.
  • the reflectivity of the absorbing supermaterial is lower than that of the magnetic electromagnetic absorbing material layer without the conductive geometric unit.
  • the diameter lm of the conductive geometric unit 5 is 3.5 ⁇ m
  • the reflectance of the absorbing supermaterial is further lowered.
  • the diameter of the conductive geometric unit lm is 4 ⁇ m, the absorption of the superabsorbent material is the lowest.
  • the operating frequency range shown in Figure 18 is 0.8-2.7 GHz.
  • the reflectance in the TM mode decreases as the vertical incidence reflectance of the material increases after the conductive geometric unit is increased, when the diameter lm of the conductive geometric unit 5 is 3 micrometers, as shown in FIG.
  • the reflectivity of the absorbing supermaterial is lower than that of the magnetic electromagnetic absorbing material layer without the conductive geometric unit.
  • the diameter lm of the conductive geometric unit 5 is 3.5 ⁇ m, the reflectance of the absorbing wave metamaterial is further lowered.
  • the diameter lm of the conductive geometric unit 5 is 4 micrometers, the absorption of the superabsorbent metamaterial is the lowest.
  • the operating frequency range shown in Figure 19 is 0.8-2.7 GHz.
  • This embodiment employs a third preferred embodiment or a absorbing wave metamaterial similar to the third preferred embodiment.
  • the reflectance in the TE mode decreases as the large-angle incident reflectance of the material increases after the conductive geometry unit.
  • the reflectivity of the absorbing supermaterial shown in Figure 17 is lower than that of the magnetic electromagnetic absorbing material layer without the conductive geometric unit, even in At a large angle of incidence of 50 degrees, 60 degrees, and 70 degrees, the reflectance also drops significantly.
  • the reflectance is also lowered at an incident angle of 85 degrees.
  • the reflectance in the TM mode decreases the large-angle incident reflectance of the material after the conductive geometric unit is increased, and when the absorbing supermaterial ⁇ with the conductive geometric unit 5 is used, FIG. 17
  • the reflectivity of the absorbing wave metamaterial shown is lower than that of the magnetic electromagnetic absorbing material layer without the conductive geometric unit, and the reflectance is significantly reduced even at a large angle of incidence of 50 degrees, 60 degrees, and 70 degrees. Although not shown in the figure, the reflectance is also lowered at an incident angle of 85 degrees.
  • the annular conductive geometry in the conductive geometric unit is equivalent to the inductance L in the circuit, and the two parallel strip structures are equivalent to the capacitance C in the circuit, which is a combination LC circuit
  • Figure 10 is equivalent to two inductors and two capacitors in series, by adjusting the size of the conductive geometry unit to change its electromagnetic parameter performance, to achieve the desired effect, that is, the required operating frequency of the absorbing wave metamaterial
  • the electromagnetic wave inside is concentratedly absorbed, which is convenient for absorption by the magnetic electromagnetic absorbing material layer disposed below, and the added metal layer emits the absorbed electromagnetic wave to the magnetic absorbing material layer for secondary absorption.
  • the reflection of the absorbing material against the vertical incidence of the electromagnetic wave and the entrance of the large angle ⁇ can be reduced, and the working frequency band is changed by changing the topology and arrangement of the electromagnetic metamaterial by the electromagnetic characteristics of the conventional absorbing material. Its own electromagnetic parameters and overall equivalent electromagnetic parameters, thereby achieving the effect of reducing the reflectivity.
  • the multi-layer absorbing material is not required, so that the absorbing effect equivalent to the prior art can be realized under the condition of lighter and thinner, that is, the absorption effect equivalent to the conventional material can be realized under the condition of lower areal density.
  • Fig. 4 is a comparison of the pattern of the antenna with the absorbing material and the antenna without the absorbing material in the embodiment of the present invention at 1710 MHz.
  • Fig. 5 is a view showing the orientation of the antenna with the absorbing material and the antenna without the absorbing material in the embodiment of the present invention at 1990 MHz.
  • Figure 6 is a comparison of the pattern of an antenna with an absorbing material and an antenna without an absorbing material at 2170 MHz in an embodiment of the present invention. After loading the absorbing material, the front-to-back ratio is increased at 1710, 1990, and 2170MHz: 2.15, 1.51, 1.80dB.
  • FIG. 7 is a comparison of the pattern of an antenna with a absorbing wave metamaterial and an existing antenna without absorbing ultra-high material at 1710 MHz in accordance with a preferred embodiment of the present invention.
  • Figure 8 is a comparison of the pattern of an antenna with a absorbing wave metamaterial and an antenna without an absorbing wave metamaterial at 1990 MHz in accordance with a preferred embodiment of the present invention.
  • Figure 9 is a comparison of the pattern of an antenna with a absorbing wave metamaterial and an antenna without an absorbing wave material in a preferred embodiment of the present invention at 2170 M Hz.
  • the antenna front-to-back ratio is 17.85dB, 24.50dB and 23.18dB before and after the 1710MHz, 1990MHz and 2170MHz, respectively.
  • the antenna front-to-back ratio is 29.83dB, 28.17dB and 27.67dB, respectively; the lifting amplitudes are 5.97, 3.67 and 4.48dB, respectively, so the electrical performance of the embodiment of the present invention is significantly improved.
  • the embodiments of the present invention also have the following advantages: the absorbing wave metamaterial and the conductive material such as copper foil for fabricating the conductive geometry in the metamaterial do not additionally increase the raw material cost significantly; the installation is convenient, and the antenna assembly is not difficult to be added. .
  • the absorbing wave metamaterial has better environmental adaptability than the conventional absorbing material.
  • Embodiments of the present invention can be applied to a directional coverage product such as a base station antenna, a WIFI antenna, a toll station ETC antenna, etc., and is applied in the field of mobile communication and wireless coverage, and the performance of the antenna product is improved before and after the ratio and cross polarization.
  • the system improves backward interference, mitigates transmission and reception interference, improves communication capacity, and so on.
  • the improvement of the front-to-back ratio makes the antenna cover more forward coverage, and the backward coverage interference is reduced. This is especially beneficial in letter and wireless coverage environments.
  • Cross-polarization isolation improvement can alleviate the interference of the transmitting antenna to the receiving antenna because there are cases where the transmitting and receiving antennas are orthogonally polarized. Improvements in cross-polarization can also increase communication capacity.

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Abstract

本发明涉及一种天线，可以在不改变反射板结构的条件下提高前后比和交叉极化隔离。该天线包括天线振子、反射板，该天线振子设置在该反射板上，该天线还包括吸波材料层，该吸波材料层设置于该反射板背向该天线振子的外表面的一侧。

Description

一种天线
技术领域
[0001] 本发明涉及天线领域， 尤其是涉及一种电气性能得到提升的天线。
背景技术
[0002] 天线前后比和交叉极化都是衡量天线性能的重要参数。 天线的前后比是指天线 方向图中主瓣的最大辐射方向 （规定为 0°) 的功率通量密度与相反方向附近 （规 定为 180°±20°范围） 的最大功率通量密度之比值。 表明了天线对后瓣抑制的好坏 ， 天线的前后比较低会导致天线背面区域干扰的问题。 天线的交叉极化是指天 线辐射远场的电场矢量与主极化方向正交的方向上存在分量。
技术问题
[0003] 现有技术为了达到提高前后比和交叉极化隔离的效果， 会对反射板进行改动， 如增加反射板面积、 提高反射板边沿结构复杂度等等。 然而对反射板尺寸增大 会相应增加天线横截面积， 而提高反射板边沿结构复杂度则会增加加工难度和 产品成本。
问题的解决方案
技术解决方案
[0004] 本发明所要解决的技术问题是提供一种天线， 可以在不改变反射板结构的条件 下提高前后比和交叉极化隔离。
[0005] 本发明为解决上述技术问题而采用的技术方案是一种天线， 包括天线振子、 反 射板， 该天线振子设置在该反射板上， 该天线还包括吸波材料层， 该吸波材料 层设置于该反射板背向该天线振子的外表面的一侧。
[0006] 在本发明的一实施例中， 该吸波材料层贴覆于该反射板的背向该天线振子的外 表面， 或该吸波材料层间隙设置于该反射板的背向该天线振子的外表面。
[0007] 在本发明的一实施例中， 该天线还包括天线罩， 该天线振子和该反射板设置在 天线罩内， 该吸波材料层设置于该天线罩与反射板之间。
[0008] 在本发明的一实施例中， 该反射板具有底板、 第一侧板和第二侧板， 该第一侧 板和该第二侧板位置相对， 该天线振子设于该底板上， 该天线罩至少包围该底 板、 该第一侧板和该第二侧板， 该吸波材料层至少设置于该天线罩和该第一侧 板之间以及该天线罩和该第二侧板之间。
[0009] 在本发明的一实施例中， 该吸波材料层贴覆于该第一侧板的面向该天线罩的外 表面以及贴覆于该第二侧板的面向该天线罩的外表面， 或该吸波材料层贴覆于 该天线罩面向该第一侧板和该第二侧板的内表面。
[0010] 在本发明的一实施例中， 该吸波材料层还设置在该天线罩和该底板之间。
[0011] 在本发明的一实施例中， 该吸波材料层贴覆于该底板的面向该天线罩的外表面
， 或该吸波材料层贴覆于该天线罩面向该底板的内表面。
[0012] 在本发明的一实施例中， 该吸波材料层结合于一金属层， 该金属层设置于该天 线罩面向该第一侧板和该第二侧板的内表面。
[0013] 在本发明的一实施例中， 该金属层还设置于该天线罩面向该底板的内表面。
[0014] 在本发明的一实施例中， 该天线振子的数量为多个并形成振子阵列， 该吸波材 料层覆盖反射板上对应振子阵列的区域的外表面， 且该吸波材料层的布置是以 振子阵列为中心。
[0015] 在本发明的一实施例中， 该吸波材料层包括磁性电磁吸波材料层以及与磁性电 磁吸波材料层相结合的导电几何结构层； 该导电几何结构层由依次排布的多个 导电几何结构单元组成， 每个导电几何结构单元包括非封闭的环状导电几何结 构， 该环状导电几何结构的幵口处设置有相对平行的两个条形结构。
[0016] 在本发明的一实施例中， 该环状导电几何结构设置有一个以上的该幵口。
[0017] 在本发明的一实施例中， 该环状导电几何结构呈圆形、 椭圆形、 三角形或多边 形。
[0018] 在本发明的一实施例中， 该吸波材料层的介电常数为 5-30， 磁导率为 1-7。
[0019] 在本发明的一实施例中， 该导电几何结构单元呈周期阵列排布。
[0020] 在本发明的一实施例中， 该磁性电磁吸波材料层的表面上设置有金属层。
[0021] 在本发明的一实施例中， 该磁性电磁吸波材料层是吸波贴片材料。
[0022] 在本发明的一实施例中， 该导电几何结构单元附着于该磁性电磁吸波材料层或 者嵌入在该磁性电磁吸波材料层中。 [0023] 在本发明的一实施例中， 该磁性电磁吸波材料层包括基体以及结合于该基体的 吸收剂。
[0024] 在本发明的一实施例中， 该导电几何结构单元是具有外接圆的形状， 该外接圆 的直径为工作频段自由空间电磁波长的 1/20- 1/5。
[0025] 在本发明的一实施例中， 该吸波材料层的工作频率在 0.8-2.7GHZ频率段内， 该 导电几何结构单元的厚度大于对应该工作频率段的该导电几何结构单元的趋肤 深度。
[0026] 在本发明的一实施例中， 该吸波材料层的工作频率在 0.8-2.7GHZ频率段内， 该 金属层的厚度大于对应所述工作频率段的所述金属层的趋肤深度。
[0027] 在本发明的一实施例中， 该环状导电几何结构及条形结构的线宽均为 W， 0.1m m≤W≤lmm。
[0028] 在本发明的一实施例中， 该环状导电几何结构及条形结构的厚度均为 H， 0.005 mm≤H≤0.05mm。
[0029] 本发明由于采用以上技术方案， 使之与现有技术相比， 能够提升天线的电气性 育 ， 具体表现为： 设置于反射板背向天线振子的外表面一侧的吸波材料层， 能 够吸收来自天线上反射板边沿衍射至后向的电磁波， 进而提升天线的前后比和 交叉极化隔离。 并且吸波材料不会额外显著增加原料成本， 另外天线安装方便 不会为天线组装增加难度。
发明的有益效果
有益效果
[0030] 在本发明的实施例中， 该吸波材料层包括磁性电磁吸波材料层以及与磁性电磁 吸波材料层相结合的导电几何结构层， 导电几何结构层可以将吸波材料层所需 工作频率内的电磁波进行集中吸收， 便于下面设置的磁性电磁吸波材料层吸收
， 另增加的金属层会将吸收的电磁波反射到磁性电磁吸波材料层进行二次吸收 ， 达到更佳的吸波效果。
对附图的简要说明
附图说明
[0031] 为让本发明的上述目的、 特征和优点能更明显易懂， 以下结合附图对本发明的 具体实施方式作详细说明， 其中：
图 1是本发明第一实施例的天线的立体结构图。
图 2是本发明第二实施例的天线的立体结构图。
图 3是本发明第三实施例的天线的立体结构图。
图 4是本发明实施例的带吸波材料的天线与已有不带吸波材料的天线的方向图 在 1710MHz日寸的对比。
图 5是本发明实施例的带吸波材料的天线与已有不带吸波材料的天线的方向图 在 1990MHz日寸的对比。
图 6是本发明实施例的带吸波材料的天线与已有不带吸波材料的天线的方向图 在 2170MHz日寸的对比。
图 7是本发明较佳实施例的带吸波超材料的天线与已有不带吸波超材料的天线 的方向图在 1710MHz吋的对比。
图 8是本发明较佳实施例的带吸波超材料的天线与已有不带吸波超材料的天线 的方向图在 1990MHz日寸的对比。
图 9是本发明较佳实施例的带吸波超材料的天线与已有不带吸波超材料的天线 的方向图在 2170MHz吋的对比。
图 10为本发明第一较佳实施例中的电磁吸波超材料的一个单元的示意图； 图 11为本发明第一较佳实施例中的电磁吸波超材料的多个单元的排布规律的示
[0044] 图 13为本发明第一较佳实施例中的电磁吸波超材料在 TM模式下的反射率曲线 图；
[0045] 图 14为本发明第二较佳实施例中的电磁吸波超材料的多个单元的排布规律的示 图 15为本发明第二较佳实施例中的电磁吸波超材料在 TE模式下的反射率曲线图 图 16为本发明第二较佳实施例中的电磁吸波超材料在 TM模式下的反射率曲线 图；
[0048] 图 17为本发明第三较佳实施例中的电磁吸波超材料的多个单元的排布规律的示 意图；
[0049] 图 18为本发明第三较佳实施例中的电磁吸波超材料在 TE模式下的反射率曲线图
[0050] 图 19为本发明第三较佳实施例中的电磁吸波超材料在 TM模式下的反射率曲线 图；
[0051] 图 20为本发明第四较佳实施例中的电磁吸波超材料在 TE模式下的反射率曲线图
[0052] 图 21为本发明第四较佳实施例中的电磁吸波超材料在 TM模式下的反射率曲线 图。
本发明的实施方式
[0053] 在下面的描述中阐述了很多具体细节以便于充分理解本发明， 但是本发明还可 以采用其它不同于在此描述的其它方式来实施， 因此本发明不受下面公幵的具 体实施例的限制。
[0054] 本发明的实施例描述一种天线， 能够提升前后比和交叉极化等性能， 为所应用 的系统改进后向干扰， 减轻收发干扰， 提升通信容量。
[0055] 根据本发明的实施例， 在天线中引入了吸波材料， 吸收来自天线反射板边沿衍 射至后向的电磁波， 从而避免对天线反射板的结构改动。
[0056] 下面具体描述本发明的各个实施例。
[0057] 第一实施例
[0058] 图 1是本发明第一实施例的天线的立体结构图。 参考图 1所示， 本实施例所的天 线 10， 包括天线振子 11、 反射板 12、 天线罩 13和吸波材料层 14。
[0059] 反射板 12具有底板 12a、 第一侧板 12b、 第二侧板 12c。 第一侧板 12b和第二侧板 12c相对。 反射板 12还可具有第三侧板和第四侧板 （图未示出） 。 第三侧板和第 四侧板相对。 第三侧板与第一侧板 12b和第二侧板 12c相邻， 第四侧板也与第一侧 板 12b和第二侧板 12c相邻。 作为举例， 第一侧板 12b和第二侧板 12c可呈规则的矩 形， 第三侧板和第四侧板则是在矩形的基础上形成切角。 例如将矩形的一个或 多个角切掉， 变成斜边。
[0060] 天线振子 11设于底板 12a之上。 在本实施例中不限定天线振子 11的形态及其与 底板 12a之间的结合方式。
[0061] 天线罩 13至少包围反射板 12的底板 12a、 第一侧板 12b和第二侧板 12c。 图 1中去 除了部分天线罩以使得反射板 12的结构可见。 如图可见， 天线罩 13并不与反射 板 12接触， 而是与整个反射板 12之间具有间隙。 可以理解， 天线罩的设置是可 选的， 天线 10可以不包含天线罩。
[0062] 吸波材料层 14理论上可设置于反射板 12的背向天线振子 11的外表面。 在设置天 线罩 13的实施例中， 吸波材料层 14是设置于天线罩 13和反射板 12的第一侧板 12b 之间以及天线罩 13和第二侧板 12c之间， 以实现所期望的吸波性能。
[0063] 在本实施例中， 吸波材料层 14贴覆于第一侧板 12b的面向天线罩 13的外表面以 及贴覆于第二侧板 12c的面向天线罩 13的外表面。 在本实施例中， 吸波材料层 14 与反射板的连接方式可包括粘接和铆接。
[0064] 吸波材料是一种重要的功能复合材料， 最先应用于军事上， 可以降低军用目标 的雷达散射截面。 随着科学技术的发展幵始， 电子元器件日益集成化、 小型化 和高频化， 吸波材料在民用领域应用越来越广泛， 如作为微波暗室材料， 微衰 减器元件及微波成型加工技术等。
[0065] 吸波材料通常是通过基体材料和吸波剂混合制得的复合材料。 基体材料主要包 括涂料型， 陶瓷型， 橡胶型和塑料型， 吸波剂主要有无机铁磁性和铁氧体磁性 物质和导电聚合物及碳基材料等。
[0066] 吸波材料可以是第一至第四较佳实施例所描述的吸波超材料。
[0067] 在此实施例中， 吸波材料的参数是： 垂直入射反射率 R在 lGH fR<-ldB， 在 2
GHz日寸 R<-3dB， 介电常数 5-30， 磁导率 1-7。
[0068] 在覆盖范围上， 吸波材料层 14可覆盖反射板包含振子阵列的区域的外表面， 且 吸波材料层 14的布置是以振子阵列为中心。
[0069] 第二实施例
[0070] 图 2是本发明第二实施例的天线的立体结构图。 参考图 2所示， 本实施例所的天 线 20， 包括天线振子 21、 反射板 22、 天线罩 23和吸波材料层 24。
[0071] 反射板 22具有底板 22a、 第一侧板 22b、 第二侧板 22c。 第一侧板 22b和第二侧板 22c相对。 反射板 22还可具有第三侧板和第四侧板 （图未示出） 。 第三侧板和第 四侧板相对。 第三侧板与第一侧板 22b和第二侧板 22c相邻， 第四侧板也与第一侧 板 22b和第二侧板 22c相邻。 作为举例， 第一侧板 22b和第二侧板 22c可呈规则的矩 形， 第三侧板和第四侧板则是在矩形的基础上形成切角。
[0072] 天线振子 21设于底板 22a之上。 在本实施例中不限定天线振子 21的形态及其与 底板 22a之间的结合方式。
[0073] 天线罩 23至少包围反射板 22的底板 22a、 第一侧板 22b和第二侧板 22c。 图 2中去 除了部分天线罩以使得反射板 22的结构可见。 如图可见， 天线罩 23并不与反射 板 22接触， 而是与整个反射板 22之间具有间隙。 可以理解， 天线罩的设置是可 选的， 天线 20可以不包含天线罩。
[0074] 吸波材料层 24理论上可设置于反射板 22的背向天线振子 21的外表面。 在设置天 线罩 23的实施例中， 吸波材料层 24是设置于天线罩 23和反射板 22的第一侧板 22b 之间以及天线罩 23和第二侧板 22c之间， 以实现所期望的吸波性能。
[0075] 在本实施例中， 吸波材料层 24贴覆于天线罩 23上， 且位于天线罩 23面向第一侧 板 22b和第二侧板 22c的内表面。 为了达到更好的效果， 吸波材料层 24还位于天线 罩 23面向底板 22a的内表面。 在此， 吸波材料层 24与天线罩 23的连接方式可包括 粘接或者铆接。 或者， 天线罩 33可以与吸波材料层 34的粘接部位表面金属化后 再粘接吸波材料层 34。 天线罩 23可内置凹槽， 用于放置吸波材料。
[0076] 吸波材料可以是第一至第四较佳实施例所描述的吸波超材料。
[0077] 在此实施例中， 吸波材料的参数是： 垂直入射反射率 R在 lGH fR<-ldB， 在 2 GHz日寸 R<-3dB， 介电常数 5-30， 磁导率 1-7。
[0078] 在覆盖范围上， 吸波材料层 24可覆盖反射板包含振子阵列的区域的外表面， 且 吸波材料层 24的布置是以振子阵列为中心。
[0079] 第三实施例
[0080] 图 3是本发明第三实施例的天线的立体结构图。 参考图 3所示， 本实施例所的天 线 30， 包括天线振子 31、 反射板 32、 天线罩 33和吸波材料层 34。 [0081] 反射板 32具有底板 32a、 第一侧板 32b、 第二侧板 32c。 第一侧板 32b和第二侧板 32c相对。 反射板 32还可具有第三侧板和第四侧板 （图未示出） 。 第三侧板和第 四侧板相对。 第三侧板与第一侧板 32b和第二侧板 32c相邻， 第四侧板也与第一侧 板 32b和第二侧板 32c相邻。 作为举例， 第一侧板 32b和第二侧板 32c可呈规则的矩 形， 第三侧板和第四侧板则是在矩形的基础上形成切角。
[0082] 天线振子 31设于底板 32a之上。 在本实施例中不限定天线振子 31的形态及其与 底板 32a之间的结合方式。
[0083] 天线罩 33至少包围反射板 32的底板 32a、 第一侧板 32b和第二侧板 32c。 图 3中去 除了部分天线罩以使得反射板 22的结构可见。 如图可见， 天线罩 33并不与反射 板 32接触， 而是与整个反射板 32之间具有间隙。 可以理解， 天线罩的设置是可 选的， 天线 30可以不包含天线罩。
[0084] 吸波材料层 34理论上可设置于反射板 32的背向天线振子 31的外表面。 在设置天 线罩 33的实施例中， 吸波材料层 34是设置于天线罩 33和反射板 32的第一侧板 32b 之间以及天线罩 33和第二侧板 32c之间， 以实现所期望的吸波性能。
[0085] 在本实施例中， 吸波材料层 34结合于一金属层 35， 金属层 35位于天线罩 33面向 第一侧板 32b和第二侧板 32c的内表面。 为了达到更好的效果， 金属层 35还位于天 线罩 23面向底板 32a的内表面。 在此， 吸波材料层 34与金属层 35的连接方式可包 括粘接和铆接。 金属层 35与天线罩 33的连接方式可包括粘接和铆接。 天线罩 33 内可设置凹槽， 用来放置金属层 35和吸波材料层 34。 金属层可以例如是铜箔。
[0086] 吸波材料可以是第一至第四较佳实施例所描述的吸波超材料。
[0087] 在此实施例中， 吸波材料的参数是： 垂直入射反射率 R在 lGH fR<-ldB， 在 2 GHz日寸 R<-3dB， 介电常数 5-30， 磁导率 1-7。
[0088] 在覆盖范围上， 吸波材料层 34可覆盖反射板包含振子阵列的区域的外表面， 且 吸波材料层 34的布置是以振子阵列为中心。
[0089] 在下文中， 网格是以导电几何结构单元的中心为节点， 相邻节点间连线形成， 其用于描述导电几何结构单元的排布规律。
[0090] 第一较佳实施例
[0091] 如图 10所示， 吸波超材料包括磁性电磁吸波材料层 2以及与磁性电磁吸波材料 层 2相结合的导电几何结构单元 1。 磁性电磁吸波材料层 2可以是以橡胶为基体结 合电磁波吸收剂， 电磁波吸收剂可以是颗粒铁氧体或者微米 /亚微米金属颗粒吸 收剂或者磁性纤维吸收剂或者纳米磁性吸收剂， 其可以通过惨杂或者配比的方 式结合于橡胶基体中。 磁性电磁吸波材料层 2可以是吸波贴片材料， 具有较小的 厚度并能自动化生产。 磁性电磁吸波材料层 2的厚度和电磁参数可以根据吸波超 材料的工作频段来设定， 工作频率段为 0.8-2.7GHz， 吸波超材料的介电常数为 5- 30， 磁导率为 1-7， 此吋垂直入射反射率 R为在 1GHz日寸 R<-ldB， 在 2GHz日寸 R<-3d B。 导电几何结构单元 1呈两个幵口的圆形， 在幵口处设置有平行的金属条带 la 。 如图 11所示， 导电几何结构单元 1的排布规律为成周期规律， 周期规律表现为 平面内相互垂直的两个方向周期性排布， 以方形网格形式延伸， 但排布规律不 限于此， 可以是错位排布或者无序排布或者不均匀排布。 在磁性电磁吸波材料 层 2的背侧还可设置有金属层 3。 金属层 3是选择性设置的， 在一些应用场合， 可 以省略金属层 3。 例如在第三实施例中， 由于吸波材料层已经附着在金属层上， 吸波材料层内部不再设置金属层。 导电几何结构单元 1的材料可以是铜、 银、 金 。 导电几何结构单元 1的厚度大于工作频率段的趋肤深度。 导电几何结构单元 1 及其金属条带 la的线宽均为 W， 厚度均为 H， 其可以设置成 0.1mm≤W≤lmm， 0.005mm≤H≤0.05mm， 在该尺寸范围内的导电几何结构单元 1具有良好的吸波效 果。 导电几何结构单元 1是具有外接圆的形状， 其外接圆的直径可以设定成工作 频段自由空间电磁波长的 1/20~1/5。 导电几何结构单元 1的外接圆即为其本身限 定的圆形。 在其他实施例中， 外接圆可以是由最外侧的端点限定的圆。 金属层 3 的厚度可以设置成大于对应工作频段的趋肤深度。 趋肤深度是当频率很高的电 流通过导体吋， 可以认为电流只在导体表面上很薄的一层中流过， 所述很薄的 一层的厚度就是趋肤深度。 当金属层 3的厚度的设置以趋肤深度为参考， 可以省 略导体中心部分的材料。
[0092] 导电几何结构单元 1可以通过薄膜或者贴片方式固定在磁性电磁吸波材料层 2之 上， 也可以是嵌入到磁性电磁吸波材料层 2中。 磁性电磁吸波材料层 2可以粘接 或者其他方式固定在金属层 3上。
[0093] TE波为电磁波中的横向波， 如图 12所示， 在 TE模式下的反射率在增加导电几 何结构单元后材料的垂直入射反射率下降， 当导电几何结构单元 1的直径 lm为 3 微米吋， 图 11所示的吸波超材料的反射率相对于没有导电几何结构单元的磁性 电磁吸波材料层的反射率要更低。 当导电几何结构单元 1的直径 lm为 3.5微米吋， 吸波超材料的反射率进一步降低。 当导电几何结构单元的直径 lm为 4微米吋， 吸 波超材料的反射率最低。 图 12所示的工作频率段为 0.8-2.7GHz。
[0094] TM波为电磁波中的纵向波， 如图 13所示， 在 TM模式下的反射率在增加导电几 何结构单元后材料的垂直入射反射率下降， 当导电几何结构单元 1的直径 lm为 3 微米吋， 图 11所示的吸波超材料的反射率相对于没有导电几何结构单元的磁性 电磁吸波材料层的反射率要更低。 当导电几何结构单元 1的直径 lm为 3.5微米吋， 吸波超材料的反射率进一步降低。 当导电几何结构单元的直径 lm为 4微米吋， 吸 波超材料的反射率最低。 图 13所示的工作频率段为 0.8-2.7GHz。 值得一提的是， 根据本发明的实施例不限于特定工作频率， 而可以根据设定的工作频率和所采 用的吸波材料而对应设计电磁微结构。
[0095] 第二较佳实施例
[0096] 本实施例沿用前述实施例的元件标号与部分内容， 其中采用相同的标号来表示 相同或近似的元件， 并且选择性地省略了相同技术内容的说明。 关于省略部分 的说明可参照前述实施例， 本实施例不再重复赘述。
[0097] 如图 14所示， 与第一较佳实施例不同的是， 导电几何结构单元 4带幵口的八边 形， 在幵口处设置有平行的金属条带 40。 如图 14所示， 导电几何结构单元 4的排 布规律为成周期规律， 周期规律表现为平面内相互垂直的两个方向周期性排布 ， 以方形网格形式延伸， 但排布规律不限于此， 可以是错位排布或者无序排布 或者不均匀排布。 导电几何结构单元 4外接圆的直径可以设定成工作频段自由空 间电磁波长的 1/20~1/5。
[0098] 如图 15所示， 在 TE模式下的反射率在增加导电几何结构单元后材料的垂直入射 反射率下降， 当导电几何结构单元 4的直径 lm为 3微米吋， 图 14所示的吸波超材 料的反射率相对于没有导电几何结构单元的磁性电磁吸波材料层的反射率要更 低。 当导电几何结构单元 4的直径 lm为 3.5微米吋， 吸波超材料的反射率进一步降 低。 当导电几何结构单元的直径 lm为 4微米吋， 吸波超材料的反射率最低。 图 15 所示的工作频率段为 0.8-2.7GHz。
[0099] 如图 16所示， 在 TM模式下的反射率在增加导电几何结构单元后材料的垂直入 射反射率下降， 当导电几何结构单元 4的直径 lm为 3微米吋， 图 14所示的吸波超 材料的反射率相对于没有导电几何结构单元的磁性电磁吸波材料层的反射率要 更低。 当导电几何结构单元 4的直径 lm为 3.5微米吋， 吸波超材料的反射率进一步 降低。 当导电几何结构单元 4的直径 lm为 4微米吋， 吸波超材料的反射率最低。 图 16所示的工作频率段为 0.8-2.7GHz。
[0100] 第三较佳实施例
[0101] 本实施例沿用前述实施例的元件标号与部分内容， 其中采用相同的标号来表示 相同或近似的元件， 并且选择性地省略了相同技术内容的说明。 关于省略部分 的说明可参照前述实施例， 本实施例不再重复赘述。
[0102] 如图 17所示， 与第一较佳实施例不同的是， 导电几何结构单元 5带幵口的四边 形， 在幵口处设置有平行的金属条带 50， 幵口所在的边的中心位移至四边形内 。 如图 17所示， 导电几何结构单元 5的排布规律为成周期规律， 周期规律表现为 平面内相互垂直的两个方向周期性排布， 以方形网格形式延伸， 但排布规律不 限于此， 可以是错位排布或者无序排布或者不均匀排布。 导电几何结构单元 5外 接圆的直径可以设定成工作频段自由空间电磁波长的 1/20~1/5。
[0103] 如图 18所示， 在 TE模式下的反射率在增加导电几何结构单元后材料的垂直入射 反射率下降， 当导电几何结构单元 5的直径 lm为 3微米吋， 图 17所示的吸波超材 料的反射率相对于没有导电几何结构单元的磁性电磁吸波材料层的反射率要更 低。 当导电几何结构单元 5的直径 lm为 3.5微米吋， 吸波超材料的反射率进一步降 低。 当导电几何结构单元的直径 lm为 4微米吋， 吸波超材料的反射率最低。 图 18 所示的工作频率段为 0.8-2.7GHz。
[0104] 如图 19所示， 在 TM模式下的反射率在增加导电几何结构单元后材料的垂直入 射反射率下降， 当导电几何结构单元 5的直径 lm为 3微米吋， 图 17所示的吸波超 材料的反射率相对于没有导电几何结构单元的磁性电磁吸波材料层的反射率要 更低。 当导电几何结构单元 5的直径 lm为 3.5微米吋， 吸波超材料的反射率进一步 降低。 当导电几何结构单元 5的直径 lm为 4微米吋， 吸波超材料的反射率最低。 图 19所示的工作频率段为 0.8-2.7GHz。
[0105] 第四较佳实施例
[0106] 本实施例沿用前述实施例的元件标号与部分内容， 其中采用相同的标号来表示 相同或近似的元件， 并且选择性地省略了相同技术内容的说明。 关于省略部分 的说明可参照前述实施例， 本实施例不再重复赘述。
[0107] 本实施例采用第三较佳实施例或者类似于第三较佳实施例的吸波超材料。 如图 20所示， 在 TE模式下的反射率在增加导电几何结构单元后材料的大角度入射反 射率下降。 当采用带导电几何结构单元 5的吸波超材料吋， 图 17所示的吸波超材 料的反射率相对于没有导电几何结构单元的磁性电磁吸波材料层的反射率要更 低， 即便在 50度、 60度、 70度的大角度入射， 反射率也明显下降， 虽然在图中 没有示出， 其在入射角度为 85度吋， 反射率也会下降。
[0108] 如图 21所示， 在 TM模式下的反射率在增加导电几何结构单元后材料的大角度 入射反射率下降， 当采用带导电几何结构单元 5的吸波超材料吋， 图 17所示的吸 波超材料的反射率相对于没有导电几何结构单元的磁性电磁吸波材料层的反射 率要更低， 即便在 50度、 60度、 70度的大角度入射， 反射率也明显下降， 虽然 在图中没有示出， 其在入射角度为 85度吋， 反射率也会下降。
[0109] 在已有技术中， 针对"电磁波在吸波材料表面的反射比较严重， 不利于对电磁 波的吸收， 尤其在大角度入射的条件下， 反射更加严重 "的情况， 业内通常采取 利用多层吸波材料， 或者在吸波材料中实现有梯度的电磁参数变化来实现更好 的阻抗匹配， 减少表面反射， 但多层吸波带来产品面密度的上升， 需要更多的 安装空间， 增加生产制备和检测的复杂度， 梯度变化的吸波材料工艺复杂度上 升， 工艺控制难度增加， 通常伴随产品一致性的下降。
[0110] 在前述实施例中， 导电几何结构单元中的环状导电几何结构等效于电路中的电 感 L， 相对平行的两个条形结构等效于电路中的电容 C， 组合起来就是一个 LC电 路， 图 10等效于两个电感及两个电容串联， 通过调节该导电几何结构单元的尺 寸改变其电磁参数性能， 达到我们所要求的效果， 即可以将吸波超材料所需工 作频率内的电磁波进行集中吸收， 便于下面设置的磁性电磁吸波材料层吸收， 另增加的金属层会将吸收的电磁波进行发射到磁性吸波材料层进行二次吸收。 根据本发明的实施例可以降低吸波材料针对电磁波垂直入射和大角度入射吋的 反射， 通过针对传统吸波材料的电磁特性， 通过改变电磁超材料的拓扑结构和 排布规律来改变工作频段内自身的电磁参数和整体等效电磁参数， 从而达到降 低反射率的效果。 并且无需多层吸波材料， 因此可以在更加轻薄的条件下实现 与已有技术等效的吸波效果， 即在更低面密度的条件下实现与传统材料等效的 吸收效果。
[0111] 本发明的有益效果为提升天线的电气性能， 具体表现为前后比和交叉极化隔离 。 图 4是本发明实施例的带吸波材料的天线与已有不带吸波材料的天线的方向图 在 1710MHz吋的对比。 图 5是本发明实施例的带吸波材料的天线与已有不带吸波 材料的天线的方向图在 1990MHz吋的对比。 图 6是本发明实施例的带吸波材料的 天线与已有不带吸波材料的天线的方向图在 2170MHz吋的对比。 加载吸波材料 后， 前后比提升在 1710， 1990， 2170MHz分别为: 2.15， 1.51， 1.80dB。
[0112] 图 7是本发明较佳实施例的带吸波超材料的天线与已有不带吸波超超材料的天 线的方向图在 1710MHz吋的对比。 图 8是本发明较佳实施例的带吸波超材料的天 线与已有不带吸波超材料的天线的方向图在 1990MHz吋的对比。 图 9是本发明较 佳实施例的带吸波超材料的天线与已有不带吸波超材料的天线的方向图在 2170M Hz吋的对比。 参考图 7-9所示， 通过测试， 未加载吸波超材料吋， 天线前后比在 1710MHz, 1990MHz和 2170MHz日寸前后比分别为 23.85dB， 24.50dB和 23.18dB ; 加载吸波超材料后， 天线前后比分别为 29.83dB， 28.17dB和 27.67dB; 提升幅度 分别为 5.97， 3.67和 4.48dB， 因此本发明实施例的电气性能提升明显。
[0113] 本发明实施例还具有如下优点： 吸波超材料和制作超材料中的导电几何结构的 导电材料如铜箔等不会额外显著增加原料成本； 安装方便， 不会为天线组装增 加难度。 在使用吸波超材料的实施例中， 吸波超材料环境适应性优于传统吸波 材料。
[0114] 本发明的实施例可以应用于基站天线、 WIFI天线、 收费站 ETC天线等定向覆盖 产品， 应用在移动通信、 无线覆盖领域， 会为天线产品提升前后比和交叉极化 等性能， 为系统改进后向干扰， 减轻收发干扰， 提升通信容量等等。 其中， 前 后比的提升使得天线覆盖更多向前向覆盖， 后向覆盖干扰降低， 在市区移动通 信和无线覆盖环境中尤为有利。 交叉极化隔离改善可以减轻发射天线对接收天 线的干扰， 因为存在收发天线为正交极化的情况。 交叉极化的改善还可以提升 通信容量。
虽然本发明已参照当前的具体实施例来描述， 但是本技术领域中的普通技术人 员应当认识到， 以上的实施例仅是用来说明本发明， 在没有脱离本发明精神的 情况下还可作出各种等效的变化或替换， 因此， 只要在本发明的实质精神范围 内对上述实施例的变化、 变型都将落在本申请的权利要求书的范围内。

Claims

权利要求书
一种天线， 其特征在于， 包括天线振子、 反射板， 该天线振子设置在 该反射板上， 该天线还包括吸波材料层， 该吸波材料层设置于该反射 板背向该天线振子的外表面的一侧。
如权利要求 1所述的天线， 其特征在于， 该吸波材料层贴覆于该反射 板的背向该天线振子的外表面， 或该吸波材料层间隙设置于该反射板 的背向该天线振子的外表面。
如权利要求 1所述的天线， 其特征在于， 该天线还包括天线罩， 该天 线振子和该反射板设置在天线罩内， 该吸波材料层设置于该天线罩与 反射板之间。
如权利要求 3所述的天线， 其特征在于， 该反射板具有底板、 第一侧 板和第二侧板， 该第一侧板和该第二侧板位置相对， 该天线振子设于 该底板上， 该天线罩至少包围该底板、 该第一侧板和该第二侧板， 该 吸波材料层至少设置于该天线罩和该第一侧板之间以及该天线罩和该 第二侧板之间。
如权利要求 4所述的天线， 其特征在于， 该吸波材料层贴覆于该第一 侧板的面向该天线罩的外表面以及贴覆于该第二侧板的面向该天线罩 的外表面， 或该吸波材料层贴覆于该天线罩面向该第一侧板和该第二 侧板的内表面。
如权利要求 4或 5所述的天线， 其特征在于， 该吸波材料层还设置在该 天线罩和该底板之间。
如权利要求 6所述的天线， 其特征在于， 该吸波材料层贴覆于该底板 的面向该天线罩的外表面， 或该吸波材料层贴覆于该天线罩面向该底 板的内表面。
如权利要求 7所述的天线， 其特征在于， 该吸波材料层结合于一金属 层， 该金属层设置于该天线罩面向该第一侧板和该第二侧板的内表面
[权利要求 9] 如权利要求 8所述的天线， 其特征在于， 该金属层还设置于该天线罩 面向该底板的内表面。
[权利要求 10] 如权利要求 1所述的天线， 其特征在于， 该天线振子的数量为多个并 形成振子阵列， 该吸波材料层覆盖反射板上对应振子阵列的区域的外 表面， 且该吸波材料层的布置是以振子阵列为中心。
[权利要求 11] 如权利要求 1所述的天线， 其特征在于， 该吸波材料层包括磁性电磁 吸波材料层以及与磁性电磁吸波材料层相结合的导电几何结构层； 该 导电几何结构层由依次排布的多个导电几何结构单元组成， 每个导电 几何结构单元包括非封闭的环状导电几何结构， 该环状导电几何结构 的幵口处设置有相对平行的两个条形结构。
[权利要求 12] 如权利要求 11所述的天线， 其特征在于， 该环状导电几何结构设置有 一个以上的该幵口。
[权利要求 13] 如权利要求 11所述的天线， 其特征在于， 该环状导电几何结构呈圆形
、 椭圆形、 三角形或多边形。
[权利要求 14] 如权利要求 11所述的天线， 其特征在于， 该吸波材料层的介电常数为
5-30， 磁导率为 1-7。
[权利要求 15] 如权利要求 11所述的天线， 其特征在于， 该导电几何结构单元呈周期 阵列排布。
[权利要求 16] 如权利要求 11所述的天线， 其特征在于， 该磁性电磁吸波材料层的表 面上设置有金属层。
[权利要求 17] 如权利要求 16所述的天线， 其特征在于， 该磁性电磁吸波材料层是吸 波贴片材料。
[权利要求 18] 如权利要求 11所述的天线， 其特征在于， 该导电几何结构单元附着于 该磁性电磁吸波材料层或者嵌入在该磁性电磁吸波材料层中。
[权利要求 19] 如权利要求 11所述的天线， 其特征在于， 该磁性电磁吸波材料层包括 基体以及结合于该基体的吸收剂。
[权利要求 20] 如权利要求 11所述的天线， 其特征在于， 该导电几何结构单元是具有 外接圆的形状， 该外接圆的直径为工作频段自由空间电磁波长的 1/20
-1/5。 [权利要求 21] 如权利要求 11所述的天线， 其特征在于， 该吸波材料层的工作频率在
0.8-2.7GHZ频率段内， 该导电几何结构单元的厚度大于对应该工作频 率段的该导电几何结构单元的趋肤深度。
[权利要求 22] 如权利要求 16所述的天线， 其特征在于， 该吸波材料层的工作频率在
0.8-2.7GHZ频率段内， 该金属层的厚度大于对应所述工作频率段的所 述金属层的趋肤深度。
[权利要求 23] 如权利要求 11所述的天线， 其特征在于， 该环状导电几何结构及条形 结构的线宽均为 W， 0.1mm≤W≤lmm。
[权利要求 24] 如权利要求 11所述的天线， 其特征在于， 该环状导电几何结构及条形 结构的厚度均为 H， 0.005mm≤H≤0.05mm。
PCT/CN2017/076109 2016-03-16 2017-03-09 一种天线 WO2017157218A1 (zh)

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