WO2017078957A1 - Procédé et appareil pour une détermination de canal pour des systèmes de duplexage à répartition dans le temps avec des antennes couplées - Google Patents

Procédé et appareil pour une détermination de canal pour des systèmes de duplexage à répartition dans le temps avec des antennes couplées Download PDF

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Publication number
WO2017078957A1
WO2017078957A1 PCT/US2016/058488 US2016058488W WO2017078957A1 WO 2017078957 A1 WO2017078957 A1 WO 2017078957A1 US 2016058488 W US2016058488 W US 2016058488W WO 2017078957 A1 WO2017078957 A1 WO 2017078957A1
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Prior art keywords
enb
transmitting device
matrix
channel
receive
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PCT/US2016/058488
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English (en)
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WO2017078957A8 (fr
Inventor
Frank COLIN
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Motorola Mobility Llc
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Priority claimed from US14/933,459 external-priority patent/US10148327B2/en
Application filed by Motorola Mobility Llc filed Critical Motorola Mobility Llc
Priority to CN201680064621.3A priority Critical patent/CN108352872B/zh
Priority to EP16788400.6A priority patent/EP3342060B1/fr
Publication of WO2017078957A1 publication Critical patent/WO2017078957A1/fr
Publication of WO2017078957A8 publication Critical patent/WO2017078957A8/fr

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/10—Monitoring; Testing of transmitters
    • H04B17/11—Monitoring; Testing of transmitters for calibration
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/10—Monitoring; Testing of transmitters
    • H04B17/11—Monitoring; Testing of transmitters for calibration
    • H04B17/14—Monitoring; Testing of transmitters for calibration of the whole transmission and reception path, e.g. self-test loop-back
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems

Definitions

  • the present disclosure is directed to a method and apparatus for channel determination for time division duplex systems with coupled antennas.
  • Time Division Duplex (TDD) systems have an advantage over Frequency Division Duplex (FDD) systems in that adaptive transmit beamforming can be implemented without feedback from the receiver by exploiting channel reciprocity.
  • UE User Equipment
  • FDD Frequency Division Duplex
  • eNB enhanced NodeB
  • the matrix H eNB ⁇ UE has dimension x N
  • H UE ⁇ eNB has dimension NxM.
  • FIG. 1 is an example block diagram of a system according to a possible embodiment
  • FIG. 2 is an example illustration of a two-port model for a two-element array according to a possible embodiment
  • FIG. 3 is an example illustration of a Thevenin source model according to a possible embodiment
  • FIG. 4 is an example illustration of a Norton source model according to a possible embodiment
  • FIG. 5 is an example illustration of a circuit model for a single receive antenna according to a possible embodiment
  • FIG. 6 is an example illustration of a circuit model for a two-element receive array according to a possible embodiment
  • FIG. 7 is an example flowchart illustrating the operation of a receiving device according to a possible embodiment.
  • FIG. 8 is an example block diagram of an apparatus according to a possible embodiment. DETAILED DESCRIPTION
  • Embodiments provide a method and apparatus for channel determination for time division duplex systems with coupled antennas.
  • a signal can be received at a receiving device.
  • the signal can be based on a first product of an inverse of a transmit coupling matrix of a transmitting device and a receive coupling matrix of the transmitting device.
  • a second product of a transmit coupling matrix of the receiving device and an inverse of a receive coupling matrix of the receiving device can be calculated.
  • a receive channel from the transmitting device to the receiving device using reference symbols transmitted by the transmitting device can be measured at the receiving device.
  • a reverse channel can be determined based on the signal and based on a third product of the second product and the transpose of the measurement of the receive channel.
  • a precoded signal based on the reverse channel can be transmitted.
  • FIG. 1 is an example block diagram of a system 100 according to a possible embodiment.
  • the system 100 can include a receiving device 1 10 and a transmitting device 120.
  • the receiving device 110 can be a User Equipment (UE), a base station, an access point, or any other device that can transmit wireless signals.
  • the transmitting device 120 can be a UE, a base station, an access point, or any other device that can receive wireless signals.
  • UE User Equipment
  • a UE can be a wireless terminal, a portable wireless communication device, a smartphone, a cellular telephone, a flip phone, a personal digital assistant, a device having a subscriber identity module, a personal computer, a selective call receiver, a tablet computer, a laptop computer, or any other device that is capable of sending and receiving wireless communication signals.
  • the receiving device 110 can include a controller 112, a transceiver 1 14, and an antenna array 116, such as a plurality of antennas, as well as other operational elements.
  • the controller 112 can be one element or can be distributed between different elements.
  • the controller 1 12 can be part of a processor, can be part of a transceiver, can be part of a precoder, can be part of other elements in a transmitting device, and/or can be distributed between combinations of elements in a transmitting device and/or over cloud computing.
  • the transmitting device 120 can include a transceiver 122 and an antenna array 124, as well as other operational elements.
  • the transceivers 114 and 122 can each include a transmitter, a receiver, and/or more than one transceiver including transmitters and receivers.
  • the transceiver 114 can receive a signal based on a first product of an inverse transpose of a transmit coupling matrix of the transmitting device 120 and a transpose of a receive coupling matrix of the transmitting device 120.
  • the controller 112 can calculate a second product of a transmit coupling matrix of the receiving device 110 and an inverse of a receive coupling matrix of the receiving device 110.
  • the controller 112 can measure a receive channel from the transmitting device 120 to the receiving device 1 10 using reference symbols transmitted by the transmitting device 120.
  • the controller 112 can determine a reverse channel based on the signal and based on a third product of the second product and the measurement of the receive channel.
  • the controller 112 can receive a signal 118 for transmission and the transceiver 114 can transmit a precoded signal based on the reverse channel and based on the signal 1 18.
  • D Tx UE denote a diagonal matrix of dimension N x N with diagonal elements equal to the gain and phase of the signal path from each UE baseband transmitter to its corresponding antenna
  • D Rx UE denote a diagonal matrix of dimension N x N with diagonal elements equal to the gain and phase of the signal path from each UE receive antenna element to the UE baseband receiver.
  • the matrices D Tx eNB and D Rx eNB are similarly defined for the transmitting device 122, such as an eNB, and have dimension M x M.
  • the channel measured by the UE can have a dimension M x N and can be given by
  • the eNB In order for reciprocity to be maintained at the eNB, the eNB should be calibrated so that
  • the impairments from the antenna to the baseband receiver can be the same as from the baseband transmitter to the antenna.
  • the UE should be calibrated so that
  • a slightly more relaxed calibration condition allows for a common phase offset between the transmitter and receiver so that D Tx_eNB ⁇ Rx_eNB
  • a first calibration method can use active calibration internal to the device. Generally, this can be implemented in two steps. In the first step, the signal received at each antenna element from its transceiver can be coupled (with a known coupling coefficient) into a single common return path (with known gain and phase) to a receiver which can then determine the gain and phase of each transmit signal path. These gains and phases can be compensated in the baseband transmitter. In the second step, the signal from a single common transmitter (with known gain and phase) can be coupled (with a known coupling coefficient) into the signal path from each array element down to its corresponding transceiver. Given the common signal source, the gain and phase of the signal paths from the antenna elements down to the transceivers can be measured and compensated when measuring the channel.
  • a second calibration method can use active calibration using receiver feedback. This method can require that the device providing the feedback be calibrated, but in a slightly more restrictive sense than that given above. If the eNB is providing feedback to the UE, a requirement can be that
  • the number of antenna elements at the eNB can be greater than or equal to the number of antennas at the UE.
  • the calibration process can begin when the uncalibrated UE sends a full rank reference symbol transmission to the eNB.
  • the eNB can measure the channel given by
  • the calibrated eNB signals the matrix F 2 to the UE.
  • the eNB next sends a full rank reference symbol transmission to the UE. Assuming that channel reciprocity holds, the UE measures the channel
  • the UE then performs the following computation
  • the number of eNB antennas, M should be greater than or equal to the number of UE antennas, N, in order for the matrices Y 1 T Y 1 and H UE ⁇ em H l T
  • the UE ⁇ eNB to have full rank, and so be invertible.
  • the UE can perform the
  • the vector input to the UE antenna elements can be given by
  • the transmitter baseband vector input can be multiplied by Z 2 with the result that
  • the UE can be calibrated in the sense that its transmit and receive impairments are equal.
  • a reverse channel can be determined in several ways. The requirement which should be satisfied can be that
  • the eNB and the UE can self- calibrate so that
  • transmit calibration can be implemented at baseband by multiplying the transmit baseband vector input by Z3 ⁇ 4 eNB
  • receive calibration can be implemented by multiplying the received baseband signal by eNB .
  • this approach reduces the capacity of the channel from the UE to the eNB since multiplication of the receive signal by D j ⁇ eNB will cause the receiver noise power to be unequal across the M receive paths
  • the eNB can implement both transmit and receive calibration by multiplying the transmit baseband vector input by eNB D ⁇ x l eNB so that the transmit impairment becomes D Rx eNB .
  • the transmit power per antenna will vary even if the power of the baseband inputs is equal.
  • the eNB precoder can take this variation into account when choosing the precoder to optimize capacity.
  • the eNB can multiply the transmit baseband vector input by eNB D ⁇ x l eNB only when reference symbols are transmitted, and otherwise leave the baseband input unchanged.
  • the eNB signals this measurement to the UE.
  • the eNB sends full rank reference symbols to UE from which the UE measures
  • Y 1 -D Tx _ eNB H eNB ⁇ UE- ⁇ Rx JE
  • the UE uses the measurements Y 1 and Y 2 to compute D Tx ⁇ , as indicated above.
  • the UE then multiplies the output of the baseband transmitter by D Tx m D ⁇ m with the result that the input to the UE array is given by
  • the eNB can measure both D Tx eNB and D Rx eNB .
  • the UE can measure both D Tx UE and D Rx UE .
  • the eNB transmits full rank reference symbols to the UE which allows the UE to measure the channel
  • the UE then computes the channel from the eNB to the UE as
  • ⁇ T n which is the channel from the UE to the eNB.
  • the UE signals to the eNB.
  • the UE transmits full rank reference symbols to the eNB which allows the eNB to measure the channel
  • the eNB then computes the channel from the eNB to the UE as
  • equalizing the transmit and receive impairments may have the effect of degrading both links by application of equalizing attenuations.
  • a full-rank N x M matrix should be signaled from the eNB to the UE, which requires signaling M ⁇ N coefficients.
  • the two matrices which should be signaled are diagonal, so the matrix signaled from the eNB to the UE has M
  • the channel between the eNB and the UE can be a function of both the circuits used to drive the transmit array and the impedances used to load the receive array.
  • the condition that the signal paths to and from the arrays are gain and phase matched so that and D T or even the stronger condition that
  • Rx UE I M xM is not sufficient to ensure that a channel measurement taken at the UE of the of the channel from the eNB to the UE is equal to the transpose of the channel measurement taken at the eNB of UE to the eNB.
  • the channel observed between the z ' -th element of the eNB array and the j ' -th element of the UE array can depend on all of the following: (i) the propagation channel between the z ' -th element of the eNB array and the j ' -th element of the UE antenna array; (ii) the antenna pattern of z ' -th element of the eNB array; and (iii) the antenna pattern of the j ' -th element of the UE array.
  • H e NB ⁇ UE H e NB ⁇ UE; i,j to denote the channel from the z ' -th eNB antenna to the j ' -th UE antenna, with the restriction that this is the channel observed at the UE when all antennas other than the z ' -th eNB antenna are open circuit and the elements of the UE antenna array are open circuit.
  • the channel is measured by transmitting a known reference symbol from the z ' -th eNB antenna and measuring the reference symbol at the j ' -th antenna of the UE array.
  • the channel is only a function of (i), (ii), and (iii) above. That is, H eNB ⁇ UE . , is only a function of the propagation channel between the z ' -th element of the eNB and the j ' -th element of the UE, and of the antenna patterns of these two antenna elements.
  • FIG. 2 is an example illustration of a two-port model 200 for a two-element array according to a possible embodiment.
  • the two ports can correspond to two antennas in an antenna array.
  • An -port circuit can be used to model the vector voltage-current relationship for the -ports of the -element antenna array, which can be given by
  • V Z I , where Z can be the Mx M impedance matrix for the array.
  • Z can be the Mx M impedance matrix for the array.
  • v 1 denote the current and voltage for the first antenna
  • i 2 and v 2 denote the current and voltage for the second antenna.
  • FIG. 3 is an example illustration of a Thevenin source model 300 according to a possible embodiment.
  • FIG. 4 is an example illustration of a Norton source model 400 according to a possible embodiment.
  • the two linear source models 300 and 400 can be considered for driving an antenna array.
  • Thevenin source model 300 can include ideal voltage sources v s in combination with series impedances Z s Thev, while the Norton source model 400 can include an ideal current source z s in combination with a parallel shunt impedance Z s Nor-
  • the degree of coupling will depend on the circuits used to drive the array. For example, the coupling of the transmitted symbol into adjacent elements will depend both on the mutual coupling of the antenna elements and on the source impedance associated with the Norton or Thevenin source used to drive each element of the array. Similarly, for a symbol arriving at the j-th element of the receive array, the degree to which the symbol couples into the other elements of the receive array is a function of both the mutual coupling of the antenna elements and of the impedances used to load the receive antenna array elements.
  • the signal observed at the j-th element of the UE array also depends on the source model used.
  • An interesting question to consider is whether or not the channel observed at the j- th element of the UE array with one source model used to drive the eNB array can be determined from the channel observed with a different source model, and furthermore, whether this transformation can be determined using only the impedance parameters for the array and without knowledge of the antenna element patterns.
  • H eNB ⁇ UE . j the channel from the z ' -th eNB antenna to the j ' -th UE antenna when the elements of the UE antenna array are open circuit and all eNB elements other than the z ' -th element are open circuit. From the definition of H eNB ⁇ UE . , it follows that the antenna pattern
  • the antenna pattern corresponding to the precoder v k is given by
  • the channel observed at the UE antenna array for a given precoder depends on both: (i) whether the precoder is implemented as a Thevenin source driven by a voltage vector or a Norton source driven by a current vector; and (ii) the source impedance used.
  • the channel vectors observed at the UE antenna array with a Thevenin source model driving the eNB array is the same, within a scalar constant, as the channel vector observed from each element of the eNB array when all other antenna elements of the eNB are open circuit, so that
  • ⁇ eNB ⁇ UE " ⁇ eNB Nor ) " ⁇ eNB Nor ( ⁇ eNB Nor + ⁇ eNB ) (" ⁇ eNB Thev + “ ⁇ eNB ) ⁇ eNB ⁇ UE (" ⁇ eNB Thev ) ' for the Thevenin and Norton source models, respectively.
  • the relationship can be expressed as ⁇ eNB ⁇ UE (" ⁇ eNB Thev ) ( “ ⁇ eNB Thev + ⁇ eNB ) ( “ ⁇ eNB Nor + ⁇ eNB ) " ⁇ eNB Nor ⁇ eNB ⁇ UE ( " ⁇ eNB Nor ) ⁇
  • V S ⁇ eNB_Nor l S > then the vector channel resulting from the Norton source can be expressed as •r ⁇ Nor l 7 ⁇ _ jT( 7 -l 7 - ⁇ ⁇ 1 y- ⁇
  • FIG. 5 is an example illustration of a circuit model 500 for a single receive antenna according to a possible embodiment.
  • the circuit can be represented as the circuit model 500.
  • v denotes the open-circuit voltage induced on the UE receive antenna by the signal arriving from the z ' -th eNB antenna
  • Z A denotes the self-impedance of the antenna
  • Z L denotes the load impedance. The power delivered to the load impedance is maximized in the case that
  • FIG. 6 is an example illustration of a circuit model 600 for a two-element receive array according to a possible embodiment.
  • the channel vector measured by an array of coupled antennas at the UE when the UE antenna array load impedance is Z UE L we consider the case of a two element array with impedance matrix Z w as shown in the circuit model 600.
  • Z UE L is the diagonal matrix given by
  • ⁇ *eNB ⁇ UE denote the matrix channel from the eNB transmitter to the voltages across the load impedances at the UE when a Norton source is used at the eNB.
  • the channel matrix measured across the load impedances at the UE is given by
  • the channel measurement reflects the antenna patterns of both the transmit and receive antennas. However, what has generally not been considered is the impact of antenna coupling at both the transmitter and the receiver on the channel that is measured at the receiver. [0053] In the case that a Thevenin source is used at both the eNB and the UE, the measurements at the UE and the eNB will be reciprocal if and only if
  • ⁇ UE ⁇ eNB ( ⁇ UE Thev ' ⁇ e B L ) ( ⁇ UE Thev + ⁇ UE ) ( ⁇ eNB ⁇ UE (" ⁇ eNB + " ⁇ eNB L ) eNB L '
  • the UE measures G ⁇ ⁇ UE ( eNB Thev , UE L ) using reference symbols transmitted from the eNB. If the eNB signals the x matrix
  • ⁇ UE ⁇ eNB ( " ⁇ UE Thev ' ⁇ eNB L ) ( " ⁇ UE Thev + ⁇ UE ) ( ⁇ UE + ⁇ UEL ) ⁇ UE L
  • the eNB measures GTM ⁇ eNB (z uE Thev , Z eNB L ) using reference symbols transmitted from the UE. If the UE signals the Nx N matrix to the eNB, then the eNB can compute the channel from the eNB to the UE as
  • the eNB has knowledge of its own impedance matrix Z eNB , transmit source impedance Z eNB Thev , and receive load impedance Z eNB L , and can compute
  • the matrices Z eNB and Z eNB are diagonal. Since the matrices Z eNB Thev and Z UE Thev are diagonal, it follows in this case the matrices needed to compute the reverse channel,
  • ⁇ eNB Thev + " ⁇ eNB ) ⁇ eNB + ⁇ eNB L
  • ⁇ eNB L ⁇ eNB L and are also diagonal, and it is only necessary to signal M values from the eNB to the UE and N values from the UE to the eNB in order for each to compute the reverse channel.
  • the UE In order for the eNB to compute channel from the eNB to the UE from the measurement of the channel from the UE to the eNB, the UE should signal the diagonal Nx N matrix Z UE L to the eNB.
  • the eNB should signal the diagonal Nx N matrix Z eNB L to the UE. Because the matrices Z UE L and Z eNB L are diagonal, it is only necessary to signal N and M values should be signaled to the eNB and UE, respectively, in order for each to compute the reverse channel.
  • the load impedance matrices can be expressed as
  • the scale factor is due to the fact that for the model used here, the radiated power is inversely proportional to the source impedance when the source impedance and the antenna self-impedance are matched.
  • the UE In assessing the quality of the link from the UE to the eNB from measurements of the link from the eNB to the UE, the UE should account for this difference in transmit power between the two links.
  • the UE in order for the eNB to compute the forward channel from the reverse channel measurement, the UE should signal the Nx N matrix ⁇ z ⁇ + L ) to the eNB.
  • the eNb in order for the UE to compute the reverse channel from the forward channel measurement, the eNb should signal the x matrix ( e ⁇ B + e ⁇ B L ) to the UE.
  • the impedance matrices Z eNB and Z w are diagonal (no coupling in the eNB and UE arrays)
  • the matrices [z ⁇ + L ) and ( ⁇ + e ⁇ B L ) are diagonal.
  • the impedance matrices can be expressed as
  • the load impedance matrices can be expressed as
  • the measured channels are reciprocal within a multiplicative constant so long as there is no mutual coupling of the antennas at the eNB array or the UE array.
  • the multiplicative constant is the ratio of the harmonic mean of the load impedance and the antenna self-impedance for the UE to that of the harmonic mean of the load impedance and antenna self-impedance for the eNB.
  • the UE measures G e N ⁇ ⁇ UE (Z eNB noisy ,Z m L ) using reference symbols transmitted from the eNB. If the eNB signals the x matnx
  • the UE can compute the channel from the UE to the eNB as
  • the eNB measures G* r ⁇ eNB ( ⁇ UE Nor ' - ⁇ eNB L ) using reference symbols transmitted from the UE. If the UE signals the Nx N matrix
  • the eNB can compute the channel from the eNB to the UE as
  • the UE in order for the eNB to compute the forward channel from the reverse channel measurement, the UE should signal the Nx N matrix (z uE + Z w L ) T Z ⁇ E L to the eNB.
  • the eNB in order for the UE to compute the reverse channel from the forward channel measurement, the eNB should signal the x matrix (z eNB + Z eNB L ) Z e T mi L to the UE.
  • the impedance matrices Z eNB and Z w are diagonal (no coupling in the eNB and UE arrays)
  • the impedance matrices can be expressed as 1 J NxN
  • the load impedance matrices can be expressed as
  • the measured channels are reciprocal within a multiplicative constant so long as there is no mutual coupling of the antennas at the eNB array or the UE array.
  • UE->eNB UE Thev ' ⁇ eNB and its presumed knowledge of the UE should signal the Nx N matrix to the eNB.
  • ⁇ eNB L (“ ⁇ eNB + ⁇ eNB L ) (" ⁇ eNB Thev + “ ⁇ eNB ) ⁇ eNB ⁇ UE (“ ⁇ eNB Thev ' ⁇ UE L ) ⁇ > so that the UE no longer needs explicit knowledge of the eNB coupling in order to compute the UE to eNB channel since it is no longer necessary to correct the measured channel for the difference between the eNB transmitter and the eNB receiver.
  • the channel from the eNB to the UE can be expressed as
  • ⁇ UE L (“ ⁇ UE + ⁇ UE L ) (" ⁇ UE Thev + ⁇ UE ) ⁇ UE ⁇ eNB (“ ⁇ UE Thev ⁇ eNB L ) ⁇ > so that the eNB no longer needs explicit knowledge of the UE coupling in order to compute the eNB to UE channel since it is no longer necessary to correct the measured channel for the difference between the UE transmitter and the UE receiver.
  • ⁇ UE ⁇ eNB (“ ⁇ UE Nor ' “ ⁇ eNB L ) (" ⁇ UE Nor + “ ⁇ UE ) " ⁇ UE ( ⁇ UE + ⁇ UE L ) ⁇ UE L and
  • ⁇ eNB L " ⁇ eNB + ⁇ eNB L ) " ⁇ eNB (" ⁇ eNB Nor + “ ⁇ eNB ) ⁇ eNB ⁇ UE (" ⁇ eNB Nor ' ⁇ UE L ) ⁇ > so that the UE no longer needs explicit knowledge of the eNB coupling in order to compute the UE to eNB channel since it is no longer necessary to correct the measured channel for the difference between the eNB transmitter and the eNB receiver.
  • the channel from the eNB to the UE can be expressed as ⁇ eNB— >UE ( ⁇ eNB Nor ' ⁇ UE L ) ( ⁇ eNB Nor ⁇ * ⁇ ⁇ eNB ) ⁇ eNB ( ⁇ eNB ⁇ * ⁇ ⁇ eNB L ) ⁇ eNB L
  • Norton source were used at both the eNB and the UE, there are essentially two methods that can be used to enable the UE to learn G ⁇ TM_ ⁇ .
  • the eNB signals the x matrix (A TX ) T (A ⁇ f to the UE.
  • the UE uses the reference symbols transmitted by the eNB to measure (3 ⁇ 4 ⁇ UE M & tnen computes G ⁇ NB as
  • the vector input to the eNB array is multiplied by A ⁇ i ( A TX ) 1 when reference symbols are transmitted.
  • the UE measures the channel
  • the UE signals the N x N matrix (B TX ) ⁇ T (B ⁇ f to the eNB.
  • the eNB uses the reference symbols transmitted by the UE to measure G UE - ⁇ NB m & then computes ( 3 ⁇ 4 ⁇ UE AS
  • the vector input to the UE array is multiplied by B m ⁇ ⁇ ) when reference symbols are transmitted.
  • the eNB measures the channel general
  • the eNB can compute the eNB to UE channel as
  • FIG. 7 is an example flowchart 700 illustrating the operation of a receiving device, such as the receiving device 1 10, according to a possible embodiment. At 710, the flowchart 700 can begin.
  • a signal based on a first product of an inverse transpose of a transmit coupling matrix of a transmitting device and a transpose of a receive coupling matrix of the transmitting device can be received at the receiving device.
  • the transmit coupling matrix of the transmitting device can be based on a source impedance matrix of a transmitter at the transmitting device and an impedance matrix of an array of antennas at the transmitting device.
  • the receive coupling matrix of the transmitting device can be based on a load impedance of a receiver at the transmitting device and an impedance matrix of an array of antennas at the transmitting device.
  • the first product of a transpose inverse of a transmit coupling matrix of the transmitting device and a transpose receive coupling matrix of the transmitting device can be based on:
  • a UE as the transmitting device, but can also apply to an eNB or other transmitting device.
  • the signal based on the first product can include data comprising the first product of the inverse transpose of the transmit coupling matrix of the transmitting device and a transpose of the receive coupling matrix of the transmitting device.
  • the transmitting device can send the first product as data.
  • the signal based on the first product can include reference symbols multiplied by a transpose of the first product of the transpose inverse of the transmit coupling matrix of the transmitting device and the transpose of the receive coupling matrix of the transmitting device.
  • a second product of a transmit coupling matrix of the receiving device and an inverse of a receive coupling matrix of the receiving device can be calculated.
  • the transmit coupling matrix of the receiving device can be based on a source impedance matrix of a transmitter at the receiving device and an impedance matrix of an array of antennas at the receiving device.
  • the receive coupling matrix of the receiving device can be based on a load impedance of a receiver at the receiving device and an impedance matrix of an array of antennas at the receiving device.
  • a receive channel from the transmitting device to the receiving device using reference symbols transmitted by the transmitting device can be measured.
  • a reverse channel can be determined based on the signal and based on a third product of the second product and the measurement of the receive channel.
  • the reverse channel can be determined based on a third product of the second product, the measurement of the receive channel, and the first product of the transpose inverse of the transmit coupling matrix of the transmitting device and the transpose of the receive coupling matrix of the transmitting device.
  • the transpose inverse of the first product of the transmit coupling matrix of the transmitting device and the transpose of the receive coupling matrix of the transmitting device can be determined at the transmitting device and sent as data to save bandwidth by not requiring data for both matrices.
  • the both matrices can be sent as data and the first product of the transpose inverse of the transmit coupling matrix of the transmitting device and the transpose of the receive coupling matrix of the transmitting device can be determined at the receiving device.
  • a precoding matrix can be generated based on the reverse channel.
  • a signal can be received for transmission.
  • the signal can be received from other elements in the receiving device.
  • the precoding matrix can be applied to the signal to generate a precoded signal for transmission over a physical channel.
  • the precoded signal based on the reverse channel can be transmitted.
  • the flowchart 700 can end.
  • FIG. 8 is an example block diagram of an apparatus 800, such as the device 110 or the device 120, according to a possible embodiment.
  • the apparatus 800 can include a housing 810, a controller 820 within the housing 810, audio input and output circuitry 830 coupled to the controller 820, a display 840 coupled to the controller 820, a transceiver 850 coupled to the controller 820, a plurality of antennas 855 and 857, such as an array of antennas, coupled to the transceiver 850, a user interface 860 coupled to the controller 820, a memory 870 coupled to the controller 820, and a network interface 880 coupled to the controller 820.
  • the apparatus 800 can also include additional elements or less elements depending on the device in which it is implemented.
  • the apparatus 800 can perform the methods described in all the embodiments.
  • the display 840 can be a viewfinder, a liquid crystal display (LCD), a light emitting diode (LED) display, a plasma display, a projection display, a touch screen, or any other device that displays information.
  • the transceiver 850 can include a transmitter and/or a receiver.
  • the transceiver 850 can also include a plurality of transceivers with each transceiver coupled a corresponding antenna of the plurality of antennas 855 and 857.
  • the audio input and output circuitry 830 can include a microphone, a speaker, a transducer, or any other audio input and output circuitry.
  • the user interface 860 can include a keypad, a keyboard, buttons, a touch pad, a joystick, a touch screen display, another additional display, or any other device useful for providing an interface between a user and an electronic device.
  • the network interface 880 can be a Universal Serial Bus (USB) port, an Ethernet port, an infrared transmitter/receiver, an IEEE 1398 port, a WLAN transceiver, or any other interface that can connect an apparatus to a network, device, or computer and that can transmit and receive data communication signals.
  • the memory 870 can include a random access memory, a read only memory, an optical memory, a flash memory, a removable memory, a hard drive, a cache, or any other memory that can be coupled to a wireless communication device.
  • the plurality of antennas 855 and 857 can be considered a transmitter array of antennas when the transceiver 850 is transmitting signals.
  • the transmitter array of antennas 855 and 857 can include two or more antennas.
  • the transmitter array of antennas 855 and 857 can be mutually coupled in that one of a voltage and current applied to one antenna element induces a voltage or current on another antenna element in the transmitter array of antennas 855 and 857.
  • the apparatus 800 or the controller 820 may implement any operating system, such as Microsoft Windows®, UNIX®, or LINUX®, AndroidTM, or any other operating system.
  • Apparatus operation software may be written in any programming language, such as C, C++, Java or Visual Basic, for example. Apparatus software may also run on an application framework, such as, for example, a Java® framework, a .NET®
  • the software and/or the operating system may be stored in the memory 870 or elsewhere on the apparatus 800.
  • the apparatus 800 or the controller 820 may also use hardware to implement disclosed operations.
  • the controller 820 may be any programmable processor.
  • Disclosed embodiments may also be implemented on a general-purpose or a special purpose computer, a programmed microprocessor or microprocessor, peripheral integrated circuit elements, an application- specific integrated circuit or other integrated circuits, hardware/electronic logic circuits, such as a discrete element circuit, a
  • controller 820 may be any controller or processor device or devices capable of operating a communication device and implementing the disclosed embodiments.
  • the transceiver 850 can receive a signal based on a first product of an inverse transpose of a transmit coupling matrix of a transmitting device and a transpose of a receive coupling matrix of the transmitting device.
  • the transmit coupling matrix of the transmitting device can be based on a source impedance matrix of a transmitter at the transmitting device and an impedance matrix of an array of antennas at the transmitting device.
  • the receive coupling matrix of the transmitting device can be based on a load impedance of a receiver at the transmitting device and an impedance matrix of an array of antennas at the transmitting device.
  • the signal can include data comprising the first product of the inverse transpose of the transmit coupling matrix of the transmitting device and a transpose of the receive coupling matrix of the transmitting device.
  • the controller 820 can determine the determined receive channel based on a third product of the second product, the measurement of the receive channel, and the first product of the transpose inverse of the transmit coupling matrix of the transmitting device and the transpose of the receive coupling matrix of the transmitting device.
  • the signal can also include reference symbols multiplied by a transpose of the first product of the transpose inverse of the transmit coupling matrix of the transmitting device and the transpose of the receive coupling matrix of the transmitting device.
  • the controller 820 can calculate a second product of a transmit coupling matrix of the apparatus 800 and an inverse of a receive coupling matrix of the apparatus 800.
  • the transmit coupling matrix of the apparatus 800 and the receive coupling matrix of the apparatus 800 can be based on the plurality of antennas 855 and 857.
  • the transmit coupling matrix of the apparatus 800 can be based on a source impedance matrix of a transmitter at the apparatus and an impedance matrix of the plurality of antennas at the apparatus.
  • the receive coupling matrix of the apparatus 800 can be based on a load impedance of a receiver at the apparatus and an impedance matrix of the plurality of antennas at the apparatus.
  • the controller 820 can measure a receive channel from the transmitting device to the apparatus using reference symbols transmitted by the transmitting device.
  • the controller 820 can determine a reverse channel based on the signal and based on a third product of the second product and the measurement of the receive channel.
  • the controller 820 can generate a precoding matrix based on the reverse channel, can receive a signal for transmission, and can apply the precoding matrix to the signal to generate a precoded signal for transmission over a physical channel.
  • the transceiver 850 can transmit the precoded signal based on the reverse channel.
  • the controller 820 can calculate a first product of an inverse of a transmit coupling matrix of the apparatus 800 and a receive coupling matrix of the apparatus 800.
  • the first product of the inverse of transmit coupling matrix of the apparatus 800 and the receive coupling matrix of the apparatus 800 can be determined as described in the above embodiments.
  • the signal can be based on the first product can include data comprising the first product of the inverse of the transmit coupling matrix of the apparatus 800 and the receive coupling matrix of the apparatus 800.
  • the signal based on the first product can also comprise reference symbols multiplied by a first product of the inverse of the transmit coupling matrix of the apparatus 800 and the receive coupling matrix of the apparatus 800.
  • the transceiver 850 can then transmit the signal based on the first product of an inverse of the transmit coupling matrix of the apparatus 800 and the receive coupling matrix of the apparatus 800 to a receiving device.
  • the method of this disclosure can be implemented on a programmed processor.
  • the controllers, flowcharts, and modules may also be implemented on a general purpose or special purpose computer, a programmed microprocessor or microcontroller and peripheral integrated circuit elements, an integrated circuit, a hardware electronic or logic circuit such as a discrete element circuit, a programmable logic device, or the like.
  • any device on which resides a finite state machine capable of implementing the flowcharts shown in the figures may be used to implement the processor functions of this disclosure.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Radio Transmission System (AREA)

Abstract

L'invention concerne un procédé et un appareil pour une détermination de canal pour des systèmes de duplexage à répartition dans le temps avec des antennes couplées. Un signal peut être reçu au niveau d'un dispositif de réception (715). Le signal peut être basé sur un premier produit d'un inverse d'une matrice de couplage d'émission d'un dispositif d'émission et d'une matrice de couplage de réception du dispositif d'émission. Un second produit d'une matrice de couplage d'émission du dispositif de réception et d'un inverse d'une matrice de couplage de réception du dispositif de réception peut être calculé (720). Un canal de réception allant du dispositif d'émission au dispositif de réception en utilisant des symboles de référence transmis par le dispositif d'émission peut être mesuré au niveau du dispositif de réception (725). Un canal inverse peut être déterminé sur la base du signal et sur la base d'un troisième produit du second produit et de la transposition de la mesure du canal de réception (730). Un canal précodé basé sur le canal inverse peut être émis (750).
PCT/US2016/058488 2015-08-25 2016-10-24 Procédé et appareil pour une détermination de canal pour des systèmes de duplexage à répartition dans le temps avec des antennes couplées WO2017078957A1 (fr)

Priority Applications (2)

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CN201680064621.3A CN108352872B (zh) 2015-08-25 2016-10-24 具有耦合天线的时分双工系统的信道确定的方法和装置
EP16788400.6A EP3342060B1 (fr) 2015-08-25 2016-10-24 Procédé et appareil pour une détermination de canal pour des systèmes de duplexage à répartition dans le temps avec des antennes couplées

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US14/933,459 US10148327B2 (en) 2015-08-25 2015-11-05 Method and apparatus for channel determination for time division duplex systems with coupled antennas
US14/933,459 2015-11-05

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Cited By (1)

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Publication number Priority date Publication date Assignee Title
US20170134077A1 (en) * 2015-08-25 2017-05-11 Motorola Mobility Llc Method and apparatus for channel determination for time division duplex systems with coupled antennas

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Publication number Priority date Publication date Assignee Title
EP2448137A1 (fr) * 2009-06-23 2012-05-02 Alcatel Lucent Procédé et dispositif d'émission de signaux dans un système mimo à duplexage par répartition temporelle
CN103249080A (zh) * 2012-02-03 2013-08-14 中国移动通信集团公司 一种确定基站的天线校准系数的方法、系统以及装置

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP2448137A1 (fr) * 2009-06-23 2012-05-02 Alcatel Lucent Procédé et dispositif d'émission de signaux dans un système mimo à duplexage par répartition temporelle
CN103249080A (zh) * 2012-02-03 2013-08-14 中国移动通信集团公司 一种确定基站的天线校准系数的方法、系统以及装置

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20170134077A1 (en) * 2015-08-25 2017-05-11 Motorola Mobility Llc Method and apparatus for channel determination for time division duplex systems with coupled antennas
US10148327B2 (en) * 2015-08-25 2018-12-04 Motorola Mobility Llc Method and apparatus for channel determination for time division duplex systems with coupled antennas

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