WO2017000541A1 - 一种本振相位噪声检测方法、装置及射频拉远单元 - Google Patents

一种本振相位噪声检测方法、装置及射频拉远单元 Download PDF

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WO2017000541A1
WO2017000541A1 PCT/CN2016/070434 CN2016070434W WO2017000541A1 WO 2017000541 A1 WO2017000541 A1 WO 2017000541A1 CN 2016070434 W CN2016070434 W CN 2016070434W WO 2017000541 A1 WO2017000541 A1 WO 2017000541A1
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signal
frequency
phase noise
frequency point
intermediate frequency
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PCT/CN2016/070434
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English (en)
French (fr)
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李雪林
陈豪
吴丽红
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中兴通讯股份有限公司
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Publication of WO2017000541A1 publication Critical patent/WO2017000541A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/10—Monitoring; Testing of transmitters
    • H04B17/15—Performance testing

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  • the present invention relates to the field of communications technologies, and in particular, to a local oscillator phase noise detecting method, apparatus, and radio remote unit.
  • the phase noise performance of the local oscillator directly affects the performance of the RF remote unit transmission and reception.
  • the phase noise performance of the RF remote unit is usually tested with a phase noise meter.
  • the cost is too high.
  • the RF remote unit test tooling there is no local oscillator phase noise performance test. How to realize the performance of detecting the phase noise of the local oscillator in a large-volume radio remote unit has become an urgent problem to be solved.
  • the present invention aims to provide a local oscillator phase noise detecting method, device and radio remote unit, which solves the problem of high phase noise cost of the radio frequency remote unit tested by the phase noise meter in the prior art.
  • the present invention is mainly implemented by the following technical solutions:
  • One aspect of the present invention provides a local oscillator phase noise detecting method, the method comprising:
  • the offset from the RF center frequency f RF signal with a predetermined distance ⁇ f measured local oscillator signal f LO mixes, respectively, to give the intermediate frequency f IF center frequency offset from said intermediate frequency signal and the center frequency f IF predetermined distance ⁇ f signal of;
  • the digital signal is processed to obtain a phase noise value that deviates from the corresponding frequency point ⁇ f of the local frequency point f LO .
  • the signal is a tone signal, a two tone signal or a narrowband signal.
  • the method further includes:
  • the signal of the intermediate frequency center frequency point f IF obtained after the mixing and the signal deviated from the intermediate frequency center frequency point f IF by the predetermined distance ⁇ f are amplified and the aliasing frequency component processing is suppressed.
  • the step of processing the digital signal to obtain a phase noise value that is offset from a corresponding frequency point ⁇ f of the local frequency point f LO includes:
  • the digital signal is separately frequency-shifted to zero frequency, and filtered, and the phase noise value deviating from the corresponding frequency point ⁇ f of the local frequency point f LO is obtained according to the filtered digital signal.
  • the step of separately shifting the digital signal to zero frequency, filtering, and obtaining a phase noise value from the corresponding frequency point ⁇ f of the local frequency point f LO according to the filtered digital signal includes:
  • the digital signals are respectively frequency-shifted to zero frequency, and filtered, and the power of each digital signal after filtering is calculated, and the power is subtracted to obtain a phase noise value that deviates from the corresponding frequency point ⁇ f of the local frequency point f LO .
  • Another aspect of the present invention also provides a local oscillator phase noise detecting apparatus, the apparatus comprising:
  • a mixer configured to mix a signal deviating from the RF center frequency point f RF preset distance ⁇ f with the local oscillator signal f LO to obtain a signal of the intermediate frequency center frequency point f IF and deviating from the intermediate frequency center frequency point ⁇ f from f IF signals of the preset;
  • the analog-to-digital converter ADC is configured to convert a signal of the intermediate frequency center frequency point f IF mixed by the mixer and a signal deviating from the intermediate frequency center frequency point f IF by a preset distance ⁇ f to obtain a corresponding digital signal;
  • the field programmable gate array FPGA is configured to process the digital signal converted by the analog-to-digital converter ADC to obtain a phase noise value deviating from the corresponding frequency point ⁇ f of the local frequency point f LO .
  • the apparatus further comprises an intermediate frequency amplifier and an intermediate frequency anti-aliasing filter;
  • the intermediate frequency amplifier is configured to amplify a signal of an intermediate frequency center frequency point f IF obtained by mixing the mixer and a signal deviating from the intermediate frequency center frequency point f IF by a preset distance ⁇ f;
  • the intermediate frequency anti-aliasing filter is configured to perform an anti-aliasing frequency component processing on the signal amplified by the intermediate frequency amplifier.
  • the field programmable gate array FPGA is specifically configured to separately frequency-shift the digital signal to a zero frequency, and perform filtering, and obtain a corresponding frequency point ⁇ f from the local frequency point f LO according to the filtered digital signal.
  • the phase noise value of the position is specifically configured to separately frequency-shift the digital signal to a zero frequency, and perform filtering, and obtain a corresponding frequency point ⁇ f from the local frequency point f LO according to the filtered digital signal.
  • the phase noise value of the position is specifically configured to separately frequency-shift the digital signal to a zero frequency, and perform filtering, and obtain a corresponding frequency point ⁇ f from the local frequency point f LO according to the filtered digital signal.
  • the field programmable gate array FPGA is specifically configured to separately frequency-shift the digital signal to zero frequency, perform filtering, calculate power of each digital signal after filtering, and subtract power to obtain a deviation from the local frequency.
  • the point f LO corresponds to the phase noise value of the frequency point ⁇ f.
  • Another aspect of the present invention provides a radio remote unit including any one of the above-described local oscillator phase noise detecting devices.
  • the invention tests the phase noise value deviating from the local oscillator ⁇ f position by adding a signal at a position deviating from the main signal ⁇ f, and realizes the phase noise performance of the local oscillator by using a common signal source and borrowing the receiving channel of the radio remote unit itself. Detecting, extremely full It is sufficient to test the local oscillator performance of the tooling during mass production.
  • the local oscillator phase noise detecting method provided by the invention is easy to implement, low in cost, convenient for popularization, and effectively solves the problem of high phase noise cost of the radio frequency remote unit tested by the phase noise meter in the prior art.
  • FIG. 1 is a schematic flow chart of a local phase noise detection method according to an embodiment of the present invention
  • FIG. 2 is a schematic structural diagram of a local oscillator phase noise detecting apparatus according to an embodiment of the present invention
  • FIG. 3 is a schematic flow chart of another local oscillator phase noise detecting method according to an embodiment of the present invention.
  • FIG. 4 is a schematic flowchart of a first frequency shifting according to an embodiment of the present invention.
  • FIG. 5 is a schematic flowchart of a second frequency shifting according to an embodiment of the present invention.
  • the main object of the embodiments of the present invention is to provide a local oscillator phase noise detecting method, device, and radio remote unit, which can detect the phase noise value deviating from the local oscillator ⁇ f by adding a signal at a position offset from the main signal ⁇ f, and using the radio frequency remote
  • the unit's own receiving channel requires only one ordinary signal source to realize the initial detection function of the local oscillator phase noise, eliminating the expensive phase noise meter cost.
  • Embodiments of the present invention provide a local oscillator phase noise detecting method. Referring to FIGS. 1 and 2, the method includes:
  • the offset from the RF center frequency f RF signal with a predetermined distance ⁇ f measured local oscillator signal f LO mixes, respectively, to give the intermediate frequency f IF center frequency offset from said intermediate frequency signal and the center frequency f IF preset Signal of distance ⁇ f;
  • Examples of the present invention is achieved by a signal source to the RF input of the mixer plus an offset from the RF center frequency f RF signal frequency ⁇ f corresponding to the position of the signal source is a common source, as long as the output A larger signal can be used.
  • the signal input in the embodiment of the present invention may be a single tone signal, a two-tone signal or a narrowband signal.
  • the interval of the two-tone signal and the bandwidth of the narrowband signal should be smaller than the subsequent digital number.
  • the mixer Since the power of the signal offset from the corresponding frequency point ⁇ f of the RF center frequency point f RF is sufficiently large, the mixer outputs two signals: one is located at the center frequency of the offset center frequency f IF corresponding frequency point ⁇ f The large signal of the position has a large amplitude, and the second is a small signal located at the frequency center f IF of the intermediate frequency, and the amplitude is small.
  • the signal processed in step 101 is subjected to ADC sampling by an analog-to-digital converter in the radio remote unit, and the mixed signal is converted to obtain a corresponding digital signal.
  • the present invention samples the signal obtained by mixing the position of the corresponding frequency point ⁇ f from the intermediate frequency center frequency point f IF and the signal located at the intermediate frequency center frequency point f IF by the analog-to-digital converter ADC in the radio remote unit. And the sampled signal is quantized and encoded to obtain a corresponding digital signal, and sent to a Field-Programmable Gate Array (FPGA) for processing.
  • FPGA Field-Programmable Gate Array
  • the ADC of the embodiment of the present invention has the highest possible dynamics, so that the accuracy of the phase noise detection is more accurate.
  • the number of bits of the ADC used in the embodiment of the present invention is not less than 11 bits.
  • step S103 the digital signal is separately frequency-shifted to zero frequency and filtered, and the phase noise value deviating from the local frequency point ⁇ f of the local frequency point f LO is obtained according to the filtered digital signal.
  • the present invention separately shifts the digital signal to zero frequency and performs filtering to calculate the power of each digital signal after filtering, and subtracts the power to obtain a position deviating from the local frequency point ⁇ f of the local frequency point f LO . Phase noise value.
  • the present invention separately performs two different frequency shifts on the converted digital signal by using an FPGA, including:
  • the first frequency shift is to shift the large signal deviating from the corresponding frequency point ⁇ f of the intermediate frequency center frequency f IF to zero frequency, and then filtering through the digital low-pass filter to shift the small signal from the corresponding frequency point ⁇ f of the zero frequency. Filter out, leaving only the large signal at zero frequency. Calculate the signal power value in the passband of the filter, and record it as power one;
  • the second frequency shift is to move the previous intermediate frequency center frequency f IF to zero frequency, and then filter it through a digital low-pass filter to filter out the large signal that deviates from the corresponding frequency point ⁇ f of the zero frequency, leaving only the location Small signal with zero frequency.
  • the signal power value in the passband of this filter is calculated and recorded as power two.
  • the digital low-pass filter after frequency shifting is the same filter, and the bandwidth of the filter should be as narrow as possible, for ⁇ f frequency.
  • the suppression of the point position should be as high as possible.
  • the bandwidth of the digital low-pass filter can be flexibly set according to the magnitude of ⁇ f, taking into account the suppression of the position of the ⁇ f frequency point, and the signal power within the bandwidth can be correctly detected. If the phase noise is deviated from 1KHz, the bandwidth BW of the digital low-pass filter can be set to 40Hz. When the phase noise is deviated from 10KHz, the bandwidth BW of the digital low-pass filter can be widened to 200Hz.
  • the invention tests the phase noise value deviating from the position of the local oscillator ⁇ f by adding a signal at a position deviating from the main signal ⁇ f, and using the receiving channel of the radio remote unit itself, only one ordinary signal source is needed, and the phase noise of the local oscillator can be realized.
  • the initial detection function eliminates the cost of expensive phase noise meters.
  • the invention adds a signal to the RF input end of the mixer by a signal source that deviates from the corresponding frequency point ⁇ f of the RF center frequency point f RF , and the signal is mixed with the local oscillator input of the mixer, that is, the local oscillator f LO to be tested.
  • frequency of the IF output of the mixer is amplified, anti-aliasing filter and ADC into a digital signal after sampling, then the frequency shift of the FPGA and the digital filtering, to obtain departing from the present oscillation frequency f LO frequency corresponding to the position of point ⁇ f Phase noise value.
  • the embodiment of the present invention further provides a preferred implementation manner. Specifically, after the step of mixing the signal deviating from the corresponding frequency point ⁇ f of the RF center frequency point f RF with the local oscillator signal f LO to be measured, before the center of said intermediate frequency f IF mixing frequency signals and the center frequency offset from said intermediate frequency f IF ⁇ f predetermined distance signal obtained by converting the digital signal corresponding to the step, further comprising:
  • the signal of the intermediate frequency center frequency point f IF obtained after the mixing and the signal deviated from the intermediate frequency center frequency point f IF by the predetermined distance ⁇ f are amplified and the aliasing frequency component processing is suppressed.
  • the embodiment of the present invention amplifies the signal obtained by the mixing by the intermediate frequency amplifier, and performs the anti-aliasing frequency component processing on the signal amplified by the intermediate frequency amplifier by the intermediate frequency anti-aliasing filter.
  • the present invention amplifies the signal output from the mixer through the intermediate frequency amplifier, wherein the gain of the intermediate frequency amplifier according to the embodiment of the present invention is adjustable, and the offset from the intermediate frequency center frequency f IF corresponding frequency point ⁇ f is ensured.
  • the large signal of the position does not exceed the full-scale power of the ADC after amplification, and ensures that the small signal at the center frequency f IF of the intermediate frequency is amplified and higher than the noise floor of the ADC and the noise floor of the entire RF link.
  • the signal amplified by the intermediate frequency amplifier passes through an intermediate frequency anti-aliasing filter before being input to the ADC for sampling, and the aliasing frequency component is suppressed by the intermediate frequency anti-aliasing filter to avoid interference with useful signals in the band.
  • the two signals output by the IF amplifier are all within the passband of the anti-aliasing filter, so the power attenuation of the signal after processing by the IF anti-aliasing filter is small.
  • the invention realizes the detection of the phase noise value deviating from the position of the local oscillator ⁇ f by adding a signal from the position of the main signal ⁇ f.
  • the method of the invention does not require an expensive phase noise analyzer, and only needs one ordinary
  • the signal source can realize the detection of the local phase noise of the local oscillator, which greatly saves the test cost.
  • the other device in addition to the signal source of the input signal, the other device is a part of the internal part of the radio frequency remote unit, and the receiving channel inside the radio frequency remote unit is the mixed frequency intermediate frequency amplification and anti-aliasing filtering last ADC sampling.
  • Link architecture Therefore, the method of the present invention can directly borrow the radio remote unit without an additional hardware link.
  • the self-receiving channel is simple to implement and is easy to apply in large scale in production test fixtures.
  • FIG. 3 is a schematic flowchart diagram of another local oscillator phase noise detecting method according to an embodiment of the present invention. The method according to the present invention will be described in detail below with reference to FIG. 3 :
  • Step 301 Test a signal deviating from the position of the local oscillator ⁇ f;
  • Step 302 The signal source is set to have an output frequency of 1950.001 MHz, an output power of 0 dBm, and an output mode of a single tone;
  • Step 303 Connect the output of the signal source to the mixer of the internal receiving channel of the radio remote unit, and the RF signal of 1950.001 MHz is mixed with the local oscillator signal of 1810 MHz by the mixer, and the intermediate frequency is large signal of 140.001 MHz, and 140 MHz is obtained.
  • Step 304 The two signals are input together to the intermediate frequency amplifier of the internal receiving channel of the remote radio unit for amplification, and the gain of the intermediate frequency amplifier is adjustable, which ensures that the intermediate frequency of the 140.001 MHz signal does not exceed the full scale of the ADC, and ensures The 140MHz IF small signal is higher than the ADC noise floor and the RF link noise floor;
  • Step 305 The two signals output by the intermediate frequency amplifier pass through the intermediate frequency anti-aliasing filter of the internal receiving channel of the radio remote unit to suppress the aliasing frequency component, so that the correct detection of the power of the two signals in the band is not affected;
  • Step 306 Connect the two signals filtered by the intermediate frequency anti-aliasing filter to the analog-to-digital converter of the internal receiving channel of the radio remote unit.
  • the 140.001MHz IF large signal and the 140MHz IF small signal are converted from the analog signal to the digital signal after being sampled by the ADC;
  • Step 307 The converted digital signal is further input into the FPGA inside the radio remote unit for digital processing, and the frequency shift is first, and becomes a large signal of zero frequency and a small signal of 1 KHz, as shown in FIG. 4;
  • Step 308 The frequency-shifted signal is filtered by the designed digital low-pass filter, and the small signal of 1 KHz is filtered out, leaving only the large signal in the passband.
  • This digital filter is assumed to be a low pass filter with a passband of 40 Hz;
  • Step 309 The FPGA calculates the signal power in the passband as Sout1dBm;
  • Step 310 The second frequency shifting becomes a small signal of zero frequency and a large signal of 1 KHz, as shown in FIG. 5;
  • Step 311 The frequency-shifted signal is filtered out by the designed digital low-pass filter, and the large signal of 1 KHz is filtered out, leaving only the small signal in the passband.
  • This digital filter, and the digital filter after the first frequency shift, have the same design parameters and performance;
  • Step 312 The FPGA calculates the signal power in the channel, which is Sout 2dBm;
  • Step 313 Finally, the power calculated twice before and after, Sout2_Sout1, the phase noise value dBc/Hz at 1KHz from the local oscillator is obtained;
  • the detection accuracy of the phase noise value depends on the following factors: First, Sout 2 (amplified phase noise value) is higher than the bottom noise of the entire RF link; second, Sout 2 is higher than the ADC's noise floor; Third, the digital low-pass filter suppresses at 1 kHz more than the phase noise value. For example, if the phase noise value of 1 kHz is -100 dBc/Hz, the designed digital low-pass filter should have a rejection of more than 100 dBc at 1 kHz.
  • the example of the invention utilizes a signal added at a position 1KHz away from the main signal to test the phase noise value deviating from the local oscillator 1KHz position, and realizes the phase noise performance of the local oscillator by using a common signal source and borrowing the receiving channel of the radio remote unit itself.
  • the preliminary test greatly satisfies the test requirements of the local oscillator performance for large-scale production.
  • the local oscillator phase noise detecting method provided by the invention is easy to implement and low in cost, and the supported hardware system can be completely borrowed, which is convenient for popularization and application.
  • the embodiment of the invention provides a local oscillator phase noise detecting device.
  • the device includes:
  • a mixer configured to mix a signal deviating from the RF center frequency point f RF preset distance ⁇ f with the local oscillator signal f LO to obtain a signal of the intermediate frequency center frequency point f IF and deviating from the intermediate frequency center frequency point ⁇ f from f IF signals of the preset;
  • the analog-to-digital converter ADC is configured to convert a signal of the intermediate frequency center frequency point f IF mixed by the mixer and a signal deviating from the intermediate frequency center frequency point f IF by a preset distance ⁇ f to obtain a corresponding digital signal;
  • a field programmable gate array FPGA the digital signal is provided to the analog to digital converter ADC conversion departing obtained by processing the local oscillation frequency f LO phase noise corresponding frequency value ⁇ f position.
  • the invention tests the phase noise value deviating from the position of the local oscillator ⁇ f by adding a signal at a position deviating from the main signal ⁇ f, and using the receiving channel of the radio remote unit itself, only one ordinary signal source is needed, and the phase noise of the local oscillator can be realized.
  • the initial detection function eliminates the cost of expensive phase noise meters.
  • the signal input in the embodiment of the present invention may be a single tone signal, a two-tone signal or a narrowband signal.
  • the interval of the two-tone signal and the bandwidth of the narrowband signal should be smaller than the subsequent digital number.
  • the embodiment of the present invention further includes an intermediate frequency amplifier and an intermediate frequency anti-aliasing filter.
  • an intermediate frequency amplifier and an intermediate frequency anti-aliasing filter.
  • the intermediate frequency amplifier is configured to amplify a signal of an intermediate frequency center frequency point f IF obtained by mixing the mixer and a signal deviating from the intermediate frequency center frequency point f IF by a preset distance ⁇ f;
  • the intermediate frequency anti-aliasing filter is configured to perform an anti-aliasing frequency component processing on the signal amplified by the intermediate frequency amplifier.
  • the amplification processing condition of the embodiment of the present invention is that the signal of the corresponding intermediate frequency center point f IF corresponding to the frequency point ⁇ f after amplification is smaller than the full-scale power of the analog-to-digital converter ADC, and the amplified intermediate frequency center frequency point The signal of f IF is higher than the noise floor of the analog-to-digital converter ADC.
  • the field programmable gate array FPGA is specifically configured to separately frequency-shift the digital signal to zero frequency, and perform filtering, and obtain a deviation from the local oscillation frequency point f LO according to the filtered digital signal.
  • the phase noise value of the corresponding frequency point ⁇ f is specifically shifted to the zero frequency and filtered, and the power of each digital signal after filtering is calculated, and the power is subtracted to obtain a deviation from the local frequency f LO
  • the phase noise value of the corresponding frequency point ⁇ f position is specifically configured to separately frequency-shift the digital signal to zero frequency, and perform filtering, and obtain a deviation from the local oscillation frequency point f LO according to the filtered digital signal.
  • the related content of the device in the embodiment of the present invention can be understood by referring to the related content of the foregoing method or device embodiment, and details are not described herein again.
  • the embodiment of the invention provides a radio remote unit, which includes any one of the devices described in the device embodiment.
  • the present invention provides a local oscillator phase noise detecting method, device and radio remote unit, which can bring the following beneficial effects:
  • the invention tests the phase noise value deviating from the local oscillator ⁇ f position by adding a signal at a position deviating from the main signal ⁇ f, and realizes the phase noise performance of the local oscillator by using a common signal source and borrowing the receiving channel of the radio remote unit itself.
  • the inspection greatly satisfies the test requirements of the local oscillator performance for large-scale production.
  • the local oscillator phase noise detecting method provided by the invention is easy to implement, low in cost, convenient for popularization, and effectively solves the problem of high phase noise cost of the radio frequency remote unit tested by the phase noise meter in the prior art.
  • a local oscillator phase noise detecting method, apparatus, and radio remote unit provide the following beneficial effects: the present invention tests a phase deviating from the local oscillator ⁇ f by adding a signal at a position deviating from the main signal ⁇ f.
  • the noise value is detected by a common signal source and the receiving channel of the radio remote unit itself, which realizes the detection of the phase noise performance of the local oscillator, which greatly satisfies the testing requirements of the local oscillator performance of the tooling during mass production.
  • the local oscillator phase noise detecting method provided by the invention is easy to implement, low in cost, convenient for popularization, and effectively solves the problem of high phase noise cost of the radio frequency remote unit tested by the phase noise meter in the prior art.

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Abstract

一种本振相位噪声检测方法、装置及射频拉远单元，包括：在偏离主信号Δf位置加信号来测试偏离本振Δf位置的相噪值，只通过一台普通的信号源，借用射频拉远单元本身的接收通道，实现了本振相噪性能的检测，极大地满足了大规模生产时工装对本振性能的测试要求,本振相位噪声检测方法实现容易，成本低廉，便于普及应用，有效解决了现有技术中使用相噪仪测试射频拉远单元的相噪值成本高的问题。

Description

一种本振相位噪声检测方法、装置及射频拉远单元 技术领域
本发明涉及通信技术领域，尤其涉及一种本振相位噪声检测方法、装置及射频拉远单元。
背景技术
随着无线通讯技术的发展，射频拉远单元的应用越来越广泛。众所周知，本振的相噪性能直接影响到射频拉远单元发送和接收的性能。在调试阶段，通常是用相噪仪来测试射频拉远单元的相噪性能，而到了大批量生产时，如果为每个工位都配置一台相噪仪，成本就太高了，所以，在射频拉远单元测试工装中，都没有本振相噪性能测试这一项。而如何在大批量射频拉远单元的生产中，实现简单快速地检测本振相位噪声的性能成为现在亟待需要解决的问题。
发明内容
鉴于上述的分析，本发明旨在提供一种本振相位噪声检测方法、装置及射频拉远单元，用以解决现有技术中使用相噪仪测试射频拉远单元的相噪值成本高的问题。
为解决上述问题，本发明主要是通过以下技术方案实现的：
本发明一方面提供了一种本振相位噪声检测方法，该方法包括：
将偏离射频中心频点fRF预设距离Δf的信号与待测本振信号fLO进行混频，分别得到中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号；
对混频后的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行转换得到相应的数字信号；
对所述数字信号进行处理得到偏离本振频点fLO相应频点Δf位置的相噪值。
优选地，所述信号是单音信号、双音信号或窄带信号。
优选地，所述将偏离射频中心频点fRF相应频点Δf位置的信号与待测本振信号fLO进行混频的步骤之后，所述对混频后的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行转换得到相应的数字信号的步骤之前，还包括：
将混频后得到的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行放大处理以及抑制混叠频率分量处理。
优选地，所述对所述数字信号进行处理得到偏离本振频点fLO相应频点Δf位置的相噪值的步骤具体包括：
对所述数字信号分别移频到零频，并进行滤波，并根据滤波后的数字信号得到偏离本振频点fLO相应频点Δf位置的相噪值。
优选地，所述对所述数字信号分别移频到零频，并进行滤波，并根据滤波后的数字信号得到偏离本振频点fLO相应频点Δf位置的相噪值的步骤具体包括：
对所述数字信号分别移频到零频，并进行滤波，计算滤波后各个数字信号的功率，将功率相减，得到偏离本振频点fLO相应频点Δf位置的相噪值。
本发明另一方面还提供了一种本振相位噪声检测装置，该装置包括：
混频器，设置为将偏离射频中心频点fRF预设距离Δf的信号与待测本振信号fLO进行混频，分别得到中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号；
模数转换器ADC，设置为对所述混频器混频后的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行转换得到相应的数字信号；
现场可编程门阵列FPGA，设置为对所述模数转换器ADC转换后的数字信号进行处理得到偏离本振频点fLO相应频点Δf位置的相噪值。
优选地，该装置还包括中频放大器和中频抗混叠滤波器；
所述中频放大器，设置为将所述混频器混频后得到的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行放大处理；
所述中频抗混叠滤波器，设置为对所述中频放大器放大处理后的信号进行抑制混叠频率分量处理。
优选地，所述现场可编程门阵列FPGA具体设置为，对所述数字信号分别移频到零频，并进行滤波，并根据滤波后的数字信号得到偏离本振频点fLO相应频点Δf位置的相噪值。
优选地，所述现场可编程门阵列FPGA具体设置为，对所述数字信号分别移频到零频，并进行滤波，计算滤波后各个数字信号的功率，将功率相减，得到偏离本振频点fLO相应频点Δf位置的相噪值。
本发明另一方面还提供了一种射频拉远单元，该射频拉远单元包括上述任意一种本振相位噪声检测装置。
本发明有益效果如下：
本发明通过在偏离主信号Δf位置加信号来测试偏离本振Δf位置的相噪值，只通过一台普通的信号源，借用射频拉远单元本身的接收通道，实现了本振相噪性能的检测，极大地满 足了大规模生产时工装对本振性能的测试要求。另外，本发明提供的本振相位噪声检测方法实现容易，成本低廉，便于普及应用，有效解决了现有技术中使用相噪仪测试射频拉远单元的相噪值成本高的问题。
本发明的其他特征和优点将在随后的说明书中阐述，并且部分的从说明书中变得显而易见，或者通过实施本发明而了解。本发明的目的和其他优点可通过在所写的说明书、权利要求书、以及附图中所特别指出的结构来实现和获得。
附图说明
图1为本发明实施例的一种本振相位噪声检测方法的流程示意图；
图2为本发明实施例的一种本振相位噪声检测装置的结构示意图；
图3为本发明实施例的另一种本振相位噪声检测方法的流程示意图；
图4为本发明实施例的第一次移频的流程示意图；
图5为本发明实施例的第二次移频的流程示意图。
具体实施方式
下面结合附图来具体描述本发明的优选实施例，其中，附图构成本申请一部分，并与本发明的实施例一起用于阐释本发明的原理。为了清楚和简化目的，当其可能使本发明的主题模糊不清时，将省略本文所描述的器件中已知功能和结构的详细具体说明。
本发明实施例的主要目的是提供一种本振相位噪声检测方法、装置及射频拉远单元，通过在偏离主信号Δf位置加信号来测试偏离本振Δf位置的相噪值，利用射频拉远单元自身的接收通道，只需要一台普通的信号源，就可以实现本振相噪的初步检测功能，省去了价格昂贵的相噪仪费用。下面就通过几个具体实施例对本发明的技术方案进行详细说明。
方法实施例
本发明实施例提供了一种本振相位噪声检测方法，参见图1和2，该方法包括：
S101、将偏离射频中心频点fRF预设距离Δf的信号与待测本振信号fLO进行混频，分别得到中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号；
具体实施时，本发明实施例是通过一个信号源给混频器的射频输入端加一个偏离射频中心频点fRF相应频点Δf位置的信号，该信号源是普通的信号源，只要能输出较大幅度的信号 即可。
本发明实施例所输入的信号可以是单音信号、双音信号或窄带信号，当所输入的信号是双音信号或窄带信号时，双音信号的间隔，以及窄带信号的带宽应小于后续进行数字信号处理时数字低通滤波器的带宽。
由于本发明所加的偏离射频中心频点fRF相应频点Δf位置的信号的功率足够大，所以混频器输出的信号有两个：一是位于偏离中频中心频点fIF相应频点Δf位置的大信号，幅度较大，二是位于中频中心频点fIF的小信号，幅度较小。
S102、对混频后的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行转换得到相应的数字信号；
具体实施时，本发明实施例是通过射频拉远单元内的模数转换器将步骤101处理后的信号进行ADC采样，并将混频后的信号进行转换得到对应的数字信号。
即，本发明通过射频拉远单元内的模数转换器ADC对混频后得到的位于偏离中频中心频点fIF相应频点Δf位置的信号，以及位于中频中心频点fIF的信号进行采样，并将采样到的信号进行量化编码得到相应的数字信号，并发送给现场可编程门阵列(Field－Programmable Gate Array，FPGA)进行处理。
本发明实施例的ADC具有尽可能高的动态，这样相噪检测的精度更准确，具体实施时，本发明实施例采用的ADC的位数不小于11bit。
S103、对所述数字信号进行处理得到偏离本振频点fLO相应频点Δf位置的相噪值。
本发明实施例步骤S103对所述数字信号分别移频到零频，并进行滤波，并根据滤波后的数字信号得到偏离本振频点fLO相应频点Δf位置的相噪值。
具体的，本发明通过对所述数字信号分别移频到零频，并进行滤波，计算滤波后各个数字信号的功率，将功率相减，得到偏离本振频点fLO相应频点Δf位置的相噪值。
具体实施时，本发明通过FPGA对转换后的数字信号分别进行两次不同的移频，具体包括：
第一次移频，就是将偏离中频中心频点fIF相应频点Δf位置的大信号移到零频，然后经过数字低通滤波器进行滤波，将偏离零频相应频点Δf位置的小信号滤除，只剩下位于零频的大信号。再计算此滤波器通带内的信号功率值，记为功率一；
第二次移频，就是将之前的中频中心频点fIF移到零频，然后经过数字低通滤波器进行滤波，将偏离零频相应频点Δf位置的大信号滤除，只剩下位于零频的小信号。再计算此滤波器通带内的信号功率值，记为功率二。
最后用功率二减去功率一，就得出偏离本振相应频点Δf位置的相噪值。
这里，两次移频后的数字低通滤波器是同一个滤波器，滤波器的带宽要尽量窄，对Δf频 点位置的抑制要尽量高。数字低通滤波器的带宽可以根据Δf的大小来灵活设置，既要考虑到对Δf频点位置的抑制，又要考虑到带宽内的信号功率可以被正确检测到。如测试偏离1KHz的相噪，则数字低通滤波器的带宽BW可以设置为40Hz；而测试偏离10KHz的相噪，则数字低通滤波器的带宽BW可以加宽到200Hz。
本发明通过在偏离主信号Δf位置加信号来测试偏离本振Δf位置的相噪值，利用射频拉远单元自身的接收通道，只需要一台普通的信号源，就可以实现本振相噪的初步检测功能，省去了价格昂贵的相噪仪费用。
本发明通过一个信号源给混频器的射频输入端加一个偏离射频中心频点fRF相应频点Δf位置的信号，该信号与混频器的本振输入即待测本振fLO进行混频，对混频器的中频输出经过放大、抗混叠滤波和ADC采样后变成数字信号，再由FPGA进行移频和数字滤波处理，得到偏离本振频点fLO相应频点Δf位置的相噪值。
本发明实施例还提供了一种优选的实施方式，具体为，所述将偏离射频中心频点fRF相应频点Δf位置的信号与待测本振信号fLO进行混频的步骤之后，所述对混频后的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行转换得到相应的数字信号的步骤之前，还包括：
将混频后得到的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行放大处理以及抑制混叠频率分量处理。
具体实施时，本发明实施例通过中频放大器将混频后得到的信号进行放大处理，并通过中频抗混叠滤波器对所述中频放大器放大处理后的信号进行抑制混叠频率分量处理。
即，本发明通过对混频器输出的信号再经过中频放大器进行放大，其中，本发明实施例所述的中频放大器的增益是可调的，既保证偏离中频中心频点fIF相应频点Δf位置的大信号经过放大后不超出ADC的满量程功率，又保证位于中频中心频点fIF的小信号经过放大后高于ADC的底噪和整个射频链路的底噪。
且，经中频放大器放大后的信号在输入到ADC进行采样之前，要经过一个中频抗混叠滤波器，通过该中频抗混叠滤波器抑制混叠频率分量，以避免对带内有用信号的干扰。
这里，中频放大器输出的两个信号都是落在抗混叠滤波器的通带内的，所以，经中频抗混叠滤波器处理后的对信号的功率衰减很小。
本发明通过在偏离主信号Δf位置加信号的方法，实现了对偏离本振Δf位置的相噪值的检测，本发明所述的方法不需要昂贵的相噪分析仪，只需要一台普通的信号源，就能实现本振相噪的检测，大大节省了测试成本。
另外，本发明除了要设置一个输入信号的信号源外，其他装置都是射频拉远单元内部的一部分，且射频拉远单元内部的接收通道就是混频后中频放大再抗混叠滤波最后ADC采样的链路架构。所以本发明所述的方法，不需要额外的硬件链路，直接就可以借用射频拉远单元 自身的接收通道，实现简单，便于在生产测试工装中大规模应用。
图3为本发明实施例的另一种本振相位噪声检测方法的流程示意图，下面将结合图3对本发明所述的方法进行详细的说明：
假设，射频拉远单元的射频中心频点fRF为1950MHz，其对应的中频中心频点fIF为140MHz，则对应的本振fLO为1810MHz。设现在要测试的是本振1810MHz偏离位置Δf为1KHz处的相噪值，则包括以下步骤：
步骤301：要测试偏离本振Δf位置的信号；
步骤302：信号源，设置输出频点为1950.001MHz，输出功率为0dBm，输出模式为单音；
步骤303：将信号源的输出连接到射频拉远单元内部接收通道的混频器，射频信号1950.001MHz与本振信号1810MHz经混频器混频后输出，得到140.001MHz的中频大信号，和140MHz的中频小信号；
步骤304：这两个信号一起输入到射频拉远单元内部接收通道的中频放大器进行放大，这个中频放大器的增益是可调的，既保证140.001MHz的中频大信号不超出ADC的满量程，又保证140MHz的中频小信号高出ADC底噪和射频链路底噪；
步骤305：中频放大器输出的两个信号经过射频拉远单元内部接收通道的中频抗混叠滤波器，抑制混叠频率分量，这样就不会影响带内这两个信号功率的正确检测；
步骤306：将经过中频抗混叠滤波器滤波后的两个信号连接到射频拉远单元内部接收通道的模数转换器。140.001MHz的中频大信号和140MHz的中频小信号一起经过ADC采样后从模拟信号转换成数字信号；
步骤307：转换后的数字信号再进入射频拉远单元内部的FPGA进行数字处理，第一次移频，变成零频的大信号和1KHz的小信号，具体如图4所示；
步骤308：移频后的信号，通过设计的数字低通滤波器，1KHz的小信号被滤除，只剩下通带内的大信号。这个数字滤波器，假设是一个通带为40Hz的低通滤波器；
步骤309：FPGA计算通带内的信号功率，为Sout1dBm；
步骤310：第二次移频，变成零频的小信号和1KHz的大信号，具体如图5所示；
步骤311：移频后的信号，通过设计的数字低通滤波器，1KHz的大信号被滤除，只剩下通带内的小信号。这个数字滤波器，和第一次移频后的数字滤波器，设计参数和性能是完全一样的；
步骤312：FPGA计算通道内的信号功率，为Sout 2dBm；
步骤313：最后，将前后两次计算的功率一比，Sout2—Sout1，就得到了偏离本振1KHz处的相噪值dBc/Hz；
这里，相噪值的检测精度取决于以下几方面因素：一是Sout 2(放大后的相噪值)要高于整个射频链路的底噪；二是Sout 2要高于ADC的底噪；三是数字低通滤波器对于1KHz处的抑制要大于相噪值。例如，如果1KHz的相噪值是-100dBc/Hz，则设计的数字低通滤波器在1KHz处的抑制度要在100dBc以上。
本发明实例利用在偏离主信号1KHz位置加信号来测试偏离本振1KHz位置的相噪值，只通过一台普通的信号源，借用射频拉远单元本身的接收通道，实现了本振相噪性能的初步检测，极大地满足了大规模生产时工装对本振性能的测试要求。另外，本发明提供的本振相位噪声检测方法实现容易，成本低廉，支持的硬件系统可以完全借用，便于普及应用。
装置实施例
本发明实施例提供了一种本振相位噪声检测装置，参见图2，该装置包括：
混频器，设置为将偏离射频中心频点fRF预设距离Δf的信号与待测本振信号fLO进行混频，分别得到中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号；
模数转换器ADC，设置为对所述混频器混频后的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行转换得到相应的数字信号；
现场可编程门阵列FPGA，设置为对所述模数转换器ADC转换后的数字信号进行处理得到偏离本振频点fLO相应频点Δf位置的相噪值。
本发明通过在偏离主信号Δf位置加信号来测试偏离本振Δf位置的相噪值，利用射频拉远单元自身的接收通道，只需要一台普通的信号源，就可以实现本振相噪的初步检测功能，省去了价格昂贵的相噪仪费用。
本发明实施例所输入的信号可以是单音信号、双音信号或窄带信号，当所输入的信号是双音信号或窄带信号时，双音信号的间隔，以及窄带信号的带宽应小于后续进行数字信号处理时数字低通滤波器的带宽。
优选地，本发明实施例还设有中频放大器和中频抗混叠滤波器，具体的，
所述中频放大器，设置为将所述混频器混频后得到的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行放大处理；
所述中频抗混叠滤波器，设置为对所述中频放大器放大处理后的信号进行抑制混叠频率分量处理。
其中，本发明实施例的所述放大处理条件为：放大后的偏离中频中心频点fIF相应频点Δf位置的信号小于模数转换器ADC的满量程功率，且放大后的中频中心频点fIF的信号高于模数转换器ADC的底噪。
优选地，本发明实施例所述现场可编程门阵列FPGA具体设置为，对所述数字信号分别 移频到零频，并进行滤波，并根据滤波后的数字信号得到偏离本振频点fLO相应频点Δf位置的相噪值，具体为对所述数字信号分别移频到零频，并进行滤波，计算滤波后各个数字信号的功率，将功率相减，得到偏离本振频点fLO相应频点Δf位置的相噪值。
本发明实施例装置的相关内容可参考上述方法或装置实施例的相关内容进行理解，此处不再赘述。
射频拉远单元实施例
本发明实施例提供了一种射频拉远单元，该射频拉远单元包括装置实施例中所述的任意一种装置。
本发明实施例中的相关内容可参照装置实施例和方法实施例部分进行理解，在此不再赘述。
本发明提供的一种本振相位噪声检测方法、装置及射频拉远单元，能够带来以下有益效果：
本发明通过在偏离主信号Δf位置加信号来测试偏离本振Δf位置的相噪值，只通过一台普通的信号源，借用射频拉远单元本身的接收通道，实现了本振相噪性能的检测，极大地满足了大规模生产时工装对本振性能的测试要求。另外，本发明提供的本振相位噪声检测方法实现容易，成本低廉，便于普及应用，有效解决了现有技术中使用相噪仪测试射频拉远单元的相噪值成本高的问题。
以上所述，仅为本发明较佳的具体实施方式，但本发明的保护范围并不局限于此，任何熟悉本技术领域的技术人员在本发明揭露的技术范围内，可轻易想到的变化或替换，都应涵盖在本发明的保护范围之内。因此，本发明的保护范围应该以权利要求书的保护范围为准。
工业实用性
如上所述，本发明实施例提供的一种本振相位噪声检测方法、装置及射频拉远单元具有以下有益效果：本发明通过在偏离主信号Δf位置加信号来测试偏离本振Δf位置的相噪值，只通过一台普通的信号源，借用射频拉远单元本身的接收通道，实现了本振相噪性能的检测，极大地满足了大规模生产时工装对本振性能的测试要求。另外，本发明提供的本振相位噪声检测方法实现容易，成本低廉，便于普及应用，有效解决了现有技术中使用相噪仪测试射频拉远单元的相噪值成本高的问题。

Claims (10)

  1. 一种本振相位噪声检测方法，包括：
    将偏离射频中心频点fRF预设距离Δf的信号与待测本振信号fLO进行混频，分别得到中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号；
    对混频后的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行转换得到相应的数字信号；
    对所述数字信号进行处理得到偏离本振频点fLO相应频点Δf位置的相噪值。
  2. 根据权利要求1所述的方法，其中，
    所述信号是单音信号、双音信号或窄带信号。
  3. 根据权利要求1所述的方法，其中，所述将偏离射频中心频点fRF相应频点Δf位置的信号与待测本振信号fLO进行混频的步骤之后，所述对混频后的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行转换得到相应的数字信号的步骤之前，还包括：
    将混频后得到的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行放大处理以及抑制混叠频率分量处理。
  4. 根据权利要求1-3中任意一项所述的方法，其中，所述对所述数字信号进行处理得到偏离本振频点fLO相应频点Δf位置的相噪值的步骤具体包括：
    对所述数字信号分别移频到零频，并进行滤波，并根据滤波后的数字信号得到偏离本振频点fLO相应频点Δf位置的相噪值。
  5. 根据权利要求4所述的方法，其中，所述对所述数字信号分别移频到零频，并进行滤波，并根据滤波后的数字信号得到偏离本振频点fLO相应频点Δf位置的相噪值的步骤具体包括：
    对所述数字信号分别移频到零频，并进行滤波，计算滤波后各个数字信号的功率，将功率相减，得到偏离本振频点fLO相应频点Δf位置的相噪值。
  6. 一种本振相位噪声检测装置，包括：
    混频器，设置为将偏离射频中心频点fRF预设距离Δf的信号与待测本振信号fLO进行混频，分别得到中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号；
    模数转换器ADC，设置为对所述混频器混频后的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行转换得到相应的数字信号；
    现场可编程门阵列FPGA，设置为对所述模数转换器ADC转换后的数字信号进行处理得到偏离本振频点fLO相应频点Δf位置的相噪值。
  7. 根据权利要求6所述的装置，其中，还包括中频放大器和中频抗混叠滤波器；
    所述中频放大器，设置为将所述混频器混频后得到的中频中心频点fIF的信号以及偏离所述中频中心频点fIF预设距离Δf的信号进行放大处理；
    所述中频抗混叠滤波器，设置为对所述中频放大器放大处理后的信号进行抑制混叠频率分量处理。
  8. 根据权利要求6或7所述的装置，其中，
    所述现场可编程门阵列FPGA具体设置为，对所述数字信号分别移频到零频，并进行滤波，并根据滤波后的数字信号得到偏离本振频点fLO相应频点Δf位置的相噪值。
  9. 根据权利要求8所述的装置，其中，
    所述现场可编程门阵列FPGA具体设置为，对所述数字信号分别移频到零频，并进行滤波，计算滤波后各个数字信号的功率，将功率相减，得到偏离本振频点fLO相应频点Δf位置的相噪值。
  10. 一种射频拉远单元，该射频拉远单元包括权利要求6-9中任意一项所述的装置。
PCT/CN2016/070434 2015-06-29 2016-01-07 一种本振相位噪声检测方法、装置及射频拉远单元 WO2017000541A1 (zh)

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