WO2016129758A1 - 3-레벨 세픽 컨버터 회로 - Google Patents

3-레벨 세픽 컨버터 회로 Download PDF

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Publication number
WO2016129758A1
WO2016129758A1 PCT/KR2015/006554 KR2015006554W WO2016129758A1 WO 2016129758 A1 WO2016129758 A1 WO 2016129758A1 KR 2015006554 W KR2015006554 W KR 2015006554W WO 2016129758 A1 WO2016129758 A1 WO 2016129758A1
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WO
WIPO (PCT)
Prior art keywords
switch
capacitor
diode
output
converter circuit
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PCT/KR2015/006554
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English (en)
French (fr)
Inventor
최우영
강용철
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전북대학교 산학협력단
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Publication of WO2016129758A1 publication Critical patent/WO2016129758A1/ko

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/1557—Single ended primary inductor converters [SEPIC]
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to the converter circuit, and more specifically, the voltage in the converter.
  • Switched-mode power supply is widely used as a power supply unit that can supply stable DC power to electronic circuits.
  • An important part of defining the characteristics of the SMPS is the DC-DC converter, and the type of the SMPS is determined by the type of the converter.
  • Width Modulation which is divided into non-isolated DC-DC converters whose input and output are not electrically isolated, and isolated DC-DC converters in which the primary and secondary sides of the transformer are electrically insulated from the center of the transformer.
  • the energy flowing into the transformer primary side is converted to SEPIC (Single Ended Primary).
  • Inductor Converter mode is used to transfer to the output and the switch
  • the transformer secondary side flyback mode circuit When turned off (1-D), the transformer secondary side flyback mode circuit is used.
  • the switch delivers energy to the secondary side of the transformer when the switch is ON and OFF, and proposes a new type of flyback converter that can greatly increase the transformer utilization and output.
  • [8] Separator converters have inductors at the input and output stages, respectively, for input and output.
  • the current ripple characteristic of the side is excellent, and the output voltage can be higher or lower than the input voltage, so that various industrial power converters such as power factor correction and voltage regulator module can be used.
  • conventional thin converters have the disadvantage of applying a high voltage stress to the power semiconductor during the switching operation. These high voltage stresses reduce the power conversion efficiency of the circuit converter and reduce the stability of the circuit. Cause it to be.
  • Fig. 1 is a diagram of the conventional thin converter
  • Fig. 2 is a graph showing the voltage across the switch and the diode over time when the switch is controlled by the duty cycle D in the existing serial converter.
  • Conventional safety converters include input inductors (Li), switches (si), capacitors ( ⁇ ), and outputs.
  • the voltage across the overdiode (Do) is Vci + Vo, respectively.
  • the switch S1 is off, the output diode Do is shorted, and the voltage across the switch S1 becomes Vci + Vo, respectively.
  • the capacitor voltage (Vci) becomes the input voltage (Vi) in the steady state (the inductor is shorted and the capacitor is open in the case of the DC steady state).
  • the voltage applied to the switch (S1) and the output diode (Do) in the conventional serial converter is Vi + Vo. Therefore, when the input voltage (Vi) and the output voltage (Vo) are high, the switching loss due to the high voltage stress is high. Power Loss increases the switching loss due to high voltage stress, which lowers the power conversion efficiency and reduces the stability of the circuit.
  • a three-level thin converter circuit of the present invention for solving the above-mentioned problems includes an input inductor connected to one side of an input terminal, a first switch and a second switch connected in series between the input inductor and the other side of the input terminal.
  • a first capacitor and a first diode connected in series between the first switch and one side of the output terminal, a second diode and a second capacitor connected in series between the other side of the output terminal and the other end of the output terminal, and between the output terminal.
  • the control unit may further include a control unit for controlling on / off of the first switch or the second switch.
  • the control unit may turn on / off the first switch and the second switch according to a predetermined period. It can be turned off and controlled so that the on or off time of the first switch and the second switch is half a cycle apart.
  • control unit may control the on duration of the first switch and the second switch to be less than half a cycle, and in another embodiment, the on duration of the first switch and the second switch is maintained. It can be controlled so that time is less than 1 cycle or more than half cycle.
  • the first capacitor and the first diode may include the first capacitor connected to the first switch and the first diode connected to one side of the output terminal.
  • the first diode may include the anode capacitor, the first capacitor 1, The cathode may be connected to one side of the output stage.
  • the second capacitor and the second diode may include the second capacitor connected to the second switch, and the second diode may be connected to the other side of the output stage.
  • the second diode The anode is connected to the other side of the output terminal, the cathode may be connected to the second capacitor.
  • the capacitance of the first capacitor and the second capacitor may be implemented in the same device, and the first output capacitor and the second output capacitor may also be implemented in the same device.
  • 1 is a circuit diagram showing a conventional converter circuit.
  • FIG. 2 is a graph showing the voltage of the diode and the switch according to the operation of the switch in the conventional converter circuit.
  • FIG. 3 shows a three-level thin converter circuit according to an embodiment of the present invention.
  • FIG. 4 illustrates a three-level thin converter circuit according to another embodiment of the present invention.
  • FIG. 5 and 6 illustrate a three-level thin converter circuit in accordance with an embodiment of the present invention.
  • This graph shows the voltage of this diode and the switch according to the operation of the switch.
  • FIG. 15 illustrates a three-level thin converter circuit according to an embodiment of the present invention.
  • FIG. 3 shows a three-level thin converter converter according to an embodiment of the present invention.
  • a three-level thin converter circuit is provided on one side of an input terminal.
  • a first switch and a second switch connected in series between the input inductor, the input inductor and the other end of the input terminal, a first capacitor and a first diode connected in series between the first switch and one side of the output terminal, A second diode and a second capacitor connected in series between the other side of the output terminal and the other side of the input terminal, a first output capacitor and a second output capacitor connected between the output terminal, and a node between the first capacitor and the first diode. And an output inductor connected between the node between the second capacitor and the second diode, wherein a node between the first switch and the second switch and a node between the first output capacitor and the second output capacitor are connected.
  • FIG. 4 shows a three-level level serial converter circuit according to another embodiment of the present invention.
  • the converter circuit further includes a control unit for controlling on / off of the first switch or the second switch.
  • the operation of the first switch and the second switch according to the control command of the control unit The first switch and the second switch
  • control unit can be switched on / off at various periods and durations.
  • the control unit can be implemented by various configurations that can control the switch according to the input control command or a preset control command. It can be implemented by a semiconductor device.
  • control unit presets the first switch and the second switch.
  • Jugie may sikilsu on / off in accordance with particular, the machine can have a set jugineun the first switch and the second switch, all of the same period that is, the first switch is on -. Be> off
  • Tsl time required from the point of time when the switch is off-> on to the point of turning on-> off again (Tsl) (Ts2) can be set in the same manner, and the control unit can control the first switch and the second switch according to this setting.
  • control unit may control the difference between the on and off time of the first switch and the second switch by a half cycle. This operation will be described later through 5 and 6. see.
  • the first capacitor and the first diode are the first capacitor.
  • a capacitor may be connected to the first switch, and the first diode may be connected to one side of the output terminal.
  • the first diode may be connected to the anode of the first capacitor and the cathode may be connected to one side of the output terminal.
  • the influence of the overall circuit operation depends on the connection direction. In the present invention, by connecting in the same structure as in the present embodiment, voltage stress applied to the switches and the diodes can be reduced.
  • FIG. 3 is a circuit diagram showing a converter circuit according to this structure.
  • FIG. 5 and 6 illustrate a three-level thin converter circuit in accordance with an embodiment of the present invention.
  • FIG. 5 shows a case where the duty cycle D is 0.5 or less
  • FIG. 6 shows a case where the duty cycle D exceeds 0.5.
  • the on duration of the first switch and the second switch is less than half cycle.
  • the first switch is turned on and the second switch is turned off. Looking at the operation of the three-level thin converter circuit of the present invention, the first diode is opened and the second diode is shorted.
  • the first switch and the second diode are shorted, so the voltage is zero and the second switch and the second diode are
  • the diode takes on a voltage of the size described above when compared to the voltage of each element in the entire circuit.
  • Vs2 Vc2 + Vo2
  • the first switch is turned off while the second switch is turned on.
  • the first diode is shorted and the second diode is operated in an open form. 9 is shown.
  • the voltage across the first and second switches and the first and second diodes is as follows.
  • VD2 Vc2 + Vo2
  • the first switch remains off and the second switch is turned off.
  • the first and second diodes are the same.
  • the short-circuit voltage is as follows.
  • Vs2 Vc2 + Vo2
  • Vsl, Vs2, VD1, and VD2 From point 1 to point 4, it can be seen that it is 0 or Vcl + Vol, or Vc2 + Vo2.
  • the voltage across the switch and diode is 1, 2 capacitor, 1 This is determined by the voltage across the 1 and 2 output capacitors. Therefore, the circuit in the steady state is shown in Fig. 15 to check the voltage of the above capacitors. In the DC steady state, the inductor is shorted and the capacitor is open circuit. In this case, look at the relationship between the voltage across the capacitor and the input / output voltage.
  • the same capacity of the capacitors does not mean that the values are exactly the same.
  • the concept includes a range of errors that may occur in the manufacturing process of capacitors, and capacitors manufactured and sold at the same capacity in commercial capacitors may be used.
  • ⁇ Capacity is same, it is equivalent to one capacitor.
  • the conventional converter circuit structure has a significant voltage stress, but the converter circuit proposed in the present invention can reduce the voltage across the switch and the diode in half, so that the switching loss is reduced. Switching power loss can be reduced by 25% or less.
  • the on duration time of the first switch and the second switch is half a period. 1 cycle or less, that is, when the duty cycle (D) exceeds 0.5.
  • both the first switch and the second switch are turned on.
  • both the first diode and the second diode are opened. 11 the voltage across the first and second switches and the first and second diodes is as follows.
  • VD1 Vcl + Vol
  • VD2 Vc2 + Vo2
  • the voltage is zero, and the first and second diodes take voltages as described above when compared with the voltages of the respective elements in the entire circuit.
  • the first switch remains on and the second switch is turned on.
  • the second diode operates in an open form while the first diode remains open.
  • the circuit diagram at this time is shown in Fig. 13.
  • the voltage across the first and second switches and the first and second diodes is as follows.
  • VD2 Vc2 + Vo2
  • the first switch is turned off and the second switch remains on.
  • the first diode is opened and the second diode is shorted. It looks like this:
  • VD2 Vc2 + Vo2
  • Vsl, Vs2, VDl, and VD2 From time point 1 to time point 4, it can be seen that it is 0 or Vcl + Vol, or Vc2 + Vo2.
  • the voltages of the first and second switches and the first and second diodes are calculated in consideration of the voltages of the capacitors in the normal state, they are compared with the conventional structure as in the embodiment of FIG. You can see that the voltage is cut in half. Thus, switching losses can be reduced.
  • Embodiments of the present invention have been disclosed for purposes of illustration, and those who have ordinary knowledge in the technical field to which the present invention belongs may modify, change, or add within the scope of the technical scope of the present invention. It should be seen as belonging to.
  • the present invention relates to a converter circuit and can be used in the energy storage and conversion industry.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

본 발명은 3-레벨 세픽 컨버터 회로에 관한 것으로, 보다 상세하게는 입력단의 일측에 연결되는 입력 인덕터, 상기 입력 인덕터 및 상기 입력단의 타측 사이에 직렬로 연결되는 제 1 스위치 및 제 2 스위치, 상기 제 1 스위치와 출력단의 일측 사이에 직렬로 연결되는 제 1 캐패시터 및 제 1 다이오드, 상기 출력단의 타측과 상기 입력단의 타측 사이에 직렬로 연결되는 제 2 다이오드 및 제 2 캐패시터, 상기 출력단 사이에 연결되는 제 1 출력 캐패시터 및 제 2 출력 캐패시터 및 상기 제 1 캐패시터 및 제 1 다이오드 사이의 노드와, 상기 제 2 캐패시터 및 상기 제 2 다이오드 사이의 노드 사이에 연결되는 출력 인덕터를 포함하고, 상기 제 1 스위치 및 제 2 스위치 사이의 노드와 상기 제 1 출력 캐패시터 및 제 2 출력 캐패시터 사이의 노드가 연결되는 3-레벨 세픽 컨버터 회로에 관한 것이다.

Description

명세서
발명의명칭: 3-레벨세픽컨버터회로 기술분야
[1] 본발명은컨버터회로에관한것으로,보다상세하게는컨버터내의전압
스트레스를줄이고전력변환효율올개선시키기위한컨버터회로에관한 것이다.
[2]
배경기술
[3] 전자계산기，전자교환기등오늘날의거의모든전자통신기기들은
전자회로부에안정적인직류전력올공급할수있는전원부로서스위치모드 파워서플라이 (Swiched-Mode Power Suply: SMPS)가폭넓게사용되고있다. 이러한 SMPS의특성을규정짓는중요한부분이 DC-DC컨버터이며，컨버터의 종류에따라 SMPS의종류가결정된다.
[4] 현재이러한 DC-DC컨버터증에서주류를이루고있는방식이 PWM(Pulse
Width Modulation)컨버터이고，이는입출력이전기적인절연되어있지않은 비절연형 DC-DC컨버터와변압기를중심으로변압기의 1차측과 2차측이서로 전기적으로절연된형태인절연형 DC-DC컨버터로구분된다.
[5] 절연형 DC-DC컨버터는스위치가온 (ON)일경우에너지를전달하는
포워드 (Forward)방식과스위치가오프 (OFF)일경우에너지를전달하는 (Flyback) 방식이존재하는데상기와같은방식으로는스위치가온일경우또는오프일 경우에만변압기의 1차측에너지가변압기 2차측출력으로전달되므로
변압기의이용율이제한될수밖에없다.
[6] 물론스위치가온일경우와오프일경우모두 2차측으로에너지를전달할수 있는 Forward-Flyback컨버터가존재하나 Forward모드는입력직류전압 (Vin)이 출력직류전압 (Vo)보다항상큰강압형이며， Flyback모드는입력직류
전압 (Vin)이출력직류전압 (Vo)보다항상작은승압형이므로단일출력으로 시스템올구성하여제어하는테는서로다른두개의전력희로특성상어려움이 있다.
[7] 아래선행문헌 1에서는 1개의스위치를이용하여스위치가턴온 (D)되었을
때는변압기 1차측에흐르는에너지를변압기 2차측 SEPIC(Single Ended Primary
Inductor Converter)모드회로를이용하여출력으로전달하고스위치가
턴오프 (1-D)되었을때에는변압기 2차측 Flyback모드회로를이용하여
출력으로전달하여스위치가은 (ON),오프 (OFF)시모두변압기 2차측으로 에너지전달이가능하며，변압기이용율과출력을크 증가시킬수있는새로운 형태의세픽플라이백컨버터를제안하였다
[8] 세픽컨버터는입력단과출력단에각각인덕터를구비함으로써입력및출력 측의전류리플 (Current Ripple)특성이우수하다.또한출력전압이입력 전압보다높거나낮을수있는특징을지님으로서역률개선 (Power Factor Correction)과전압조절장치 (Voltage Regulator Module)등의다양한산업용 전력변환장치로이용된다.하지만기존세픽컨버터는스위칭동작시전력용 반도체에높은전압스트레스가인가되는단점을지닌다.이러한높은전압 스트레스는세픽컨버터의전력변환효율 (Power Conversion Efficiency)를절감 시키고회로의안정성을저하시키는원인이된다.
발명의상세한설명
기술적과제
[9] 종래세픽컨버터의문제에대해도 1， 2를통해좀더상세하게살펴본다.도
1은기존의세픽컨버터의희로도이고,도 2는기존의세픽컨버터에서스위치를 듀티사이클 D로제어하는경우시간에따라스위치와다이오드에걸리는 전압을나타낸그래프이다.
[10] 종래의세픽컨버터는입력인덕터 (Li)，스위치 (si)，커패시터 (α)，출력
인덕터 (Lo),출력다이오드 (Do)및출력커패시터 (Co)로구성된다.종래기술의 세픽컨버터는입력단과출력단에각각입력인덕터 (Li)와출력인덕터 (Lo)를 구비한다.도 1에서스위치 (S1)이 on되는경우,출력다이오드 (Do)는
개방 (open)된다.이때，과다이오드 (Do)에걸리는전압은각각 Vci + Vo가된다. 한편，스위치 (S1)이 off되는경우,출력다이오드 (Do)는단락 (short)되며, 스위치 (S1)에걸리는전압은각각 Vci + Vo가된다.
[11] 종래기술의세픽컨버터는정상상태 (steady state)에서 (직류정상상태인경우 인덕터는단락，커패시터는개방)커패시터전압 (Vci)는입력전압 (Vi)이된다.도 2에도시된것처럼종래의세픽컨버터에서스위치 (S1)과출력다이오드 (Do)에 걸리는전압은 Vi + Vo가된다.따라서입력전압 (Vi)과출력전압 (Vo)이높은 경우,높은전압스트레스로인한스위칭손실 (Switching Power Loss)이증가되는 문제점을지니고있다.높은전압스트레스로인한스위칭손실은세픽컨버터의 전력변환효율 (Power Conversion Efficiency)을낮추고회로의안정성을
저하시키는원인이된다.
과제해결수단
[12] 상술한과제를해결하기위한본발명의 3-레벨세픽컨버터회로는입력단의 일측에연결되는입력인덕터，상기입력인덕터및상기입력단의타측사이에 직렬로연결되는제 1스위치및제 2스위치，상기제 1스위치와출력단의일측 사이에직렬로연결되는제 1캐패시터및제 1다이오드,상기출력단의타측과 상기입력단의타측사이에직렬로연결되는제 2다이오드및제 2캐패시터, 상기출력단사이에연결되는제 1출력캐패시터및제 2출력캐패시터및상기 제 1캐패시터및제 1다이오드사이의노드와，상기제 2캐패시터및상기제 2 다이오드사이의노드사이에연결되는출력인덕터를포함하고，상기제 1 스위치및제 2스위치사이의노드와상기제 1출력캐패시터및제 2출력 캐패시터사이의노드가연결된다.
[13] 한편，제 1스위치또는상기제 2스위치의 on/off를제어하기위한제어부를더 포함할수도있다.이때，상기제어부는상기제 1스위치와상기제 2스위치를 기설정된주기에따라 on/off시킬수있고，상기제 1스위치와상기제 2스위치의 on또는 off시점이반주기차이나도록제어할수도있다.
[14] 본발명의일실시예에서제어부는상기제 1스위치와상기제 2스위치의 on 지속시간이반주기이하가되도록제어할수있고,다른실시예에서는상기제 1 스위치와상기제 2스위치의 on지속시간이반주기이상 1주기이하가되도록 제어할수있다.
[15] 한편，상기제 1캐패시터및제 1다이오드는상기제 1캐패시터가상기제 1 스위치에,상기제 I다이오드가출력단의일측에연결될수있고특히상기제 1 다이오드는애노드가상기제 1캐패시터어 1,캐소드가상기출력단의일측에 연결될수있다.상기제 2캐패시터및제 2다이오드는상기제 2캐패시터가 상기제 2스위치에,상기제 2다이오드가출력단의타측에연결될수있고， 특히，상기제 2다이오드는애노드가상기출력단의타측에，캐소드가상기제 2 캐패시터에연결될수있다.
[16] 본발명의일실시예에서제 1캐패시터와상기제 2캐패시터의용량이동일한 소자로구현될수있으며，상기제 1출력캐패시터와상기제 2출력캐패시터 또한용량이동일한소자로구현될수있다.
발명의효과
[17] 본발명에따르면， 3-레벨세픽컨버터의스위치와다이오드의전압
스트레스를낮추고전력변환효율을개선시킬수있다.
도면의간단한설명
[18] 도 1은종래의컨버터회로를나타낸회로도이다.
[19] 도 2는종래의컨버터회로에서스위치의동작에따른다이오드와스위치의 전압을나타낸그래프이다.
[20] 도 3은본발명의일실시예에따론 3-레벨세픽컨버터회로를나타낸
희로도이다.
[21] 도 4는본발명의다른실시예에따른 3-레벨세픽컨버터회로를나타낸
희로도이다.
[22] 도 5및도 6은본발명의일실시예에따른 3-레벨세픽컨버터회로에서
스위치의동작에따른다이오드와스위치의전압을나타낸그래프이다.
[23] 도 7 ~도 10및도 11 ~ 14는본발명의일실시예에따른 3-레벨세픽컨버터 희로에서스위치의동작에따른등가회로를나타낸것이다.
[24] 도 15는본발명의일실시예에따른 3-레벨세픽컨버터회로의
정상상태에서의등가회로를나타낸것이다. 발명의실시를위한형태
[26] 이하，첨부된도면들을참조하여본발명에따른 3-레벨세픽컨버터회로에 대해상세하게설명한다.설명하는실시예들은본발명의기술사상을통상의 기술자가용이하게이해할수있도록제공되는것으로이에의해본발명이 한정되지않는다.또한，첨부된도면에표현된사항들은본발명의실시예들을 쉽게설명하기위해도식화된도면으로실제로구현되는형태와상이할수있다.
[27] 한편，어떤구성요소들을 '포함 '한다는표현은， '개방형'의표현으로서해당
구성요소들이존재하는것올단순히지칭할뿐이며,추가적인구성요소들을 배제하는것으로이해되어서는안된다.
[28] 또한，쩨 1，제 2'등과같은표현은，복수의구성들을구분하기위한용도로만 사용되는표현으로써，구성들사이의순서나기타특징들을한정하지않는다.
[29]
[30] 도 3은본발명의일실시예에따른 3-레벨세픽컨버터희로를나타낸
회로도이다.
[31] 본발명의일실시예에따른 3-레벨세픽컨버터회로는입력단의일측에
연결되는입력인덕터，상기입력인덕터및상기입력단의타측사이에직렬로 연결되는제 1스위치및제 2스위치，상기제 1스위치와출력단의일측사이에 직렬로연결되는제 1캐패시터및제 1다이오드,상기출력단의타측과상기 입력단의타측사이에직렬로연결되는제 2다이오드및제 2캐패시터，상기 출력단사이에연결되는제 1출력캐패시터및제 2출력캐패시터및상기제 1 캐패시터및제 1다이오드사이의노드와，상기제 2캐패시터및상기제 2 다이오드사이의노드사이에연결되는출력인덕터를포함하고,상기제 1 스위치및제 2스위치사이의노드와상기제 1출력캐패시터및제 2출력 캐패시터사이의노드가연결된다.
[32]
[33] 도 4는본발명의다른실시예에따른 3ᅳ레벨세픽컨버터회로를나타낸
화로도이다.본실시예에서컨버터회로는제 1스위치또는상기제 2스위치의 on/off를제어하기위한제어부를더포함한다.제어부의제어명령에따라상기 제 1스위치，제 2스위치의동작이제어된다.제 1스위치와제 2스위치는
제어부의제어에따라다양한주기，지속시간을두고 on/off될수있다.상기 제어부는입력된제어명령또는사전에설정된제어명령에따라스위치를 제어할수있는다양한구성에의해구현될수있다.일례로아날로그 /디지털 반도체소자에의해구현될수있다.
[34] 본발명의일실시예에서제어부는제 1스위치와제 2스위치를기설정된
주기에따라 on/off시킬수있다.특히，상기기설정된주기는제 1스위치와제 2 스위치모두동일한주기를가질수있다.즉,제 1스위치가 on -> off되는 시점부터 off -> on된후，다시 on -> off되는시점까지소요되는시간 (Tsl)이제 2 스위치가 on -> off되는시점부터 off -> on된후，다시 on -> off되는시점까지 소요되는시간 (Ts2)과동일하게설정될수있으며，이러한설정에따라제어부가 상기제 1스위치및제 2스위치를제어할수있다.
[35] 특히，본발명의일실시예에서는제어부가제 1스위치와상기제 2스위치의 on또는 off시점이반주기만큼차이가발생하도록제어할수있다.이에따른 동작을추후도 5， 6을통해살펴본다.
[36]
[37] 본발명의다른실시예에서제 1캐패시터및제 1다이오드는상기제 1
캐패시터가상기제 1스위치에,상기제 1다이오드가출력단의일측에연결될 수있다.특히，상기제 1다이오드는애노드가상기제 1캐패시터에,캐소드가 상기출력단의일측에연결된다.다이오드는방향성을가지는소자이고연결 방향에따라전체회로의동작에미치는영향이달라진다.본발명에서는본 실시예와같은구조로연결함으로써스위치와다이오드에각각걸리는전압 스트레스를낮출수있다.
[38] 뿐만아니라본발명의다른실시예에서제 2캐패시터및제 2다이오드는상기 제 2캐패시터가상기제 2스위치에，상기제 2다이오드가출력단의타측에 연결될수있고，이때,제 2다이오드는애노드가상기출력단의타측에， 캐소드가상기제 2캐패시터에연결될수있다.도 3은이러한구조에따른 컨버터회로를도시한회로도이다.
[39]
[40] 이하에서는제어부의제어에따른스위치의동작,그리고이때스위치와
다이오드에걸리는전압을도 5, 6을통해살펴본다.
[41] 도 5및도 6은본발명의일실시예에따른 3-레벨세픽컨버터회로에서
스위치의동작에따른다이오드와스위치의전압을나타낸그래프이다.도 5는 듀티사이클 (D)이 0.5이하인경우이고,도 6은듀티사이클 (D)이 0.5를초과하는 경우이다.
[42] 도 5에나타난실시예는제 1스위치와상기제 2스위치의 on지속시간이 반주기이하인경우이다.도 5에서， 1번시점에는제 1스위치는 on되고제 2 스위치는 off된다.이때본발명의 3-레벨세픽컨버터회로의동작을살펴보면， 제 1다이오드는개방되고，제 2다이오드는단락된다.이를나타낸것이도
7이다.도 7의경우제 1， 2스위치및제 1， 2다이오드에걸리는전압은다음과 같다.
[43] Vsl = 0
[44] Vs2 = Vc2 + Vo2
[45] VD1 = Vcl + Vol
[46] VD2 = 0
[47] 제 1스위치와제 2다이오드는단락되므로전압이 0이고제 2스위치와제 2 다이오드는전체회로에서의각소자의전압과비교하면상술한크기의전압이 걸린다.
[48]
[49] 2번시점에서는제 1스위치는 off가되고,제 2스위치도 off상태를유지한다. 한편，이러한스위칭상태에서제 1다이오드와제 2다이오드모두단락된다. 이는도 8에나타나있다.이때제 1, 2스위치및제 1, 2다이오드에걸리는 전압은다음과같다.
[50] Vsl = Vcl + Vol
[51] Vs2 = Vc2 + Vo2
[52] VD1 = 0
[53] VD2 = 0
[54] 제 1， 2다이오드모두단락되므로다이오드양단전압은 0고제 1， 2스위치에 걸리는전압은상술한수식과같다.
[55]
[56] 3번시점에서는제 1스위치는 off상태를유지하면서，제 2스위치가 on상태로 전환된다.이경우제 1다이오드는단락되고，제 2다이오드는개방된형태로 동작한다.이때의회로도는도 9에나타나있다.이때제 1, 2스위치및제 1， 2 다이오드에걸리는전압은아래와같다.
[57] Vsl = Vcl + Vol
[58] Vs2 = 0
[59] VD1 = 0
[60] VD2 = Vc2 + Vo2
[61]
[62] 4번시점에서는제 1스위치는 off상태를유지하면서다시제 2스위치가 off 상태로전환한다.이때는 2번시점과마찬가지로제 1， 2다이오드가모두
단락된다.각구성의전압은아래와같다.
[63] Vsl = Vcl + Vol
[64] Vs2 = Vc2 + Vo2
[65] VD1 = 0
[66] VD2 = 0
[67]
[68] 1번시점부터 4번시점까지 Vsl, Vs2, VD1, VD2를살펴보면， 0또는 Vcl + Vol, 또는 Vc2 + Vo2임을알수있다.스위치와다이오드양단에걸리는전압은제 1， 2캐패시터，제 1， 2출력캐패시터양단와전압에의해결정되는것이다.따라서 위캐패시터들의전압을확인하기위하여정상상태 (steady state)에서의회로를 도 15에나타내었다.직류정상상태에서는인덕터는단락，캐패시터는개방 회로가된다.이때，각캐패시터양단의전압과입출력전압의관계를살펴보면，
[69] Vi = Vcl + Vc2 [70] Vo = Vol + Vo2
[71] 가된다.
[72] 본발명의일실시예에서제 1캐패시터와상기제 2캐패시터가용량이동일한 경우,
[73] Vcl = Vc2 = Vi/2
[74] 가된다.
[75] 본발명의다른실시예에서제 1출력캐패시터와상기제 2출력캐패시터의 용량이동일한경우
[76] Vol = Vo2 = Vo/2
[77] 가된다.
[78] 다만여기서캐패시터의용량이동일하다는것은수치가완벽하게동일한것을 의미하지는않는다.캐패시터의제조과정에서발생할수있는오차범위를 포함하는개념이며,상용캐패시터에서동일용량으로제조되어판매，실시되는 캐패시터들은、용량이동일、한캐패시터에해당한다.
[79]
[80] 따라서，앞서살펴본스위치，다이오드의양단전압은 (Vi + Vo)/2가된다.즉,도
1, 2에나타난구조에비하여스위치및다이오드양단에걸리는전압이
절반으로줄어드는것이다.따라서，입력전압과출력전압이높은경우，기존의 컨버터회로구조는전압스트레스가상당하나본발명에서제안하는컨버터 회로는스위치，다이오드양단의전압을절반으로줄일수있으므로,스위칭 손실 (Switching power loss)울 25%이하까지도줄일수있다.
[81]
[82] 도 6은본발명의일실시예에따른컨버터회로에서스위치의동작에따른 다이오드와스위치의전압을나타낸그래프이다.본실시예는상기제 1 스위치와상기제 2스위치의 on지속시간이반주기이상 1주기이하이다.즉, 듀티사이클 (D)이 0.5를초과하는경우이다.
[83] 도 6을살펴보면, 1번시점에는제 1스위치，제 2스위치모두 on된다.이때본 발명의컨버터회로의동작을살펴보면,제 1다이오드와제 2다이오드모두 개방된다.이를나타낸것이도 11이다.도 11과같은경우제 1, 2스위치및제 1， 2다이오드에걸리는전압은다음과같다.
[84] Vsl = 0
[85] Vs2 = 0
[86] VD1 = Vcl + Vol
[87] VD2 = Vc2 + Vo2
[88] 제 1, 2스위치는단락되므로전압이 0이고제 1, 2다이오드는전체회로에서의 각소자의전압과비교하면상술한크기의전압이걸린다.
[89]
[90] 2번시점에서는제 1스위치는 on상태를유지하면서제 2스위치는 off상태로 전환된다ᅳ한편,이러한스위칭상태에서제 1다이오드는개방되고，제 2
다이오드단락된다.이는도 12에나타나있다.이때제 1， 2스위치및제 1, 2 다이오드에걸리는전압은다음과같다.
[91] Vsl = 0
[92] Vs2 = Vc2 + Vo2
[93] VD1 = Vcl + Vol
[94] VD2 = 0
[95]
[96] 3번시점에서는제 1스위치는 on상태를유지하면서，제 2스위치가 on상태로 전환된다.이경우제 1다이오드는개방된상태를유지하면서，제 2다이오드는 개방된형태로동작한다.이때의회로도는도 13에나타나있다.이때제 1, 2 스위치및제 1, 2다이오드에걸리는전압은아래와같다.
[97] Vsl = 0
[98] Vs2 = 0
[99] VD1 = Vcl + Vol
[100] VD2 = Vc2 + Vo2
[101]
[102] 4번시점에서는제 1스위치는 off상태로전환하고제 2스위치는 on상태로 유지된다.이때는 2번시점과마찬가지로제 1다이오드는개방되고，제 2 다이오드단락된다.각구성의전압은아래와같다.
[103] Vsl = Vcl + Vol
[104] Vs2 = 0
[105] VD1 = 0
[106] VD2 = Vc2 + Vo2
[107]
[108] 1번시점부터 4번시점까지 Vsl, Vs2, VDl, VD2를살펴보면， 0또는 Vcl + Vol, 또는 Vc2 + Vo2임을알수있다.
[109] 앞서살핀바와같이，정상상태에서각캐패시터의전압을고려하여제 1, 2 스위치및제 1， 2다이오드의각시점별전압을연산하면，도 5의실시예와 마찬가지로종래의구조에비해전압이절반으로줄어드는것을확인할수있다. 따라서스위칭손실을줄일수있다.
[110]
[111] 본발명의실시예들은예시의목적을위해개시된것으로본발명이속한기술 분야의통상의지식을가진자가본발명의기술사상범위내에서수정，변경， 부가가가능한부분까지본특허청구범위에속하는것으로보아야할것이다.
[112]
산업상이용가능성 [113] 본발명은컨버터회로에관한기술로서，에너지저장및변환산업에이용 가능하다.
[114]

Claims

청구범위
[청구항 1] 입력단의일측에연결되는입력인덕터;
상기입력인덕터및상기입력단의타측사이에직렬로연결되는 제 1스위치및제 2스위치;
상기제 1스위치와출력단의일측사이에직렬로연결되는제 1 캐패시터및제 1다이오드;
상기출력단의타측과상기입력단의타측사이에직렬로 연결되는제 2다이오드및제 2캐패시터;
상기출력단사이에연결되는제 1출력캐패시터및제 2출력 캐패시터;및
상기제 1캐패시터및제 1다이오드사이의노드와，상기제 2 캐패시터및상기제 2다이오드사이의노드사이에연결되는 출력인덕터;
를포함하고，
상기제 1스위치및제 2스위치사이의노드와상기제 1출력 캐패시터및제 2출력캐패시터사이의노드가연결되며， 상기제 1캐패시터가상기제 1스위치에，상기제 1다이오드가 출력단의일측에연결되고，상기제 2캐패시터가상기제 2 스위치에，상기제 2다이오드가출력단의타측에연결되는 3-레벨 세픽컨버터회로
[청구항 2] 청구항 1에있어서，
상기제 1스위치또는상기제 2스위치의 on/off를제어하기위한 제어부;
를더포함하는 3-레벨세픽컨버터회로
[청구항 3] 청구항 2에있어서，상기제어부는
상기제 1스위치와상기제 2스위치를기설정된주기에따라 on/off시키는 3-레벨세픽컨버터희로
[청구항 4] 청구항 3에있어서，상기제어부는
상기제 1스위치와상기제 2스위치의 on또는 off시점이반주기 차이나도록제어하는 3-레벨세픽컨버터회로
[청구항 5] 청구항 4에있어서，상기제어부는
상기제 1스위치와상기제 2스위치의 on지속시간이반주기 이하인 3-레벨세픽컨버터회로
[청구항 6] 청구항 4에있어서，상기제어부는
상기제 1스위치와상기제 2스위치의 on지속시간이반주기 이상 1주기이하인 3-레벨세픽컨버터회로
[청구항 7] 청구항 1에있어서,상기제 1다이오드는 애노드가상기제 1캐패시터에，캐소드가상기출력단의일측에 연결되는 3-레벨세픽컨버터회로
[청구항 8] 청구항 1에있어서，상기제 2다이오드는
애노드가상기출력단의타측에，캐소드가상기제 2캐패시터에 연결되는 3-레벨세픽컨버터회로
[청구항 9] 청구항 1에있어서，
상기제 1캐패시터와상기제 2캐패시터의용량이동일한 3-레벨 세픽컨버터회로
[청구항 10] 청구항 1에있어서,
상기제 1출력캐패시터와상기제 2출력캐패시터의용량이 동일한 3-레벨세픽컨버터회로
PCT/KR2015/006554 2015-02-09 2015-06-26 3-레벨 세픽 컨버터 회로 WO2016129758A1 (ko)

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