WO2016086457A1 - 带二次滤波电路的牵引变流器 - Google Patents

带二次滤波电路的牵引变流器 Download PDF

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Publication number
WO2016086457A1
WO2016086457A1 PCT/CN2014/094047 CN2014094047W WO2016086457A1 WO 2016086457 A1 WO2016086457 A1 WO 2016086457A1 CN 2014094047 W CN2014094047 W CN 2014094047W WO 2016086457 A1 WO2016086457 A1 WO 2016086457A1
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Prior art keywords
circuit
parallel
traction
rectifier
filter
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PCT/CN2014/094047
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English (en)
French (fr)
Inventor
姬惠刚
高永军
张桂成
管俊青
张瑞峰
顾秀江
张创业
王惠萍
孟丹
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永济新时速电机电器有限责任公司
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Publication of WO2016086457A1 publication Critical patent/WO2016086457A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation

Definitions

  • the invention relates to the technical field of high-speed motor trains, in particular to a traction converter with a secondary filter circuit.
  • High-speed EMU technology has developed rapidly in recent years, and traction converters are an important part of high-speed EMUs.
  • the traction converter outputs three-phase alternating current to drive the traction motor in the high-speed EMU, thereby driving the operation of the EMU.
  • the traction converter is generally composed of a rectifier, an inverter, and the like.
  • the rectifier rectifies the input alternating current
  • the inverter is used to convert the rectified direct current into alternating current to drive the traction motor to operate.
  • the voltage of the rectifier rectified output still contains a large number of second harmonic components. These second harmonic components will cause distortion of the voltage waveform, which will not only damage other devices in the converter, but also cause traction converters. An abnormal operation has occurred, which affects the operation of the traction motor. Therefore, it is important to ensure that the rectifier output voltage waveform is stable and minimize harmonics, which is critical for the reliable operation of the traction motor and the safety of the device of the traction converter.
  • the present invention provides a traction converter with a secondary filter circuit for achieving safe and reliable control of the traction motor.
  • the invention provides a traction converter with a secondary filter circuit, comprising:
  • the rectifier circuit includes at least one four-quadrant rectifier in parallel, and two output ends of each of the four-quadrant rectifiers are respectively connected to a positive terminal and a negative terminal of the bus bar;
  • the secondary filter circuit is connected between the positive terminal and the negative terminal of the bus bar for filtering the second harmonic in the bus voltage
  • the secondary filtering circuit includes at least two filter capacitors connected in parallel, at least two filter inductors connected in parallel, and at least one discharge resistor, the at least one discharge resistor being connected in series and then in parallel Connected to both ends of the filter capacitor, the filter inductor is connected in series with the filter capacitor;
  • the inverter circuit includes at least one three-phase inverter connected in parallel, and two input ends of each of the three-phase inverters are respectively connected to a positive end and a negative end of the bus bar, and each of the three-phase inverse
  • the three-phase outputs of the transformer are respectively connected to corresponding three-phase inputs of at least one traction motor.
  • the traction converter with a secondary filter circuit comprises a rectifier circuit, a secondary filter circuit and an inverter circuit which are sequentially connected.
  • the rectifier circuit includes at least one four-quadrant rectifier connected in parallel;
  • the secondary filter circuit is configured to filter the second harmonic in the output voltage of the rectifier circuit, so that the voltage input to the inverter circuit is more accurate and stable;
  • the inverter circuit includes at least A parallel inverter for converting the DC power input thereto into AC power to drive the traction motor to operate.
  • FIG. 1 is a schematic structural diagram of a circuit of a first embodiment of a traction converter with a secondary filter circuit according to the present invention
  • FIG. 2 is a schematic diagram showing the circuit structure of a second embodiment of a traction converter with a secondary filter circuit according to the present invention.
  • FIG. 1 is a schematic structural diagram of a circuit of a first embodiment of a traction converter according to the present invention. As shown in FIG. 1, the traction converter includes:
  • the rectifier circuit 1 includes at least one four-quadrant rectifier in parallel, and two output ends of each of the four-quadrant rectifiers are respectively connected to a positive terminal VDC+ and a negative terminal of the bus bar. VDC-.
  • the number of four-quadrant rectifiers is two, and two four-quadrant rectifiers are denoted as 11 and 12, respectively.
  • the first four-quadrant rectifier 11 and the second four-quadrant rectifier 12 are connected in parallel, and the first output terminal E1 and the second output terminal F1 of the first four-quadrant rectifier 11 are respectively connected to the positive terminal VDC+ and the negative terminal VDC- of the bus bar, respectively.
  • the first input terminal A3 and the second input terminal B3 of the four-quadrant rectifier 11 are configured to receive an input voltage; the first output terminal E2 and the second output terminal F2 of the second four-quadrant rectifier 12 are respectively connected to the positive terminal VDC+ and the negative terminal of the busbar.
  • the first input terminal A4 and the second input terminal B4 of the second four-quadrant rectifier 12 are for receiving another input voltage.
  • the inputs of the two four-quadrant rectifiers are all alternating currents with a frequency of 50 Hz.
  • the secondary filter circuit 2 is connected between the positive terminal VDC+ and the negative terminal VDC- of the bus bar for filtering out the output voltage of the rectifier circuit 1, that is, the second harmonic in the bus voltage;
  • the secondary filter circuit 2 includes at least two filter capacitors connected in parallel, at least two filter inductors connected in parallel, and at least one discharge resistor, the at least one discharge resistor being connected in series and then connected in parallel at both ends of the filter capacitor, the filtering An inductor is connected in series with the filter capacitor.
  • the number of the filter capacitors is three, the number of the filter inductors is two, the number of the discharge resistors is two, and the three filter capacitors are respectively represented as C1, C2, and C3.
  • the two filter inductors are denoted as L1 and L2, respectively, and the two discharge resistors are denoted as R1 and R2, respectively.
  • the value of the capacitors C1, C2, and C3 in parallel is set to C.
  • the value of the inductances L1 and L2 in parallel is set to L. Regardless of the influence of the resistance, the resonance point of the secondary filter circuit is designed near the second harmonic, that is, 100 Hz, then the resonant frequency:
  • a set of suitable values of capacitance and inductance can be obtained by considering the cost and volume of the capacitor and the inductor.
  • the discharge resistors R1 and R2 mainly discharge the both ends of the filter capacitor.
  • the secondary filter circuit adopts the connection mode using multiple capacitors and inductors in parallel, which is more reliable than the method of using single capacitors and single inductors.
  • the main reason is that the parallel connection makes the current flowing through each component smaller and improves the life of the component.
  • the secondary filter circuit filters out the second harmonic of the bus voltage, thereby reducing waveform distortion. Improve the control performance of the overall traction converter.
  • the inductance and capacitance in the secondary filter loop adopt multiple parallel connections.
  • the discharge resistor adopts a double resistor series connection method, which improves the life of the device and enhances the reliability of the system.
  • the inverter circuit 3 includes at least one three-phase inverter connected in parallel, and two input ends of each of the three-phase inverters are respectively connected to a positive terminal VDC+ and a negative terminal VDC- of the bus bar.
  • the three-phase output terminals of each of the three-phase inverters are respectively connected to corresponding three-phase input ends of at least one traction motor. Taking the number of three-phase inverters included in the inverter circuit as two as an example, the first three-phase inverter 31 and the second three-phase inverter 32 are respectively.
  • the first input end A5 and the second input end B5 of the first three-phase inverter 31 are respectively connected to the positive terminal VDC+ and the negative terminal VDC- of the bus, and the three-phase output of the first three-phase inverter Connecting at least one traction motor;
  • the first input terminal A6 and the second input terminal B6 of the second three-phase inverter 32 are respectively connected to the positive terminal VDC+ and the negative terminal VDC- of the bus bar, and the second three-phase inverter
  • the three-phase output of the unit 32 is coupled to at least one traction motor.
  • the traction converter provided in this embodiment includes a rectifier circuit, a secondary filter circuit and an inverter circuit which are sequentially connected.
  • the rectifier circuit includes at least one four-quadrant rectifier connected in parallel;
  • the secondary filter circuit is configured to filter the second harmonic in the output voltage of the rectifier circuit, so that the voltage input to the inverter circuit is more accurate and stable;
  • the inverter circuit includes at least A parallel inverter for converting the voltage input to it to AC power to drive the traction motor.
  • the traction converter further includes: a supporting capacitor 4, the supporting capacitor 4 is connected in parallel with the output of the secondary filter circuit 2 and connected between the positive terminal and the negative terminal of the bus bar, the support capacitor 4 for removing ripple in the output voltage.
  • the traction converter further includes: a first pre-charging circuit 51 and a second pre-charging circuit 52, configured to control a variation amplitude of the input current when the traction converter is initially powered up, so as to change the input current The amplitude is not too large and damages the device.
  • the input terminal A1 of the first pre-charging circuit 51 is connected to the secondary side output winding P1 of the traction transformer, and the output terminal B1 of the first pre-charging circuit 52 is connected to the first input terminal A3 of the first four-quadrant rectifier 11.
  • the second input end B3 of the first four-quadrant rectifier 11 is connected to the secondary side output winding N1 of the traction transformer;
  • the input terminal A2 of the second pre-charging circuit 52 is connected to the secondary side output winding P2 of the traction transformer, and the output terminal B2 of the second pre-charging circuit 52 is connected to the first input terminal A4 of the second four-quadrant rectifier 12.
  • the second input end of the second four-quadrant rectifier 12 is connected to the secondary side output winding N2 of the traction transformer of B4.
  • the first pre-charging circuit 51 includes a first switch K1, a second switch K2 and a resistor R3, and the second pre-charge circuit 52 includes a third switch K3;
  • the first switch K1 and the resistor R3 are connected in series and connected in parallel with the second switch K2.
  • the first switch K1 in the first pre-charging circuit 51 is closed, the second switch K2 is turned off, and the third switch K3 of the second pre-charging circuit 52 is turned off.
  • the current reaches the first four-quadrant rectifier 11 through the resistor R3, so that the current variation amplitude (di/dt) at the start of power-on is not excessive, reducing the hazard to each device.
  • the switch K1 is disconnected, and K2 and K3 are closed.
  • the resistance R3 ranges from 10 ⁇ to 50 ⁇ .
  • the rectifier circuit 1 in this embodiment is composed of two parallel four-quadrant rectifiers.
  • the first four-quadrant rectifier 11 and the second four-quadrant rectifier 12 are respectively composed of eight insulated gates.
  • the first four-quadrant rectifier 11 is composed of an IGBT characterized by S1-S8, and the second four-quadrant rectifier 12 is composed of an IGBT characterized by S9-S16.
  • the emitter of S1 is coupled to the collector of S3
  • the emitter of S2 is coupled to the collector of S4
  • the emitter of S5 is coupled to the collector of S7
  • the emitter of S6 is coupled to the emitter of S8.
  • the collectors are connected together.
  • the emitters of S1 and S2 are connected together and connected to the first input terminal A3 of the first four-quadrant rectifier 11; the emitters of S5 and S6 are connected together, and the second input terminal B3 of the first four-quadrant rectifier 11 Connecting; the collectors of S1, S2, S5 and S6 are connected together and connected to the first output E1 of the first four-quadrant rectifier 11; the emitters of S3, S4, S7 and S8 are connected together and first The second output terminal F1 of the four-quadrant rectifier 11 is connected.
  • a similar connection relationship is also applicable to the second four-quadrant rectifier 12, and the specific connection relationship is as shown in FIG. 2 and will not be described again.
  • the rectifier circuit is composed of two cascaded four-quadrant rectifiers, and the phase shift angle is controlled by Pulse-Width Modulation (PWM) technology, and the input currents of the two rectifiers are high harmonic.
  • PWM Pulse-Width Modulation
  • the peaks and troughs of the waves are just staggered so that the higher harmonics of the current can cancel each other out.
  • the switching frequency of the high-power switching device is relatively low, in order to increase the system capacity and reduce the harmonic of the input current of the grid side
  • the content is usually multiplexed to the rectifier.
  • a two-folded pulse rectifier that is, two four-quadrant rectifiers, is used, and the triangular carrier phases of the two rectifiers are shifted from each other by a phase angle of ⁇ /2, and then the waveform generation method and carrier phase shift in the PWM technology are utilized.
  • the stepped wave obtained by the phase shift superposition in the technology, so that the peaks and troughs of the input current higher harmonics of the two rectifiers are exactly shifted, so that some harmonics in the harmonic content of the primary current of the transformer cancel each other out.
  • the inverter circuit 3 is composed of two parallel three-phase inverters, as shown in FIG. 2, the first three-phase inverter 31 and the second three.
  • the phase inverters 32 are each composed of six IGBTs, that is, the first three-phase inverter 31 is composed of S17-S22, and the second three-phase inverter 32 is composed of S23-S28.
  • the emitter of S17 is connected to the collector of S20
  • the emitter of S18 is connected to the collector of S21
  • the emitter of S19 is connected to the collector of S22.
  • the collectors of S17, S18 and S19 are connected together and connected to the first input terminal A5 of the first three-phase inverter 31, and the emitters of S20, S21 and S22 are connected together, and the first three The second input terminal B5 of the phase inverter 31 is connected.
  • the emitters of S17, S18 and S19 are respectively the three-phase outputs of the first three-phase inverter 31, and are respectively connected to corresponding three-phase inputs of at least one traction motor.
  • the emitter of S23 is connected to the collector of S26
  • the emitter of S24 is connected to the collector of S27
  • the emitter of S25 is connected to the collector of S28.
  • the collectors of S23, S24 and S25 are connected together and connected to the first input A6 of the second three-phase inverter 32
  • the emitters of S26, S27 and S28 are connected together, and the second three phase The second input B6 of the inverter 32 is connected.
  • the emitters of S23, S24 and S25 are respectively the three-phase outputs of the second three-phase inverter 32, and are respectively connected to corresponding three-phase inputs of at least one traction motor.
  • the main circuit of the traction converter includes a pre-charging circuit, a rectifying circuit, a secondary filtering circuit, a supporting capacitor and an inverter circuit which are sequentially connected.
  • the pre-charging circuit is used to control the variation range of the input current when the traction converter is initially powered up, so that the variation of the current of the input rectifying circuit is not excessively large, which is beneficial to reducing damage to the components of the converter;
  • the circuit includes two four-quadrant rectifiers connected in parallel. By adopting pulse width modulation technology to control the phase shift angle, the peaks and troughs of the input current higher harmonics of the two rectifiers are exactly staggered, so that the harmonic content of the primary side current of the transformer is made.
  • the bus voltage processing circuit includes a secondary filter circuit and a supporting capacitor for filtering the second harmonic and ripple in the voltage, so that the input inverter
  • the inverter circuit includes two inverters connected in parallel for converting the DC power input thereto into AC power to drive the traction motor to operate.

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Abstract

一种带二次滤波电路（2）的牵引变流器，包括：依次连接在母线的正端（VDC+）和负端（VDC-）间的整流电路（1）、二次滤波电路和逆变电路（3）；整流电路包括并联的至少一个四象限整流器（11、12）；二次滤波电路，用于滤除二次谐波，包括至少两个并联连接的滤波电容（C1、C2、C3）、至少两个并联连接的滤波电感（L1、L2）和至少一个放电电阻（R1、R2），至少一个放电电阻串联后并联连接在滤波电容的两端，滤波电感与滤波电容串联；逆变电路包括并联的至少一个三相逆变器（31、32），分别连接在至少一个牵引电机。通过滤除母线电压中的二次谐波，使得输入逆变器的电压准确可靠，有利于保证对牵引电机的安全可靠驱动。

Description

带二次滤波电路的牵引变流器 技术领域
本发明涉及高速动车组技术领域，尤其涉及一种带二次滤波电路的牵引变流器。
背景技术
高速动车组技术近年来得到了飞速的发展，牵引变流器是高速动车组的重要组成部分。牵引变流器输出三相交流电驱动高速动车组内的牵引电机运行，从而驱动动车组的运行。
牵引变流器一般由整流器、逆变器等组成。其中，整流器对输入的交流电进行整流处理，逆变器用于将整流处理后的直流电变为交流电，以驱动牵引电机运行。但是，整流器整流输出的电压中仍会含有大量的二次谐波分量，这些二次谐波分量会导致电压波形畸变，不但会对变流器中其他器件造成损害，还会导致牵引变流器运行出现异常，影响牵引电机的运行。因此，保证整流器输出电压波形稳定，尽量降低谐波，对于牵引电机的可靠运行以及牵引变流器的器件安全至关重要。
发明内容
针对上述存在的问题，本发明提供一种带二次滤波电路的牵引变流器，用以实现对牵引电机的安全、可靠控制。
本发明提供了一种带二次滤波电路的牵引变流器，包括：
依次连接的整流电路、二次滤波电路和逆变电路；
所述整流电路包括并联的至少一个四象限整流器，每个所述四象限整流器的两个输出端分别连接在母线的正端和负端；
所述二次滤波电路连接在所述母线的正端和负端间，用于滤除母线电压中的二次谐波；
所述二次滤波电路包括至少两个并联连接的滤波电容、至少两个并联连接的滤波电感和至少一个放电电阻，所述至少一个放电电阻串联后并联 连接在所述滤波电容的两端，所述滤波电感与所述滤波电容串联；
所述逆变电路包括并联的至少一个三相逆变器，每个所述三相逆变器的两个输入端分别连接在所述母线的正端和负端，每个所述三相逆变器的三相输出端分别连接在至少一个牵引电机的对应三相输入端。
本发明提供的带二次滤波电路的牵引变流器，包括依次连接的整流电路、二次滤波电路和逆变电路。其中，整流电路包括并联连接的至少一个四象限整流器；二次滤波电路，用于滤除整流电路输出电压中的二次谐波，使得输入逆变电路的电压更加准确稳定；逆变电路包括至少一个并联的逆变器，用于将输入其的直流电转换为交流电以驱动牵引电机运行。通过滤除输入电压中的二次谐波，使得输入逆变器的电压准确可靠，有利于保证对牵引电机的安全可靠驱动。
附图说明
图1为本发明带二次滤波电路的牵引变流器实施例一的电路结构示意图；
图2为本发明带二次滤波电路的牵引变流器实施例二的电路结构示意图。
具体实施方式
为使本发明实施例的目的、技术方案和优点更加清楚，下面将结合本发明实施例中的附图，对本发明实施例中的技术方案进行清楚、完整地描述，显然，所描述的实施例是本发明一部分实施例，而不是全部的实施例。基于本发明中的实施例，本领域普通技术人员在没有作出创造性劳动前提下所获得的所有其他实施例，都属于本发明保护的范围。
图1为本发明牵引变流器实施例一的电路结构示意图，如图1所示，该牵引变流器包括：
依次连接的整流电路1、二次滤波电路2和逆变电路3；
具体地，其中，所述整流电路1包括并联的至少一个四象限整流器，每个所述四象限整流器的两个输出端分别连接在母线的正端VDC+和负端 VDC-。
本实施例中，以四象限整流器的数量为2个为例，两个四象限整流器分别表示为11和12。第一四象限整流器11和第二四象限整流器12并联，且第一四象限整流器11的第一输出端E1和第二输出端F1分别连接在母线的正端VDC+和负端VDC-，第一四象限整流器11的第一输入端A3和第二输入端B3用于接收输入电压；第二四象限整流器12的第一输出端E2和第二输出端F2分别连接在母线的正端VDC+和负端VDC-，第二四象限整流器12的第一输入端A4和第二输入端B4用于接收另一输入电压。其中，这两个四象限整流器的输入都是频率为50Hz的交流电。
具体地，所述二次滤波电路2连接在所述母线的正端VDC+和负端VDC-间，用于滤除所述整流电路1输出电压即母线电压中的二次谐波；所述二次滤波电路2包括至少两个并联连接的滤波电容、至少两个并联连接的滤波电感和至少一个放电电阻，所述至少一个放电电阻串联后并联连接在所述滤波电容的两端，所述滤波电感与所述滤波电容串联。具体来说，以所述滤波电容的数量为3个，所述滤波电感的数量为2个，所述放电电阻的数量为2个为例，3个滤波电容分别表示为C1、C2和C3，2个滤波电感分别表示为L1和L2，2个放电电阻分别表示为R1和R2。
将电容C1、C2和C3并联后的值定为C。电感L1、L2并联后的值定为L。暂不考虑电阻的影响，二次滤波电路的谐振点设计在二次谐波附近，即100Hz，则谐振频率：
Figure PCTCN2014094047-appb-000001
通过以上公式就可以得到多组L与C的值。通过考虑到电容与电感的成本以及体积等因素就可以得到一组合适的电容、电感的值。
另外，放电电阻R1和R2主要是对滤波电容两端进行放电。
在实际应用中，滤波电容的取值范围可以是：C1＝C2＝C3＝(1-3mF)；电感的取值范围可以是：L1＝L2＝(0.5-1.5mH)；放电电阻的取值范围可以是：R2＝R3＝(10-30kΩ)。
本实施例中，该二次滤波电路采用这种使用多电容、电感并联的连接方式，比使用单电容、单电感的方式可靠性更强。主要原因是并联的连接方式使得流经每个元件的电流更小，提高了元件的寿命。
通过该二次滤波电路滤除了母线电压的二次谐波，减少了波形畸变， 提高了整体牵引变流器的控制性能。二次滤波回路中的电感和电容采用多个并联的方式，放电电阻采用双电阻串联的方式，提高了器件的寿命，也增强了系统的可靠性。
再具体地，所述逆变电路3包括并联的至少一个三相逆变器，每个所述三相逆变器的两个输入端分别连接在所述母线的正端VDC+和负端VDC-，每个所述三相逆变器的三相输出端分别连接在至少一个牵引电机的对应三相输入端。以逆变电路包括的三相逆变器的数量为2个为例，分别为第一三相逆变器31和第二三相逆变器32。所述第一三相逆变器31的第一输入端A5和第二输入端B5分别连接在母线的正端VDC+和负端VDC-，所述第一三相逆变器的三相输出端连接至少一个牵引电机；所述第二三相逆变器32的第一输入端A6和第二输入端B6分别连接在母线的正端VDC+和负端VDC-，所述第二三相逆变器32的三相输出端连接至少一个牵引电机。
本实施例提供的牵引变流器，包括依次连接的整流电路、二次滤波电路和逆变电路。其中，整流电路包括并联连接的至少一个四象限整流器；二次滤波电路，用于滤除整流电路输出电压中的二次谐波，使得输入逆变电路的电压更加准确稳定；逆变电路包括至少一个并联的逆变器，用于将输入其的电压转换为交流电以驱动牵引电机运行。通过滤除输入电压中的二次谐波，使得输入逆变器的电压准确可靠，有利于保证对牵引电机的安全可靠驱动。
图2为本发明牵引变流器实施例二的电路结构示意图，如图2所示，在图1所示实施例的基础上，该牵引变流器还包括：支撑电容4，所述支撑电容4与所述二次滤波电路2的输出并联，并连接在所述母线的正端和负端间，所述支撑电容4用于去除所述输出电压中的纹波。
进一步地，该牵引变流器还包括：第一预充电电路51和第二预充电电路52，用于在所述牵引变流器初始上电时控制输入电流的变化幅度，使输入电流的变化幅度不至于过大，损坏器件。
所述第一预充电电路51的输入端A1与牵引变压器的二次侧输出绕组P1连接，所述第一预充电电路52的输出端B1与第一四象限整流器11的第一输入端A3连接，所述第一四象限整流器11的第二输入端B3与所述牵引变压器的二次侧输出绕组N1连接；
所述第二预充电电路52的输入端A2与牵引变压器的二次侧输出绕组P2连接，所述第二预充电电路52的输出端B2与第二四象限整流器12的第一输入端A4连接，所述第二四象限整流器12的第二输入端与B4所述牵引变压器的二次侧输出绕组N2连接。
具体地，所述第一预充电电路51包括第一开关K1、第二开关K2和电阻R3，所述第二预充电电路52包括第三开关K3；
所述第一开关K1和所述电阻R3串联后与所述第二开关K2并联。
实际使用时，当牵引变流器上电时，第一预充电电路51中的第一开关K1闭合，第二开关K2断开，第二预充电电路52的第三开关K3断开。电流经过电阻R3到达第一四象限整流器11，使得开始上电时的电流变化幅度(di/dt)不至于过大，减小对各器件的危害。3-10ms后开关K1断开，K2、K3闭合。电阻R3的取值范围为10Ω-50Ω。
具体地，本实施例中的整流电路1是由两个并联的四象限整流器组成，如图2所示，第一四象限整流器11和第二四象限整流器12都是分别由8个绝缘栅双极型晶体管(IGBT)组成的，即第一四象限整流器11由S1-S8所表征的IGBT组成，第二四象限整流器12由S9-S16所表征的IGBT组成。具体来说，S1的发射极与S3的集电极连接在一起，S2的发射极与S4的集电极连接在一起，S5的发射极与S7的集电极连接在一起，S6的发射极与S8的集电极连接在一起。其中，S1和S2的发射极连接在一起，并与第一四象限整流器11第一输入端A3连接；S5和S6的发射极连接在一起，并与第一四象限整流器11第二输入端B3连接；S1、S2、S5和S6的集电极连接在一起，并与第一四象限整流器11的第一输出端E1连接；S3、S4、S7和S8的发射极连接在一起，并与第一四象限整流器11的第二输出端F1连接。同理，类似的连接关系也适用于第二四象限整流器12，具体的连接关系如图2中所示，不再赘述。
本实施例中，整流电路由两台级联的四象限整流器构成，通过采用脉宽调制(Pulse-Width Modulation，以下简称PWM)技术对移相角的控制，两台整流器的输入电流高次谐波的波峰和波谷正好错开，使电流的高次谐波能够相互抵消一部分。具体来说，在电力牵引交流传动系统中，由于大功率的开关器件的开关频率比较低，为了提高系统容量和减小网侧输入电流的谐波 含量，通常对整流器采用多重化技术。本实施例具体采用两重化的脉冲整流器，即两个四象限整流器，将两台整流器的三角载波相位相互错开一个π/2的相位角，然后利用PWM技术中的波形生成方式和载波移相技术中的移相叠加得到的阶梯波，从而两台整流器的输入电流高次谐波的波峰和波谷正好错开，使变压器一次侧电流的谐波含量中部分谐波相互抵消。
再具体来说，在本实施例的牵引变流器中，逆变电路3由两个并联的三相逆变器组成，如图2所示，第一三相逆变器31和第二三相逆变器32分别由6个IGBT组成，即第一三相逆变器31由S17-S22组成，第二三相逆变器32由S23-S28组成。其中，对于第一三相逆变器31来说，S17的发射极与S20的集电极连接在一起，S18的发射极与S21的集电极连接在一起，S19的发射极与S22的集电极连接在一起，S17、S18和S19的集电极连接在一起，并与第一三相逆变器31的第一输入端A5连接，S20、S21和S22的发射极连接在一起，并与第一三相逆变器31的第二输入端B5连接。S17、S18和S19的发射极分别为第一三相逆变器31的三相输出端，分别连接至少一个牵引电机的对应三相输入端。
相应的，对于第二三相逆变器32，S23的发射极与S26的集电极连接在一起，S24的发射极与S27的集电极连接在一起，S25的发射极与S28的集电极连接在一起，S23、S24和S25的集电极连接在一起，并与第二三相逆变器32的第一输入端A6连接，S26、S27和S28的发射极连接在一起，并与第二三相逆变器32的第二输入端B6连接。S23、S24和S25的发射极分别为第二三相逆变器32的三相输出端，分别连接至少一个牵引电机的对应三相输入端。
本实施例中，该牵引变流器主电路包括依次连接的预充电电路、整流电路、二次滤波电路、支撑电容和逆变电路。其中，预充电电路用于在牵引变流器初始上电时控制输入电流的变化幅度，使得输入整流电路的电流的变化幅度不至于过大，有利于降低对变流器各器件的损坏；整流电路包括并联连接的两个四象限整流器，通过采用脉宽调制技术对移相角的控制，两台整流器的输入电流高次谐波的波峰和波谷正好错开，使变压器一次侧电流的谐波含量中部分谐波相互抵消；母线电压处理电路包括二次滤波电路和支撑电容，用于滤除电压中的二次谐波和纹波，使得输入逆变电 路的电压更加准确稳定；逆变电路包括两个并联的逆变器，用于将输入其的直流电转换为交流电以驱动牵引电机运行。通过控制输入电流的变化幅度、滤除输入电流中的高次谐波、滤除中间母线电压二次谐波、纹波，使得输入逆变器的电压准确可靠，有利于保证对牵引电机的安全可靠驱动。
最后应说明的是：以上各实施例仅用以说明本发明的技术方案，而非对其限制；尽管参照前述各实施例对本发明进行了详细的说明，本领域的普通技术人员应当理解：其依然可以对前述各实施例所记载的技术方案进行修改，或者对其中部分或者全部技术特征进行等同替换；而这些修改或者替换，并不使相应技术方案的本质脱离本发明各实施例技术方案的范围。

Claims (6)

  1. 一种带二次滤波电路的牵引变流器，其特征在于，包括：
    依次连接的整流电路、二次滤波电路和逆变电路；
    所述整流电路包括并联的至少一个四象限整流器，每个所述四象限整流器的两个输出端分别连接在母线的正端和负端；
    所述二次滤波电路连接在所述母线的正端和负端间，用于滤除所述母线电压中的二次谐波；
    所述二次滤波电路包括至少两个并联连接的滤波电容、至少两个并联连接的滤波电感和至少一个放电电阻，所述至少一个放电电阻串联后并联连接在所述滤波电容的两端，所述滤波电感与所述滤波电容串联；
    所述逆变电路包括并联的至少一个三相逆变器，每个所述三相逆变器的两个输入端分别连接在所述母线的正端和负端，每个所述三相逆变器的三相输出端分别连接在至少一个牵引电机的对应三相输入端。
  2. 根据权利要求1所述的牵引变流器，其特征在于，还包括：支撑电容，所述支撑电容与所述二次滤波电路的输出并联，并连接在所述母线的正端和负端间，所述支撑电容用于去除所述母线电压中的纹波。
  3. 根据权利要求1所述的牵引变流器，其特征在于，所述滤波电容的数量为3个，所述滤波电感的数量为2个，所述放电电阻的数量为2个。
  4. 根据权利要求1所述的牵引变流器，其特征在于，所述四象限整流器的数量为2个，所述三相逆变器的数量为2个。
  5. 根据权利要求4所述的牵引变流器，其特征在于，还包括：第一预充电电路和第二预充电电路，用于在所述牵引变流器初始上电时控制输入电流的变化幅度；
    所述第一预充电电路的输入端与牵引变压器的二次侧输出绕组P1连接，所述第一预充电电路的输出端与第一四象限整流器的第一输入端连接，所述第一四象限整流器的第二输入端与所述牵引变压器的二次侧输出绕组N1连接；
    所述第二预充电电路的输入端与牵引变压器的二次侧输出绕组P2连接，所述第二预充电电路的输出端与第二四象限整流器的第一输入端连接，所述第二四象限整流器的第二输入端与所述牵引变压器的二次侧输出 绕组N2连接。
  6. 根据权利要求5所述的牵引变流器，其特征在于，所述第一预充电电路包括第一开关、第二开关和电阻，所述第二预充电电路包括第三开关；
    所述第一开关和所述电阻串联后与所述第二开关并联。
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CN112255530B (zh) * 2020-10-13 2024-03-01 中车株洲电力机车研究所有限公司 一种高速磁浮牵引系统的电气设备自检装置和方法
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