WO2015103804A1 - Méthode parallèle d'égalisation de canal et d'estimation de décalage de fréquence conjointes basée sur lms - Google Patents

Méthode parallèle d'égalisation de canal et d'estimation de décalage de fréquence conjointes basée sur lms Download PDF

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WO2015103804A1
WO2015103804A1 PCT/CN2014/072120 CN2014072120W WO2015103804A1 WO 2015103804 A1 WO2015103804 A1 WO 2015103804A1 CN 2014072120 W CN2014072120 W CN 2014072120W WO 2015103804 A1 WO2015103804 A1 WO 2015103804A1
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signal
frequency offset
parallel
branch
data
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PCT/CN2014/072120
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English (en)
Chinese (zh)
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吴晨雨
许渤
刘芯羽
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电子科技大学
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03178—Arrangements involving sequence estimation techniques
    • H04L25/03248—Arrangements for operating in conjunction with other apparatus
    • H04L25/03273—Arrangements for operating in conjunction with other apparatus with carrier recovery circuitry
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03012—Arrangements for removing intersymbol interference operating in the time domain
    • H04L25/03114—Arrangements for removing intersymbol interference operating in the time domain non-adaptive, i.e. not adjustable, manually adjustable, or adjustable only during the reception of special signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L2025/03592—Adaptation methods
    • H04L2025/03598—Algorithms
    • H04L2025/03611—Iterative algorithms
    • H04L2025/03636—Algorithms using least mean square [LMS]

Definitions

  • the invention belongs to the technical field of optical burst receivers, and more particularly to a joint parallelization method based on LMS (Least Mean Square) for channel equalization and frequency offset estimation. Background technique
  • PDM-QPSK polarization multiplexing-four-phase absolute phase shift keying coherent optical transmission system
  • the transmission signal is mainly affected by the linear damage of the Chromatic Dispersion (CD) and the Polarization Mode Dispersion (PMD) of the fiber and the frequency offset generated by the transceiver laser. Impact, these two problems seriously affect the performance of the optical receiver.
  • the adaptive equalization technique can basically eliminate crosstalk between codes caused by dispersion, and the frequency offset estimation technique can be used to solve the effect of frequency offset. Since the equalizer and the frequency offset estimator interact with each other, a joint algorithm of time domain equalization and frequency offset estimation can be used.
  • FIG. 1 is a system block diagram of an optical burst receiver.
  • the input signal 0 of the receiver is a signal in which two PDM-QPSK signals whose polarization directions are perpendicular to each other are polarization-coupled and transmitted over a certain distance of the optical fiber channel.
  • the optical signal is affected by factors such as dispersion, polarization mode dispersion, and optical amplifier noise, resulting in degradation of the quality of the transmitted signal.
  • the PDM-QPSK signal r(t) enters the 90-degree mixer with the FTLO (fast tunable laser) light wave for coherent demodulation.
  • the four signals after coherent demodulation are subjected to AD sampling and quantization.
  • the sampled and quantized 4-channel signals /x, Qx, ly, respectively represent the in-phase and quadrature-modulated signals of the two polarization states x, _y, which enter the digital signal processing module for channel equalization.
  • Frequency Offset Estimation (FOE) and compensation, and the final phase decision recovers the transmitted data.
  • FOE Frequency Offset Estimation
  • a joint algorithm based on LMS for channel equalization and frequency offset estimation is an effective method to improve the performance of coherent optical receivers.
  • a digital signal processing algorithm is implemented using an FPGA (Field-Programmable Gate Array) or an application-specific integrated circuit
  • FPGA Field-Programmable Gate Array
  • the calculation speed and chip area are two main problems that are mutually constrained. Therefore, it is necessary to choose between performance and implementation complexity. Due to the high rate characteristics of fiber-optic communication, the 112Gb/s PDM-QPSK fiber transmission system is taken as an example.
  • the symbol rate of each of the four signals after coherent demodulation is 28G/S, and the four branch electrical signals need to be first.
  • each branch signal rate is up to 56G / S, so the symbol entering the equalizer is a discrete signal with a symbol rate of 56G / S.
  • the subsequent digital signal processing unit (DSPU) cannot handle the rate in hardware, so parallel processing must be used.
  • parallel processing must be used.
  • the algorithm must meet the requirements of parallel processing.
  • the update of the equalizer tap coefficients and the frequency offset estimation algorithm based on the pre-decision all require signal feedback.
  • the delay caused by the feedback has a great influence on the performance of the system. Therefore, in the specific implementation design of the optical burst receiver, the effects of parallel and feedback delay on receiver performance must also be considered. Summary of the invention
  • the object of the present invention is to overcome the deficiencies of the prior art and provide a joint parallel method for channel equalization and frequency offset estimation based on LMS, which reduces the influence of data signal processing hardware on system performance.
  • the present invention is based on an LMS-based joint equalization method for channel equalization and frequency offset estimation, including the following steps:
  • the frequency offset estimation module performs frequency offset estimation on the equalized signal 3 ⁇ 4 according to the known training symbol e , and obtains a cumulative phase error “3 ⁇ 4 and a frequency offset estimation value ⁇ cauliflower ;
  • +1 respectively represent the equalizer tap coefficients used in the “+ 1 group, the first group” parallel signal; the delay indicating the error signal; the set iteration length, which is a positive number; represents the N branches
  • the number of error signals selected to participate in the tap coefficient calculation 1 ⁇ ⁇ N, 1 ⁇ C ⁇ N C ;
  • V(n - D, i c ) denotes the observation vector corresponding to DJc , f(n - denotes f(n - Conjugation of D, i c );
  • step S1.7 determining whether the training sequence is processed, if not processed, returning to step S 1.2 to continue processing the next set of parallel signals, if the processing is completed, proceed to step S2;
  • the data transmitting end inserts a training symbol into the data symbol, and the insertion method is: grouping N sending symbols into groups, and then dividing the N sending symbols into R groups, and each group of sending symbols includes one training. Symbol, the serial number of the R training symbols in the parallel symbol is recorded as i ⁇ r ⁇ w;
  • S2.2 transmitting a data signal to the optical burst receiver, performing serial-to-parallel conversion on the coherent demodulation and sampling and quantizing data signals to obtain N parallel signals, and the “group parallel signals enter N parallel signal processing branches, data
  • the parallel signal processing branch of the transmitting phase includes an equalizer, a frequency offset estimation module and a decision module, and the equalizer of the first branch processes the equalized signal
  • the frequency offset estimation is performed on the equalized signal ⁇ directly according to the known training symbol e , and the cumulative phase error "3 ⁇ 4 and the frequency offset estimated value ⁇ caravan is obtained; when the branch is a data signal, the equalized signal is first used.
  • 3 ⁇ 4 for phase compensation the phase compensated signal 3 ⁇ 4 is:
  • ⁇ represents the delay of the average value of the frequency offset estimation
  • ⁇ 1 indicates rounding up
  • the decision module decides the signal to obtain the decision signal, and performs frequency offset estimation on the equalized signal 3 ⁇ 4 according to the decision signal to obtain the frequency offset estimated value ⁇ farmer and Cumulative phase error ⁇ 3 ⁇ 4;
  • the error signal ⁇ is:
  • N represents the number of error signals calculated by the participating tap coefficients selected from the N branches in the data transmission phase, i ⁇ N: ⁇ N,
  • step S2.7 Determine whether the data has been processed. If it has not been processed, return to step S2.2 to continue processing. If the processing is completed, the process ends.
  • the specific method of frequency offset estimation includes the following steps:
  • the cumulative phase error "3 ⁇ 4 ⁇ ⁇ _ , where the phase of the known training symbol is represented, represents the phase of the equalized signal 3 ⁇ 4;
  • the invention is based on the LMS-based channel equalization and frequency offset estimation joint parallel method.
  • the sampling signal of the training sequence signal is converted into a parallel signal by serial-to-parallel conversion and then sent to the parallel signal processing branch, each branch
  • the equalization and frequency offset estimation are performed respectively, and the frequency offset estimates obtained by all the branches are averaged to obtain the average of the frequency offset estimation.
  • Each branch calculates the error signal according to the average value of the frequency offset estimation, and each group of parallel signals is unified.
  • the equalizer tap coefficient is updated by the mean value of the branch error signal when the equalizer tap coefficient is updated; in the data transmission phase, the transmitting end inserts the training symbol into the data symbol, and passes the coherent demodulation and the sampled quantized data signal through the string. And transform to obtain a parallel signal, the training signal uses the equalized signal and the known training symbols for frequency offset estimation, and the data signal uses corresponding The accumulated phase error of the training signal and the obtained average of the frequency offset estimation are compensated and then judged, and then the equalization signal and the decision signal are used for frequency offset estimation, and then the equalizer tap coefficient is updated in the same manner as the initialization phase.
  • the present invention reduces the signal rate by parallelization, thereby reducing the influence of data signal processing hardware on system performance
  • the error signal is calculated by using the average value of the frequency offset estimation, which can improve the reliability of the equalizer initialization;
  • FIG. 1 is a system block diagram of an optical burst receiver
  • FIG. 2 is a schematic diagram of a parallel signal branch algorithm in an initialization phase
  • FIG. 3 is a schematic diagram of a parallel signal branch algorithm in a data transmission phase
  • Figure 5 is a comparison of the convergence speeds of the computational delay and the no computational delay in the parallel method of the present invention
  • Figure 6 is a comparison of the bit error rate of the serial method and the parallel method of the different delays of the present invention.
  • the operation of an optical burst receiver is divided into two phases: an initialization phase and a data transmission phase.
  • the optical burst receiver After detecting the arrival of the optical burst signal, the optical burst receiver first enters the initialization phase, and the training sequence is used to iteratively update the equalizer tap coefficients until convergence, and the initialization of the equalizer and the optical burst receiver is completed. After the initialization of the optical burst receiver is completed, the data transmission phase is entered.
  • the algorithm of the two stages of the present invention will be described in detail below.
  • FIG. 2 is a schematic diagram of the parallel signal branch algorithm in the initialization phase.
  • the parallel algorithm of the present invention is different from the serial algorithm in that a set of 128 parallel symbols corresponds to 128 LMS algorithm-based equalizers (EQs), each equalizer adopts the same The tap coefficient.
  • the update of the tap coefficients is the key to the initialization of the equalizer.
  • the update of the tap coefficients requires the use of an error signal, so the error signal for each branch needs to be obtained first.
  • the training sequence used in the initialization phase should be long enough to ensure that the equalizer tap coefficients obtained by the initialization can converge.
  • the initialization phase includes the following specific steps:
  • it is 128 channels.
  • the frequency offset estimation module performs frequency offset estimation on the equalization signal 3 ⁇ 4 according to the known training symbol e , to obtain a cumulative phase error 3 ⁇ 4 and a frequency offset estimation value ⁇ ong.
  • the frequency offset estimation method used in this embodiment is a phase estimation method based on pre-decision, and the algorithm considers:
  • the phase of the equalized signal ⁇ can be expressed as: where is the phase information carried by the symbol, and "3 ⁇ 4 is the cumulative phase error.
  • the phase error "3 ⁇ 4 can be expressed as:
  • step S3.1 and step S3.2 are obtained by multiplying the equalization signal ⁇ with the conjugate (" ⁇ ( ⁇ )) of the training sequence symbol e to obtain 6 ⁇ , The multiplication of e ⁇ with the conjugate gives ⁇ , and the angle of the angle (arg( ) is obtained to obtain the frequency offset estimate ⁇ ischen.
  • d Volunteer +1 represents the equalizer tap coefficients used in the “+ i group and the “group” parallel signals respectively. It represents the delay of the error signal, that is, the time when the parallel symbol is input to the error signal and fed back to the equalizer. Delay, so when 1 ⁇ M ⁇ , the tap coefficients cannot be updated, and the tap coefficients always use the initial value ⁇ . It is the set iteration length, which is a positive number, and its selection needs to be small enough to ensure that the iterative process can converge. .
  • the equalizer used in the present invention is an equalizer based on the LMS algorithm.
  • the mean value of the branch error signal that is, -V(n - D,i ] , N. indicates the error of the participation in the calculation of the tap coefficients selected from the N branches
  • the number of signals 1 ⁇ ⁇ W, i c ⁇ N c .
  • the number of branches is large, all the calculation of a set of error signals will generate a large delay, so under the condition that convergence can be satisfied, the number of error signals participating in the average calculation can be reduced, that is, ⁇ W.
  • f(M -A represents the corresponding observation vector, that is, the signal input to the equalizer, the conjugate of the representation.
  • step S107 Determine whether the training sequence signal is processed or not. If the processing is not completed, the processing returns to step S102 to continue processing the next set of parallel signals. If the processing is completed, the data transmission phase is entered.
  • FIG. 3 is a schematic diagram of the parallel signal branch algorithm in the data transmission phase. As shown in Figure 3, the data transmission phase includes the following steps:
  • S201 The data sending end inserts the training symbol into the data symbol, and the insertion method is: grouping the N sending symbols into groups, and then dividing the N sending symbols into R groups, and each group of sending symbols includes a training symbol.
  • the serial numbers of the R training symbols in the parallel symbols are denoted by i ⁇ ⁇ ⁇ w.
  • the present invention inserts a certain number of training symbols into the transmitted symbols when the transmitting end transmits a signal.
  • the branch corresponding to the training symbol is the same as the calculation method of each branch in the training sequence stage, and the training signal branch first calculates the accurate cumulative phase as the reference phase used in the determination of the data signal branches before and after the branch, so as to perform More accurate frequency offset estimation.
  • the phase compensation error can be reduced at the time of the decision, and up to 16 times the estimated value of the training signal branch frequency offset is used.
  • the parallel signal processing branch includes an equalizer, a frequency offset estimation module, and a decision module, and the equalizer of the first branch processes the equalized signal 3 ⁇ 4.
  • the parallel symbol group number "in the data transmission phase” is continuously arranged from the sequence number of the last parallel symbol group in the initialization phase.
  • the equalizer tap coefficient of the first group of parallel symbols in the data transmission phase is the equalization obtained at the end of the initialization phase. Tap coefficient.
  • S203 Perform frequency offset estimation on each of the N branches.
  • the processing flow of the training signal and the data signal are different.
  • the 16 signals shown in FIG. 3 are obtained by the same algorithm as the initialization phase, and SP is used to directly estimate the frequency offset of the equalized signal 3 ⁇ 4 according to the known training symbol ⁇ '.
  • the 15 and 17 signals are phase compensated for the equalized signal 3 ⁇ 4, and the phase compensated signal 3 ⁇ 4 is:
  • phase compensation of the data signal in the “parallel signal of the group” in the data transmission phase uses the frequency offset obtained by the first parallel signal. Estimate the average and the cumulative phase error obtained from the training signals in the group to which it belongs.
  • the decision module judges the signal to obtain a decision signal, and the equalization is performed according to the decision signal No. 3 ⁇ 4 performs frequency offset estimation, and obtains the frequency offset estimation value ⁇ cauliflower and the cumulative phase error “3 ⁇ 4, as shown in Figure 3
  • N branches calculate their error signals respectively. Similarly, the processing methods of training signals and data signals are different.
  • the error signal ⁇ is:
  • N represents the number of error signals calculated by the participating tap coefficients selected from the N branches in the data transmission phase, i ⁇ N: ⁇ N, ⁇ ⁇ i: ⁇ . If the number of error signals involved in the average calculation in the initialization phase and the data transmission phase is different from N:, the iteration lengths ⁇ and ⁇ they use also need to be adjusted accordingly.
  • step S207 Determine whether the data is processed. If the processing is not completed, return to step S202 to continue processing the next set of parallel signals, and if the processing is completed, the process ends.
  • the following is a simulation verification of the LMS-based channel equalization and frequency offset estimation joint parallel method of the present invention.
  • the number of parallel branches in the simulation is 256.
  • the fiber transmission distance is about 50km, and the equalizer uses 11 taps.
  • the calculation delay of the equalizer error signal takes 10 clock units, and the delay of FOE calculation also takes 10 clock units, for a total of 20 delay units.
  • 12 frames of training data are used, 1024 symbols per frame, with a duration of approximately 440 ns.
  • each Four training symbols are inserted into the group parallel data.
  • Other parameters used in the simulation include a 1G frequency offset and an optical signal-to-noise ratio (OSNR) fixed at 13 dB.
  • OSNR optical signal-to-noise ratio
  • the number of inserted training symbols is 4, and sufficient performance can be obtained.
  • the number of different insertion training symbols can be selected according to different system design requirements.
  • Figure 5 is a graph comparing the convergence speeds of the calculated delay and the no computational delay in the joint parallel method of the present invention.
  • the total delay used in this simulation is 20 clock units.
  • the convergence of the equalizer is only delayed with the delay of the iterative calculation, and does not affect the performance after the iteration is converged. And if you use other different delay sizes in your simulation, you can get similar effects.
  • the present invention has a good tolerance for calculating the magnitude of the delay.
  • FIG. 6 is a comparison of bit error rates of the serial method and the parallel method of different delays of the present invention. As shown in Fig. 6, the calculated delay size in the present invention has no effect on the bit error rate (BER) performance of the optical burst receiver as long as the optical burst receiver is properly initialized. At the same time, compared with the performance of the ideal serial method, the performance loss due to parallelization in the present invention is only about 0.2 dB.
  • BER bit error rate

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Optical Communication System (AREA)
  • Cable Transmission Systems, Equalization Of Radio And Reduction Of Echo (AREA)

Abstract

L'invention concerne une méthode parallèle d'égalisation de canal et d'estimation de décalage de fréquence conjointes basée sur LMS. Après qu'un signal de séquence d'apprentissage a été converti en un signal parallèle à un étage d'initialisation d'un photorécepteur, le signal est envoyé à une branche de traitement de signal parallèle, et une égalisation et une estimation de décalage de fréquence sont respectivement effectuées sur le signal ; une valeur moyenne d'estimation de décalage de fréquence de toutes les branches et un signal d'erreur de chaque branche sont calculés ; chaque groupe de signaux parallèles utilisent un coefficient de prise d'égalisateur unifié, et une valeur moyenne des signaux d'erreur de branche est utilisée quand le coefficient de prise d'égalisateur est mis à jour ; une extrémité d'envoi insère un symbole d'apprentissage dans un symbole de données dans un étage d'envoi de données ; le photorécepteur convertit un signal de données en un signal parallèle ; un signal d'apprentissage utilise un signal d'égalisation et le symbole d'apprentissage connu pour effectuer une estimation de décalage de fréquence ; et le signal de données utilise une erreur de phase cumulée d'un signal d'apprentissage correspondant et la valeur moyenne d'estimation de décalage de fréquence obtenue pour effectuer une compensation puis une détermination, et utilise ensuite le signal d'égalisation et un signal de détermination pour effectuer une estimation de décalage de fréquence. Par emploi d'un traitement de signal parallèle, la présente invention réduit les limitations d'un matériel de traitement de signal de données et son influence sur les performance du système.
PCT/CN2014/072120 2014-01-07 2014-02-16 Méthode parallèle d'égalisation de canal et d'estimation de décalage de fréquence conjointes basée sur lms WO2015103804A1 (fr)

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107925483A (zh) * 2015-08-27 2018-04-17 华为技术有限公司 光信号处理方法及相干接收机

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CN111245499B (zh) * 2020-01-08 2021-07-27 西安电子科技大学 基于预整形的时域并行分数间隔均衡器及均衡方法
TWI769033B (zh) * 2021-03-04 2022-06-21 瑞昱半導體股份有限公司 接收資料等化裝置及方法
CN114039623B (zh) * 2021-10-22 2023-05-19 中国电子科技集团公司第五十四研究所 一种低载噪比的短突发扩频信号跟踪方法

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1498487A (zh) * 2002-02-14 2004-05-19 ������������ʽ���� 迭代循环短训练序列直至均方差低于目标阈值的最小均方差均衡方法和系统
US20120070159A1 (en) * 2009-05-18 2012-03-22 Nippon Telegraph And Telephone Corporation Signal generating circuit, optical signal transmitting apparatus, signal receiving circuit, method for establishing optical signal synchronization, and optical signal synchronization system
CN103095614A (zh) * 2013-01-24 2013-05-08 电子科技大学 一种突发相干光纤通信中的联合均衡和频偏估计装置

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1498487A (zh) * 2002-02-14 2004-05-19 ������������ʽ���� 迭代循环短训练序列直至均方差低于目标阈值的最小均方差均衡方法和系统
US20120070159A1 (en) * 2009-05-18 2012-03-22 Nippon Telegraph And Telephone Corporation Signal generating circuit, optical signal transmitting apparatus, signal receiving circuit, method for establishing optical signal synchronization, and optical signal synchronization system
CN103095614A (zh) * 2013-01-24 2013-05-08 电子科技大学 一种突发相干光纤通信中的联合均衡和频偏估计装置

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107925483A (zh) * 2015-08-27 2018-04-17 华为技术有限公司 光信号处理方法及相干接收机
US10491308B2 (en) 2015-08-27 2019-11-26 Huawei Technologies Co., Ltd. Optical signal processing method and coherent receiver
CN107925483B (zh) * 2015-08-27 2019-12-17 华为技术有限公司 光信号处理方法及相干接收机

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