WO2015005702A1 - Appareil d'émission de signaux de diffusion, appareil de réception de signaux de diffusion, procédé d'émission de signaux de diffusion et procédé de réception de signaux de diffusion - Google Patents

Appareil d'émission de signaux de diffusion, appareil de réception de signaux de diffusion, procédé d'émission de signaux de diffusion et procédé de réception de signaux de diffusion Download PDF

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Publication number
WO2015005702A1
WO2015005702A1 PCT/KR2014/006213 KR2014006213W WO2015005702A1 WO 2015005702 A1 WO2015005702 A1 WO 2015005702A1 KR 2014006213 W KR2014006213 W KR 2014006213W WO 2015005702 A1 WO2015005702 A1 WO 2015005702A1
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WIPO (PCT)
Prior art keywords
block
data
phase
broadcast signals
signal
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PCT/KR2014/006213
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English (en)
Inventor
Woochan Kim
Sungryong HONG
Jongseob Baek
Woosuk Ko
Chulkyu Mun
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Lg Electronics Inc.
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Priority to CN201480046442.8A priority Critical patent/CN105474596A/zh
Priority to EP14823547.6A priority patent/EP3020174A4/fr
Publication of WO2015005702A1 publication Critical patent/WO2015005702A1/fr

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/003—Arrangements for allocating sub-channels of the transmission path
    • H04L5/0053—Allocation of signaling, i.e. of overhead other than pilot signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0041—Arrangements at the transmitter end
    • H04L1/0042—Encoding specially adapted to other signal generation operation, e.g. in order to reduce transmit distortions, jitter, or to improve signal shape
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0045—Arrangements at the receiver end
    • H04L1/0047—Decoding adapted to other signal detection operation
    • H04L1/0048—Decoding adapted to other signal detection operation in conjunction with detection of multiuser or interfering signals, e.g. iteration between CDMA or MIMO detector and FEC decoder
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0056—Systems characterized by the type of code used
    • H04L1/0057—Block codes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0056—Systems characterized by the type of code used
    • H04L1/0071—Use of interleaving
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N21/00—Selective content distribution, e.g. interactive television or video on demand [VOD]
    • H04N21/20—Servers specifically adapted for the distribution of content, e.g. VOD servers; Operations thereof
    • H04N21/23—Processing of content or additional data; Elementary server operations; Server middleware
    • H04N21/236—Assembling of a multiplex stream, e.g. transport stream, by combining a video stream with other content or additional data, e.g. inserting a URL [Uniform Resource Locator] into a video stream, multiplexing software data into a video stream; Remultiplexing of multiplex streams; Insertion of stuffing bits into the multiplex stream, e.g. to obtain a constant bit-rate; Assembling of a packetised elementary stream
    • H04N21/23611—Insertion of stuffing data into a multiplex stream, e.g. to obtain a constant bitrate
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N21/00—Selective content distribution, e.g. interactive television or video on demand [VOD]
    • H04N21/20—Servers specifically adapted for the distribution of content, e.g. VOD servers; Operations thereof
    • H04N21/23—Processing of content or additional data; Elementary server operations; Server middleware
    • H04N21/236—Assembling of a multiplex stream, e.g. transport stream, by combining a video stream with other content or additional data, e.g. inserting a URL [Uniform Resource Locator] into a video stream, multiplexing software data into a video stream; Remultiplexing of multiplex streams; Insertion of stuffing bits into the multiplex stream, e.g. to obtain a constant bit-rate; Assembling of a packetised elementary stream
    • H04N21/23614—Multiplexing of additional data and video streams
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N21/00—Selective content distribution, e.g. interactive television or video on demand [VOD]
    • H04N21/20—Servers specifically adapted for the distribution of content, e.g. VOD servers; Operations thereof
    • H04N21/23—Processing of content or additional data; Elementary server operations; Server middleware
    • H04N21/236—Assembling of a multiplex stream, e.g. transport stream, by combining a video stream with other content or additional data, e.g. inserting a URL [Uniform Resource Locator] into a video stream, multiplexing software data into a video stream; Remultiplexing of multiplex streams; Insertion of stuffing bits into the multiplex stream, e.g. to obtain a constant bit-rate; Assembling of a packetised elementary stream
    • H04N21/2365—Multiplexing of several video streams
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N21/00—Selective content distribution, e.g. interactive television or video on demand [VOD]
    • H04N21/40—Client devices specifically adapted for the reception of or interaction with content, e.g. set-top-box [STB]; Operations thereof
    • H04N21/41—Structure of client; Structure of client peripherals
    • H04N21/426—Internal components of the client ; Characteristics thereof
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N21/00—Selective content distribution, e.g. interactive television or video on demand [VOD]
    • H04N21/60—Network structure or processes for video distribution between server and client or between remote clients; Control signalling between clients, server and network components; Transmission of management data between server and client, e.g. sending from server to client commands for recording incoming content stream; Communication details between server and client 
    • H04N21/61—Network physical structure; Signal processing
    • H04N21/6106—Network physical structure; Signal processing specially adapted to the downstream path of the transmission network
    • H04N21/6112—Network physical structure; Signal processing specially adapted to the downstream path of the transmission network involving terrestrial transmission, e.g. DVB-T
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L2001/0092—Error control systems characterised by the topology of the transmission link
    • H04L2001/0093—Point-to-multipoint
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems

Definitions

  • the present invention relates to an apparatus for transmitting broadcast signals, an apparatus for receiving broadcast signals and methods for transmitting and receiving broadcast signals.
  • a digital broadcast signal may include a larger amount of video/audio data than an analog broadcast signal and further include various types of additional data in addition to the video/audio data.
  • a digital broadcast system can provide HD (high definition) images, multi-channel audio and various additional services.
  • HD high definition
  • data transmission efficiency for transmission of large amounts of data, robustness of transmission/reception networks and network flexibility in consideration of mobile reception equipment need to be improved for digital broadcast.
  • a method for transmitting broadcast signals comprises encoding DP (Data Pipe) data corresponding to each of a plurality of DPs, wherein the each of a plurality of DPs carries at least one service component, mapping the encoded DP data onto constellations, time interleaving the mapped DP data, building at least one signal frame including the time interleaved DP data, performing a phase distortion of at least one broadcast signal having the built at least one signal frame, modulating the at least one broadcast signal by an OFDM (Orthogonal Frequency Division Multiplex) scheme and transmitting the at least one broadcast signal.
  • OFDM Orthogonal Frequency Division Multiplex
  • the present invention can process data according to service characteristics to control QoS for each service or service component, thereby providing various broadcast services.
  • the present invention can achieve transmission flexibility by transmitting various broadcast services through the same RF signal bandwidth.
  • the present invention can improve data transmission efficiency and increase robustness of transmission/reception of broadcast signals using a MIMO system.
  • the present invention it is possible to provide broadcast signal transmission and reception methods and apparatus capable of receiving digital broadcast signals without error even with mobile reception equipment or in an indoor environment.
  • FIG. 2 illustrates an input formatting module according to an embodiment of the present invention.
  • FIG. 3 illustrates an input formatting module according to another embodiment of the present invention.
  • FIG. 4 illustrates an input formatting module according to another embodiment of the present invention.
  • FIG. 5 illustrates a coding & modulation module according to an embodiment of the present invention.
  • FIG. 6 illustrates a frame structure module according to an embodiment of the present invention.
  • FIG. 7 illustrates a waveform generation module according to an embodiment of the present invention.
  • FIG. 8 illustrates a structure of an apparatus for receiving broadcast signals for future broadcast services according to an embodiment of the present invention.
  • FIG. 9 illustrates a synchronization & demodulation module according to an embodiment of the present invention.
  • FIG. 10 illustrates a frame parsing module according to an embodiment of the present invention.
  • FIG. 11 illustrates a demapping & decoding module according to an embodiment of the present invention.
  • FIG. 12 illustrates an output processor according to an embodiment of the present invention.
  • FIG. 13 illustrates an output processor according to another embodiment of the present invention.
  • FIG. 14 illustrates a coding & modulation module according to another embodiment of the present invention.
  • FIG. 15 illustrates a demapping & decoding module according to another embodiment of the present invention.
  • FIG. 16 is a view illustrating a waveform generation module according to another embodiment of the present invention.
  • FIG. 17 is a conceptual view of phase pre-distortion according to an embodiment of the present invention.
  • FIG. 18 is a conceptual view of phase pre-distortion according to another embodiment of the present invention.
  • FIG. 19 is a view illustrating a PPD method according to a first embodiment of the present invention.
  • FIG. 20 is a view illustrating a PPD method according to a second embodiment of the present invention.
  • FIG. 21 is a view illustrating a PPD method according to a third embodiment of the present invention.
  • FIG. 22 is a flowchart illustrating operation of the phase pre-distortion block 16000 according to an embodiment of the present invention.
  • FIG. 23 is a flowchart illustrating a method for transmitting broadcast signals according to an embodiment of the present invention.
  • FIG. 24 is a flowchart illustrating a method for receiving broadcast signals according to an embodiment of the present invention.
  • the present invention provides apparatuses and methods for transmitting and receiving broadcast signals for future broadcast services.
  • Future broadcast services according to an embodiment of the present invention include a terrestrial broadcast service, a mobile broadcast service, a UHDTV service, etc.
  • the apparatuses and methods for transmitting according to an embodiment of the present invention may be categorized into a base profile for the terrestrial broadcast service, a handheld profile for the mobile broadcast service and an advanced profile for the UHDTV service.
  • the base profile can be used as a profile for both the terrestrial broadcast service and the mobile broadcast service. That is, the base profile can be used to define a concept of a profile which includes the mobile profile. This can be changed according to intention of the designer.
  • the present invention may process broadcast signals for the future broadcast services through non-MIMO (Multiple Input Multiple Output) or MIMO according to one embodiment.
  • a non-MIMO scheme according to an embodiment of the present invention may include a MISO (Multiple Input Single Output) scheme, a SISO (Single Input Single Output) scheme, etc.
  • MISO or MIMO uses two antennas in the following for convenience of description, the present invention is applicable to systems using two or more antennas.
  • FIG. 1 illustrates a structure of an apparatus for transmitting broadcast signals for future broadcast services according to an embodiment of the present invention.
  • the apparatus for transmitting broadcast signals for future broadcast services can include an input formatting module 1000, a coding & modulation module 1100, a frame structure module 1200, a waveform generation module 1300 and a signaling generation module 1400. A description will be given of the operation of each module of the apparatus for transmitting broadcast signals.
  • the apparatus for transmitting broadcast signals for future broadcast services can receive MPEG-TSs, IP streams (v4/v6) and generic streams (GSs) as an input signal.
  • the apparatus for transmitting broadcast signals can receive management information about the configuration of each stream constituting the input signal and generate a final physical layer signal with reference to the received management information.
  • the input formatting module 1000 can classify the input streams on the basis of a standard for coding and modulation or services or service components and output the input streams as a plurality of logical data pipes (or data pipes or DP data).
  • the data pipe is a logical channel in the physical layer that carries service data or related metadata, which may carry one or multiple service(s) or service component(s).
  • data transmitted through each data pipe may be called DP data.
  • the input formatting module 1000 can divide each data pipe into blocks necessary to perform coding and modulation and carry out processes necessary to increase transmission efficiency or to perform scheduling. Details of operations of the input formatting module 1000 will be described later.
  • the coding & modulation module 1100 can perform forward error correction (FEC) encoding on each data pipe received from the input formatting module 1000 such that an apparatus for receiving broadcast signals can correct an error that may be generated on a transmission channel.
  • FEC forward error correction
  • the coding & modulation module 1100 according to an embodiment of the present invention can convert FEC output bit data to symbol data and interleave the symbol data to correct burst error caused by a channel.
  • the coding & modulation module 1100 according to an embodiment of the present invention can divide the processed data such that the divided data can be output through data paths for respective antenna outputs in order to transmit the data through two or more Tx antennas.
  • the frame structure module 1200 can map the data output from the coding & modulation module 1100 to signal frames.
  • the frame structure module 1200 according to an embodiment of the present invention can perform mapping using scheduling information output from the input formatting module 1000 and interleave data in the signal frames in order to obtain additional diversity gain.
  • the waveform generation module 1300 can convert the signal frames output from the frame structure module 1200 into a signal for transmission.
  • the waveform generation module 1300 according to an embodiment of the present invention can insert a preamble signal (or preamble) into the signal for detection of the transmission apparatus and insert a reference signal for estimating a transmission channel to compensate for distortion into the signal.
  • the waveform generation module 1300 according to an embodiment of the present invention can provide a guard interval and insert a specific sequence into the same in order to offset the influence of channel delay spread due to multi-path reception.
  • the waveform generation module 1300 according to an embodiment of the present invention can perform a procedure necessary for efficient transmission in consideration of signal characteristics such as a peak-to-average power ratio of the output signal.
  • the signaling generation module 1400 generates final physical layer signaling information using the input management information and information generated by the input formatting module 1000, coding & modulation module 1100 and frame structure module 1200. Accordingly, a reception apparatus according to an embodiment of the present invention can decode a received signal by decoding the signaling information.
  • the apparatus for transmitting broadcast signals for future broadcast services can provide terrestrial broadcast service, mobile broadcast service, UHDTV service, etc. Accordingly, the apparatus for transmitting broadcast signals for future broadcast services according to one embodiment of the present invention can multiplex signals for different services in the time domain and transmit the same.
  • FIGS. 2, 3 and 4 illustrate the input formatting module 1000 according to embodiments of the present invention. A description will be given of each figure.
  • FIG. 2 illustrates an input formatting module according to one embodiment of the present invention.
  • FIG. 2 shows an input formatting module when the input signal is a single input stream.
  • the input formatting module can include a mode adaptation module 2000 and a stream adaptation module 2100.
  • the mode adaptation module 2000 can include an input interface block 2010, a CRC-8 encoder block 2020 and a BB header insertion block 2030. Description will be given of each block of the mode adaptation module 2000.
  • the input interface block 2010 can divide the single input stream input thereto into data pieces each having the length of a baseband (BB) frame used for FEC (BCH/LDPC) which will be performed later and output the data pieces.
  • BB baseband
  • BCH/LDPC FEC
  • the CRC-8 encoder block 2020 can perform CRC encoding on BB frame data to add redundancy data thereto.
  • the BB header insertion block 2030 can insert, into the BB frame data, a header including information such as mode adaptation type (TS/GS/IP), a user packet length, a data field length, user packet sync byte, start address of user packet sync byte in data field, a high efficiency mode indicator, an input stream synchronization field, etc.
  • a header including information such as mode adaptation type (TS/GS/IP), a user packet length, a data field length, user packet sync byte, start address of user packet sync byte in data field, a high efficiency mode indicator, an input stream synchronization field, etc.
  • TS/GS/IP mode adaptation type
  • the stream adaptation module 2100 can include a padding insertion block 2110 and a BB scrambler block 2120. Description will be given of each block of the stream adaptation module 2100.
  • the padding insertion block 2110 can insert a padding bit into the data such that the data has the input data length and output the data including the padding bit.
  • the BB scrambler block 2120 can randomize the input bit stream by performing an XOR operation on the input bit stream and a pseudo random binary sequence (PRBS).
  • PRBS pseudo random binary sequence
  • the input formatting module can finally output data pipes to the coding & modulation module.
  • FIG. 3 illustrates an input formatting module according to another embodiment of the present invention.
  • FIG. 3 shows a mode adaptation module 3000 of the input formatting module when the input signal corresponds to multiple input streams.
  • the mode adaptation module 3000 of the input formatting module for processing the multiple input streams can independently process the multiple input streams.
  • the mode adaptation module 3000 for respectively processing the multiple input streams can include input interface blocks, input stream synchronizer blocks 3100, compensating delay blocks 3200, null packet deletion blocks 3300, CRC-8 encoder blocks and BB header insertion blocks. Description will be given of each block of the mode adaptation module 3000.
  • the input stream synchronizer block 3100 can transmit input stream clock reference (ISCR) information to generate timing information necessary for the apparatus for receiving broadcast signals to restore the TSs or GSs.
  • ISCR input stream clock reference
  • the compensating delay block 3200 can delay input data and output the delayed input data such that the apparatus for receiving broadcast signals can synchronize the input data if a delay is generated between data pipes according to processing of data including the timing information by the transmission apparatus.
  • the null packet deletion block 3300 can delete unnecessarily transmitted input null packets from the input data, insert the number of deleted null packets into the input data based on positions in which the null packets are deleted and transmit the input data.
  • FIG. 4 illustrates an input formatting module according to another embodiment of the present invention.
  • FIG. 4 illustrates a stream adaptation module of the input formatting module when the input signal corresponds to multiple input streams.
  • the stream adaptation module of the input formatting module when the input signal corresponds to multiple input streams can include a scheduler 4000, a 1-frame delay block 4100, an in-band signaling or padding insertion block 4200, a physical layer signaling generation block 4300 and a BB scrambler block 4400. Description will be given of each block of the stream adaptation module.
  • the scheduler 4000 can perform scheduling for a MIMO system using multiple antennas having dual polarity.
  • the scheduler 4000 can generate parameters for use in signal processing blocks for antenna paths, such as a bit-to-cell demux block, a cell interleaver block, a time interleaver block, etc. included in the coding & modulation module illustrated in FIG. 1.
  • the 1-frame delay block 4100 can delay the input data by one transmission frame such that scheduling information about the next frame can be transmitted through the current frame for in-band signaling information to be inserted into the data pipes.
  • the in-band signaling or padding insertion block 4200 can insert undelayed physical layer signaling (PLS)-dynamic signaling information into the data delayed by one transmission frame.
  • PLS physical layer signaling
  • the in-band signaling or padding insertion block 4200 can insert a padding bit when a space for padding is present or insert in-band signaling information into the padding space.
  • the scheduler 4000 can output physical layer signaling-dynamic signaling information about the current frame separately from in-band signaling information. Accordingly, a cell mapper, which will be described later, can map input cells according to scheduling information output from the scheduler 4000.
  • the physical layer signaling generation block 4300 can generate physical layer signaling data which will be transmitted through a preamble symbol of a transmission frame or spread and transmitted through a data symbol other than the in-band signaling information.
  • the physical layer signaling data according to an embodiment of the present invention can be referred to as signaling information.
  • the physical layer signaling data according to an embodiment of the present invention can be divided into PLS-pre information and PLS-post information.
  • the PLS-pre information can include parameters necessary to encode the PLS-post information and static PLS signaling data and the PLS-post information can include parameters necessary to encode the data pipes.
  • the parameters necessary to encode the data pipes can be classified into static PLS signaling data and dynamic PLS signaling data.
  • the static PLS signaling data is a parameter commonly applicable to all frames included in a super-frame and can be changed on a super-frame basis.
  • the dynamic PLS signaling data is a parameter differently applicable to respective frames included in a super-frame and can be changed on a frame-by-frame basis. Accordingly, the reception apparatus can acquire the PLS-post information by decoding the PLS-pre information and decode desired data pipes by decoding the PLS-post information.
  • the BB scrambler block 4400 can generate a pseudo-random binary sequence (PRBS) and perform an XOR operation on the PRBS and the input bit streams to decrease the peak-to-average power ratio (PAPR) of the output signal of the waveform generation block.
  • PRBS pseudo-random binary sequence
  • PAPR peak-to-average power ratio
  • scrambling of the BB scrambler block 4400 is applicable to both data pipes and physical layer signaling information.
  • the stream adaptation module can finally output the data pipes to the coding & modulation module.
  • FIG. 5 illustrates a coding & modulation module according to an embodiment of the present invention.
  • the coding & modulation module shown in FIG. 5 corresponds to an embodiment of the coding & modulation module illustrated in FIG. 1.
  • the apparatus for transmitting broadcast signals for future broadcast services can provide a terrestrial broadcast service, mobile broadcast service, UHDTV service, etc.
  • the coding & modulation module can independently process data pipes input thereto by independently applying SISO, MISO and MIMO schemes to the data pipes respectively corresponding to data paths. Consequently, the apparatus for transmitting broadcast signals for future broadcast services according to an embodiment of the present invention can control QoS for each service or service component transmitted through each data pipe.
  • the coding & modulation module can include a first block 5000 for SISO, a second block 5100 for MISO, a third block 5200 for MIMO and a fourth block 5300 for processing the PLS-pre/PLS-post information.
  • the coding & modulation module illustrated in FIG. 5 is an exemplary and may include only the first block 5000 and the fourth block 5300, the second block 5100 and the fourth block 5300 or the third block 5200 and the fourth block 5300 according to design. That is, the coding & modulation module can include blocks for processing data pipes equally or differently according to design.
  • the first block 5000 processes an input data pipe according to SISO and can include an FEC encoder block 5010, a bit interleaver block 5020, a bit-to-cell demux block 5030, a constellation mapper block 5040, a cell interleaver block 5050 and a time interleaver block 5060.
  • the FEC encoder block 5010 can perform BCH encoding and LDPC encoding on the input data pipe to add redundancy thereto such that the reception apparatus can correct an error generated on a transmission channel.
  • the bit interleaver block 5020 can interleave bit streams of the FEC-encoded data pipe according to an interleaving rule such that the bit streams have robustness against burst error that may be generated on the transmission channel. Accordingly, when deep fading or erasure is applied to QAM symbols, errors can be prevented from being generated in consecutive bits from among all codeword bits since interleaved bits are mapped to the QAM symbols.
  • the bit-to-cell demux block 5030 can determine the order of input bit streams such that each bit in an FEC block can be transmitted with appropriate robustness in consideration of both the order of input bit streams and a constellation mapping rule.
  • bit interleaver block 5020 is located between the FEC encoder block 5010 and the constellation mapper block 5040 and can connect output bits of LDPC encoding performed by the FEC encoder block 5010 to bit positions having different reliability values and optimal values of the constellation mapper in consideration of LDPC decoding of the apparatus for receiving broadcast signals. Accordingly, the bit-to-cell demux block 5030 can be replaced by a block having a similar or equal function.
  • the constellation mapper block 5040 can map a bit word input thereto to one constellation.
  • the constellation mapper block 5040 can additionally perform rotation & Q-delay. That is, the constellation mapper block 5040 can rotate input constellations according to a rotation angle, divide the constellations into an in-phase component and a quadrature-phase component and delay only the quadrature-phase component by an arbitrary value. Then, the constellation mapper block 5040 can remap the constellations to new constellations using a paired in-phase component and quadrature-phase component.
  • the constellation mapper block 5040 can move constellation points on a two-dimensional plane in order to find optimal constellation points. Through this process, capacity of the coding & modulation module 1100 can be optimized. Furthermore, the constellation mapper block 5040 can perform the above-described operation using IQ-balanced constellation points and rotation. The constellation mapper block 5040 can be replaced by a block having a similar or equal function.
  • the cell interleaver block 5050 can randomly interleave cells corresponding to one FEC block and output the interleaved cells such that cells corresponding to respective FEC blocks can be output in different orders.
  • the time interleaver block 5060 can interleave cells belonging to a plurality of FEC blocks and output the interleaved cells. Accordingly, the cells corresponding to the FEC blocks are dispersed and transmitted in a period corresponding to a time interleaving depth and thus diversity gain can be obtained.
  • the second block 5100 processes an input data pipe according to MISO and can include the FEC encoder block, bit interleaver block, bit-to-cell demux block, constellation mapper block, cell interleaver block and time interleaver block in the same manner as the first block 5000.
  • the second block 5100 is distinguished from the first block 5000 in that the second block 5100 further includes a MISO processing block 5110.
  • the second block 5100 performs the same procedure including the input operation to the time interleaver operation as those of the first block 5000 and thus description of the corresponding blocks is omitted.
  • the MISO processing block 5110 can encode input cells according to a MISO encoding matrix providing transmit diversity and output MISO-processed data through two paths.
  • MISO processing according to one embodiment of the present invention can include OSTBC (orthogonal space time block coding)/OSFBC (orthogonal space frequency block coding, Alamouti coding).
  • the third block 5200 processes an input data pipe according to MIMO and can include the FEC encoder block, bit interleaver block, bit-to-cell demux block, constellation mapper block, cell interleaver block and time interleaver block in the same manner as the second block 5100, as shown in FIG. 5.
  • the data processing procedure of the third block 5200 is different from that of the second block 5100 since the third block 5200 includes a MIMO processing block 5220.
  • the third block 5200 basic roles of the FEC encoder block and the bit interleaver block are identical to those of the first and second blocks 5000 and 5100 although functions thereof may be different from those of the first and second blocks 5000 and 5100.
  • the bit-to-cell demux block 5210 can generate as many output bit streams as input bit streams of MIMO processing and output the output bit streams through MIMO paths for MIMO processing.
  • the bit-to-cell demux block 5210 can be designed to optimize the decoding performance of the reception apparatus in consideration of characteristics of LDPC and MIMO processing.
  • constellation mapper block Basic roles of the constellation mapper block, cell interleaver block and time interleaver block are identical to those of the first and second blocks 5000 and 5100 although functions thereof may be different from those of the first and second blocks 5000 and 5100.
  • FIG. 5 as many constellation mapper blocks, cell interleaver blocks and time interleaver blocks as the number of MIMO paths for MIMO processing can be present.
  • the constellation mapper blocks, cell interleaver blocks and time interleaver blocks can operate equally or independently for data input through the respective paths.
  • the MIMO processing block 5220 can perform MIMO processing on two input cells using a MIMO encoding matrix and output the MIMO-processed data through two paths.
  • the MIMO encoding matrix according to an embodiment of the present invention can include spatial multiplexing, Golden code, full-rate full diversity code, linear dispersion code, etc.
  • the fourth block 5300 processes the PLS-pre/PLS-post information and can perform SISO or MISO processing.
  • bit interleaver block bit-to-cell demux block, constellation mapper block, cell interleaver block, time interleaver block and MISO processing block included in the fourth block 5300 correspond to those of the second block 5100 although functions thereof may be different from those of the second block 5100.
  • a shortened/punctured FEC encoder block 5310 included in the fourth block 5300 can process PLS data using an FEC encoding scheme for a PLS path provided for a case in which the length of input data is shorter than a length necessary to perform FEC encoding.
  • the shortened/punctured FEC encoder block 5310 can perform BCH encoding on input bit streams, pad 0s corresponding to a desired input bit stream length necessary for normal LDPC encoding, carry out LDPC encoding and then remove the padded 0s to puncture parity bits such that an effective code rate becomes equal to or lower than the data pipe rate.
  • the blocks included in the first block 5000 to fourth block 5300 may be omitted or replaced by blocks having similar or identical functions according to design.
  • the coding & modulation module can output the data pipes (or DP data), PLS-pre information and PLS-post information processed for the respective paths to the frame structure module.
  • FIG. 6 illustrates a frame structure module according to one embodiment of the present invention.
  • the frame structure module shown in FIG. 6 corresponds to an embodiment of the frame structure module 1200 illustrated in FIG. 1.
  • the frame structure module can include at least one cell-mapper 6000, at least one delay compensation module 6100 and at least one block interleaver 6200.
  • the number of cell mappers 6000, delay compensation modules 6100 and block interleavers 6200 can be changed. A description will be given of each module of the frame structure block.
  • the cell-mapper 6000 can allocate cells corresponding to SISO-, MISO- or MIMO-processed data pipes output from the coding & modulation module, cells corresponding to common data commonly applicable to the data pipes and cells corresponding to the PLS-pre/PLS-post information to signal frames according to scheduling information.
  • the common data refers to signaling information commonly applied to all or some data pipes and can be transmitted through a specific data pipe.
  • the data pipe through which the common data is transmitted can be referred to as a common data pipe and can be changed according to design.
  • the cell-mapper 6000 can perform pair-wise cell mapping in order to maintain orthogonality according to Alamouti encoding. That is, the cell-mapper 6000 can process two consecutive cells of the input cells as one unit and map the unit to a frame. Accordingly, paired cells in an input path corresponding to an output path of each antenna can be allocated to neighboring positions in a transmission frame.
  • the delay compensation block 6100 can obtain PLS data corresponding to the current transmission frame by delaying input PLS data cells for the next transmission frame by one frame.
  • the PLS data corresponding to the current frame can be transmitted through a preamble part in the current signal frame and PLS data corresponding to the next signal frame can be transmitted through a preamble part in the current signal frame or in-band signaling in each data pipe of the current signal frame. This can be changed by the designer.
  • the block interleaver 6200 can obtain additional diversity gain by interleaving cells in a transport block corresponding to the unit of a signal frame.
  • the block interleaver 6200 can perform interleaving by processing two consecutive cells of the input cells as one unit when the above-described pair-wise cell mapping is performed. Accordingly, cells output from the block interleaver 6200 can be two consecutive identical cells.
  • At least one cell mapper and at least one block interleaver can operate equally or independently for data input through the paths.
  • the frame structure module can output at least one signal frame to the waveform generation module.
  • FIG. 7 illustrates a waveform generation module according to an embodiment of the present invention.
  • the waveform generation module illustrated in FIG. 7 corresponds to an embodiment of the waveform generation module 1300 described with reference to FIG. 1.
  • the waveform generation module can modulate and transmit as many signal frames as the number of antennas for receiving and outputting signal frames output from the frame structure module illustrated in FIG. 6.
  • the waveform generation module illustrated in FIG. 7 is an embodiment of a waveform generation module of an apparatus for transmitting broadcast signals using m Tx antennas and can include m processing blocks for modulating and outputting frames corresponding to m paths.
  • the m processing blocks can perform the same processing procedure. A description will be given of operation of the first processing block 7000 from among the m processing blocks.
  • the first processing block 7000 can include a reference signal & PAPR reduction block 7100, an inverse waveform transform block 7200, a PAPR reduction in time block 7300, a guard sequence insertion block 7400, a preamble insertion block 7500, a waveform processing block 7600, other system insertion block 7700 and a DAC (digital analog converter) block 7800.
  • the reference signal insertion & PAPR reduction block 7100 can insert a reference signal into a predetermined position of each signal block and apply a PAPR reduction scheme to reduce a PAPR in the time domain. If a broadcast transmission/reception system according to an embodiment of the present invention corresponds to an OFDM system, the reference signal insertion & PAPR reduction block 7100 can use a method of reserving some active subcarriers rather than using the same. In addition, the reference signal insertion & PAPR reduction block 7100 may not use the PAPR reduction scheme as an optional feature according to broadcast transmission/reception system.
  • the inverse waveform transform block 7200 can transform an input signal in a manner of improving transmission efficiency and flexibility in consideration of transmission channel characteristics and system architecture. If the broadcast transmission/reception system according to an embodiment of the present invention corresponds to an OFDM system, the inverse waveform transform block 7200 can employ a method of transforming a frequency domain signal into a time domain signal through inverse FFT operation. If the broadcast transmission/reception system according to an embodiment of the present invention corresponds to a single carrier system, the inverse waveform transform block 7200 may not be used in the waveform generation module.
  • the PAPR reduction in time block 7300 can use a method for reducing PAPR of an input signal in the time domain. If the broadcast transmission/reception system according to an embodiment of the present invention corresponds to an OFDM system, the PAPR reduction in time block 7300 may use a method of simply clipping peak amplitude. Furthermore, the PAPR reduction in time block 7300 may not be used in the broadcast transmission/reception system according to an embodiment of the present invention since it is an optional feature.
  • the guard sequence insertion block 7400 can provide a guard interval between neighboring signal blocks and insert a specific sequence into the guard interval as necessary in order to minimize the influence of delay spread of a transmission channel. Accordingly, the reception apparatus can easily perform synchronization or channel estimation. If the broadcast transmission/reception system according to an embodiment of the present invention corresponds to an OFDM system, the guard sequence insertion block 7400 may insert a cyclic prefix into a guard interval of an OFDM symbol.
  • the preamble insertion block 7500 can insert a signal of a known type (e.g. the preamble or preamble symbol) agreed upon between the transmission apparatus and the reception apparatus into a transmission signal such that the reception apparatus can rapidly and efficiently detect a target system signal.
  • a signal of a known type e.g. the preamble or preamble symbol
  • the preamble insertion block 7500 can define a signal frame composed of a plurality of OFDM symbols and insert a preamble symbol into the beginning of each signal frame. That is, the preamble carries basic PLS data and is located in the beginning of a signal frame.
  • the waveform processing block 7600 can perform waveform processing on an input baseband signal such that the input baseband signal meets channel transmission characteristics.
  • the waveform processing block 7600 may use a method of performing square-root-raised cosine (SRRC) filtering to obtain a standard for out-of-band emission of a transmission signal. If the broadcast transmission/reception system according to an embodiment of the present invention corresponds to a multi-carrier system, the waveform processing block 7600 may not be used.
  • SRRC square-root-raised cosine
  • the other system insertion block 7700 can multiplex signals of a plurality of broadcast transmission/reception systems in the time domain such that data of two or more different broadcast transmission/reception systems providing broadcast services can be simultaneously transmitted in the same RF signal bandwidth.
  • the two or more different broadcast transmission/reception systems refer to systems providing different broadcast services.
  • the different broadcast services may refer to a terrestrial broadcast service, mobile broadcast service, etc. Data related to respective broadcast services can be transmitted through different frames.
  • the DAC block 7800 can convert an input digital signal into an analog signal and output the analog signal.
  • the signal output from the DAC block 7800 can be transmitted through m output antennas.
  • a Tx antenna according to an embodiment of the present invention can have vertical or horizontal polarity.
  • FIG. 8 illustrates a structure of an apparatus for receiving broadcast signals for future broadcast services according to an embodiment of the present invention.
  • the apparatus for receiving broadcast signals for future broadcast services can correspond to the apparatus for transmitting broadcast signals for future broadcast services, described with reference to FIG. 1.
  • the apparatus for receiving broadcast signals for future broadcast services according to an embodiment of the present invention can include a synchronization & demodulation module 8000, a frame parsing module 8100, a demapping & decoding module 8200, an output processor 8300 and a signaling decoding module 8400. A description will be given of operation of each module of the apparatus for receiving broadcast signals.
  • the synchronization & demodulation module 8000 can receive input signals through m Rx antennas, perform signal detection and synchronization with respect to a system corresponding to the apparatus for receiving broadcast signals and carry out demodulation corresponding to a reverse procedure of the procedure performed by the apparatus for transmitting broadcast signals.
  • the frame parsing module 8100 can parse input signal frames and extract data through which a service selected by a user is transmitted. If the apparatus for transmitting broadcast signals performs interleaving, the frame parsing module 8100 can carry out deinterleaving corresponding to a reverse procedure of interleaving. In this case, the positions of a signal and data that need to be extracted can be obtained by decoding data output from the signaling decoding module 8400 to restore scheduling information generated by the apparatus for transmitting broadcast signals.
  • the demapping & decoding module 8200 can convert the input signals into bit domain data and then deinterleave the same as necessary.
  • the demapping & decoding module 8200 can perform demapping for mapping applied for transmission efficiency and correct an error generated on a transmission channel through decoding. In this case, the demapping & decoding module 8200 can obtain transmission parameters necessary for demapping and decoding by decoding the data output from the signaling decoding module 8400.
  • the output processor 8300 can perform reverse procedures of various compression/signal processing procedures which are applied by the apparatus for transmitting broadcast signals to improve transmission efficiency.
  • the output processor 8300 can acquire necessary control information from data output from the signaling decoding module 8400.
  • the output of the output processor 8300 corresponds to a signal input to the apparatus for transmitting broadcast signals and may be MPEG-TSs, IP streams (v4 or v6) and generic streams.
  • the signaling decoding module 8400 can obtain PLS information from the signal demodulated by the synchronization & demodulation module 8000. As described above, the frame parsing module 8100, demapping & decoding module 8200 and output processor 8300 can execute functions thereof using the data output from the signaling decoding module 8400.
  • FIG. 9 illustrates a synchronization & demodulation module according to an embodiment of the present invention.
  • the synchronization & demodulation module shown in FIG. 9 corresponds to an embodiment of the synchronization & demodulation module described with reference to FIG. 8.
  • the synchronization & demodulation module shown in FIG. 9 can perform a reverse operation of the operation of the waveform generation module illustrated in FIG. 7.
  • the synchronization & demodulation module corresponds to a synchronization & demodulation module of an apparatus for receiving broadcast signals using m Rx antennas and can include m processing blocks for demodulating signals respectively input through m paths.
  • the m processing blocks can perform the same processing procedure. A description will be given of operation of the first processing block 9000 from among the m processing blocks.
  • the first processing block 9000 can include a tuner 9100, an ADC block 9200, a preamble detector 9300, a guard sequence detector 9400, a waveform transform block 9500, a time/frequency synchronization block 9600, a reference signal detector 9700, a channel equalizer 9800 and an inverse waveform transform block 9900.
  • the tuner 9100 can select a desired frequency band, compensate for the magnitude of a received signal and output the compensated signal to the ADC block 9200.
  • the ADC block 9200 can convert the signal output from the tuner 9100 into a digital signal.
  • the preamble detector 9300 can detect a preamble (or preamble signal or preamble symbol) in order to check whether or not the digital signal is a signal of the system corresponding to the apparatus for receiving broadcast signals. In this case, the preamble detector 9300 can decode basic transmission parameters received through the preamble.
  • the guard sequence detector 9400 can detect a guard sequence in the digital signal.
  • the time/frequency synchronization block 9600 can perform time/frequency synchronization using the detected guard sequence and the channel equalizer 9800 can estimate a channel through a received/restored sequence using the detected guard sequence.
  • the waveform transform block 9500 can perform a reverse operation of inverse waveform transform when the apparatus for transmitting broadcast signals has performed inverse waveform transform.
  • the waveform transform block 9500 can perform FFT.
  • the waveform transform block 9500 may not be used if a received time domain signal is processed in the frequency domain or processed in the time domain.
  • the time/frequency synchronization block 9600 can receive output data of the preamble detector 9300, guard sequence detector 9400 and reference signal detector 9700 and perform time synchronization and carrier frequency synchronization including guard sequence detection and block window positioning on a detected signal.
  • the time/frequency synchronization block 9600 can feed back the output signal of the waveform transform block 9500 for frequency synchronization.
  • the reference signal detector 9700 can detect a received reference signal. Accordingly, the apparatus for receiving broadcast signals according to an embodiment of the present invention can perform synchronization or channel estimation.
  • the channel equalizer 9800 can estimate a transmission channel from each Tx antenna to each Rx antenna from the guard sequence or reference signal and perform channel equalization for received data using the estimated channel.
  • the inverse waveform transform block 9900 may restore the original received data domain when the waveform transform block 9500 performs waveform transform for efficient synchronization and channel estimation/equalization. If the broadcast transmission/reception system according to an embodiment of the present invention is a single carrier system, the waveform transform block 9500 can perform FFT in order to carry out synchronization/channel estimation/equalization in the frequency domain and the inverse waveform transform block 9900 can perform IFFT on the channel-equalized signal to restore transmitted data symbols. If the broadcast transmission/reception system according to an embodiment of the present invention is a multi-carrier system, the inverse waveform transform block 9900 may not be used.
  • FIG. 10 illustrates a frame parsing module according to an embodiment of the present invention.
  • the frame parsing module illustrated in FIG. 10 corresponds to an embodiment of the frame parsing module described with reference to FIG. 8.
  • the frame parsing module shown in FIG. 10 can perform a reverse operation of the operation of the frame structure module illustrated in FIG. 6.
  • the frame parsing module can include at least one block deinterleaver 10000 and at least one cell demapper 10100.
  • the block deinterleaver 10000 can deinterleave data input through data paths of the m Rx antennas and processed by the synchronization & demodulation module on a signal block basis.
  • the block deinterleaver 10000 can process two consecutive pieces of data as a pair for each input path. Accordingly, the block interleaver 10000 can output two consecutive pieces of data even when deinterleaving has been performed.
  • the block deinterleaver 10000 can perform a reverse operation of the interleaving operation performed by the apparatus for transmitting broadcast signals to output data in the original order.
  • the cell demapper 10100 can extract cells corresponding to common data, cells corresponding to data pipes and cells corresponding to PLS data from received signal frames.
  • the cell demapper 10100 can merge data distributed and transmitted and output the same as a stream as necessary.
  • the cell demapper 10100 can perform pair-wise cell demapping for processing two consecutive input cells as one unit as a reverse procedure of the mapping operation of the apparatus for transmitting broadcast signals.
  • the cell demapper 10100 can extract PLS signaling data received through the current frame as PLS-pre & PLS-post data and output the PLS-pre & PLS-post data.
  • FIG. 11 illustrates a demapping & decoding module according to an embodiment of the present invention.
  • the demapping & decoding module shown in FIG. 11 corresponds to an embodiment of the demapping & decoding module illustrated in FIG. 8.
  • the demapping & decoding module shown in FIG. 11 can perform a reverse operation of the operation of the coding & modulation module illustrated in FIG. 5.
  • the coding & modulation module of the apparatus for transmitting broadcast signals can process input data pipes by independently applying SISO, MISO and MIMO thereto for respective paths, as described above. Accordingly, the demapping & decoding module illustrated in FIG. 11 can include blocks for processing data output from the frame parsing module according to SISO, MISO and MIMO in response to the apparatus for transmitting broadcast signals.
  • the demapping & decoding module can include a first block 11000 for SISO, a second block 11100 for MISO, a third block 11200 for MIMO and a fourth block 11300 for processing the PLS-pre/PLS-post information.
  • the demapping & decoding module shown in FIG. 11 is exemplary and may include only the first block 11000 and the fourth block 11300, only the second block 11100 and the fourth block 11300 or only the third block 11200 and the fourth block 11300 according to design. That is, the demapping & decoding module can include blocks for processing data pipes equally or differently according to design.
  • the first block 11000 processes an input data pipe according to SISO and can include a time deinterleaver block 11010, a cell deinterleaver block 11020, a constellation demapper block 11030, a cell-to-bit mux block 11040, a bit deinterleaver block 11050 and an FEC decoder block 11060.
  • the time deinterleaver block 11010 can perform a reverse process of the process performed by the time interleaver block 5060 illustrated in FIG. 5. That is, the time deinterleaver block 11010 can deinterleave input symbols interleaved in the time domain into original positions thereof.
  • the cell deinterleaver block 11020 can perform a reverse process of the process performed by the cell interleaver block 5050 illustrated in FIG. 5. That is, the cell deinterleaver block 11020 can deinterleave positions of cells spread in one FEC block into original positions thereof.
  • the constellation demapper block 11030 can perform a reverse process of the process performed by the constellation mapper block 5040 illustrated in FIG. 5. That is, the constellation demapper block 11030 can demap a symbol domain input signal to bit domain data. In addition, the constellation demapper block 11030 may perform hard decision and output decided bit data. Furthermore, the constellation demapper block 11030 may output a log-likelihood ratio (LLR) of each bit, which corresponds to a soft decision value or probability value. If the apparatus for transmitting broadcast signals applies a rotated constellation in order to obtain additional diversity gain, the constellation demapper block 11030 can perform 2-dimensional LLR demapping corresponding to the rotated constellation. Here, the constellation demapper block 11030 can calculate the LLR such that a delay applied by the apparatus for transmitting broadcast signals to the I or Q component can be compensated.
  • LLR log-likelihood ratio
  • the cell-to-bit mux block 11040 can perform a reverse process of the process performed by the bit-to-cell demux block 5030 illustrated in FIG. 5. That is, the cell-to-bit mux block 11040 can restore bit data mapped by the bit-to-cell demux block 5030 to the original bit streams.
  • the bit deinterleaver block 11050 can perform a reverse process of the process performed by the bit interleaver 5020 illustrated in FIG. 5. That is, the bit deinterleaver block 11050 can deinterleave the bit streams output from the cell-to-bit mux block 11040 in the original order.
  • the FEC decoder block 11060 can perform a reverse process of the process performed by the FEC encoder block 5010 illustrated in FIG. 5. That is, the FEC decoder block 11060 can correct an error generated on a transmission channel by performing LDPC decoding and BCH decoding.
  • the second block 11100 processes an input data pipe according to MISO and can include the time deinterleaver block, cell deinterleaver block, constellation demapper block, cell-to-bit mux block, bit deinterleaver block and FEC decoder block in the same manner as the first block 11000, as shown in FIG. 11.
  • the second block 11100 is distinguished from the first block 11000 in that the second block 11100 further includes a MISO decoding block 11110.
  • the second block 11100 performs the same procedure including time deinterleaving operation to outputting operation as the first block 11000 and thus description of the corresponding blocks is omitted.
  • the MISO decoding block 11110 can perform a reverse operation of the operation of the MISO processing block 5110 illustrated in FIG. 5. If the broadcast transmission/reception system according to an embodiment of the present invention uses STBC, the MISO decoding block 11110 can perform Alamouti decoding.
  • the third block 11200 processes an input data pipe according to MIMO and can include the time deinterleaver block, cell deinterleaver block, constellation demapper block, cell-to-bit mux block, bit deinterleaver block and FEC decoder block in the same manner as the second block 11100, as shown in FIG. 11.
  • the third block 11200 is distinguished from the second block 11100 in that the third block 11200 further includes a MIMO decoding block 11210.
  • the basic roles of the time deinterleaver block, cell deinterleaver block, constellation demapper block, cell-to-bit mux block and bit deinterleaver block included in the third block 11200 are identical to those of the corresponding blocks included in the first and second blocks 11000 and 11100 although functions thereof may be different from the first and second blocks 11000 and 11100.
  • the MIMO decoding block 11210 can receive output data of the cell deinterleaver for input signals of the m Rx antennas and perform MIMO decoding as a reverse operation of the operation of the MIMO processing block 5220 illustrated in FIG. 5.
  • the MIMO decoding block 11210 can perform maximum likelihood decoding to obtain optimal decoding performance or carry out sphere decoding with reduced complexity. Otherwise, the MIMO decoding block 11210 can achieve improved decoding performance by performing MMSE detection or carrying out iterative decoding with MMSE detection.
  • the fourth block 11300 processes the PLS-pre/PLS-post information and can perform SISO or MISO decoding.
  • the fourth block 11300 can carry out a reverse process of the process performed by the fourth block 5300 described with reference to FIG. 5.
  • the basic roles of the time deinterleaver block, cell deinterleaver block, constellation demapper block, cell-to-bit mux block and bit deinterleaver block included in the fourth block 11300 are identical to those of the corresponding blocks of the first, second and third blocks 11000, 11100 and 11200 although functions thereof may be different from the first, second and third blocks 11000, 11100 and 11200.
  • the shortened/punctured FEC decoder 11310 included in the fourth block 11300 can perform a reverse process of the process performed by the shortened/punctured FEC encoder block 5310 described with reference to FIG. 5. That is, the shortened/punctured FEC decoder 11310 can perform de-shortening and de-puncturing on data shortened/punctured according to PLS data length and then carry out FEC decoding thereon. In this case, the FEC decoder used for data pipes can also be used for PLS. Accordingly, additional FEC decoder hardware for the PLS only is not needed and thus system design is simplified and efficient coding is achieved.
  • the demapping & decoding module can output data pipes and PLS information processed for the respective paths to the output processor, as illustrated in FIG. 11.
  • FIGS. 12 and 13 illustrate output processors according to embodiments of the present invention.
  • FIG. 12 illustrates an output processor according to an embodiment of the present invention.
  • the output processor illustrated in FIG. 12 corresponds to an embodiment of the output processor illustrated in FIG. 8.
  • the output processor illustrated in FIG. 12 receives a single data pipe output from the demapping & decoding module and outputs a single output stream.
  • the output processor can perform a reverse operation of the operation of the input formatting module illustrated in FIG. 2.
  • the output processor shown in FIG. 12 can include a BB scrambler block 12000, a padding removal block 12100, a CRC-8 decoder block 12200 and a BB frame processor block 12300.
  • the BB scrambler block 12000 can descramble an input bit stream by generating the same PRBS as that used in the apparatus for transmitting broadcast signals for the input bit stream and carrying out an XOR operation on the PRBS and the bit stream.
  • the padding removal block 12100 can remove padding bits inserted by the apparatus for transmitting broadcast signals as necessary.
  • the CRC-8 decoder block 12200 can check a block error by performing CRC decoding on the bit stream received from the padding removal block 12100.
  • the BB frame processor block 12300 can decode information transmitted through a BB frame header and restore MPEG-TSs, IP streams (v4 or v6) or generic streams using the decoded information.
  • FIG. 13 illustrates an output processor according to another embodiment of the present invention.
  • the output processor shown in FIG. 13 corresponds to an embodiment of the output processor illustrated in FIG. 8.
  • the output processor shown in FIG. 13 receives multiple data pipes output from the demapping & decoding module.
  • Decoding multiple data pipes can include a process of merging common data commonly applicable to a plurality of data pipes and data pipes related thereto and decoding the same or a process of simultaneously decoding a plurality of services or service components (including a scalable video service) by the apparatus for receiving broadcast signals.
  • the output processor shown in FIG. 13 can include a BB descrambler block, a padding removal block, a CRC-8 decoder block and a BB frame processor block as the output processor illustrated in FIG. 12.
  • the basic roles of these blocks correspond to those of the blocks described with reference to FIG. 12 although operations thereof may differ from those of the blocks illustrated in FIG. 12.
  • a de-jitter buffer block 13000 included in the output processor shown in FIG. 13 can compensate for a delay, inserted by the apparatus for transmitting broadcast signals for synchronization of multiple data pipes, according to a restored TTO (time to output) parameter.
  • a null packet insertion block 13100 can restore a null packet removed from a stream with reference to a restored DNP (deleted null packet) and output common data.
  • a TS clock regeneration block 13200 can restore time synchronization of output packets based on ISCR (input stream time reference) information.
  • a TS recombining block 13300 can recombine the common data and data pipes related thereto, output from the null packet insertion block 13100, to restore the original MPEG-TSs, IP streams (v4 or v6) or generic streams.
  • the TTO, DNT and ISCR information can be obtained through the BB frame header.
  • An in-band signaling decoding block 13400 can decode and output in-band physical layer signaling information transmitted through a padding bit field in each FEC frame of a data pipe.
  • the output processor shown in FIG. 13 can BB-descramble the PLS-pre information and PLS-post information respectively input through a PLS-pre path and a PLS-post path and decode the descrambled data to restore the original PLS data.
  • the restored PLS data is delivered to a system controller included in the apparatus for receiving broadcast signals.
  • the system controller can provide parameters necessary for the synchronization & demodulation module, frame parsing module, demapping & decoding module and output processor module of the apparatus for receiving broadcast signals.
  • FIG. 14 illustrates a coding & modulation module according to another embodiment of the present invention.
  • the coding & modulation module shown in FIG. 14 corresponds to another embodiment of the coding & modulation module illustrated in FIGS. 1 to 5.
  • the coding & modulation module shown in FIG. 14 can include a first block 14000 for SISO, a second block 14100 for MISO, a third block 14200 for MIMO and a fourth block 14300 for processing the PLS-pre/PLS-post information.
  • the coding & modulation module can include blocks for processing data pipes equally or differently according to the design.
  • the first to fourth blocks 14000 to 14300 shown in FIG. 14 are similar to the first to fourth blocks 5000 to 5300 illustrated in FIG. 5.
  • the first to fourth blocks 14000 to 14300 shown in FIG. 14 are distinguished from the first to fourth blocks 5000 to 5300 illustrated in FIG. 5 in that a constellation mapper 14010 included in the first to fourth blocks 14000 to 14300 has a function different from the first to fourth blocks 5000 to 5300 illustrated in FIG. 5, a rotation & I/Q interleaver block 14020 is present between the cell interleaver and the time interleaver of the first to fourth blocks 14000 to 14300 illustrated in FIG. 14 and the third block 14200 for MIMO has a configuration different from the third block 5200 for MIMO illustrated in FIG. 5.
  • the following description focuses on these differences between the first to fourth blocks 14000 to 14300 shown in FIG. 14 and the first to fourth blocks 5000 to 5300 illustrated in FIG. 5.
  • the constellation mapper block 14010 shown in FIG. 14 can map an input bit word to a complex symbol. However, the constellation mapper block 14010 may not perform constellation rotation, differently from the constellation mapper block shown in FIG. 5.
  • the constellation mapper block 14010 shown in FIG. 14 is commonly applicable to the first, second and third blocks 14000, 14100 and 14200, as described above.
  • the rotation & I/Q interleaver block 14020 can independently interleave in-phase and quadrature-phase components of each complex symbol of cell-interleaved data output from the cell interleaver and output the in-phase and quadrature-phase components on a symbol-by-symbol basis.
  • the number of number of input data pieces and output data pieces of the rotation & I/Q interleaver block 14020 is two or more which can be changed by the designer.
  • the rotation & I/Q interleaver block 14020 may not interleave the in-phase component.
  • the rotation & I/Q interleaver block 14020 is commonly applicable to the first to fourth blocks 14000 to 14300, as described above. In this case, whether or not the rotation & I/Q interleaver block 14020 is applied to the fourth block 14300 for processing the PLS-pre/post information can be signaled through the above-described preamble.
  • the third block 14200 for MIMO can include a Q-block interleaver block 14210 and a complex symbol generator block 14220, as illustrated in FIG. 14.
  • the Q-block interleaver block 14210 can permute a parity part of an FEC-encoded FEC block received from the FEC encoder. Accordingly, a parity part of an LDPC H matrix can be made into a cyclic structure like an information part.
  • the Q-block interleaver block 14210 can permute the order of output bit blocks having Q size of the LDPC H matrix and then perform row-column block interleaving to generate final bit streams.
  • the complex symbol generator block 14220 receives the bit streams output from the Q-block interleaver block 14210, maps the bit streams to complex symbols and outputs the complex symbols. In this case, the complex symbol generator block 14220 can output the complex symbols through at least two paths. This can be modified by the designer.
  • the coding & modulation module can output data pipes, PLS-pre information and PLS-post information processed for respective paths to the frame structure module.
  • FIG. 15 illustrates a demapping & decoding module according to another embodiment of the present invention.
  • the demapping & decoding module shown in FIG. 15 corresponds to another embodiment of the demapping & decoding module illustrated in FIG. 11.
  • the demapping & decoding module shown in FIG. 15 can perform a reverse operation of the operation of the coding & modulation module illustrated in FIG. 14.
  • the demapping & decoding module can include a first block 15000 for SISO, a second block 11100 for MISO, a third block 15200 for MIMO and a fourth block 14300 for processing the PLS-pre/PLS-post information.
  • the demapping & decoding module can include blocks for processing data pipes equally or differently according to design.
  • the first to fourth blocks 15000 to 15300 shown in FIG. 15 are similar to the first to fourth blocks 11000 to 11300 illustrated in FIG. 11.
  • first to fourth blocks 15000 to 15300 shown in FIG. 15 are distinguished from the first to fourth blocks 11000 to 11300 illustrated in FIG. 11 in that an I/Q deinterleaver and derotation block 15010 is present between the time interleaver and the cell deinterleaver of the first to fourth blocks 15000 to 15300, a constellation mapper 15010 included in the first to fourth blocks 15000 to 15300 has a function different from the first to fourth blocks 11000 to 11300 illustrated in FIG. 11 and the third block 15200 for MIMO has a configuration different from the third block 11200 for MIMO illustrated in FIG. 11.
  • the following description focuses on these differences between the first to fourth blocks 15000 to 15300 shown in FIG. 15 and the first to fourth blocks 11000 to 11300 illustrated in FIG. 11.
  • the I/Q deinterleaver & derotation block 15010 can perform a reverse process of the process performed by the rotation & I/Q interleaver block 14020 illustrated in FIG. 14. That is, the I/Q deinterleaver & derotation block 15010 can deinterleave I and Q components I/Q-interleaved and transmitted by the apparatus for transmitting broadcast signals and derotate complex symbols having the restored I and Q components.
  • the I/Q deinterleaver & derotation block 15010 is commonly applicable to the first to fourth blocks 15000 to 15300, as described above. In this case, whether or not the I/Q deinterleaver & derotation block 15010 is applied to the fourth block 15300 for processing the PLS-pre/post information can be signaled through the above-described preamble.
  • the constellation demapper block 15020 can perform a reverse process of the process performed by the constellation mapper block 14010 illustrated in FIG. 14. That is, the constellation demapper block 15020 can demap cell-deinterleaved data without performing derotation.
  • the third block 15200 for MIMO can include a complex symbol parsing block 15210 and a Q-block deinterleaver block 15220, as shown in FIG. 15.
  • the complex symbol parsing block 15210 can perform a reverse process of the process performed by the complex symbol generator block 14220 illustrated in FIG. 14. That is, the complex symbol parsing block 15210 can parse complex data symbols and demap the same to bit data. In this case, the complex symbol parsing block 15210 can receive complex data symbols through at least two paths.
  • the Q-block deinterleaver block 15220 can perform a reverse process of the process carried out by the Q-block interleaver block 14210 illustrated in FIG. 14. That is, the Q-block deinterleaver block 15220 can restore Q size blocks according to row-column deinterleaving, restore the order of permuted blocks to the original order and then restore positions of parity bits to original positions according to parity deinterleaving.
  • the demapping & decoding module can output data pipes and PLS information processed for respective paths to the output processor.
  • the apparatus and method for transmitting broadcast signals according to an embodiment of the present invention can multiplex signals of different broadcast transmission/reception systems within the same RF channel and transmit the multiplexed signals and the apparatus and method for receiving broadcast signals according to an embodiment of the present invention can process the signals in response to the broadcast signal transmission operation. Accordingly, it is possible to provide a flexible broadcast transmission and reception system.
  • the waveform generation module 1300 may convert signal frames output from the frame structure module 1200 into ultimately transmittable signals.
  • the waveform generation module 1300 according to an embodiment of the present invention may use a phase pre-distortion (PPD) method (or phase distortion).
  • PPD phase pre-distortion
  • the phase pre-distortion method according to an embodiment of the present invention may be also referred to as a distributed MISO scheme or 2D-eSFN.
  • the present invention assumes that input signals of the waveform generation block 1300 are the same.
  • the system according to the present invention supports the SFN (Single Frequency Network) network, where distributed MISO scheme is optionally used to support very robust transmission mode.
  • the 2D-eSFN is a distributed MISO scheme that uses multiple TX antennas, each of which is located in the different transmitter site in the SFN network.
  • the 2D-eSFN processing independently distorts the phase of the signals transmitted from multiple transmitters, in order to create both time and frequency diversity. Hence, burst errors due to low flat fading or deep-fading for a long time can be mitigated.
  • the performance of channel estimation by a broadcast signal reception apparatus may not deteriorate and gain distortion of a transmission signal may not be caused and thus the loss of transmission capacity due to the gain distortion may be minimized.
  • phase pre-distortion method of the present invention may be applied independently to a plurality of TX antennas as described above and thus a diversity gain may be achieved. Further, since the broadcast signal reception apparatus does not need to process phase pre-distortion, additional complexity is not required to design the broadcast signal reception apparatus.
  • FIG. 16 is a view illustrating a waveform generation module according to another embodiment of the present invention.
  • the waveform generation module illustrated in FIG. 16 corresponds to another embodiment of the waveform generation module 1300 described above in relation to FIGS. 1 and 7.
  • the waveform generation module may receive signal frames output from the frame structure module described above in relation to FIG. 6 and modulate the received signal frames to correspond to the number of antennas to output the modulated signal frames.
  • the waveform generation module corresponds to an embodiment of a waveform generation module a transmission apparatus using m Tx antennas, and may include m processing blocks for modulating input frames by m paths and outputting the modulated frames.
  • the m processing blocks may perform the same processing procedure.
  • Each processing block included in the waveform generation module illustrated in FIG. 16 may include a reference signal insertion & PAPR reduction block, a phase pre-distortion block 16000, an inverse waveform transform block, a PAPR reduction in time block, a guard sequence insertion block, a preamble insertion block, a waveform processing block, an other system insertion block and a Digital Analog Conveter (DAC) block.
  • the processing blocks included in the waveform generation module illustrated in FIG. 16 are the same as the processing blocks included in the waveform generation module illustrated in FIG. 7 except that each processing block includes the phase pre-distortion block 16000 in FIG. 16.
  • phase pre-distortion block 16000 operations and functions of the blocks other than the phase pre-distortion block 16000 are the same as those described above in relation to FIG. 7 and thus are not described here, and a description is now given of the phase pre-distortion block 16000 only.
  • the phase pre-distortion block 16000 may apply different phase pre-distortion methods to broadcast signals to be transmitted through different antennas, before the broadcast signals are transmitted. As such, a reception rate of a broadcast signal reception apparatus may be improved.
  • FIG. 17 is a conceptual view of phase pre-distortion according to an embodiment of the present invention.
  • FIG. 17(a) illustrates a block-based configuration for performing phase pre-distortion
  • FIG. 17(b) illustrates coordinates indicating the location of each phase.
  • a block illustrated at the top of FIG. 17(a) indicates a PPD block.
  • the PPD block refers to a unit block for performing pre-distortion.
  • the length of PPD block may correspond to the size of FFT/IFFT, the length of user data included in the size of FFT/IFFT, or a non-integer multiple of the size of FFT/IFFT.
  • the length of PPD block may also correspond to a non-integer multiple of the length of user data. Even in the case of a single carrier system, the length of PPD block may be an arbitrary length appropriate for the system.
  • FIG. 17(a) illustrates a case in which a total number of PPD sub-blocks is 6.
  • the PPD sub-blocks may be generated to correspond to the number of phases of a phase transition sequence to be used by the PPD block. That is, the PPD sub-blocks are generated by dividing the PPD block by the number of phases of the phase transition sequences.
  • the PPD sub-blocks may have different lengths as illustrated in FIG. 17(a), only some PPD sub-blocks may have the same length, or all PPD sub-blocks may have the same length.
  • Blocks illustrated at the bottom of FIG. 17(a) indicate the phases included in the phase transition sequence corresponding to the PPD sub-blocks. Contiguous phases on the phase transition sequence may be the same phase or different phases.
  • phase transition sequence may correspond to at least two phase types.
  • FIG. 17 illustrates an embodiment in which two types of phases, e.g., phase A and phase B, are used.
  • a phase pattern of the phase transition sequence according to an embodiment of the present invention may be changed in units of a PPD block or a certain number of PPD blocks.
  • the PPD block illustrated in FIG. 17(a) may have a phase pattern of A/B/A/B/A/B but a next PPD block may have a phase pattern of A/B/B/A/B/A.
  • phase pattern when a current PPD block is referred to as PPD block 0 and a next PPD block is referred to as PPD block1, PPD block 0 may have phases A and B and a phase pattern of A/B/A/B/A/B, and PPD block 1 may have phases C and D and a phase pattern of C/D/D/C/D/C. Further, according to another embodiment of the present invention, only some phases may be changed between different PPD blocks. For example, when PPD block 0 has phases A and B and a phase pattern of A/B/A/B/A/B, PPD block 1 may have phases A and D and a phase pattern of A/D/D/A/D/A.
  • FIG. 17(b) illustrates real and imaginary coordinates indicating the locations of phase A and phase B described above in relation to FIG. 17(a).
  • the coordinates of phase A may be expressed as (cos(A), sin(A)) and the coordinates of phase B may be expressed as (cos(B), sin(B)).
  • the coordinate values of each phase may be transited from (cos(A), sin(A)) to (cos(B), sin(B)) or vice versa.
  • power of each phase may be set to 1 not to influence the gain of a transmission signal.
  • the phase pre-distortion block 16000 may cause a transition in phase of a transmission signal input to each sub-block of the PPD block by multiplying the signal by (cos(A) + j* sin(A)) or (cos(B) + j* sin(B)).
  • phase pre-distortion method may also be performed by multiplying the transmission signal by (cos(A) - j* sin(A)) or (cos(B) - j* sin(B)).
  • FIG. 18 is a conceptual view of phase pre-distortion according to another embodiment of the present invention.
  • FIG. 18(a) illustrates correlations between PDD sub-blocks and phases corresponding thereto
  • FIG. 18(b) is a graph independently showing a real value (cos(A), cos(B)) and an imaginary value (sin(A), sin(B)) of a phase corresponding to each PDD sub-block.
  • FIG. 18(c) illustrates pilot signals input for channel estimation of a reception apparatus
  • FIG. 18(d) illustrates coordinates indicating the location of each phase.
  • FIGS. 18(a) and 18(d) are the same as those given above in relation to FIGS. 17(a) and 17(b) and thus are omitted here.
  • the real value (cos(A), cos(B)) and the imaginary value (sin(A), sin(B)) of each phase may have a value between 0 and 1.
  • a phase value is transited at the end of each PDD sub-block, a real value and an imaginary value of the phase are transited directly to a real value and an imaginary value of a phase corresponding to a next PDD sub-block.
  • the pilot signals may have a gain of size pP and located at an interval of size dP.
  • the gain and the interval of the pilot signals according to an embodiment of the present invention may vary according to the intention of a designer.
  • a broadcast signal reception apparatus may estimate a channel between contiguous pilot signals using the pilot signals located in a transmission signal.
  • the broadcast signal reception apparatus may use linear interpolation for channel estimation, and may use a variety of filters, e.g., a low pass filter.
  • channel estimation errors may occur when a phase is transited rapidly.
  • a method for minimizing channel estimation errors when a phase is transited rapidly is necessary.
  • the present invention proposes three embodiments of a PPD method for minimizing the above-described channel estimation errors.
  • a first embodiment corresponds to a PPD method for transiting a phase along a straight line 18100 directly connecting (cos(A), sin(A)) and (cos(B), sin(B)) on the real/imaginary coordinates illustrated in FIG. 18(d).
  • a second embodiment corresponds to a PPD method for transiting a phase along a curved line 18200 connecting (cos(A), sin(A)) and (cos(B), sin(B)) on the real/imaginary coordinates illustrated in FIG. 18(d).
  • a third embodiment corresponds to a PPD method similar to the above-described PPD method of the second embodiment but for minimizing channel estimation errors which can occur in the second embodiment.
  • phase distortion value parameters and Math Figures used for the PPD method can be referred to as a phase distortion value.
  • a phase which is not performed the phase distortion can be referred to as a base phase and a phase changes according to the phase distortion can be referred to as a phase variation or a phase variation value. Therefore, the phase distortion value according to an embodiment of the present invention is determined based on the base phase and the phase variation.
  • FIG. 19 is a view illustrating a PPD method according to a first embodiment of the present invention.
  • the first embodiment corresponds to a PPD method for transiting a phase along the straight line 18100 directly connecting (cos(A), sin(A)) and (cos(B), sin(B)) on the real/imaginary coordinates illustrated in FIG. 18(d).
  • FIG. 19(a) illustrates correlations between PDD sub-blocks and phases corresponding thereto
  • FIG. 19(b) is a graph independently showing a real value (cos(A), cos(B)) and an imaginary value (sin(A), sin(B)) of a phase corresponding to each PDD sub-block.
  • FIG. 19(c) is a graph showing variations in power of a transmission signal due to phase pre-distortion.
  • FIG. 19(a) A description of FIG. 19(a) is the same as that given above in relation to FIGS. 17(a) and 18(a) and thus is omitted here.
  • the phase pre-distortion block 16000 when phase A is directly transited to phase B or vice versa, may perform phase distortion or linear transition along a straight line 19000 directly connecting cos(A) and cos(B) or a straight line 19100 directly connecting sin(A) and sin(B).
  • a period in which phase distortion is performed to transit phase A to phase B may be referred to as PTP1
  • a period in which phase distortion is performed to transit phase B to phase A may be referred to as PTP2.
  • Math Figure shows the phase distortion value which is applied to the first embodiment of the present invention.
  • the start of each of PTP1 and PTP2 is defined as s
  • the end thereof is defined as e
  • the location of a value to be calculated in PTP1 or PTP2 is defined as x (or x-th signal)
  • a real coordinate value and an imaginary coordinate value may be expressed as given by Math Figure 2.
  • the power of a corresponding transmission signal is less than 1 while moving along the straight line.
  • phase pre-distortion when phase pre-distortion is performed according to the first embodiment of the present invention, it is noted that the power of the transmission signal is lowered to a value less than 1 in the PTP1 and PTP2 periods 19200. Accordingly, a reception rate of a broadcast signal reception apparatus may be reduced.
  • FIG. 20 is a view illustrating a PPD method according to a second embodiment of the present invention.
  • the second embodiment corresponds to a PPD method for transiting a phase along the curved line 18200 connecting (cos(A), sin(A)) and (cos(B), sin(B)) on the real/imaginary coordinates illustrated in FIG. 18(d).
  • the power of a corresponding transmission signal may be maintained at 1 even in a period in which a phase is transited.
  • FIG. 20(a) illustrates correlations between PDD sub-blocks and phases corresponding thereto
  • FIG. 20(b) is a graph independently showing a real value (cos(A), cos(B)) and an imaginary value (sin(A), sin(B)) of a phase corresponding to each PDD sub-block.
  • FIG. 20(c) is a graph showing variations in power of a transmission signal due to phase pre-distortion according to the second embodiment.
  • FIG. 20(a) A description of FIG. 20(a) is the same as that given above in relation to FIGS. 17(a) and 18(a) and thus is omitted here.
  • phase pre-distortion block 16000 when phase A is directly transited to phase B, the phase pre-distortion block 16000 according to an embodiment of the present invention may perform phase distortion along a curved line 20000 connecting cos(A) and cos(B) or a curved line 20100 connecting sin(A) and sin(B) for a period corresponding to PTP1 or PTP2.
  • Math Figure 3 shows the phase distortion value which is applied to the second embodiment of the present invention.
  • a real coordinate value and an imaginary coordinate value may be expressed as given by Math Figure 3.
  • the power of a transmission signal in a corresponding period may be constantly maintained as 1.
  • FIG. 21 is a view illustrating a PPD method according to a third embodiment of the present invention.
  • the phase pre-distortion block 16000 may perform phase distortion along a curved line connecting cos(A) and cos(B) or a curved line connecting sin(A) and sin(B) for a period corresponding to PTP1 or PTP2.
  • the third embodiment of the present invention corresponds to a phase transition method for improving these channel estimation errors. Unlike the second embodiment, a phase transition edge smoothing method may be applied to the start or end of each period.
  • FIG. 21 illustrates a method for smoothing phase transition edges at the start and end of PTP1 illustrated in FIG. 20, according to the third embodiment of the present invention.
  • period sp a period in which phase transition edge smoothing is performed
  • period sp may include start and end portions of PTP1.
  • start portion of PTP1 may be referred to as ts and the end portion of PTP1 may be referred to as te.
  • the phase transition edge smoothing method according to the third embodiment of the present invention may be performed by applying a specific function to period sp.
  • a function applied to period sp including ts may be referred to as function Fa
  • a function applied to period sp including te may be referred to as function Fb.
  • the names of the parameters and functions may vary according to the intention of a designer.
  • Function Fa and function Fb may correspond to one of the following four methods.
  • the first moving average method is a method for calculating an average of m contiguous real/imaginary values.
  • the second low pass filter method is a method for performing smoothing by applying a low pass filter having a small bandwidth sufficient to perform smoothing, to period sp.
  • the third weighted average method is a method for calculating an average of m contiguous real/imaginary values after giving weights thereto according to contiguity thereof, differently from the moving average method.
  • the fourth replacement by the piece of sine wave method is a method for taking a period suitable to smooth the ts or te portion from a sine wave to correspond to the length of period sp and replacing period sp with the taken period.
  • Function Fa and function Fb may also use a variety of methods other than the above-described four methods, and this may vary according to the intention of a designer.
  • FIG. 22 is a flowchart illustrating operation of the phase pre-distortion block 16000 according to an embodiment of the present invention.
  • the phase pre-distortion block 16000 may generate a phase transition sequence and generate a phase pattern for each PPD block (S22000).
  • phase transition sequence may be the same phase or different phases.
  • phases of the phase transition sequence according to an embodiment of the present invention may correspond to at least two phase types.
  • phase pattern of the phase transition sequence according to an embodiment of the present invention may be changed in units of a PPD block or a certain number of PPD blocks. A detailed description thereof is the same as that given above and thus is omitted here.
  • phase pre-distortion block 16000 according to an embodiment of the present invention may perform phase transition (S22100).
  • the phase pre-distortion block 16000 according to an embodiment of the present invention may perform phase transition using the PPD methods described above in relation to FIGS. 18 to 20 according to the first to third embodiments of the present invention. A detailed description thereof is the same as that given above in relation to FIGS. 18 to 20 and thus is omitted here.
  • phase pre-distortion block 16000 according to an embodiment of the present invention may perform transition edge smoothing (S22200).
  • the phase pre-distortion block 16000 according to an embodiment of the present invention may perform transition edge smoothing only when phase transition is performed using the above-described PPD method according to the third embodiment. As such, transmission power may be constantly maintained and channel estimation errors of a broadcast signal reception apparatus may be reduced.
  • the transition edge smoothing method may be performed using a specific function and this may vary according to the intention of a designer. A detailed description of the method is the same as that given above in relation to FIG. 21 and thus is omitted here.
  • FIG. 23 is a flowchart illustrating a method for transmitting broadcast signals according to an embodiment of the present invention.
  • the apparatus for transmitting broadcast signals can encode data pipe (DP) data corresponding to each of a plurality of DPs (S23000).
  • a data pipe is a logical channel in the physical layer that carries service data or related metadata, which may carry one or multiple service(s) or service component(s).
  • Data carried on a data pipe can be referred to as DP data.
  • the detailed process of step S23000 is as described in FIG. 1, 5 or 14.
  • the apparatus for transmitting broadcast signals can map the encoded DP data onto constellations (S23100).
  • the detailed process of this step is as described in FIG. 1, 5 or 14.
  • the apparatus for transmitting broadcast signals can time-interleave the mapped DP data (S23200).
  • the detailed process of this step is as described in FIG. 1, 5 or 14
  • the apparatus for transmitting broadcast signals can build at least on signal frame including the time-interleaved DP data (S23300).
  • the detailed process of this step is as described in FIG. 1 or 6.
  • the apparatus for transmitting broadcast signals can perform a phase distortion of at least one broadcast signal having the built at least one signal frame (S23400).
  • the phase distortion may be performed based on the phase distortion value which is expressed as Math Figure 1 to Math Figure 3.
  • the phase distortion value according to the present invention is determined based on the base phase and the phase variation value. The detailed process of this step is as described in FIG. 16 to FIG. 22.
  • the apparatus for transmitting broadcast signals can modulate the at least one broadcast signal an OFDM (Othogonal Frequency Division Multiplexing) scheme (S23500).
  • OFDM Orthogonal Frequency Division Multiplexing
  • the apparatus for transmitting broadcast signals can transmit the at least one broadcast signal (S23600).
  • the detailed process of this step is as described in FIG. 1 or 7.
  • FIG. 24 is a flowchart illustrating a method for receiving broadcast signals according to an embodiment of the present invention.
  • the flowchart shown in FIG. 24 corresponds to a reverse process of the broadcast signal transmission method according to an embodiment of the present invention, described with reference to FIG. 23.
  • the apparatus for receiving broadcast signals can receive broadcast signals (S24000).
  • a phase of each of the broadcast signals is distorted according to the phase distortion value in a transmission side.
  • the detailed process of this step is as described in FIG. 16 to FIG. 22.
  • the apparatus for receiving broadcast signals can demodulate received broadcast signals using an OFDM (Othogonal Frequency Division Multiplexing) scheme (S24100). Details are as described in FIG. 8 or 9.
  • OFDM Orthogonal Frequency Division Multiplexing
  • the apparatus for receiving broadcast signals can parse at least one signal frame from the demodulated broadcast signals (S24200). Details are as described in FIG. 8 or 10.
  • the at least one signal frame can include DP data for carrying services or service components.
  • the apparatus for receiving broadcast signals can time-deinterleave the DP data included in the parsed signal frame (S24300). Details are as described in FIG. 8 or 11 and FIG. 15.
  • the apparatus for receiving broadcast signals can demap the time-deinterleaved DP data (S24400). Details are as described in FIG. 8 or 11 and FIG. 15.
  • the apparatus for receiving broadcast signals can decode the demapped DP data (S24500). Details are as described in FIG. 8 or 11 and FIG. 15.
  • the present invention is available in a series of broadcast signal provision fields.

Abstract

L'invention concerne un procédé et un appareil d'émission de signaux de diffusion associé. L'appareil d'émission de signaux de diffusion comprend un encodeur pour coder des données DP (tuyau de données) correspondant à chacun d'une pluralité de DP, un mappeur pour mapper les données DP codées en des constellations, un entrelaceur temporel pour entrelacer de manière temporelle les données DP mappées, un moyen de construction de trame pour construire au moins une trame de signal comprenant les données DP entrelacées de manière temporelle, une unité de distorsion de phase pour réaliser une distorsion de phase d'au moins un signal de diffusion ayant ladite au moins une trame de signal construite, un modulateur pour moduler ledit au moins un signal de diffusion par un mécanisme OFDM (multiplexage par répartition orthogonale de la fréquence) et un émetteur pour émettre ledit au moins un signal de diffusion.
PCT/KR2014/006213 2013-07-10 2014-07-10 Appareil d'émission de signaux de diffusion, appareil de réception de signaux de diffusion, procédé d'émission de signaux de diffusion et procédé de réception de signaux de diffusion WO2015005702A1 (fr)

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