WO2014172733A1

WO2014172733A1 - Circuit arrangement and method for operating an illuminant

Info

Publication number: WO2014172733A1
Application number: PCT/AT2014/000091
Authority: WO
Inventors: John SCHÖNBERGER
Original assignee: Tridonic Gmbh & Co. Kg
Priority date: 2013-04-26
Filing date: 2014-04-25
Publication date: 2014-10-30
Also published as: DE102013215966A1; AT15822U1

Abstract

The invention relates to a circuit arrangement for operating an illuminant (3), the circuit comprising an input and a converter with power factor correction. The converter comprises an inductor (21), a controllable switching means (23) connected in series to the inductor (21), and a regulator (13, 30). The regulator (13, 30) comprises a PI element. The regulator (13, 30) is configured to generate a phase shift for a signal component of an input signal for the regulator (13, 30), the frequency of which signal component is twice as large as a frequency of an input voltage.

Description

Circuit arrangement and method for operating a light source

The invention relates to a circuit arrangement and a method for operating a luminous means. In particular, the invention relates to circuit arrangements including a converter operated to provide power factor correction. With increasing use of light sources such as LEDs and LED modules gain circuitry for operating such bulbs continue to gain in importance. A power factor correction is used in control gear for such bulbs to reduce the unwanted generation of harmonic currents in the supply network. The power factor is a measure of harmonic currents generated by the operating circuit.

Depending on the particular application of the operating circuit, different Power Factor Conversion (PFC) solutions may be selected For example, a power factor correction circuit may be provided as an input stage between a rectifier and a transformer Booster converter work.

It is also possible to use so-called single-stage PFC converters which, in addition to a transformation, also perform the power factor correction. An example of a single stage PFC converter is a single stage PFC flyback converter. Such circuit arrangements can be used in particular in applications that do not require particularly large power.

For voltage regulated operation circuits, output side voltage ripples that oscillate at twice the line frequency can adversely affect PFC correction. For example, the attempt to correct voltage ripples on the output side, in conventional lead to the fact that harmonic currents are not reduced to the desired extent. One approach to solving these problems may be to suppress the voltage ripples on the output side. For this purpose, an output capacitor with a large capacity can be provided on the output side. Alternatively or additionally, a controller with a small bandwidth can be used. However, such approaches can bring various disadvantages. For example, the use of a large capacity capacitor as the output capacitor may be undesirable because of the size of the device and / or potential cost penalties.

The invention has for its object to provide devices and methods in which a good power factor correction can be achieved without voltage ripple must be suppressed at the output side of a converter by a high-capacity output capacitor. The invention has for its object to provide such devices and methods that can be used in PFC converters with voltage regulation. A circuit arrangement for operating a luminous means and a method having the features specified in the independent claims are provided. The dependent claims define embodiments of the invention. According to exemplary embodiments of the invention, a circuit arrangement for operating a luminous means uses a regulator which comprises a PI (proportional-integral) element and which is set up to a signal component of an input signal of the regulator which is twice the supply voltage frequency It has been found that by the phase shift of the signal component which oscillates at twice the supply voltage frequency, good power factor correction can be achieved even if these voltage ripples are not strongly suppressed on the output side. A particularly good power correction can be achieved if the phase shift at the frequency which is equal to twice the supply voltage frequency is within an interval of -90 ° and / or approximately -90 °. This allows the use of a smaller output capacitor and / or a larger bandwidth regulator than conventional control strategies that do not intentionally introduce an additional phase shift.

To generate the corresponding phase shift, the controller may be configured such that a transfer function of the regulator has two poles at frequencies that are in an environment of frequency equal to twice the supply voltage frequency.

A circuit arrangement for operating a luminous means according to an embodiment comprises an input for receiving an AC voltage having a first frequency. The circuit arrangement comprises a power factor correction converter having an inductance, a controllable switching means connected in series with the inductor, and a regulator. The regulator has a P-element and is arranged to produce a phase shift for a signal component having a second frequency twice the first frequency.

The PI element exhibits the behavior of a conventional PI controller, but the controller is supplemented by components for introducing an additional phase shift.

The regulator may include the PI member, a first pole, and a second pole. The first pole and the second pole may be at a frequency or at frequencies in an environment of the second frequency, ie, near twice the supply voltage frequency. The first pole and the second pole may be double poles or a second-order pole. The frequencies at which the poles are located may be smaller than a frequency with which the controllable switching means is switched clocked.

The controller may include a galvanic isolation.

The converter may have an input side with the inductor and one of them galvanically isolated output side. The PI member may be provided on the output side of the converter. A filter whose transfer function has the first pole and / or the second pole can be provided on the input side of the converter.

The controller can be set up so that the phase shift for the signal component, which oscillates at twice the frequency of the supply voltage, lies within an interval by a phase shift of -90 °. The controller may be arranged so that the phase shift for the signal component which oscillates at twice the frequency of the supply voltage deviates by less than a predetermined threshold value of -90 °. The controller can be set up so that the phase shift for the signal component is -90 °.

The circuit arrangement may comprise an integrated circuit for driving the controllable switching means. The integrated circuit may have an input to receive a signal containing the signal component phase shifted by the controller.

The integrated circuit may be configured to control the controllable switching means such that an on-time and / or an off-time of the controllable switching means depends on the respective phase of the phase-shifted signal component.

The integrated circuit may be configured to control the controllable switching means to provide a voltage at an output of the circuit board. Order is regulated to a desired value. The controlled variable may be a variable detected on the output side of the regulator, for example the output voltage itself. The controlled variable may also be an auxiliary variable detected on the input side, ie a primary side of the converter. The auxiliary size can be regulated to set the output voltage to a desired value. The auxiliary size can be detected, for example, with a Hilfswindung on the input side.

The converter may be a flyback converter connected to the input via a rectifier.

The converters may be a PFC flyback converter.

The circuit arrangement may be an operating circuit for at least one light-emitting diode. The circuit arrangement may form an LED converter or be comprised by an LED converter.

According to a further embodiment, a system is provided which comprises the circuit arrangement according to an embodiment and at least one light-emitting diode which is connected to an output of the converter. The at least one light-emitting diode may comprise at least one inorganic light-emitting diode and / or at least one organic light-emitting diode. The at least one light-emitting diode can be connected to the output of the converter via a converter circuit, which is connected between the output of the converter and the at least one light-emitting diode.

According to a further exemplary embodiment, a method for operating a luminous means with a circuit arrangement is specified, to which an alternating voltage with a first frequency is supplied and which comprises a converter. To operate the lamp, a controllable switching means, which is connected in series with an inductance of the converter, switched clocked. The method includes voltage regulation with a regulator having a PIL member. In voltage regulation, the controller generates a phase shift for a signal component which is a second fre- quency signal. frequency that is twice as large as the first frequency.

Further features of the method according to exemplary embodiments and the effects achieved thereby correspond to the further features of the circuit arrangement according to exemplary embodiments.

The method can be carried out with the circuit arrangement according to an embodiment. The circuit arrangement and the method according to embodiments use a control strategy in which the controller selectively causes a certain phase shift at least for those signals and signal components whose frequency is twice the supply voltage frequency. The regulator may include, in addition to the PI, at least one filter which causes the corresponding phase shift for those signals and signal components which oscillate at twice the supply voltage frequency. The at least one filter may have two poles. The poles may be approximately twice the supply voltage frequency.

Such a controller may also be referred to as a "PI + PP" or "ΡΙΡΡ" controller since it has two poles in addition to the PI.

This control strategy allows for a good performance without sacrificing the voltage ripples, which oscillate at twice the supply voltage frequency, on the output side by a high capacity output capacitor and / or in voltage regulation by a regulator must be removed with a small bandwidth. The control strategy can be used in particular for PFC flyback converter.

The invention will be explained below with reference to the figures based on preferred embodiments. In the figures, identical reference numerals denote identical elements. FIG. 1 shows a system according to an exemplary embodiment.

Figure 2 shows a circuit diagram of a circuit arrangement according to an embodiment.

FIG. 3 is a block diagram representation of a regulator according to an embodiment.

FIG. 4 is a block diagram representation of a regulator according to an embodiment.

Figure 5 shows voltage ripples of a signal generated by the controller according to an embodiment. Figure 6 shows a signal generated by the controller according to an embodiment together with an input signal of the controller.

FIG. 7 shows a Bode diagram for a regulator of a circuit arrangement according to an exemplary embodiment and for a conventional regulator.

FIG. 8 shows an input current of a circuit arrangement according to an exemplary embodiment.

FIG. 9 shows an input current of a conventional circuit arrangement in which an output capacitor with a larger capacity than in FIG. 8 is used.

FIG. 10 shows a circuit diagram of an implementation of a regulator according to an exemplary embodiment.

FIG. 1 shows a circuit diagram of a circuit arrangement according to a further exemplary embodiment.

FIG. 1 shows an illustration of a system 1 which has an operating device with a Circuit arrangement 2 for operating a luminous means 3 comprises. The luminous means 3 may comprise at least one light-emitting diode (LED). The luminous means 3 can comprise a plurality of LEDs. The LEDs may be inorganic or organic LEDs.

The circuit arrangement 2 has an input 10 to which a supply voltage is supplied. The supply voltage is an AC voltage, for example a mains voltage. A frequency of the supply voltage at the input 10 is also referred to here as Versorgungsspannungsfre- frequency or as the first frequency. Double the supply voltage frequency is called the second frequency. This second frequency plays a role in the control strategy of the circuit arrangement 2.

The circuit arrangement 2 comprises a rectifier 1 1, which provides a rectified AC voltage to a transducer 12. The converter 12 may be configured as a power factor correction (PFC) converter, which is operated to reduce the return of harmonic currents into the network. The converter 12 may be, for example, a flyback converter. Other converter types can be used. An output of the converter may be connected to the lighting means 3. The luminous means 3 can be connected to an output terminal 14 of the circuit arrangement 2. The luminous means 3 can be connected directly to an output terminal 14 of the circuit arrangement 2. Alternatively, a converter circuit can be connected between the output terminal 14 and the luminous means 3, which preferably regulates the current or the power of the luminous means 3. This converter circuit can be formed, for example, by a buck converter (buck converter), boost converter (boost converter) or an inverter circuit (buck-boost converter). The converter 12 has a regulator 13. The regulator 13 may be a voltage regulator. The controlled variable of the regulator 13 can be, for example, the output voltage of the converter 12 or an auxiliary variable, which is related to the output voltage of the converter 12. As will be described in detail with reference to FIGS. 3 to 11, the controller 13 includes a PI (proportional-integral) member. The controller is designed to cause a certain phase shift for an input signal whose frequency is twice the supply voltage frequency. The output signal generated by the input signal from the controller may, for example, have a phase shift of -90 ° with respect to the input signal, which oscillates at the second frequency, ie twice the supply voltage frequency. The phase shift caused by the sinusoidal signal controller 13 in response to the frequency of the signal may be defined by the phase response of a transfer function of the regulator 13. The transfer function can be defined as a quotient of the output variable of the controller 13 transformed into the frequency range to the input variable of the controller 13 transformed into the frequency range. The complex argument of the transfer function, ie the phase shift, as a function of the frequency defines the phase response. The controller 13 may be designed such that the phase response of the regulator 13 at the second frequency, which is twice the supply voltage frequency, has a value of -90 ° or is approximately equal to -90 °.

Figure 2 shows a circuit diagram of a circuit arrangement 2 according to an embodiment in which the converter is designed as a flyback converter. Such converters are also referred to as flyback converters or boost / buck converters.

The converter has a transformer, which may comprise a primary-side inductance 22 and a secondary-side inductance 25. A primary side of the converter has a main inductance 21 in which energy can be stored. The primary-side inductance 22 and the main inductance 21 are shown schematically separately in FIG. 2, but need not be separate components. For example, only a single coil can be provided, which performs the function of the main inductance 21 and the primary-side inductance 22 of the transformer. The primary-side inductance 22 of the transformer can be a leakage inductance.

The converter has a controllable switching means 23, which is connected in series with the main inductor 21. The controllable switching means 23 is switched in operation of the converter to transfer energy from the primary side of the transformer, which is the input side of the converter, to the secondary side, which is the output side. When the controllable switching means 23 is switched on, energy is stored in the main inductance 21. This state is also referred to as a conduction phase or charge phase in which the main inductance 21 is charged with energy. In the switched-off state of the controllable switching means 23, the cached energy is transmitted to the secondary side. This phase is also referred to as a blocking phase.

The secondary side has a rectifier, which may comprise a diode 26 or several diodes. An output capacitor 27 on the secondary side can be charged when energy is transferred from the primary side to the secondary side. The capacitor 27 is also referred to as a charging capacitor. The controllable switching means 23 may be a transistor. The controllable switching means 23 may be a power transistor. The controllable switching means 23 may be, for example, a bipolar transistor, an insulated gate transistor, a field effect transistor or another controllable switch. The circuit arrangement 2 has a voltage regulation loop 30. The voltage regulation loop 30 may use a voltage Vo of the output side as a controlled variable. The voltage Vo of the output side can be tapped at a point 28, for example via an ohmic voltage divider. A reference source 31 may specify a desired value Vo ref. A difference amplifier 32 or subtractor can determine the deviation between the voltage Vo of the output side and the desired value. The controller 13 may switch the controllable switching means 23. Depending on the deviation, which is supplied to the controller 13, for example, an on-time of the controllable switching means and / or an off-time of the controllable switching means be changed to regulate the voltage Vo of the output side in the direction of the setpoint. For example, the ratio of on-time (t _on ) to off-time (t ₀ ff) can be set depending on which control signal the controller 13 generates from the input signal supplied to it.

The output side voltage Vo may include voltage ripple at the second frequency which is twice the supply voltage frequency. Such voltage ripples are caused by the rectification, which provides a rectified AC voltage to the transducer 12.

While conventional control strategies attempt to minimize the amplitude of these voltage ripples on the output side and / or attenuate transmission of these voltage ripples by the regulator 13, in embodiments of the invention, these voltage ripples are phase-shifted and selectively utilized to provide power factor correction improve.

FIG. 3 is a block diagram of components of a regulator according to an embodiment. The controller has a P-member 41.

The controller has at least one component 42 for inducing an additional phase shift. The at least one component 42 may comprise one or more filters. The at least one component 42 causes a signal which oscillates at twice the supply voltage frequency to be provided with an additional phase shift. An output signal Vc of the combination of the PI element 41 and the at least one component 42 for causing the additional phase shift has a certain phase shift relative to the corresponding input signal. This phase shift is chosen for the second frequency, ie the frequency of the voltage ripple, so that the phase-shifted voltage ripple in the output signal Vc reduces the total harmonic distortion (THD) of the input current and / or the input voltage becomes.

The at least one component 42 for causing the additional phase shift may have a transfer function having two poles. The two poles may be in a second frequency environment that is twice the supply voltage frequency.

The output signal Vc of the combination of the PI member 41 and the at least one component 42 for causing the phase shift may influence a switch controller 43. The switch controller 43 may switch the controllable switching means 13 clocked. The switching on and off of the controllable switching means can vary with the phase-shifted voltage ripples of the output side time-dependent. These out-of-phase spanning nipples are included in the output signal Vc, which provides the combination of the PI member 41 and the at least one additional phase shifting component 42.

The switch controller 43 may be an integrated circuit. The switch controller 43 may be configured as a processor, a microprocessor, a controller, a microcontroller, or an application specific integrated circuit (ASIC).

FIG. 4 shows an implementation of the controller for a control device according to an exemplary embodiment. The regulator has the Pl member and components 45, 46. The components 45, 46 may each be an analog filter or a digital filter. The components 45, 46 each define one pole of the transfer function. For example, the filter 45 may have a transfer function having a first pole. The filter 46 may have a transfer function having a second pole. The first pole and the second pole may be in an environment of the second frequency equal to twice the supply voltage frequency. The first pole and the second pole may be at twice the supply voltage frequency. A variety of other embodiments of the controller may be used in embodiments. For example, two poles of the transfer function can also be provided by only one filter having double poles. While functional blocks are shown in FIG. 3 and FIG. 4, the different components need not be separate elements. For example, a digital processor can take over both the function of the PI controller and the generation of the additional phase shift.

The use of the filters or other components providing the first pole and the second pole causes a phase shift of approximately -90 ° for signals whose frequency is equal to twice the supply voltage frequency. For the closed control loop results in a total shift of -180 °. The PI element and the additional phase-shifting component of the regulator may be implemented by analog circuit elements or in digital technology. The order of the various components can be reversed. For example, the additional phase shift may be introduced before a signal is applied to the PI. One or both of the filters that provide the two poles of the transfer function may be located in front of the PI.

The controller may also include a galvanic isolation. This allows some of the components of the regulator to be located on the secondary side and others of the regulator components on the primary side.

FIG. 5 shows a signal 51 at the output of the components 41, 42 of FIG. 3 or at the output of the components 41, 45, 46 in FIG. 4, when an input signal of the regulator has voltage ripples which oscillate at twice the supply voltage frequency. This signal 51 can be used as a control signal, on which the switching of the controllable switching means 23 depends.

Shown by a dashed line is a signal 52 at the output of a PI element in a conventional controller, if no additional phase shift is introduced. The signal 51 has a phase shift 53 caused by the two poles in the transfer function of the regulator at twice the supply voltage frequency.

The phase shift 53 shows the change in the phase angle of a controller used in embodiments compared to a conventional PI controller without additional phase shift. FIG. 6 shows the signal 51 at the output of the components 41, 42 of FIG. 3 or at the output of the components 41, 45, 46 in FIG. 4 together with the corresponding input signal 55 of the regulator. The input signal 55 has voltage ripples corresponding to the voltage ripple on the output side of the converter.

The signal 51 has a phase shift 59 of approximately -90 ° with respect to the input signal 55. The phase shift 59 is caused by the two poles in the transfer function of the regulator at twice the supply voltage frequency.

FIG. 7 shows a Bode diagram for the regulator according to an embodiment in which an additional phase shift is introduced. The Bode diagram for the controller according to an embodiment is shown in solid lines. The Bode diagram for a conventional PI controller is shown by dashed lines for comparison.

A phase path 61 of a regulator according to an embodiment is shown in the lower part of the Bode diagram. The second frequency 60 is twice the supply voltage frequency. The absolute value of this second frequency depends on the supply voltage frequency, may be different for different supply sources and is not important for the following explanations. The phase response 61 corresponds to the complex argument of the transfer function of the regulator according to an embodiment in which an additional phase shift is generated. At the second frequency 60, the phase path 61 has a function value which lies in an interval 63. The interval 63 defines an environment of a phase shift of -90 °. An absolute value of the difference between the interval limits of the interval 63 may be less than 90 °. The interval 63 can extend symmetrically by the value of -90 °.

With a closed loop this behavior leads to a total phase shift of -180 ° at the second frequency 60. Voltage ripples, which are present on the output side, are converted into a control voltage by the PI controller with the additional phase shift. The voltage ripples in the control voltage, which affects switching of the controllable switching means of the converter, can reduce the overall harmonic delay. This is true at least as long as the amplitude of the voltage ripple does not become too large.

The function value of the phase response 61 at the second frequency 60 indicates the phase shift that undergoes a sinusoidal signal through the combination of the PI with the additional phase shift.

The phase response 61 of the regulator used in embodiments may be strictly monotonic decreasing at the second frequency 60. This can be achieved by an appropriate choice of the additional poles of the transfer function, which lead to the phase shift.

The phase response 61 of the regulator used in embodiments may have a local maximum at a frequency less than the second frequency 60. It can thereby be achieved that the phase shift at the second frequency 60 in the interval 63 is around the value -90 °.

A phase response 62 of a conventional PI controller without additional phase shift is also shown in the lower part of the Bode diagram for comparison. The phase response 62 differs significantly from the phase path 61. At the second frequency 60, the phase signal 62 has a larger (and smaller magnitude) value than the phase path 61.

The upper part of the Bode diagram shows the gain 64 of the regulator used in embodiments and the gain 65 of a conventional PI controller without additional phase shift.

As has been described, the additional phase shift provided to the voltage ripple by the regulator causes the voltage ripple to even decrease the overall harmonic delay. It is not necessary to reduce voltage ripple in the control signal generated by the regulator by using a high capacitance output capacitor and / or using a small bandwidth regulator. FIG. 8 shows an exemplary time characteristic of an input current 71 for a switching arrangement according to an exemplary embodiment. FIG. 9 shows an exemplary time characteristic of an input current 72 for a switching arrangement with a conventional PI controller, in which no additional phase shift is generated. The input current 72 of FIG. 9 (conventional PI controller) was determined for a converter with an output capacitor whose capacitance was more than twice the capacitance of the output capacitor in the circuit arrangement according to an embodiment for which the input current 71 illustrated in FIG was determined. Despite the significantly smaller capacitance of the output capacitor, the overall harmonic delay for the circuit according to one embodiment (input current 71 of FIG. 8) is smaller than in the conventional converter (input current 72 of FIG. 9). FIG. 10 is a circuit diagram illustrating an implementation of a regulator in embodiments.

The regulator comprises a PI member 80, a filter 81 for defining a first pole of the transfer function, and another filter 82 for defining a second one. pole of the transfer function. The poles in the transfer function introduced by the filters 81, 82 are in an environment of twice the supply voltage frequency. For example, the P-element may have a capacitance 83 in series with a resistor 84. The filter 81 may have a capacity 85. The further filter 82 may have a further capacitance 86 and a further resistor 87.

The governor has a galvanic isolation. For example, an opto-coupler 90 may be provided between the primary side and the secondary side of the converter. Other elements for galvanic isolation can be used. In the illustrated implementation, the PI member 80 and the filter 81 are on the secondary side. The further filter 82 is arranged on the primary side.

The optocoupler 90 may be connected via a resistor 92 to a voltage source 91. An output of the combination of the PI element 80 and the filter 81 is connected to an input side of the optocoupler 90. An operational amplifier 93 may define a voltage reference. The operational amplifier 93 can keep a current at the output of the optocoupler 90 constant.

A voltage applied to a photodiode of the optocoupler 90 is provided by a voltage source 94 via a voltage divider comprising resistors 95, 96. A current flowing through the photodiode is supplied via a resistor 97 to an input of an operational amplifier 99. A voltage source 98 may provide a reference voltage to another input. The further filter 82 may be connected to the input and the output of the operational amplifier 99.

The signal Vc provided at the output of the operational amplifier can be used to control switching operations of the controllable switching means of a converter. For example, the ratio between on-time and off-time may be changed depending on the signal Vc. voltage ripple in the signal Vo representing the voltage on the output side are present with a corresponding phase shift in the signal Vo and affect the switching of the controllable switching means. Numerous other implementations of the various components of the controller may be used in other embodiments. Other configurations of the PI member and the filters 81, 82 may be used. The Pl member 80 and the filter 81 may be disposed on the primary side. The voltage Vo on the output side can be transmitted to the primary side via an optocoupler or other galvanic isolation.

In other embodiments, another controlled variable can be used to perform a voltage regulation. For example, a voltage which depends on the voltage of the output side can be detected on the primary side. By controlling the voltage detected on the primary side, the voltage on the output side can be regulated indirectly.

Figure 1 1 is a circuit diagram of a circuit arrangement according to an embodiment. An auxiliary inductor 101 may be inductively coupled to the secondary inductance 25. A voltage at the auxiliary inductance 101 can be detected. For example, the corresponding voltage can be supplied as an auxiliary signal Vaux to the voltage regulation loop 30 via an ohmic voltage divider 102. A reference voltage source 31 provides a signal Vaux_ref representing the target value.

The controller 13 may have further inputs in addition to an input 105 at which the auxiliary signal Vaux or the deviation of the auxiliary signal from the desired value is received. For example, the controller 13 may have an input 107 to detect when the main inductance 21 is de-magnetized. Switching operations can be triggered depending on when the main inductance 21 is demagnetized. The controller 13 controls at an output 106, a control signal with which the controllable switching means 23 is controlled. While embodiments have been described with reference to the figures, modifications may be made in other embodiments. For example, the controller, in which an additional phase shift for voltage ripple is deliberately introduced, can also be implemented in digital technology. A corresponding regulation, in which an additional phase shift for voltage ripple is deliberately introduced, can be used with different converter types. Methods and devices according to embodiments can be used in operating devices for lighting, for example in an LED converter.

Claims

P AT E N T A N S P R E C H E 1. Circuit arrangement for operating a luminous means (3), comprising:

an input (10) for receiving an AC voltage having a first frequency,

a power factor correction converter (12) comprising an inductance (21), a controllable switching means (23) connected in series with the inductor (21) and a regulator (13, 30; 41-43; 41, 43, 45, 46, 80-83), wherein the regulator (13, 30, 41-43, 41, 43, 45, 46, 80-83) comprises a P-member (41, 80) and is arranged to move one Phase shift (56) for a signal component of an input signal of the regulator (13, 30; 41-43; 41, 43, 45, 46; 80-83) having a second frequency (60) twice that of FIG first frequency is.

2. Circuit arrangement according to claim 1,

wherein the controller (13, 30, 41-43, 41, 43, 45, 46, 80-83) comprises the P-member (41, 80), a first pole, and a second pole.

3. Circuit arrangement according to claim 2,

wherein the first pole and the second pole are in an environment of the second frequency (60).

4. Circuit arrangement according to claim 2 or claim 3,

wherein the converter (12) has an input side with the inductance (21) and one of them galvanically isolated output side,

wherein the PIT member (41; 80) is provided on the output side of the transducer (12), and wherein a filter (82) whose transfer function has the second pole is provided on the input side of the transducer (12).

5. Circuit arrangement according to one of the preceding claims,

wherein the controller (13, 30, 41-43, 41, 43, 45, 46, 80-83) is arranged such that the phase shift (56) for the signal component in an input signal tervall (63) is a phase shift value of -90 °.

6. Circuit arrangement according to one of the preceding claims, wherein the controller (13, 30, 41-43, 41, 43, 45, 46, 80-83) is arranged so that the phase shift (56) for the signal component is approximately equal to -90 ° is.

7. Circuit arrangement according to one of the preceding claims, wherein the circuit arrangement comprises an integrated circuit (43) for controlling the controllable switching means (23),

wherein the integrated circuit has an input to receive the phase shifted signal component (51).

8. Circuit arrangement according to claim 7,

wherein the integrated circuit (43) is arranged to control the controllable one

Control means (23) to control so that an on-time and / or an off-time of the controllable switching means (23) on a phase of the phase-shifted signal component (55) depend.

9. Circuit arrangement according to one of the preceding claims, wherein the transducer (12) is a flyback converter which is connected via a rectifier (1 1) to the input (10).

10. Circuit arrangement according to one of the preceding claims, wherein the circuit arrangement (2) is an operating circuit for at least one light emitting diode (3).

1 1. System comprising

the circuit arrangement (2) according to one of the preceding claims and

at least one light emitting diode (3) connected to an output of the transducer (12).

12. Method for operating a luminous means (3) with a circuit Arrangement (2), which is supplied with an AC voltage having a first frequency and which comprises a converter (12),

wherein a controllable switching means (23) connected in series with an inductor (21) of the converter (12) is switched in a clocked manner, and

the method comprising voltage regulation with a regulator (13, 30; 41-43; 41, 43, 45, 46; 80-83) having a P-element (41; 80), and wherein the voltage regulation comprises generating a Phase shift (56) for a signal component (51) having a second frequency (60) twice the first frequency.

13. The method according to claim 12,

which is carried out with the circuit arrangement (2) according to one of claims 1 to 10.