WO2013131279A1 - 抵消多载波发射干扰的方法、装置、设备及系统 - Google Patents

抵消多载波发射干扰的方法、装置、设备及系统 Download PDF

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Publication number
WO2013131279A1
WO2013131279A1 PCT/CN2012/072143 CN2012072143W WO2013131279A1 WO 2013131279 A1 WO2013131279 A1 WO 2013131279A1 CN 2012072143 W CN2012072143 W CN 2012072143W WO 2013131279 A1 WO2013131279 A1 WO 2013131279A1
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WO
WIPO (PCT)
Prior art keywords
signal
order intermodulation
digital signal
transmitter
signal output
Prior art date
Application number
PCT/CN2012/072143
Other languages
English (en)
French (fr)
Inventor
毛孟达
叶四清
殷潜
蒲涛
Original Assignee
华为技术有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 华为技术有限公司 filed Critical 华为技术有限公司
Priority to PCT/CN2012/072143 priority Critical patent/WO2013131279A1/zh
Priority to ES12870365.9T priority patent/ES2629402T3/es
Priority to EP16206933.0A priority patent/EP3236589B1/en
Priority to EP12870365.9A priority patent/EP2787651B1/en
Priority to CN201280000456.7A priority patent/CN103493382B/zh
Publication of WO2013131279A1 publication Critical patent/WO2013131279A1/zh
Priority to US14/337,854 priority patent/US9432173B2/en
Priority to US15/203,538 priority patent/US9762376B2/en

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2626—Arrangements specific to the transmitter only
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/02—Transmitters
    • H04B1/04—Circuits
    • H04B1/0475—Circuits with means for limiting noise, interference or distortion
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/50—Circuits using different frequencies for the two directions of communication
    • H04B1/52—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa
    • H04B1/525—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa with means for reducing leakage of transmitter signal into the receiver
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36—Modulator circuits; Transmitter circuits
    • H04L27/366—Arrangements for compensating undesirable properties of the transmission path between the modulator and the demodulator
    • H04L27/367—Arrangements for compensating undesirable properties of the transmission path between the modulator and the demodulator using predistortion
    • H04L27/368—Arrangements for compensating undesirable properties of the transmission path between the modulator and the demodulator using predistortion adaptive predistortion
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/14—Two-way operation using the same type of signal, i.e. duplex
    • H04L5/1461—Suppression of signals in the return path, i.e. bidirectional control circuits

Definitions

  • the present invention relates to the field of communications technologies, and in particular, to a method, device, device and system for canceling multi-carrier transmit interference.
  • a base station device is an important component of a cellular mobile communication system and refers to a radio transceiver station that transmits information between a mobile communication switching center and a mobile telephone terminal in a certain radio coverage area.
  • a base station device generally includes a receiving device and a transmitting device, and the receiving device and the transmitting device are collectively referred to as a transceiver.
  • a duplexer In a frequency division duplex transceiver, in order to ensure that both the receiving device and the transmitting device can operate at the same time, a duplexer is usually used to isolate the transmitted and received signals.
  • the duplexer is composed of two sets of filters of different frequencies, which can prevent the transmission signal of the local machine from being transmitted to the receiving device, and can suppress the interference and noise entering the receiving device, and suppress the external transmitting spurs and interference of the transmitting device.
  • Multi-mode multi-carrier base transceivers can support multiple communication systems, such as GSM (Global System of Mobile communication), WCDMA (Wideband Code Division Multiple Access), and the like.
  • Base station equipment supporting multiple carriers facilitates network expansion. To this end, more and more operators are now adopting multi-carrier multi-mode base stations.
  • the transmit signal of the duplexer When the transmit signal of the duplexer is insufficiently suppressed by the receiver, it can be further filtered by other SAW (Surface Acoustic Wave) filters behind the receiver, but when the intermodulation of the signal transmitted by the multi-carrier base station passes through After the device falls into the receiving frequency band, if the intermodulation and the received signal are at the same frequency, the intermodulation will directly interfere with the received signal.
  • SAW Surface Acoustic Wave
  • the receive filter does not filter this band and can therefore only be suppressed by the transmit filter in the duplexer.
  • the transmit power per carrier is 40dBm
  • the transmitter's far-end intermodulation that is, the power difference between the intermodulation and the carrier
  • the signal's resolution bandwidth is 200kHz.
  • the noise of the interference signal entering the receiver is required to be compared with the antenna port thermal noise.
  • Such a high degree of suppression requires that the duplexer can only be realized by increasing the number of filter chambers, resulting in a large size of the duplexer.
  • One aspect of the present invention provides a method and apparatus for canceling multi-carrier transmit interference, which can effectively cancel high-order intermodulation interference of a multi-carrier transmitter to a receiver, thereby reducing the design difficulty and suppression requirements of the duplexer.
  • Another aspect of the present invention provides a transceiver, a base station, and a communication system, which effectively cancels high-order intermodulation interference in a multi-carrier system receiver and reduces device complexity.
  • a method for canceling multi-carrier transmit interference including:
  • the digital signal output by the receiver is interfered with by the second digital signal.
  • a device for canceling multi-carrier transmit interference comprising:
  • a high-order intermodulation signal acquisition unit for collecting high-order intermodulation signals in a radio frequency signal output by the transmitter
  • a first signal processing unit configured to process the high-order intermodulation signal to generate a first digital signal
  • a high-order intermodulation model establishing unit configured to establish a high-order intermodulation model by using the first digital signal and the first baseband signal output by the transmitter;
  • a second signal processing unit configured to generate a second digital signal by using a coefficient of the high-order intermodulation model and a second baseband signal output by the transmitter;
  • the interference cancellation unit is configured to perform interference cancellation on the digital signal output by the receiver and the second digital signal.
  • a transceiver comprising a transmitter and a receiver, further comprising said means for canceling multi-carrier transmit interference.
  • An embodiment of the present invention further provides a base station including the transceiver.
  • the embodiment of the invention further provides a communication system including the base station.
  • the method, device, device and system for canceling multi-carrier transmit interference process a high-order intermodulation signal by acquiring a high-order intermodulation signal in a radio frequency signal output by a transmitter to generate a first digital signal And using the first digital signal and the baseband signal output by the transmitter to establish a high-order intermodulation model, using the coefficients of the high-order intermodulation model and the baseband signal to generate a second digital signal, and outputting the digital signal of the receiver Interference cancellation is performed with the second digital signal, so that high-order intermodulation interference in the receiver can be effectively cancelled, and the design difficulty and suppression requirement of the duplexer are reduced.
  • 1 is a basic block diagram of a conventional multi-carrier transceiver
  • FIG. 2 is a non-linear diagram of an output signal and an input signal in a conventional multi-carrier transceiver;
  • FIG. 3 is a flowchart of a method for canceling multi-carrier transmission interference according to an embodiment of the present invention
  • FIG. 4 is a schematic structural diagram of an apparatus for canceling multi-carrier transmission interference according to an embodiment of the present invention
  • FIG. 5 is a schematic structural diagram of a transceiver according to an embodiment of the present invention
  • FIG. 6 is another schematic structural diagram of a transceiver according to an embodiment of the present invention.
  • FIG. 1 A basic block diagram of an existing multi-carrier transceiver is shown in FIG. 1, wherein the transmitter includes a transmitter digital processing unit 111 and a transmitter radio frequency processing unit 112, and the receiver includes a receiver digital processing unit 121 and receiver radio frequency processing.
  • Unit 122 the multi-carrier transceiver can also To include: a duplexer 13, a transmit feedback unit 14, and a digital predistortion unit 15.
  • the output signal and the input signal are nonlinear, as shown in Figure 2, 21, such nonlinearity will lead to spectrum proliferation, and intermodulation signals appear. If the compensation function is added in the digital domain, so that the compensation characteristics (shown as 22 in Fig. 2) and the nonlinearity of the downlink cancel each other out, the entire system can be operated in a linear state.
  • the transmitting feedback unit 14 in FIG. 1 is disposed in the feedback channel, and performs frequency conversion, analog-to-digital conversion and the like on the RF signal outputted by the coupled transmitter, and then outputs the processed digital signal to the digital predistortion unit. 15.
  • the digital predistortion unit 15 performs downlink nonlinear modeling according to the baseband signal of the transmitter and the digital signal output by the transmission feedback unit 14, obtains a compensation coefficient according to the nonlinear model, and compensates the output signal in the digital domain by using the obtained compensation coefficient, thereby Make the entire system work close to linear.
  • the sampling rate of the DAC (digital-to-analog converter) of the transmit channel and the sampling rate of the ADC (analog-to-digital converter) of the feedback channel are limited, and the modeling dynamics are limited (according to Nyquist) Nyquist's law, the sampling signal bandwidth is up to half of the sampling rate. If the sampling rate of the ADC is 500MHz, then theoretically, only the signal with a bandwidth of 250MHz can be collected, that is, the intermodulation distance from the center frequency is up to 125MHz. The dynamics are limited, such as a signal-to-noise ratio of 70 dB, and the high-order intermodulation signal is 70 dB lower than the main signal.
  • digital pre-distortion can only be used for a band close to the baseband signal (ie, the effective acquisition on the feedback channel).
  • Correction of the intermodulation of the bandwidth of the signal for example, in the case of a large bandwidth of a multi-carrier signal (such as 75 MHz), only the correction of 3rd order and 5th order can be supported, and for the high order (usually 5th order or more, specific The order is related to the bandwidth of the multicarrier signal and the frequency of the resulting intermodulation signal.
  • the intermodulation signal that falls into the receiver section cannot be acquired and corrected.
  • the method, device and transceiver for canceling multi-carrier transmit interference based on the original feedback channel, acquire high-order intermodulation signals of the transmit channel, and amplify the need for cancellation
  • the order intermodulation signal improves the signal-to-noise ratio of the high-order intermodulation signal, adaptively cancels the generated high-order intermodulation signal and the signal collected by the receiver, achieves the purpose of canceling the transmission interference, and reduces the transmission filtering of the duplexer.
  • the requirement for the degree of suppression of the receiving band is the requirement for the degree of suppression of the receiving band.
  • FIG. 3 it is a flowchart of a method for canceling multi-carrier transmission interference according to an embodiment of the present invention, which includes the following steps:
  • Step 301 Acquire a high-order intermodulation signal in the radio frequency signal output by the transmitter.
  • the radio frequency signal outputted by the radio frequency processing unit of the transmitter may be coupled out a part, and then the main signal and the low-order intermodulation signal in the coupled radio frequency signal are filtered out to obtain a high-order intermodulation signal, and the high-order inter-modulation signal is amplified. Adjust the signal to the desired signal amplitude.
  • a part of the radio frequency signal can be coupled through a parallel transmission line, and the coupling degree can be 20-50 dB, that is, the coupled RF signal power is 1/100-1 of the total power of the RF signal output by the transmitter RF processing unit. /100000, that is to say, the power of the RF signal to be transmitted has substantially no effect.
  • Step 302 Process the high-order intermodulation signal to generate a first digital signal.
  • the processing may mainly include performing a process of down-converting, analog-to-digital conversion, and the like on the high-order intermodulation signal.
  • Step 303 Establish a high-order intermodulation model by using the first digital signal and the baseband signal output by the transmitter.
  • a coefficient table of the high-order intermodulation model may be established according to the amplitude and phase characteristics of the baseband signal and the amplitude and phase characteristics of the first digital signal, where different coefficients correspond to different amplitudes and Phase.
  • the baseband signal output by the transmitter can correspond to the RF signal output by the acquired transmitter.
  • the process of establishing the high-order intermodulation model may be performed only by using the baseband signal for a period of time when the transceiver is initialized, or may be performed as needed, for example, to improve accuracy, Performed at intervals (equal or unequal).
  • Step 304 Generate a second digital signal by using the coefficients of the high-order intermodulation model and the baseband signal output by the transmitter.
  • the baseband signal is multiplied by the coefficients of the high-order intermodulation model to obtain a second digital signal.
  • the coefficients of the above high-order intermodulation model may be a discrete set of values.
  • the baseband signal output by the transmitter may be a baseband signal in the process of establishing the high-order intermodulation model in steps 301-303, or may be a baseband signal in the process of establishing the non-step 301-303 high-order intermodulation model.
  • a set of high-order intermodulation models can be used to establish the required device time-sharing to establish a high-order intermodulation model for the multi-channel transmission channel, or
  • devices such as acquisition and/or analog to digital conversion required to establish a high-order intermodulation model are time-sharing, so that the device structure of the high-order intermodulation cancellation can be reduced and the system cost can be reduced.
  • Step 305 Perform interference cancellation on the digital signal output by the receiver and the second digital signal.
  • the digital signal output by the receiver corresponds to the baseband signal output by the transmitter described in step 304.
  • the RF signal output by the transmitter collected in step 301 is compared with the RF signal output by the undetected transmitter, the transmission of the RF signal output by the undetected transmitter will pass through the duplexer, the antenna, and the air interface. a transmission path such as a transmission and reception channel. Therefore, the digital signal output by the receiver has the aforementioned transmission path in accordance with the amplitude and phase of the second digital signal obtained from the high-order intermodulation model established based on the acquired RF signal output from the transmitter. Therefore, during the cancellation, the second digital signal can be adaptively equalized, that is, the influence of the transmission path on the signal is simulated to adjust the second digital signal.
  • the digital signal output by the receiver can be delayed for a predetermined time. That is, it is optional to delay the digital signal output by the receiver for a predetermined time.
  • the adaptively equalized second digital signal can be subtracted from the delayed digital output of the receiver.
  • the above adaptive equalization can be implemented on multiple carriers that are combined, and specifically, can be implemented in the time domain or in the frequency domain.
  • time domain When implemented in the time domain, it can be filtered by FIR (finite impulse response) or IIR (infinite impulse response); when implemented in the frequency domain, FFT (fast Fourier transform), frequency domain amplitude and phase weighting and IFFT (fast) can be used.
  • FFT fast Fourier transform
  • frequency domain amplitude and phase weighting and IFFT fast
  • Fourier inverse transform is combined with filtering.
  • time domain equalization and the frequency domain equalization can implement complex amplitude and phase adjustment. Whether it is time domain equalization or frequency domain equalization, adaptive equalization can use LMS (least mean square), LS (least squares), RLS ( Recursive least squares) or other adaptive equalization algorithms.
  • LMS least mean square
  • LS least squares
  • RLS Recursive least squares
  • the predetermined time delay of the digital signal output by the receiver is used to compensate for the average delay difference between the adaptively equalized digital signal and the digital signal output by the receiver digital processing unit.
  • the average delay difference may be a frequency domain average. Differences at different frequency points are achieved by adaptive equalization.
  • the digital signal output by the receiver may not be delayed by a predetermined time, that is, the predetermined time may be zero.
  • the foregoing adaptive equalization may also be implemented separately on each multi-carrier, and correspondingly, the second digital signal is adaptively equalized on each carrier, and similarly, the digital processing unit from the receiver The digital signals are each delayed by a predetermined time on each carrier. Then, the adaptively equalized second digital signal is correspondingly subtracted from the delayed digital signal on each carrier.
  • the high-order intermodulation interference signal can be completely cancelled, that is, the subtracted difference
  • the signal no longer contains high order intermodulation interference signals. Therefore, it is possible to reduce the design difficulty and suppression requirements of the duplexer under the same transmission and reception isolation.
  • the method for canceling multi-carrier transmission interference in the embodiment of the present invention can be applied to all wireless communication technologies, such as mobile communication systems, fixed wireless access, wireless data transmission, and the like.
  • the embodiment of the present invention further provides a device for canceling multi-carrier transmission interference, as shown in FIG. 4, which is a schematic structural diagram of the device.
  • the apparatus includes:
  • a high-order intermodulation signal acquisition unit 401 configured to acquire a high-order intermodulation signal in the radio frequency signal output by the transmitter;
  • the first signal processing unit 402 is configured to process the high-order intermodulation signal to generate a first digital signal
  • a high-order intermodulation model establishing unit 403, configured to establish a high-order intermodulation model by using the first digital signal and the first baseband signal output by the transmitter; wherein the first baseband signal output by the transmitter can be combined with the collected transmission Corresponding to the RF signal output by the machine;
  • a second signal processing unit 404 configured to generate a second digital signal by using a coefficient of the high-order intermodulation model and a second baseband signal output by the transmitter; where the second baseband signal output by the transmitter may be a transmitter output
  • the first baseband signal may also be another baseband signal output by the transmitter;
  • the interference cancellation unit 405 is configured to perform interference cancellation on the digital signal output by the receiver and the second digital signal, where the digital signal output by the receiver is The second baseband signal output by the transmitter utilized by the second signal processing unit 404 corresponds.
  • a specific structure of the high-order intermodulation signal acquisition unit 401 may include: a coupling unit, Filter unit and amplification unit. among them:
  • the coupling unit is configured to couple a radio frequency signal output by the transmitter out of a part
  • the filtering unit is configured to filter out the main signal and the low-order intermodulation signal in the coupled RF signal to obtain a high-order intermodulation signal;
  • the amplifying unit is configured to amplify the high-order intermodulation signal.
  • a specific structure of the above-described interference cancellation unit 405 may include: an adaptive equalization unit and a subtraction unit. among them:
  • the adaptive equalization unit is configured to adaptively equalize the second digital signal; the subtraction unit is configured to subtract the adaptively equalized second digital signal from the delayed digital signal.
  • the phase-reduction unit may be implemented by using an inverter or an adder, and may be implemented in other forms, which is not limited herein.
  • the interference cancellation unit 405 may further include: a delay unit that delays the digital signal output by the receiver by a predetermined time when the digital signal output by the receiver is earlier in time than the second digital signal.
  • adaptive equalization may be performed on the combined multi-carriers, that is, only one adaptive equalization unit is needed, and correspondingly, only one The delay unit and one of the subtraction units.
  • the adaptive equalization may be performed on each carrier.
  • the number of the adaptive equalization units needs to be the same as the number of carriers.
  • the number of the delay unit and the subtraction unit should also be the same as the number of carriers, and each carrier signal is respectively subtracted in the corresponding subtraction unit.
  • the high-order intermodulation interference signal can be completely cancelled, that is, the subtracted difference
  • the signal no longer contains high order intermodulation interference signals. Therefore, it is possible to reduce the design difficulty and suppression requirements of the duplexer under the same transmission and reception isolation.
  • the apparatus for canceling multi-carrier transmission interference in the embodiment of the present invention can be applied to all wireless communication technologies, such as a mobile communication system, a fixed wireless access, a wireless data transmission, and the like.
  • the device embodiments described above are merely illustrative.
  • the device as a sub-transmission interference can be applied as an independent device to an existing multi-carrier transceiver, or can be combined with an existing multi-carrier transceiver.
  • the combination of machines makes full use of existing units and reduces equipment costs. This will be described in detail below.
  • FIG. 5 it is a schematic structural diagram of a transceiver to which the embodiment of the present invention is applied.
  • the means for canceling multi-carrier transmit interference is applied as an independent device to an existing multi-carrier transceiver, and the process of downlink nonlinear compensation of the transmit channel and interference cancellation of the receive channel is performed independently.
  • the transmitting feedback unit 14 performs frequency conversion, analog-to-digital conversion and the like on the RF signal outputted by the coupled transmitter, and then outputs the processed digital signal to the digital pre-distortion unit 15.
  • the digital predistortion unit 15 performs downlink nonlinear modeling according to the baseband signal of the transmitter and the digital signal output by the transmission feedback unit 14, obtains a compensation coefficient according to the nonlinear model, and compensates the output signal in the digital domain by using the obtained compensation coefficient, thereby Make the entire system work close to linear.
  • the high-order intermodulation signal acquisition unit 401 collects a high-order intermodulation signal in the radio frequency signal output by the transmitter, and the first signal processing unit 402 processes the high-order intermodulation signal to generate a first digital signal;
  • the intermodulation model establishing unit 403 uses the first digital signal and the first baseband signal output by the transmitter (the baseband signal may be a nonlinearly compensated baseband signal, or may be a baseband signal before nonlinear compensation) to establish a high-order intermodulation.
  • the second digital signal is generated by the second signal processing unit 404 using the coefficients of the high order intermodulation model and the second baseband signal output by the transmitter.
  • the interference cancellation unit 405 adaptively cancels the digital signal corresponding to the second baseband signal output by the receiver and the second digital signal, and achieves the purpose of canceling the transmission interference, and reduces the duplexer in the receiving frequency band. The requirement of the emission suppression of the reception.
  • FIG. 6 is another schematic structural diagram of a transceiver to which the embodiment of the present invention is applied.
  • the means for canceling multi-carrier transmit interference is combined with existing multi-carrier transceivers to make full use of existing units.
  • the filtering unit 501 and the amplifying unit 502 in the high-order intermodulation signal acquiring unit are disposed in the high-order intermodulation acquisition channel, and the existing transmission feedback unit 503 is disposed in the feedback channel, and the transmission feedback unit 503 also serves as the cancellation multi-carrier transmission interference.
  • First signal processing unit in the device implemented Frequency conversion and analog to digital conversion.
  • the high-order intermodulation acquisition channel and the pre-distortion channel for collecting the RF signal output by the transmitter are controlled by the control unit 504 to be connected to the feedback channel.
  • the control unit 504 can complete the above control function through a switch.
  • the predistortion channel and the high order intermodulation acquisition channel operate in a time division manner, and the specific time allocation can be determined according to the predistortion correction and the high order intermodulation cancellation performance.
  • the specific time allocation can be determined according to the predistortion correction and the high order intermodulation cancellation performance.
  • Both the downlink nonlinear modeling unit 601 and the predistortion unit 602 in the digital predistortion unit can be part of the transmitter digital processing unit 511.
  • the high-order intermodulation model establishing unit 701, the second signal processing unit 702, and the interference canceling unit 703 in the apparatus for canceling multi-carrier transmission interference can be part of the receiver digital processing unit 521.
  • the transmitter radio frequency processing unit 512, the receiver radio frequency processing unit 522, and the duplexer 531 are the same as in the prior art.
  • the hardware circuit implements the cartridge without adding additional ADC and frequency conversion modules.
  • the interference cancellation function may not be activated.
  • the high-order intermodulation model f ( MM ) of the power amplifier is obtained by collecting the high-order signal of the power amplifier. Once the model is obtained, the model and the pre-distorted baseband signal can be used to obtain the current The high-order intermodulation components are cancelled by the interference cancellation unit 703.
  • the digital pre-distorted signal is also continuously outputted, and the digital signal of the high-order intermodulation model establishing unit 701 is also continuously output, and the high-order intermodulation formed by the digital domain and the high-order mutual output of the power amplifier output.
  • the adjustment is consistent, thereby adaptively canceling the generated high-order intermodulation signal and the high-order intermodulation interference signal in the signal received by the receiver. Therefore, it is possible to reduce the design difficulty and suppression requirements of the duplexer under the same transmission and isolation isolation.
  • the embodiment of the present invention further provides a base station, where the base station includes the transceiver in the foregoing embodiment, and the transceiver includes: not only a transmitter and a receiver, but also a multi-carrier transmission interference described above.
  • Device wherein the device for canceling multi-carrier emission interference can be used as a stand-alone device It can be applied to existing multi-carrier transceivers, and can also be combined with existing multi-carrier transceivers to make full use of existing units and reduce equipment costs.
  • the base station can be applied to all wireless communication systems, such as mobile communication systems, fixed wireless access, wireless data transmission, and the like.
  • All or part of the steps in the method in the embodiment of the present invention may be completed by a related hardware such as a program, and the program may be stored in a computer readable storage medium, such as a ROM. /RAM, disk, CD, etc.
  • a related hardware such as a program
  • the program may be stored in a computer readable storage medium, such as a ROM. /RAM, disk, CD, etc.

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  • Engineering & Computer Science (AREA)
  • Signal Processing (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Transceivers (AREA)
  • Noise Elimination (AREA)
  • Transmitters (AREA)

Abstract

一种抵消多载波发射干扰的方法、装置及收发信机。该方法包括：采集发射机输出的射频信号中的高阶互调信号；对所述高阶互调信号进行处理，生成第一数字信号；利用所述第一数字信号和发射机输出的第一基带信号建立高阶互调模型；利用所述高阶互调模型的系数和发射机输出的第二基带信号生成第二数字信号；将接收机输出的数字信号与所述第二数字信号进行干扰抵消。利用本发明，可以有效抵消多载波发射机对接收机的高阶互调干扰，进而降低双工器设计难度及抑制度需求。

Description

抵消多载^射干扰的方法、 装置、 设备及系统
技术领域
本发明涉及通信技术领域， 具体涉及一种抵消多载波发射干扰的方法、 装置、 设备及系统。
背景技术
基站设备是蜂窝移动通信系统的重要部件， 是指在一定的无线电覆盖区 中， 通过移动通信交换中心与移动电话终端之间进行信息传递的无线电收发 信电台。 基站设备一般包括接收设备和发射设备， 接收设备和发射设备统称 为收发信机。
在频分双工收发信机中， 为了保证接收设备和发射设备都能同时工作， 通常会采用双工器将发射和接收信号相隔离。 双工器由两组不同频率的滤波 器组成， 可以避免本机发射信号传输到接收设备， 同时可以抑制进入到接收 设备的干扰及噪声， 抑制发射设备对外的发射杂散及干扰。
多模多载波基站收发信机可以支持多个通信制式， 比如 GSM ( Global System of Mobile communication, 全球移动通讯 )、 WCDMA ( Wideband Code Division Multiple Access, 宽带码分多址）等。 支持多个载波的基站设备， 便 于实现网络扩容。 为此， 现在越来越多的运营商采用多载波多模基站。
当双工器的发射信号对接收机抑制度不够时， 可以通过接收机后面的其 它 SAW ( Surface Acoustic Wave, 表面声波滤波）等滤波器进一步滤波， 但当 多载波基站发射信号的互调通过双工器后落入接收频段， 如果互调和接收信 号同频， 则互调会直接干扰接收信号。 例如，假设在 1800MHz的 GSM频段， 两发射信号为 1805MHz和 1828.75MHz, 两信号间隔 23.75MHz,发射信号的 7阶互调在 1805MHz-3*23.75MHz=1733.75MHz,而接收信号正好在 1710MHz 和 1733.75MHz, 这种情况下， 接收滤波器对本频段不起滤波作用， 因此只能 通过双工器中的发射滤波器来抑制。 以发射信号每载波发射功率为 40dBm, 发射机远端互调 （即互调与载波之间的功率差） 为 60dBc, 信号的解析带宽 200kHz, 要求干扰信号进入接收机的噪声比天线口热噪声低 10dB 为例， 则 在接收频段需要的发射滤波器的收发抑制度在接收频段要求为（ 40-60 ) dBm- ( -174dBm+10*lg(200k)-10 ) = 111 dB, 其中， -174dBm 为天线口常温下每 Hz的热噪声。 如此高的抑制度要求双工器只能通过增加滤波腔数来实现， 导 致双工器的尺寸很大。
随着通信基站设备的小型化需求不断深入和新形态的基站 （如具有有源 天线的基站） 的出现， 降低双工器设计难度以及降低双工器抑制度需求显得 非常重要。
发明内容
本发明一方面提供一种抵消多载波发射干扰的方法及装置， 可以有效抵 消多载波发射机对接收机的高阶互调干扰， 进而降低双工器设计难度及抑制 度需求。
本发明另一方面提供一种收发信机、 基站及通信系统， 有效抵消多载波 系统接收机中的高阶互调干扰， 降低设备的复杂度。
为此， 本发明实施例提供如下技术方案：
一种抵消多载波发射干扰的方法， 包括：
采集发射机输出的射频信号中的高阶互调信号；
对所述高阶互调信号进行处理， 生成第一数字信号；
利用所述第一数字信号和发射机输出的第一基带信号建立高阶互调模 型；
利用所述高阶互调模型的系数和发射机输出的第二基带信号生成第二数 字信号；
将接收机输出的数字信号与所述第二数字信号进行干扰抵消。
一种抵消多载波发射干扰的装置， 包括：
高阶互调信号采集单元， 用于采集发射机输出的射频信号中的高阶互调 信号；
第一信号处理单元， 用于对所述高阶互调信号进行处理， 生成第一数字 信号；
高阶互调模型建立单元， 用于利用所述第一数字信号和发射机输出的第 一基带信号建立高阶互调模型；
第二信号处理单元， 用于利用所述高阶互调模型的系数和发射机输出的 第二基带信号生成第二数字信号； 干扰抵消单元， 用于将接收机输出的数字信号与所述第二数字信号进行 干扰氏消。
一种收发信机， 包括发射机和接收机， 还包括所述的抵消多载波发射干 扰的装置。
本发明实施例还提供一种包括所述的收发信机的基站。
本发明实施例还提供一种包括所述基站的通信系统。
本发明提供的抵消多载波发射干扰的方法、 装置、 设备及系统， 通过采 集发射机输出的射频信号中的高阶互调信号，对所述高阶互调信号进行处理， 生成第一数字信号， 利用所述第一数字信号和发射机输出的基带信号建立高 阶互调模型， 利用所述高阶互调模型的系数和所述基带信号生成第二数字信 号， 将接收机输出的数字信号与所述第二数字信号进行干扰抵消， 从而可以 有效地抵消接收机中的高阶互调干扰， 降低双工器设计难度及抑制度需求。 附图说明
为了更清楚地说明本申请实施例或现有技术中的技术方案， 下面将对实 施例中所需要使用的附图作筒单地介绍， 显而易见地， 下面描述中的附图仅 仅是本发明中记载的一些实施例， 对于本领域普通技术人员来讲， 还可以根 据这些附图获得其他的附图。
图 1是现有的多载波收发信机的基本框图；
图 2是现有的多载波收发信机中输出信号与输入信号的非线性示意图； 图 3是本发明实施例抵消多载波发射干扰的方法的流程图；
图 4是本发明实施例抵消多载波发射干扰的装置的结构示意图； 图 5是本发明实施例收发信机的一种结构示意图；
图 6是本发明实施例收发信机的另一种结构示意图。
具体实施方式
为了使本技术领域的人员更好地理解本发明实施例的方案， 下面结合附 图和实施方式对本发明实施例作进一步的详细说明。
现有的多载波收发信机的基本框图如图 1所示， 其中， 发射机包括发射 机数字处理单元 111和发射机射频处理单元 112,接收机包括接收机数字处理 单元 121和接收机射频处理单元 122, 除此之外， 所述多载波收发信机还可 以包括： 双工器 13、 发射反馈单元 14和数字预失真单元 15。
由于功放的非线性， 会使输出信号和输入信号成非线性， 如图 2中 21所 示， 这样的非线性会导致频谱增生， 出现互调信号。 如果在数字域中增加补 偿功能， 使补偿特性（如图 2中 22所示 )正好和下行的非线性互相抵消， 则 可以使整个系统工作在线性状态下。
基于上述原理， 图 1中的发射反馈单元 14设置在反馈通道， 对耦合出的 发射机输出的射频信号进行变频、 模数转换等处理， 然后将处理后得到的数 字信号输出给数字预失真单元 15。 数字预失真单元 15根据发射机的基带信 号及发射反馈单元 14输出的数字信号进行下行非线性建模，根据非线性模型 获取补偿系数， 利用获取的补偿系数对输出信号在数字域进行补偿， 从而使 整个系统工作接近线性。
由于数字预失真建模的阶数有限， 发射通道的 DAC (数模转换器） 的采 样率及反馈通道的 ADC (模数转换器） 的采样率有限， 建模动态有限（根据 内奎斯特奈奎斯特定律， 采样信号带宽最高为采样率的一半， 如果 ADC的采 样率为 500MHz,那么理论上最大只能采集 250MHz带宽的信号， 即互调离中 心频点最大为 125MHz。 另外高速 ADC的动态有限， 如信噪比为 70dB, 而高 阶互调信号则会比主信号低 70dB以上）， 因此， 数字预失真只能对靠近基带 信号的一段频段 (即反馈通道上有效的采集的信号的带宽 )的互调进行校正， 比如在多载波信号的带宽很大（如 75MHz )的情况下， 只能支持 3阶和 5阶 的校正， 而对高阶（通常为 5阶以上， 具体阶数与多载波信号的带宽和所产 生的互调信号的频率相关） 落入接收机部分的互调信号则无法采集并校正。
针对上述技术问题， 本发明实施例抵消多载波发射干扰的方法、 装置及 收发信机， 在基于原反馈通道的基础上， 通过采集发射通道的高阶互调信号， 并放大需要对消的高阶互调信号， 提高高阶互调信号的信噪比， 将生成的高 阶互调信号与接收机采集到的信号自适应对消， 达到抵消发射干扰的目的， 降低双工器的发射滤波器在接收频段的抑制度的要求。
如图 3所示， 是本发明实施例抵消多载波发射干扰的方法的流程图， 包 括以下步骤：
步骤 301 , 采集发射机输出的射频信号中的高阶互调信号。 具体地， 可以将发射机射频处理单元输出的射频信号耦合出一部分， 然 后滤除耦合出的射频信号中的主信号及低阶互调信号， 得到高阶互调信号， 放大所述高阶互调信号到所需的信号幅度。
需要说明的是， 可以通过一段平行的传输线耦合出一部分射频信号， 耦 合度可以为 20-50dB , 即耦合出的射频信号功率为发射机射频处理单元输出 的射频信号总功率的 1/100-1/100000,也就是说，对待发射的射频信号的功率 基本不产生影响。
步骤 302, 对所述高阶互调信号进行处理， 生成第一数字信号。
该处理过程主要可以包括对所述高阶互调信号进行下变频、 模数转换等 处理。
步骤 303 , 利用所述第一数字信号和发射机输出的基带信号建立高阶互 调模型。
具体地， 可以根据所述基带信号的幅度及相位特性以及所述第一数字信 号的幅度及相位特性建立高阶互调模型的系数表， 在该系数表中， 不同的系 数对应不同的幅度及相位。 发射机输出的基带信号可以和所采集的发射机输 出的射频信号相对应。
在本实施例中， 高阶互调模型的建立过程， 即步骤 301-303 , 可以仅在收 发信机工作初始化时利用一段时间的基带信号进行， 也可以根据需要进行， 比如为了提高精度， 每隔一段时间 （间隔相等或不等）进行。
步骤 304, 利用所述高阶互调模型的系数和发射机输出的基带信号生成 第二数字信号。
也就是说， 将所述基带信号乘上所述高阶互调模型的系数， 得到第二数 字信号。 需要说明的是， 上述高阶互调模型的系数可以是离散的一组数值。 本步骤中， 发射机输出的基带信号可以为步骤 301-303 高阶互调模型的建立 过程中的基带信号， 也可以为非步骤 301-303 高阶互调模型的建立过程中的 基带信号。 利用建立好的高阶互调模型对非步骤 301-303 高阶互调模型的建 立过程中的基带信号进行干扰抵消， 可以避免实时地采集高阶互调信号对器 件的需求， 而且在多路发射通道的情况下， 可以利用一套高阶互调模型建立 所需的装置分时对多路发射通道进行高阶互调模型的建立， 或者， 在存在数 字预失真通道的情况下， 将高阶互调模型建立所需的采集和 /或模数转换等装 置进行分时共享， 这样， 可以筒化高阶互调对消的装置结构和降低系统成本。
步骤 305, 将接收机输出的数字信号与所述第二数字信号进行干扰抵消。 其中， 接收机输出的数字信号与步骤 304中所述的发射机输出的基带信号相 对应。
首先， 由于步骤 301 中采集到的发射机输出的射频信号与未采集到的发 射机输出的射频信号相比， 未采集到的发射机输出的射频信号的传输会经由 双工器、 天线、 空口传输及接收通道等传输路径， 因此， 接收机输出的数字 信号较根据采集到的发射机输出的射频信号建立的高阶互调模型获得的第二 数字信号的幅度和相位具备了前述的传输路径的特性， 因而， 抵消过程中， 可以将所述第二数字信号进行自适应均衡， 即模拟上述传输路径对信号的影 响对第二数字信号进行调整。 其次， 如若接收机输出的数字信号较第二数字 信号在时间上更早， 则可以将接收机输出的数字信号进行预定时间的延迟。 也就是说， 将接收机输出的数字信号进行预定时间的延迟为可选的。 最后， 可以将经过自适应均衡后的第二数字信号与经过延迟后的接收机输出的数字 信号相减。
上述自适应均衡可以在合路的多载波上实现， 具体地， 可以在时域实现， 也可以在频域实现。 当在时域实现时， 可以利用 FIR (有限脉沖响应 )或 IIR (无限脉沖响应）进行滤波； 当在频域实现时， 可以利用 FFT (快速傅立叶 变换）、 频域幅相加权与 IFFT (快速傅里叶反变换 )相结合的方法进行滤波。
所述时域均衡和频域均衡均可以实现复杂的幅相调整， 不论是时域均衡 还是频域均衡， 自适应均衡均可以使用 LMS (最小均方）、 LS (最小二乘）、 RLS (递推最小二乘）或者其它自适应均衡算法。
上述对接收机输出的数字信号进行预定时间的延迟是用来补偿自适应均 衡后的数字信号与接收机数字处理单元输出的数字信号之间的平均延时差 异。 所述平均延时差异可以是频域平均。 在不同频率点上的差异性通过自适 应均衡来完成。
需要说明的是， 在某些情况下， 也可以不用对接收机输出的数字信号进 行预定时间的延迟， 即预定时间可以是 0。 另外需要说明的是， 上述自适应均衡还可以在各个多载波上分别实现， 相应地， 即将所述第二数字信号在各个载波上分别进行自适应均衡， 同样地， 将来自接收机数字处理单元的数字信号在各个载波上分别进行预定时间的延 迟。 然后， 将自适应均衡后的第二数字信号与延迟后的数字信号在各个载波 上对应相减。
不论上述自适应均衡是在合路的多载波上实现， 还是在各个多载波上分 别实现， 在理想情况下， 高阶互调干扰信号可以被完全抵消， 也就是说， 相 减后的差值信号不再含有高阶互调干扰信号。 因此， 可以在相同的收发隔离 的情况下， 降低双工器设计难度及抑制度需求。
需要说明的是， 本发明实施例抵消多载波发射干扰的方法可以应用在所 有无线通信技术领域， 例如移动通信系统、 固定无线接入、 无线数据传输等 系统中。
相应地， 本发明实施例还提供一种抵消多载波发射干扰的装置， 如图 4 所示， 是该装置的一种结构示意图。
在该实施例中， 所述装置包括：
高阶互调信号采集单元 401 , 用于采集发射机输出的射频信号中的高阶 互调信号；
第一信号处理单元 402, 用于对所述高阶互调信号进行处理， 生成第一 数字信号；
高阶互调模型建立单元 403 , 用于利用所述第一数字信号和发射机输出 的第一基带信号建立高阶互调模型； 其中， 发射机输出的第一基带信号可以 与所采集的发射机输出的射频信号相对应；
第二信号处理单元 404, 用于利用所述高阶互调模型的系数和发射机输 出的第二基带信号生成第二数字信号； 其中， 发射机输出的第二基带信号可 以为发射机输出的第一基带信号， 也可以为发射机输出的其他基带信号； 干扰抵消单元 405 , 用于将接收机输出的数字信号与所述第二数字信号 进行干扰抵消， 其中， 接收机输出的数字信号与第二信号处理单元 404所利 用的所述的发射机输出的第二基带信号相对应。
上述高阶互调信号采集单元 401的一种具体结构可以包括： 耦合单元、 滤波单元和放大单元。 其中：
所述耦合单元用于将发射机输出的射频信号耦合出一部分；
所述滤波单元用于滤除耦合出的射频信号中的主信号及低阶互调信号， 得到高阶互调信号；
所述放大单元用于放大所述高阶互调信号。
上述干扰氏消单元 405的一种具体结构可以包括： 自适应均衡单元和相 减单元。 其中：
所述自适应均衡单元用于将所述第二数字信号进行自适应均衡； 所述相减单元用于将经过自适应均衡后的第二数字信号与经过延迟后的 数字信号相减。
所述相减单元可以采用反相器和加法器实现，也可以采用其他形式实现， 在此不作限定。
上述干扰抵消单元 405还可以包括： 延迟单元， 用于接收机输出的数字 信号较第二数字信号在时间上更早的情况下， 将接收机输出的数字信号进行 预定时间的延迟。
需要说明的是， 上述干扰抵消单元 405对多载波信号进行干扰抵消时， 可以在合路的多载波上进行自适应均衡，即只需要一个所述自适应均衡单元， 相应地， 也只需要一个所述延迟单元和一个所述相减单元。 上述干扰抵消单 元 405对多载波信号进行干扰抵消时， 也可以在各个载波上分别进行自适应 均衡， 在这种情况下， 所述自适应均衡单元的个数需要与载波个数相同， 当 然， 所述延迟单元和所述相减单元的个数也应与载波个数相同， 各个载波信 号分别在对应的相减单元中进行相减。
不论上述自适应均衡是在合路的多载波上实现， 还是在各个多载波上分 别实现， 在理想情况下， 高阶互调干扰信号可以被完全抵消， 也就是说， 相 减后的差值信号不再含有高阶互调干扰信号。 因此， 可以在相同的收发隔离 的情况下， 降低双工器设计难度及抑制度需求。
需要说明的是， 本发明实施例抵消多载波发射干扰的装置可以应用在所 有无线通信技术领域， 例如移动通信系统、 固定无线接入、 无线数据传输等 系统中。 以上所描述的装置实施例仅仅是示意性的， 在实际应用中， 其中作为分 发射干扰的装置可以作为独立设备应用于现有的多载波收发信机， 也可以与 现有的多载波收发信机相结合， 充分利用现有的单元， 降低设备成本。 下面 对此分别进行详细说明。
如图 5所示， 是应用本发明实施例收发信机的一种结构示意图。
在该实施例中， 所述抵消多载波发射干扰的装置作为独立设备应用于现 有的多载波收发信机， 发射通道的下行非线性补偿和接收通道的干扰抵消的 处理过程独立进行。
其中， 发射反馈单元 14对耦合出的发射机输出的射频信号进行变频、模 数转换等处理， 然后将处理后得到的数字信号输出给数字预失真单元 15。 数 字预失真单元 15根据发射机的基带信号及发射反馈单元 14输出的数字信号 进行下行非线性建模， 根据非线性模型获取补偿系数， 利用获取的补偿系数 对输出信号在数字域进行补偿， 从而使整个系统工作接近线性。
高阶互调信号采集单元 401采集发射机输出的射频信号中的高阶互调信 号， 第一信号处理单元 402对所述高阶互调信号进行处理， 生成第一数字信 号； 然后由高阶互调模型建立单元 403利用所述第一数字信号和发射机输出 的第一基带信号 （该基带信号可以是非线性补偿后的基带信号， 也可以是非 线性补偿前的基带信号 )建立高阶互调模型， 由第二信号处理单元 404利用 所述高阶互调模型的系数和发射机输出的第二基带信号生成第二数字信号。 干扰抵消单元 405将接收机输出的和发射机输出的第二基带信号相对应的数 字信号与所述第二数字信号进行自适应对消， 达到抵消发射干扰的目的， 降 低双工器在接收频段的发射对接收的抑制度的要求。
如图 6所示， 是应用本发明实施例收发信机的另一种结构示意图。
在该实施例中， 所述抵消多载波发射干扰的装置与现有的多载波收发信 机相结合， 充分利用现有的单元。
其中， 高阶互调信号采集单元中的滤波单元 501和放大单元 502设置在 高阶互调采集通道， 现有的发射反馈单元 503设置在反馈通道， 发射反馈单 元 503 同时兼作抵消多载波发射干扰的装置中的第一信号处理单元， 实现下 变频及模数转换功能。 通过控制单元 504分时控制所述高阶互调采集通道和 用于采集发射机输出的射频信号的预失真通道与所述反馈通道相连。具体地， 控制单元 504可以通过开关完成上述控制功能。
在该实施例中， 预失真通道和高阶互调采集通道分时工作， 具体时间分 配可以根据预失真校正和高阶互调抵消性能确定。 当然， 也可以随机分配各 通道的工作时间。
数字预失真单元中的下行非线性建模单元 601和预失真单元 602都可以 作为发射机数字处理单元 511的一部分。
同样， 抵消多载波发射干扰的装置中的高阶互调模型建立单元 701、 第 二信号处理单元 702和干扰抵消单元 703都可以作为接收机数字处理单元 521 的一部分。
发射机射频处理单元 512、 接收机射频处理单元 522和双工器 531与现 有技术中相同。
该实施例的收发信机，硬件电路实现筒单， 不用增加额外的 ADC和变频 模块。 当然， 在实际应用中， 在互调干扰不影响灵敏度的情况下， 也可以不 启动干扰 4氏消功能。
4叚设功放的非线性响应为 g(/ ) = l + /(/z g/z/M ) + /(fo¼JM ) ,通过预失真通道 采集功放失真部分， 建模得到厂^/^/ ）， 并在预失真单元中补偿。
在高阶互调通道工作时， 通过采集功放高阶信号， 建模得到功放的高阶 互调模型 f ( MM ) , 一旦得到该模型后， 可以通过该模型及预失真后的基带 信号得到当前的高阶互调成分， 并通过干扰抵消单元 703进行抵消。 这样， 当发射机连续输出信号， 数字预失真后的信号就同样连续输出， 通过高阶互 调模型建立单元 701的数字信号也连续输出， 数字域形成的高阶互调和功放 输出的高阶互调保持一致， 从而将生成的高阶互调信号和接收机接收到的信 号中的高阶互调干扰信号自适应对消。 因此， 可以在相同的收发隔离的情况 下， 降低双工器设计难度及抑制度需求。
相应地， 本发明实施例还提供一种基站， 该基站包括上述实施例中的收 发信机， 该收发信机不仅包括： 发射机和接收机， 还包括前面所述的氏消多 载波发射干扰的装置， 其中， 抵消多载波发射干扰的装置可以作为独立设备 应用于现有的多载波收发信机， 也可以与现有的多载波收发信机相结合， 充 分利用现有的单元， 降低设备成本。 该基站可以应用于所有无线通信系统， 例如移动通信系统、 固定无线接入、 无线数据传输等系统中。
本说明书中的各个实施例均采用递进的方式描述， 各个实施例之间相同 相似的部分互相参见即可， 每个实施例重点说明的都是与其他实施例的不同 之处。 尤其， 对于设备实施例而言， 由于其基本相似于方法实施例， 所以描 述得比较筒单， 相关之处参见方法实施例的部分说明即可。 以上所描述的系 统实施例仅仅是示意性的， 其中所述作为分离部件说明的单元可以是或者也 可以不是物理上分开的， 作为单元显示的部件可以是或者也可以不是物理单 元， 即可以位于一个地方， 或者也可以分布到多个网络单元上。 可以根据实 际的需要选择其中的部分或者全部模块来实现本实施例方案的目的。 本领域 普通技术人员在不付出创造性劳动的情况下， 即可以理解并实施。
本发明实施例中的方法中的全部或部分步骤是可以通过程序等指令相关 的硬件来完成， 所述的程序可以存储于一计算机可读取存储介质中， 所述的 存储介质， 如： ROM/RAM、 磁碟、 光盘等。
以上对本发明实施例进行了详细介绍， 本文中应用了具体实施方式对本 发明进行了阐述，以上实施例的说明只是用于帮助理解本发明的方法及设备； 同时， 对于本领域的一般技术人员， 依据本发明的思想， 在具体实施方式及 应用范围上均会有改变之处， 综上所述， 本说明书内容不应理解为对本发明 的限制。

Claims

权 利 要 求
1、 一种抵消多载波发射干扰的方法， 其特征在于， 包括：
采集发射机输出的射频信号中的高阶互调信号；
对所述高阶互调信号进行处理， 生成第一数字信号；
利用所述第一数字信号和发射机输出的第一基带信号建立高阶互调模 型；
利用所述高阶互调模型的系数和发射机输出的第二基带信号生成第二数 字信号；
将接收机输出的数字信号与所述第二数字信号进行干扰抵消。
2、 根据权利要求 1所述的方法， 其特征在于， 所述采集发射机输出的射 频信号中的高阶互调信号包括：
将发射机输出的射频信号耦合出一部分；
滤除耦合出的射频信号中的主信号及低阶互调信号，得到高阶互调信号； 放大所述高阶互调信号。
3、 根据权利要求 1或 2所述的方法， 其特征在于， 通过高阶互调采集通 道采集发射机输出的射频信号中的高阶互调信号； 通过反馈通道对所述高阶 互调信号进行处理， 生成第一数字信号；
所述方法还包括：
分时控制所述高阶互调采集通道和用于采集发射机输出的射频信号的预 失真通道与所述反馈通道相连。
4、 根据权利要求 1或 2或 3所述的方法， 其特征在于， 所述将接收机输 出的数字信号与所述第二数字信号进行干扰抵消包括：
将所述第二数字信号进行自适应均衡；
将经过自适应均衡后的第二数字信号与接收机输出的数字信号相减。
5、 根据权利要求 4所述的方法， 其特征在于， 所述自适应均衡在合路的 多载波上实现或在各个载波上分别实现。
6、 一种抵消多载波发射干扰的装置， 其特征在于， 包括：
高阶互调信号采集单元， 用于采集发射机输出的射频信号中的高阶互调 信号； 第一信号处理单元， 用于对所述高阶互调信号进行处理， 生成第一数字 信号；
高阶互调模型建立单元， 用于利用所述第一数字信号和发射机输出的第 一基带信号建立高阶互调模型；
第二信号处理单元， 用于利用所述高阶互调模型的系数和发射机输出的 第二基带信号生成第二数字信号；
干扰抵消单元， 用于将接收机输出的数字信号与所述第二数字信号进行 干扰氏消。
7、 根据权利要求 6所述的装置， 其特征在于， 所述高阶互调信号采集单 元包括：
耦合单元， 用于将发射机输出的射频信号耦合出一部分；
滤波单元， 用于滤除耦合出的射频信号中的主信号及低阶互调信号， 得 到高阶互调信号；
放大单元， 用于放大所述高阶互调信号。
8、 根据权利要求 6或 7所述的装置， 其特征在于， 所述高阶互调信号采 集单元设置在高阶互调采集通道； 所述第一信号处理单元设置在反馈通道； 所述装置还包括：
控制单元， 用于分时控制所述高阶互调采集通道和用于采集发射机输出 的射频信号的预失真通道与所述反馈通道相连。
9、 根据权利要求 6或 7或 8所述的装置， 其特征在于， 所述干扰抵消单 元包括：
自适应均衡单元， 用于将所述第二数字信号进行自适应均衡；
相减单元， 用于将经过自适应均衡后的第二数字信号与接收机输出的数 字信号相减。
10、 一种收发信机， 包括发射机和接收机， 其特征在于， 还包括根据权 利要求 6至 9任一项所述的抵消多载波发射干扰的装置。
11、 一种基站， 其特征在于， 包括根据权利要求 11所述的收发信机。
12、 一种通信系统， 其特征在于， 包括根据权利要求 12所述的基站。
PCT/CN2012/072143 2012-03-09 2012-03-09 抵消多载波发射干扰的方法、装置、设备及系统 WO2013131279A1 (zh)

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US9762376B2 (en) 2017-09-12
CN103493382B (zh) 2015-04-08
EP2787651B1 (en) 2017-05-10
EP2787651A1 (en) 2014-10-08
ES2629402T3 (es) 2017-08-09
US9432173B2 (en) 2016-08-30
US20160315755A1 (en) 2016-10-27
EP3236589A1 (en) 2017-10-25
EP2787651A4 (en) 2014-12-03
US20140334349A1 (en) 2014-11-13
CN103493382A (zh) 2014-01-01
EP3236589B1 (en) 2019-05-08

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