WO2013112157A1 - Redresseur synchrone autonome - Google Patents

Redresseur synchrone autonome Download PDF

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Publication number
WO2013112157A1
WO2013112157A1 PCT/US2012/022732 US2012022732W WO2013112157A1 WO 2013112157 A1 WO2013112157 A1 WO 2013112157A1 US 2012022732 W US2012022732 W US 2012022732W WO 2013112157 A1 WO2013112157 A1 WO 2013112157A1
Authority
WO
WIPO (PCT)
Prior art keywords
power supply
effect transistor
synchronous rectifier
field
current
Prior art date
Application number
PCT/US2012/022732
Other languages
English (en)
Inventor
Deepakraj M DIVAN
Ravishankar NILAKANTAN
Frank C. LAMBERT
Satish Rajagopalan
Original Assignee
Georgia Tech Research Corporation
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Georgia Tech Research Corporation filed Critical Georgia Tech Research Corporation
Priority to PCT/US2012/022732 priority Critical patent/WO2013112157A1/fr
Publication of WO2013112157A1 publication Critical patent/WO2013112157A1/fr

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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/08—Modifications for protecting switching circuit against overcurrent or overvoltage
    • H03K17/082—Modifications for protecting switching circuit against overcurrent or overvoltage by feedback from the output to the control circuit
    • H03K17/0822—Modifications for protecting switching circuit against overcurrent or overvoltage by feedback from the output to the control circuit in field-effect transistor switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/30—Modifications for providing a predetermined threshold before switching
    • H03K17/302—Modifications for providing a predetermined threshold before switching in field-effect transistor switches
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/30—Modifications for providing a predetermined threshold before switching
    • H03K2017/307—Modifications for providing a predetermined threshold before switching circuits simulating a diode, e.g. threshold zero

Definitions

  • Power supply designs are driven by cost considerations and are generally optimized for performance at the appliance's peak operating point rather than for achieving overall maximum power efficiency. This results in poor energy efficiency under light load conditions such as standby or idle mode. Appliances spend a significant amount of time in standby or idle mode, consequently, energy losses are higher than they should be. Better and more adaptable power supply designs are needed but have been slow to be introduced because they are more expensive and usually necessitate a re-design of the power supply's existing physical layout.
  • MOSFET metal oxide field effect transistor
  • SPSR Smart power synchronous rectifiers
  • the SPSR is designed specifically for low voltage applications such as on-board power supplies.
  • the voltage across the device cannot vary much as it is used to directly supply the logic and drive circuits of the SPSR.
  • Problems that arise specifically in higher voltage applications, such as input overvoltage, are not addressed in current SPSR designs.
  • Another major issue with the SPSR is that the synchronous switch in it operates over the full load current range, therefore, the synchronous rectifier must be rated for the full load current, requiring a larger, more expensive MOSFET.
  • the on-resistance, or RDS ( O N) of the synchronous switch must be very low so that the voltage drop across the synchronous rectifier is lower than the forward drop of the diode even under full load condition.
  • RDS ( O N) increases the output capacitance of the device and the gate charge. Increasing the output capacitance and the gate charge results in increased switching losses, which play a major role at light load currents. Therefore, the light load performance of the SPSR is significantly lower than its peak load performance and the SPSR is not a suitable device for improving the light load efficiency of a power supply.
  • What is needed is a simple, low cost device which improves the efficiency of a power supply without requiring major changes to existing designs, and that enables the power supply to use less energy overall, thereby saving money, conserving resources and protecting the environment.
  • FIG. 1 is a block diagram of an illustrative self-sustained synchronous rectifier device.
  • FIG. 2 is a schematic depiction of an illustrative self- sustained synchronous rectifier device.
  • FIG. 3A is a graphical representation of illustrative output associated with the voltage VKA across the terminals of a power supply output rectifier diode.
  • FIG. 3B is a graphical representation of illustrative output of the present device associated with the voltage VKA across a power supply output rectifier diode under light load conditions.
  • FIG. 3C is a graphical representation of illustrative output of the present device associated with the voltage VKA across a power supply output rectifier diode under heavy load conditions.
  • a two terminal device which operates under light power supply loading conditions to substantially reduce or eliminate output rectifier diode loss and allows the output diode to conduct under high current modes of operation.
  • the device may be paralleled with an existing output rectifier diode, and be controlled in such a way that under light loading conditions the synchronous rectifier operates and substantially reduces or eliminates, for example, parasitic or standby energy losses, and allows the output rectifier diode to conduct under high current conditions.
  • a two-terminal self-sustained synchronous rectifier device comprises a control circuit coupled to the gate terminal of a field-effect transistor, wherein the control circuit is capable of synchronously switching the field-effect transistor in accordance with voltage reversal across a power supply output rectifier diode, and further comprises a current sensing circuit for sensing an output load current of a power supply and a predetermined reference current, wherein the current sensing circuit is operative to turn off the field-effect transistor when the load current is greater than the reference current.
  • the self-sustained synchronous rectifier device control circuit comprises (a) a voltage sensing circuit comprising a first comparator, (b) a current sensing circuit comprising a second comparator, and (c) an AND gate, wherein the inputs of the AND gate are coupled to the outputs of said first and second comparators, and the output of the AND gate is operative to turn the field-effect transistor on when an output voltage of a power supply is greater than zero volts and the output load current of the power supply is less than the predetermined reference current.
  • the synchronous rectifier device includes a control circuit operative to turn the field-effect transistor off when the power supply output voltage is less than zero volts.
  • control circuit of the synchronous rectifier device is operative to turn the field-effect transistor off when the power supply output voltage is greater than zero volts and the output load current of the power supply is greater than the predetermined reference current.
  • the self-sustained synchronous rectifier device includes a protection circuit comprising at least one transistor, resistor and/or capacitor, wherein under short circuit conditions, the protection circuit is capable of turning off the field-effect transistor.
  • the field-effect transistor of the synchronous rectifier device comprises a metal-oxide semiconductor.
  • the metal-oxide semiconductor may comprise a low current MOSFET.
  • the field-effect transistor of the synchronous rectifier device may comprise an n-channel MOSFET having a low ON-state resistance.
  • the synchronous rectifier device is installed in parallel with the power supply output rectifier diode and is operative to reduce idle mode losses in a power supply.
  • control circuit of the synchronous rectifier device is coupled to a gate drive circuit capable of driving the field-effect transistor.
  • MOSFET metal-oxide semiconductor field-effect transistor
  • Synchronous rectifiers may eliminate rectifier diode losses but are cost prohibitive when rated for full load current.
  • a two terminal device which may be paralleled with a power supply output rectifier diode and controlled such that under light loading conditions the synchronous rectifier operates and substantially reduces or eliminates the diode rectifier loss, whereas under high current mode of operation the diode conducts and the circuit operates as if the synchronous rectifier were not there.
  • a low current synchronous MOSFET may be used to minimize cost and lower energy consumption.
  • the self-sustained synchronous rectifier may be self-controlled, not requiring external circuitry. Sensing for control and operation of the device may be obtained from the voltage information across the two terminals of the device.
  • the self-sustained synchronous rectifier solution is minimally intrusive, as it may be directly paralleled with an existing diode rectifier or may replace an existing rectifier diode. Therefore, the present self-sustained synchronous rectifier may be implemented with no change to existing power supply control circuitry or algorithms, or design change of the power supply circuit board layout. This solution may also be topology independent, as the two terminal device may emulate the diode operation. As shown in Fig.
  • the self-sustained synchronous rectifier 100 may be in parallel with a power supply output rectifier diode 120.
  • the two terminal self- sustained synchronous rectifier 100 may be connected at one terminal to the cathode K, and external circuit 116, and at the other terminal to the anode A of diode 120 of the power supply.
  • the power supply may be a switched-mode power supply.
  • a switched-mode power supply may incorporate a switching regulator to transfer power from a source to a load while converting voltage and current characteristics.
  • the switching regulator, or primary switch, of a switched-mode supply switches quickly and voltage regulation is provided by varying the ratio of on to off time.
  • the self-sustained synchronous rectifier 100 may comprise an energy storage element 104 for supplying power to control logic 108 and gate driver 110; a voltage sense circuit 106 for sensing the voltage across the terminals of the self-sustained synchronous rectifier 100, and as input to control logic 108; and a current sense circuit 114 for sensing current through field-effect transistor 102 and as input to control logic 108.
  • the voltage sense 106 and current sense 114 circuits are coupled to control logic 108.
  • the output of control logic 108 is connected to gate driver 110 which is coupled to the gate terminal of field-effect transistor 102.
  • Short circuit protection 112 is connected to the gate terminal of field-effect transistor 102 and is operative to protect the self-sustained synchronous rectifier 100 and the external power supply from potential short circuit conditions.
  • the self-sustained synchronous rectifier 100 is a two terminal device that emulates the operation of a power supply output rectifier diode 120.
  • the active element in the self-sustained synchronous rectifier may be a MOSFET 102 which is controlled appropriately to mimic the operation of the diode 120.
  • the device 100 senses the voltage across the MOSFET 102 and the current through it to control the MOSFET 102 appropriately.
  • the voltage VAK across the diode 120 and the self- sustained synchronous rectifier 100 is less than zero.
  • the self-sustained synchronous rectifier 100 control logic 108 senses this and prevents the synchronous switch 102 from turning ON for the entire period when the primary power supply switch is ON. During this period, the energy from the external circuit is stored in the energy storage element 104. The stored energy is used to power the control logic 108 and gate drive circuit 1 10 when the synchronous switch 102 is turned ON.
  • the current through the device Isw is determined from the voltage across the device VAK.
  • the reference current IREF may be pre-determined and configured to yield the greatest energy savings based on the target power supply and the MOSFET RDS ( O N) of the self-sustained synchronous device.
  • the RDS ( O N) of the synchronous switch MOSFET, and the cost benefit of implementing the self-sustaining synchronous rectifier may primarily determine the reference current IREF. An analysis of power loss and/or cost vs. load current, for the self-sustaining synchronous rectifier device, may be helpful in determining the optimal reference current.
  • the self-sustained synchronous rectifier 100 turns off and allows the diode 120 to carry the load current. The circuit then operates as if the self-sustained synchronous rectifier 100 were not present, and losses in the power supply remain the same as before, plus additional control power loss for the self-sustained synchronous rectifier, which is relatively small.
  • the self-sustained synchronous rectifier may include short circuit protection 1 12 to protect the self- sustained synchronous rectifier and the external power supply circuit from potential short circuit conditions.
  • a short circuit across the input power must be avoided, and may be caused by one transistor, for example, either the primary switch or MOSFET 102, turning on before the other has turned off.
  • MOSFET 102 of the self-sustained synchronous rectifier 100 immediately turns OFF.
  • MOSFET 102 then conducts the load current in place of diode 120.
  • the main power supply switch turns ON again, according to the control signals from its main controller, the MOSFET 102 should turn OFF immediately.
  • the rise in current may be sensed by the short circuit protection circuit 1 12 which immediately shorts the gate of MOSFET 102, thereby opening MOSFET 102 and preventing the short circuit.
  • the self-sustained synchronous rectifier device may be in parallel with a power supply output rectifier diode 120.
  • the two terminal self- sustained synchronous rectifier device may be connected at one terminal to the cathode K and external circuit 116, and at the other terminal to anode A of the diode 120.
  • the current through the device Isw is determined from the voltage across the device VAK.
  • the self-sustained synchronous rectifier device includes a positive voltage generator, for generating voltage Vcc, comprised of resistor 240, diode 242, capacitor 244 and linear voltage regulator 236. Voltage Vcc is supplied to comparators 206, 208 and the gate driver 212.
  • a negative voltage generator comprised of capacitors 246, 252, diodes 248, 250, and voltage regulator 238 generates voltage Vee.
  • Resistor network 224, 226 is connected to Vee, and establishes the reference voltage Vref, for use by the current sense circuit comprised of comparator 208, resistor 234 and diode 232. In certain embodiments, resistor network 224, 226 may establish the reference current IREF. Voltage Vee is also supplied to comparators 206, 208.
  • the self-sustained synchronous rectifier device comprises a voltage sense circuit comprised of comparator 206, resistor 228 and diode 230.
  • the outputs of comparator 206 and comparator 208 are coupled to the inputs of the control circuit comprised of AND gate 210.
  • the output of AND gate 210 is connected to the input of the gate driver 212.
  • the gate driver 212 is coupled to the gate terminal of field- effect transistor 102 through resistor 216.
  • Gate current Ig flows from gate driver 212 to the gate terminal of field-effect transistor 102 through resistor 216.
  • a short circuit protection circuit comprising transistor 222, resistor 220 and capacitor 218 is connected to the gate terminal and drain terminal of field-effect transistor 102.
  • the self-sustained synchronous rectifier device may emulate the operation of an output rectifier diode 120 of an existing power supply.
  • the MOSFET 102 is turned ON and operates instead of the diode 120.
  • Comparator 206 may function as a zero crossing detector. When the voltage (VAK, VKA) across the terminals of the power supply output rectifier diode 120 becomes greater than zero, the output of comparator 206 is high.
  • MOSFET gate driver 212 is coupled to MOSFET 102 through resistor 216 and MOSFET 102 is turned OFF for that switching cycle.
  • current through the MOSFET 102 is less than the reference current, the output of comparator 208 is high, the output of AND gate 210 is high and the corresponding MOSFET gate driver 212 turns the MOSFET 102 ON through resistor 216 for that switching cycle.
  • the voltage VKA is coupled to the inputs of comparators 206, 208. Any over- voltage across the input terminals of the comparators 206, 208 may damage them. Diodes 230, 232 provide input over- voltage protection to comparators 206 and 208 respectively. When VKA is greater than VCC + Vf (forward voltage drop across diode 230 or diode 232), diodes 230, 232 become forward biased and may prevent the input to comparators 206, 208 from rising above VCC + Vf. Over-current may be prevented by the resistors 228 and 234 respectively.
  • the voltage across the capacitor 244 may be regulated to VCC using a linear voltage regulator 236 to provide the stable voltage for the control logic 206, 208 and gate drive circuit 212.
  • Capacitor 244 charges through the resistor 240 and diode 242 when the voltage across the MOSFET 102 VAK is less than zero.
  • the value of the capacitor 244 may be determined, taking into consideration the energy required for the control and gate drive circuits and the operating frequency of the power converter.
  • the circuit may be designed such that the gate and control power required are negligibly small, then although the regulator 236 provides less than optimal efficiency, the amount of energy lost may be disregarded.
  • the MOSFET 102 may be chosen such that the gate power required for its turning ON and OFF is negligible.
  • the gate power required for driving a MOSFET is directly proportional to its total gate charge Qg.
  • a MOSFET with an extremely low Qg reduces the gate power required, and indirectly the loss in the regulator may be minimized.
  • Voltage VKA pulsates, therefore, a charge pump circuit comprised of capacitors 246, 252, diodes 248, 250, and a negative voltage regulator 238 may generate the negative voltage Vee.
  • the negative voltage Vee is coupled to resistor network 224, 226, establishing a negative reference voltage (VREF) for use by the current sensing comparator 208.
  • VREF negative reference voltage
  • the short circuit protection feature of the self-sustained synchronous rectifier may be realized by utilizing, for example, a single transistor 222 and an RC component 218, 220.
  • a short circuit occurs, i.e. both the primary power supply switch and MOSFET 102 are conducting. This causes the current through MOSFET 102 to rise quickly which in turn causes the voltage drop across the resistor 220 to increase above the biasing voltage of transistor 222.
  • Transistor 222 turns ON immediately and shorts the gate of MOSFET 102.
  • the self-sustained synchronous rectifier has been implemented by installing it in parallel across the terminals of a buck converter output rectifier diode.
  • the MOSFET of the self-sustained synchronous rectifier conducted and nearly eliminated the voltage drop across the rectifier diode, and consequently the inherent energy loss.
  • FIGS. 3A-3B are graphical representations of the voltage VKA across the output rectifier diode of a buck converter.
  • FIG. 3 A is a graphical representation of the voltage VKA across the output rectifier diode of a buck converter without the SSR device installed. The expected voltage drop for this embodiment of nearly 0.6V when the diode was conducting can be seen.
  • FIG. 3B is a graphical representation of the voltage VKA across the output rectifier diode of a buck converter with the self-sustained synchronous rectifier device installed under light load conditions.
  • the self-sustained synchronous rectifier turned on under light load conditions, i.e., when the load current is less than the pre- determined reference current, in this example two amps. It can clearly be seen that the self-sustained synchronous rectifier worked to substantially reduce, and nearly eliminate, the voltage drop across the diode rectifier terminals of the commercial DC to DC Converter under light load conditions.
  • FIG. 3C is a graphical representation of the voltage VKA across the output rectifier diode of a buck converter with the self-sustained synchronous rectifier device installed under heavy load conditions.
  • the self-sustained synchronous rectifier turned off under heavy load conditions, i.e., when the load current is grater than the predetermined reference current, in this example two amps.
  • the self-sustained synchronous rectifier has turned off and the output rectifier diode conducts normally.
  • the expected voltage drop for this embodiment of nearly 0.6V when the diode was conducting can be seen.
  • a first embodiment provides a two-terminal self-sustained synchronous rectifier device comprising a control circuit coupled to the gate terminal of a field- effect transistor, wherein the control circuit is capable of synchronously switching the field-effect transistor in accordance with voltage reversal across a power supply output rectifier diode, characterized by a current sensing circuit capable of sensing an output load current of a power supply and a predetermined reference current, wherein the current sensing circuit communicates with and is operative to turn off the field- effect transistor when the output load current is greater than the reference current.
  • the control circuit may comprise (a) a voltage sensing circuit comprising a first comparator, (b) a current sensing circuit comprising a second comparator, and (c) an AND gate, wherein the inputs of the AND gate are coupled to the outputs of the first comparator and the second comparator, and the output of the AND gate is operative to turn the field-effect transistor on when the voltage across the power supply output rectifier diode is greater than zero volts and the output load current of the power supply is less than the predetermined reference current.
  • the device of the first or subsequent embodiments may further include that the control circuit is operative to turn the field-effect transistor off when the when the voltage across the power supply output rectifier diode is less than zero volts.
  • the device of the first or subsequent embodiments may further include that the control circuit is operative to turn the field-effect transistor off when the when the voltage across the power supply output rectifier diode is greater than zero volts and the output load current of the power supply is greater than the predetermined reference current.
  • the device of the first or subsequent embodiments may further include a gate drive circuit responsive to an output of the control circuit, including an output terminal coupled to a control terminal of the field-effect transistor, and capable of driving the field-effect transistor.
  • the gate drive circuit comprises two complementary switches.
  • the device of the first embodiment or subsequent embodiments may further include a protection circuit in communication with the field-effect transistor comprising at least one transistor, resistor and/or capacitor, wherein under short circuit conditions, the protection circuit is capable of turning off the field-effect transistor.
  • the device of the first or subsequent embodiments may further include that the field-effect transistor comprises a metal-oxide semiconductor.
  • the device of the first or subsequent embodiments may further include that the metal-oxide semiconductor is a low current MOSFET.
  • the device of the first or subsequent embodiments may further include that the device is in parallel with the power supply output rectifier diode and is operative to reduce idle mode losses in the power supply.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)
  • Dc-Dc Converters (AREA)

Abstract

La présente invention porte sur un dispositif redresseur synchrone autonome à deux bornes (100) à faible consommation d'énergie, comprenant un circuit de commande (108) couplé à la borne de grille d'un transistor à effet de champ (102), le circuit de commande (108) pouvant commuter de manière synchrone le transistor à effet de champ (102) en fonction de l'inversion de tension aux bornes d'une diode de redressement de sortie d'alimentation électrique (120). Ledit circuit de commande peut comprendre un circuit de détection de courant (114) pouvant détecter un courant de charge de sortie d'une alimentation électrique et un courant de référence prédéterminé, ledit circuit de détection de courant (114) communiquant avec le transistor à effet de champ (102) et étant apte à fonctionner de manière à le bloquer lorsque le courant de charge de sortie est plus fort que le courant de référence.
PCT/US2012/022732 2012-01-26 2012-01-26 Redresseur synchrone autonome WO2013112157A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
PCT/US2012/022732 WO2013112157A1 (fr) 2012-01-26 2012-01-26 Redresseur synchrone autonome

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/US2012/022732 WO2013112157A1 (fr) 2012-01-26 2012-01-26 Redresseur synchrone autonome

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WO2013112157A1 true WO2013112157A1 (fr) 2013-08-01

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PCT/US2012/022732 WO2013112157A1 (fr) 2012-01-26 2012-01-26 Redresseur synchrone autonome

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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4519024A (en) * 1983-09-02 1985-05-21 At&T Bell Laboratories Two-terminal transistor rectifier circuit arrangement
US6462525B1 (en) * 2000-02-14 2002-10-08 Linear Technology Corp. Polyphase PWM converter with high efficiency at light loads
US20090243390A1 (en) * 2008-03-25 2009-10-01 Kabushiki Kaisha Toshiba Power supply apparatus and power control method
US20100073082A1 (en) * 2007-02-02 2010-03-25 Mitsubishi Electric Corporation Rectifier

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4519024A (en) * 1983-09-02 1985-05-21 At&T Bell Laboratories Two-terminal transistor rectifier circuit arrangement
US6462525B1 (en) * 2000-02-14 2002-10-08 Linear Technology Corp. Polyphase PWM converter with high efficiency at light loads
US20100073082A1 (en) * 2007-02-02 2010-03-25 Mitsubishi Electric Corporation Rectifier
US20090243390A1 (en) * 2008-03-25 2009-10-01 Kabushiki Kaisha Toshiba Power supply apparatus and power control method

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
BRIAN ACKER ET AL.: "Current-Controlled Synchronous Rectification", 1994 IEEE APPLIED POWER ELECTRONICS CONFERENCE AND EXPOSITION, February 1994 (1994-02-01), pages 185 - 191, XP010118573 *

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