WO2013000746A1 - Procédé de traitement de données pour des réseaux optiques et émetteur pour des réseaux optiques - Google Patents

Procédé de traitement de données pour des réseaux optiques et émetteur pour des réseaux optiques Download PDF

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Publication number
WO2013000746A1
WO2013000746A1 PCT/EP2012/061538 EP2012061538W WO2013000746A1 WO 2013000746 A1 WO2013000746 A1 WO 2013000746A1 EP 2012061538 W EP2012061538 W EP 2012061538W WO 2013000746 A1 WO2013000746 A1 WO 2013000746A1
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WIPO (PCT)
Prior art keywords
sequence
symbols
orthogonal
polarization
periodic
Prior art date
Application number
PCT/EP2012/061538
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English (en)
Inventor
Stefano Calabro
Bernhard Spinnler
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Nokia Siemens Networks Oy
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
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Publication date
Application filed by Nokia Siemens Networks Oy filed Critical Nokia Siemens Networks Oy
Publication of WO2013000746A1 publication Critical patent/WO2013000746A1/fr

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/25—Arrangements specific to fibre transmission
    • H04B10/2507—Arrangements specific to fibre transmission for the reduction or elimination of distortion or dispersion
    • H04B10/2569—Arrangements specific to fibre transmission for the reduction or elimination of distortion or dispersion due to polarisation mode dispersion [PMD]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/25—Arrangements specific to fibre transmission
    • H04B10/2507—Arrangements specific to fibre transmission for the reduction or elimination of distortion or dispersion
    • H04B10/2572—Arrangements specific to fibre transmission for the reduction or elimination of distortion or dispersion due to forms of polarisation-dependent distortion other than PMD
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/50—Transmitters
    • H04B10/516—Details of coding or modulation
    • H04B10/532—Polarisation modulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/50—Transmitters
    • H04B10/516—Details of coding or modulation
    • H04B10/548—Phase or frequency modulation
    • H04B10/556—Digital modulation, e.g. differential phase shift keying [DPSK] or frequency shift keying [FSK]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2626—Arrangements specific to the transmitter only
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only

Definitions

  • the invention relates to an optical communication system and to a method of processing data for optical network.
  • the invention relates to a method of increasing robustness of optical transmission towards linear and nonlinear polarization-dependent impairments .
  • Fiber-optic communications are experiencing a phase of rapid progress characterized by the introduction of advanced Digi ⁇ tal Signal Processing (DSP) capabilities.
  • DSP Digi ⁇ tal Signal Processing
  • ADC Ana ⁇ log-Digital-Converters
  • DAC Digital-Analog-Converters
  • PDM Polarization Division Multiplexing
  • PMD Polarization Mode Dispersion
  • Polarization Dependent Loss is another linear effect depending on the SOP of the transmit signals and which con- sists in polarization-selective loss (or gain) of the fiber, the amplifiers and, in general, of any device traversed by the optical signal.
  • a coherent, as well as a non-coherent, receiver may undergo a performance penalty in the presence of PDL.
  • the performance degradation depends on the orientation between the polarization of the launched signal and the PDL element .
  • polarization scram- bling to combat all types of polarization-dependent impairments could be an extension of these PMD mitigation methods.
  • polarization scram- bling suffers from several drawbacks. First, it requires additional active optical components with increased equipment costs and installation and operation ex ⁇ penditures .
  • NCG Net Coding Gain
  • the re- ceiver may experience an artificial time-variant channel.
  • the time variance may disturb mainly the clock recovery circuit.
  • Previous work (H. Bulow, "Receiver for PMD Mitigation by Polarization Scrambling", US 7,486,898 B2, Feb.3, 2009) describes a complex jitter compensation mechanism for the clock recovery of a direct detection receiver in the presence of fast polarization scrambling .
  • the time variance disturbs not only the clock recovery but all channel estimation and equalization functions.
  • an additional limit may determine the maximum fea ⁇ sible scrambling rate and prevents effective impairment miti ⁇ gation through FEC.
  • the problem to be solved is to overcome the disadvantages stated above and in particular to provide a solution that in ⁇ crease the robustness of optical transmission towards linear and nonlinear polarization-dependent impairments without un ⁇ necessary waste of capacity.
  • the present invention discloses a method of processing data, com ⁇ prising the steps of: mapping a sequence of data bits to a first sequence of symbols, the symbols belonging to a four- dimensional constellation space, multiplying the first se- quence of symbols by a periodic sequence of orthogonal four- dimensional matrices to obtain a second sequence of symbols.
  • multiplying the first sequence of symbols by a periodic sequence of orthogonal four- dimensional matrices to obtain a second sequence of symbols includes a sequence of periodic orthogonal transformations.
  • each orthogonal transformation includes a rotation in the four-dimensional constellation space .
  • each orthogonal trans- formation includes a reflection in the four-dimensional con ⁇ stellation space.
  • the method further comprises the steps of organizing the first sequence of sym ⁇ bols in frames and extending each of the frames with prede- fined training symbols.
  • the method further comprises differentially encoding the first sequence of symbols.
  • the method further comprises converting the second sequence of symbols to analog electrical signals by means of digital-analog converters.
  • the method further comprises modulating the analog electrical signals by means of optical modulators to obtain optical signals.
  • the method further comprises trans ⁇ mitting the optical signals.
  • the method further comprises receiving the optical signals, wherein receiving the optical signals includes coherent demodulation of the optical signals.
  • the modulation is implemented in a sin ⁇ gle carrier system.
  • multiplying the first sequence of symbols by a periodic sequence of orthogonal four-dimensional matrices to obtain a second sequence of symbols is implement- ed in the time domain at each signaling interval.
  • the modulation is implemented in a multi-carrier signaling system, preferably in an Orthogonal Frequency Division Multi ⁇ plexing (OFDM) system. It is also an embodiment that multiplying the first sequence of symbols by a periodic sequence of orthogonal four- dimensional matrices to obtain a second sequence of symbols is implemented in the frequency domain.
  • OFDM Orthogonal Frequency Division Multi ⁇ plexing
  • transmitter for optical signals comprising a symbol mapper configured to map a sequence of data bits to a first sequence of symbols, the symbols belonging to a four-dimensional constellation space, and a transformation unit configured to perform a sequence of periodic orthogonal transformations by multiplying the first sequence of symbols by a periodic sequence of orthogonal four-dimensional matrices to obtain a second sequence of sym ⁇ bols.
  • the method and the transmitter bears the following advantages: a) They increase the robustness of optical transmission towards linear and nonlinear polarization-dependent im ⁇ pairments without unnecessary waste of capacity. b) They have relatively broad applications and they can be easy implemented. c) Remarkable performance improvement can be achieved. d) They do not require additional active optical compo ⁇ nents with increased equipment costs and installation and operation expenditures.
  • Fig.l is a schematic representation of a single-carrier transmitter 100 using a time-variant 4D constellation according to an embodiment of the invention.
  • Fig.2 is a schematic representation of a single-carrier receiver 200 using a time-variant 4D constellation according to an embodiment of the invention.
  • Fig.3 is a schematic representation of an Orthogonal Frequen ⁇ cy Division Multiplexing (OFDM) transmitter 300 using a time- variant 4D constellation according to an embodiment of the invention .
  • OFDM Orthogonal Frequen ⁇ cy Division Multiplexing
  • Fig.4 is a schematic representation of an Orthogonal Frequency Division Multiplexing (OFDM) receiver 400 using a time- variant 4D constellation according to an embodiment of the invention.
  • OFDM Orthogonal Frequency Division Multiplexing
  • Figure 5 is a schematic representation of the resulting di ⁇ rect 4D transformation block.
  • Figure 6 is a schematic representation of the resulting inverse 4D transformation block. DESCRIPTION OF THE INVENTION
  • a simple and effective method is provided which increases the robustness of optical transmission towards linear and nonlin ⁇ ear polarization-dependent impairments.
  • the method is applicable to single-carrier signaling.
  • the method is applica- ble to multi-carrier signaling (Orthogonal Frequency Division Multiplexing - OFDM) .
  • coherent demodula ⁇ tion is assumed.
  • the method uses a periodic sequence of orthogonal transformations (in time domain for single-carrier system and in frequency domain for OFDM systems) to change the polarization coupling angle of the transmitted signal.
  • the receiver is able to achieve per ⁇ fect synchronization of the periodic sequence by exploiting suitably embedded training symbols.
  • the orthogonal transfor- mations leave demodulation and channel equalization unaffect ⁇ ed and are reversed before de-mapping and decoding.
  • Fig.l is a schematic representation of a single-carrier transmitter 100 using a time-variant 4D (4-Dimensional) con- stellation according to an embodiment of the invention.
  • the time-variant signal constellation employed avoids the persis ⁇ tence of unfavorable polarization states by using different regions of the vectorial signal space over time.
  • the channel encoder 102 maps the payload 101 to code words providing FEC capability, thereby adding the required redun ⁇ dancy and providing the requested error resilience.
  • the symbol mapper 103 maps the resulting encoded bit stream to a sequence of 4D constellation points. At each signaling interval, the mapper 103 uses a set of typically adjacent en- coded bits to select a signal vector from the signal constel ⁇ lation according to a predefined binary labeling (or addressing scheme) .
  • the signal vec ⁇ tor belongs to the 4-Dimensional (4D) space spanned by the in-phase and quadrature components of two fixed orthogonal polarization axes.
  • Single polarization transmission can be regarded as a special case in which the projection of the signal points on either polarization axis is constantly zero.
  • sequence of symbols can be differentially en ⁇ coded to convey information in the signal transitions and make the systems more resilient to phase cycle slips.
  • the sequence of symbols may be organized in frames and frame synchronization 112 may be provided.
  • a training insertion unit 104 extends each frame with predefined training symbols, which will be used at the receiver to achieve frame synchro- nization.
  • the training symbols can be prepended as preamble, appended as a postamble or else distributed along the frame.
  • an additional transmit processing unit 105 can apply any necessary additional transmit processing.
  • Each transformation represents a rotation and/or reflection in the 4D signal space and the sequence of 4D orthogonal ma ⁇ trices corresponds to rotations or reflections in the signal space.
  • the next orthogonal matrix is applied to the original 4D signal vector selected by the symbol mapper 103.
  • a transformed 4D signal point is ob ⁇ tained that is passed to two IQ modulators 110 and further processed. Since the polarization rotation is applied to the time-discrete constellation points rather than to the modu ⁇ lated signal, the transmit pulses remain undistorted and the spectrum unaffected. This allows to take arbitrary sequences of orthogonal transformations, even with abrupt steps between two successive transformations, without generating disconti- nuities in the analog signal. Consequently, the described method could be seen as selecting the transmit point from a different 4D constellation at every signaling interval.
  • the periods of the sequence ⁇ H> coincide with the frames of the transmit signal.
  • the resulting sequence ⁇ v> of 4D points might undergo Digital Up-Conversion (DUC) 107 and additional pro ⁇ cessing at higher sampling rate (e.g. digital filtering) by means of a Nyquist rate transmit processing unit 108.
  • DUC Digital Up-Conversion
  • additional pro ⁇ cessing at higher sampling rate e.g. digital filtering
  • the resulting signal is passed to a Digital-Analog Conversion (DAC) stage 109 that yields 4 time-continuous electrical sig- nals used to drive the optical modulators 110.
  • DAC Digital-Analog Conversion
  • the two IQ modulators 110 generate the projections of the op ⁇ tical signal on two orthogonal polarization axes, which are eventually merged via a polarization combiner 111.
  • the two IQ modulators 110 (e.g. consisting of a combination of digital and analog components) use the time-discrete sequence of 4D points to generate a continuous optical signal. Modulation, accordingly, could be seen as the generation of a train of optical pulses in response to a sequence of input constella ⁇ tion points.
  • Fig.2 is a schematic representation of a single-carrier receiver 200 using a time-variant 4D (4-Dimensional) constella ⁇ tion according to an embodiment of the invention.
  • the impinging optical signal 201 is decomposed along two or- thogonal polarization axes by the polarization splitter 211.
  • Two IQ demodulators 210 recover the in-phase and quadrature components of both polarizations.
  • DSP Digital Signal Processing
  • the use of a frame structure with training symbols makes da ⁇ ta-aided processing a particularly convenient choice.
  • the re ⁇ ceive processing block 208 at Nyquist rate might include frame, timing and carrier frequency synchronization, and channel equalization.
  • the processed signal is subject to Digital Down-Conversion (DDC) 207, which reduces the sampling rate to a sample per symbol .
  • DDC Digital Down-Conversion
  • the resulting 4D sequence ⁇ z> is transformed by the inverse 4D transformation block 206 according to ⁇ H > into the new sequence ⁇ s> defined by with xn[k]
  • YQ4[k] and ( ) T denotes transposition.
  • the matrix-vector multiplica ⁇ tion in (4) is obviously an orthogonal transformation and leaves the noise statistics unchanged.
  • the resulting signal may undergo additional receive processing 205 at sym ⁇ bol rate. This may include carrier phase correction and esti ⁇ mation of residual error for equalizer adjustment.
  • the symbol de-mapper 203 After removal of the training symbols by means of a training removal unit 204, the symbol de-mapper 203 provides the bits (in case of hard decision FEC) or the bit metrics (in case of soft-decision FEC) to the subsequent channel decoder 202. If the transmitter uses differential encoding, the symbol de- mapper 203 should implement the corresponding differential decoding rule. Frame synchronization 212 may be also provid- ed .
  • Fig.3 is a schematic representation of an Orthogonal Frequen ⁇ cy Division Multiplexing (OFDM) transmitter 300 using a time- variant 4D (4-Dimensional) constellation according to an embodiment of the invention.
  • OFDM Orthogonal Frequen ⁇ cy Division Multiplexing
  • mapping of the encoded bits to the constellation points occurs in the frequency domain rather than in the time do ⁇ main .
  • the channel encoder 302 maps the payload 301 to code words providing FEC capability.
  • the symbol mapper 303 selects a 4D constellation point per-subcarrier and OFDM symbol. For each OFDM symbol and each subcarrier the symbol mapper 303 uses a set of typically adjacent encoded bits to select a signal vector from the 4D signal constellation according to the predefined binary labeling
  • a training insertion unit 304 can insert training symbols either on selected dedicated subcarriers or on all active sub- carriers at selected OFDM symbols. For convenience of imple ⁇ mentation, the frame length can be chosen to be a multiple of the number of used subcarriers. If necessary, further fre- quency domain processing 305 can be applied after framing.
  • the 4D transformation block 306 operates in analogy with the single-carrier case but on a per-subcarrier rather than on a per-symbol basis. Therefore, each subcarrier within an OFDM symbol experiences in general a different transformation. Frame synchronization 312 may be also provided. Subsequently, the resulting transformed subcarriers undergo zero-padding (e.g. insertion of virtual subcarriers) and Inverse Discrete Fourier Transform (IDFT) 307 to yield the time domain signal. Additional time domain processing 308 usually includes the insertion of a Cyclic Prefix (CP) .
  • CP Cyclic Prefix
  • the resulting signal is passed to a Digital-Analog Conversion (DAC) stage 309 that yields 4 time-continuous electrical sig ⁇ nals used to drive the optical modulators 310.
  • DAC Digital-Analog Conversion
  • the two IQ modulators 310 generate the projections of the op- tical signal on two orthogonal polarization axes, which are eventually merged via a polarization combiner 311.
  • the modu- lator uses the sequence of 4D points associated with the sub- carriers to generate a continuous optical signal. Modulation may involve a Fourier transform from the frequency into the time domain. Instead of operating on the modulated signal in the time do ⁇ main, the present embodiment of the invention operates on the individual subcarriers in the frequency domain. For each OFDM symbol and each subcarrier the orthogonal transformation is applied to the original 4D vectorial symbol selected by the mapper. Thus, the transformed subcarriers are obtained that are passed to the modulator and further processed.
  • Fig.4 is a schematic representation of an Orthogonal Frequency Division Multiplexing (OFDM) receiver 400 using a time- variant 4D (4-Dimensional) constellation according to an em- bodiment of the invention.
  • OFDM Orthogonal Frequency Division Multiplexing
  • the impinging optical signal 401 is decomposed along two or ⁇ thogonal polarization axes by the polarization splitter 411.
  • Two IQ demodulators 410 recover the in-phase and quadrature components of both polarizations.
  • DSP Digital Signal Processing
  • Time domain receive processing 408 might include frame syn ⁇ chronization, Cyclic Prefix (CP) removal, clock frequency and carrier frequency recovery. After Discrete Fourier Transform (DFT) and removal of the virtual subcarriers 406, the fre ⁇ quency domain signal is obtained. The 4D subcarriers are sub ⁇ ject to the inverse orthogonal transformation according to ⁇ H > . Additional frequency domain processing 405 may comprise channel equalization and timing phase recovery. After removal of the training symbols by means of a training removal unit 404, the symbol de-mapper 403 provides the bits (in case of hard decision FEC) or the bit metrics (in case of soft-decision FEC) to the subsequent channel decoder 402. If the transmitter uses differential encoding, the symbol de- mapper 403 should implement the corresponding differential decoding rule. Frame synchronization 412 may be also provid ⁇ ed .
  • receive processing is designed to recov ⁇ er the transformed rather than the original 4D signal points.
  • channel equalization, and polarization dis ⁇ crimination have to cope only with the physical channel and not with the artificial time-variance introduced at the transmitter. This allows to change rapidly the polarization state of the transmit signal without disturbing the receiver.
  • the receiver in order to recover the original 4D sig ⁇ nal points, the receiver is provided with perfect knowledge of the sequence of orthogonal transformations. This can be achieved by repeating periodically the sequence of orthogonal matrices on a frame basis and embedding suitable training symbols for synchronization purposes. After complete equali ⁇ zation and demodulation, the inverse orthogonal transfor- mation is applied to recover the original 4D points.
  • a de-mapper provides the resulting estimated bits (in case of hard decision) or bit metrics (in case of soft- decision) to the FEC decoder, which in turn estimates the transmit payload. Since a different, completely arbitrary, orthogonal transfor ⁇ mation matrix can be applied to every subcarrier, the impact of polarization-dependent impairments can be averaged in the frequency domain at subcarrier granularity. This results in a perfectly uniform symbol error distribution, which improves the error correction capability of the FEC decoder. In order to maximize the averaging effect the separation between consecutive 4D transformations should be maximized.
  • Figure 5 is a schematic representation of the resulting di ⁇ rect 4D transformation block.
  • Figure 6 is a schematic representation of the resulting in ⁇ verse 4D transformation block.

Abstract

La présente invention concerne un procédé de traitement de données et un émetteur pour des signaux optiques. Le procédé comprend les étapes consistant à mettre en correspondance une séquence de bits de données avec une première séquence de symboles, les symboles faisant partie d'un espace de constellation à quatre dimensions; et à multiplier la première séquence de symboles par une séquence périodique de matrices orthogonales à quatre dimensions afin d'obtenir une seconde séquence de symboles.
PCT/EP2012/061538 2011-06-30 2012-06-16 Procédé de traitement de données pour des réseaux optiques et émetteur pour des réseaux optiques WO2013000746A1 (fr)

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EPEP11172134 2011-06-30

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CN109314579A (zh) * 2016-06-13 2019-02-05 三菱电机株式会社 光传输方法和光传输系统
WO2020257960A1 (fr) * 2019-06-24 2020-12-30 Zte Corporation Architectures d'émetteur-récepteur pour communication optique à haut débit
CN112367123A (zh) * 2020-11-10 2021-02-12 兰州理工大学 一种适合于湍流信道的光空时键控调制方法

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109314579A (zh) * 2016-06-13 2019-02-05 三菱电机株式会社 光传输方法和光传输系统
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WO2020257960A1 (fr) * 2019-06-24 2020-12-30 Zte Corporation Architectures d'émetteur-récepteur pour communication optique à haut débit
CN112367123A (zh) * 2020-11-10 2021-02-12 兰州理工大学 一种适合于湍流信道的光空时键控调制方法
CN112367123B (zh) * 2020-11-10 2022-08-12 兰州理工大学 一种适合于湍流信道的光空时键控调制方法

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