WO2012053027A1 - Convertisseur continu-continu d'amplification et moteur à réluctance commuté alimenté au moyen de celui-ci - Google Patents

Convertisseur continu-continu d'amplification et moteur à réluctance commuté alimenté au moyen de celui-ci Download PDF

Info

Publication number
WO2012053027A1
WO2012053027A1 PCT/JP2010/006167 JP2010006167W WO2012053027A1 WO 2012053027 A1 WO2012053027 A1 WO 2012053027A1 JP 2010006167 W JP2010006167 W JP 2010006167W WO 2012053027 A1 WO2012053027 A1 WO 2012053027A1
Authority
WO
WIPO (PCT)
Prior art keywords
converter
mode
short
series
phase
Prior art date
Application number
PCT/JP2010/006167
Other languages
English (en)
Inventor
Shouichi Tanaka
Original Assignee
Three Eye Co., Ltd.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Three Eye Co., Ltd. filed Critical Three Eye Co., Ltd.
Priority to PCT/JP2010/006167 priority Critical patent/WO2012053027A1/fr
Priority to PCT/JP2010/006674 priority patent/WO2011092774A1/fr
Publication of WO2012053027A1 publication Critical patent/WO2012053027A1/fr

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/08—Reluctance motors
    • H02P25/092—Converters specially adapted for controlling reluctance motors
    • H02P25/0925—Converters specially adapted for controlling reluctance motors wherein the converter comprises only one switch per phase
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/0013—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries acting upon several batteries simultaneously or sequentially
    • H02J7/0024—Parallel/serial switching of connection of batteries to charge or load circuit
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade

Definitions

  • the present invention relates to a DC-to-DC converter with a pair of boost choppers, and a switched reluctance motor powered by the DC-to-DC converter.
  • the DC-to-DC converter of the present invention can change a boost ratio between an input voltage and an output voltage smoothly and widely.
  • an asynchronous power converter for driving the switched reluctance motor does not need to be PWM-switched, when a DC bus voltage applied to the power converter is changed in accordance with a required current.
  • U. S. Patent. No. 5,111,095 invented by Hendershot shows a five-phase 10/8 SRM with a high torque/weight ratio.
  • the SRM has a large torque ripple in a transient period, while one phase current rises and another phase current being a freewheeling current decreases.
  • FIG. 1 shows one method to change the DC bus voltage Vx.
  • DC bus voltage Vx is changed by a boost chopper type DC-to-DC converter, the boost converter.
  • a voltage of a battery 100 is applied to a motor-driving circuit 300 via boost converter 200.
  • the well-known chopper type boost converter 200 has a reactor 201, an upper switch 202, a lower switch 203 and a parallel switch 204.
  • the parallel switch 204 is turned on, when battery voltage is applied to the motor-driving circuit 300 directly for reducing a resistive loss of the reactor 201.
  • a smoothing capacitor 400 absorbs high-frequency-components included in the DC bus voltage Vx. It is proposed to change the DC bus voltage Vx in proportional to a required torque of the motor. However, a switching power loss of boost converter 200 decreases an efficiency of the motor-driving circuit 300.
  • FIG. 2 shows another method to change the DC bus voltage.
  • a series-parallel circuit 500 consisting of three switches 501-503 shown in United Patent No. 6,140,799 and 6,674,180 has two modes. In a series mode, two batteries 101 and 102 are connected in series to each other by a series switch 501. In a parallel mode, two batteries 101 and 102 are connected in parallel to each other by two parallel switches 502 and 503.
  • the single-parallel circuit 500 only outputs one of two amplitudes of the DC bus voltage Vx. A mechanical shock of torque changing and a current of the smoothing capacitor 400 become large.
  • each of two pairs of one reactor and one battery is connected by a parallel switch.
  • the parallel switch and one pair of the reactor and the battery are short-circuited by the first parallel switch.
  • the parallel switch and the other pair of the reactor and the battery are short-circuited by the second parallel switch.
  • the boost DC-to-DC converter (1) has a series mode (A), a parallel mode (B) and a short-circuit mode (C, D1, D2).
  • the short-circuit mode has at least one of a full short-circuit mode (C), a first short-circuit mode (D1) and a second short-circuit mode (D2). Accordingly, the boost DC-to-DC converter (1) can change a variable DC voltage smoothly in the wide range.
  • the series mode (A) and the full short-circuit mode (C) are executed alternately. As the result, a higher boosted voltage can be produced.
  • the parallel mode (B) and the full short-circuit mode (C) are executed alternately. As the result, a lower boosted voltage can be produced.
  • the parallel mode (B) and either one of the first short-circuit mode (D1) and the second short-circuit mode (D2) are executed alternately. Furthermore, the first short-circuit mode (D1) and the second short-circuit mode (D2) are executed alternately. Accordingly, current ripple is reduced.
  • the boost converter operates the parallel mode (B), the first short-circuit mode (D1), parallel mode (B), the second short-circuit mode (D2) in turn. The current ripple is reduced.
  • the series mode (A) and either one of the first short-circuit mode (D1) and the second short-circuit mode (D2) are executed alternately.
  • the boost converter operates the series mode (A), the first short-circuit mode (D1), the series mode (A), the second short-circuit mode (D2) in turn.
  • the current ripple is reduced.
  • the converter (1) applies a boosted DC voltage (Vx) to a power converter for driving a switched reluctance motor (60).
  • the converter (1) applies the boosted voltage (Vx) during a transient period, while a freewheeling current of at least one phase winding of the switched reluctance motor is reducing. As the result, the freewheeling current is decreased quickly.
  • Figure 1 is a circuit diagram showing a conventional boost chopper type DC-to-DC converter.
  • Figure 2 is a circuit diagram showing a conventional series-parallel-changing circuit of two batteries.
  • Figure 3 is a circuit diagram showing a motor-driving-apparatus having the boost converter with the dual boost choppers.
  • Figure 4 is a circuit diagram showing the series mode, the parallel mode and three boost modes of the boost converter shown in Figure 3.
  • Figure 5 is a circuit diagram showing another boost mode of the boost converter shown in Figure 3.
  • Figure 6 is a timing chart showing the changing of the DC bus voltage.
  • Figure 7 is a timing chart showing a voltage applied by the conventional boost converter shown in Figure 1.
  • Figure 8 is a timing chart showing a voltage applied by the conventional series-parallel circuit shown in Figure 2.
  • Figure 9 is a circuit topology for showing an electrical energy accumulator employing two EDLCs.
  • Figure 10 is a block diagram showing a power conditioner for supplying a generated power of solar cells.
  • Figure 11 is a circuit topology showing the boost converter employed by the power conditioner shown in Figure 10.
  • Figure 12 is a circuit diagram of a five-phase asynchronous power converter for driving a five-phase switched reluctance motor.
  • Figure 13 is a schematic diagram for showing five angular positions of a rotor of the Hedershot's 10/8 five-phase SRM.
  • Figure 14 is a timing chart for showing five phase voltages and five phase currents of the five-phase SRM.
  • Figure 15 is a schematic cross-section showing a nine-phase SRM having two sets of four U-shaped rotor pole segments.
  • Figure 16 is a schematic diagram for showing six angular positions of a rotor of the nine-phase SRM shown in Figure 15.
  • Figure 17 is a schematic diagram for showing three angular positions of a rotor of the nine-phase SRM shown in Figure 15.
  • Figure 18 is a circuit topology of the nine-phase power converter for driving the nine-phase SRM shown in Figure 15.
  • Figure 19 is a timing chart showing nine excitation periods of the nine-phase SRM shown in Figure 15.
  • FIG. 3 shows a circuit topology of a motor-driving apparatus for driving an alternative current motor, for example a switched reluctance motor.
  • the motor-driving apparatus consists of a boost chopper type DC-to-DC converter 1, a motor-driving circuit 2 and a smoothing capacitor 3.
  • the boost chopper type DC-to-DC converter 1 is called the boost converter 1 briefly.
  • the motor-driving circuit 2 can employ a power converter or an inverter for driving the motor 60.
  • the boost converter 1 boosts battery voltages Vb of two batteries 4 and 5, and outputs a DC bus voltage Vx to the motor-driving circuit 2 and the smoothing capacitor 3. A multi-phase voltage produced by the motor-driving circuit 2 is applied to the motor 60.
  • Boost converter 1 has two boost choppers consisting of a series switch 110, a parallel switch 120 and 130 and an output switch 140. Furthermore, the boost converter 1 has a first reactor 150 and a second reactor 160, too. A first boost chopper consists of the reactor 150 and the switches 110, 120 and 140. A second boost chopper consists of the reactor 160 and the switch 11-130.
  • Boost converter 1 outputs a DC bus voltage Vx to motor-driving-circuit 2 and smoothing capacitor 3 via a pair of DC link consisting of a high potential line 6 and a low potential line 7.
  • FIG. 4 shows the boost converter 1 having a plurality of operating modes consisting of a series mode A, a parallel mode B, a short-circuit mode C and three boost modes 401, 402 and 403.
  • the series switch 11 keeps the turned-on state, and the parallel switches 120 and 130 keep the turned-off state each.
  • the boost converter 1 outputs a high value of voltage Vx being mostly equal to two times of the battery voltage Vb.
  • Parallel switches 120 and 130 keep the turned-on state each, and series switch 110 keeps the turned-off state.
  • the boost converter 1 outputs a low value of voltage Vx being mostly equal to the battery voltage Vb.
  • a first boost mode 401 is explained.
  • the series mode A and the short-circuit mode C are executed alternately with a predetermined career frequency.
  • the DC bus voltage Vx becomes equal to the sum of 2Vb and 2Vl.
  • the value Vb is a voltage value of one of batteries 4 and 5.
  • the value Vl means a voltage of one of the reactors 150 and 160.
  • the DC bus voltage Vx can be changed by means of changing of a duty ratio, which is equal to one series-mode-period per one career period.
  • the career period consists of the sum of the series-mode-period and a short-circuit-mode-period.
  • a second boost mode 402 is explained.
  • the parallel mode B and the short-circuit mode C are executed alternately with a predetermined career frequency.
  • the DC bus voltage Vx becomes equal to the sum of Vb and Vl.
  • the DC bus voltage Vx can be changed by means of changing of a duty ratio, which is equal to a parallel-mode-period per the career period.
  • the career period consists of the sum of the parallel-mode-period and the short-circuit-mode-period.
  • a third boost mode 403 is explained.
  • the series mode A and the parallel mode B are executed alternately with a predetermined career frequency.
  • the DC bus voltage Vx becomes equal to the sum of 2Vb and 2Vl in the series mode A.
  • the reactors 150 and 160 accumulate small magnetic energy each.
  • the DC bus voltage Vx can be changed by means of changing of a duty ratio being equal to the series-mode-period per the career period.
  • the career period consists of the sum of the series-mode-period and the parallel-mode-period.
  • a fourth boost mode 404 is explained referring to Figure 5.
  • the fourth boost mode 401 the first short-circuit mode D1, the parallel B, the second short-circuit mode D2 and the parallel B are executed in turn with a predetermined career frequency.
  • parallel switch 120 and series switch 110 are turned on, and parallel switch 130 is turned off. Accordingly, reactor 150 accumulates the magnetic energy, and battery 5 and reactor 160 outputs the boosted DC bus voltage, which is mostly equal to the sum of Vb and Vl.
  • first short-circuit mode D1 and the second short-circuit mode D2 alternately with a variable career frequency.
  • a period X of first short-circuit mode D1 is equal to a period Y of second short-circuit mode D2.
  • the duty ratio is 50%.
  • the career frequency is changed in accordance with a required DC bus voltage Vx.
  • the career frequency is reduced, when the required boost ratio is large.
  • the career frequency is increased, when the required boost ratio is small.
  • the ripple of the voltage Vx is reduced, when the boost ratio is small.
  • FIG. 6 is a timing chart showing the changing of DC bus voltage Vx.
  • Battery voltage Vb is mostly equal to 125V.
  • DC bus voltage Vx is 125V.
  • series-mode period T3 the DC bus voltage Vx is 250V.
  • either one of the second boost mode 402 and the fourth boost mode 404 is selected in accordance with a compared result among the two boost modes about the power loss and the voltage ripple.
  • either one of the first boost mode 401 and the third boost mode 403 is selected in accordance with a compared result among the two boost modes about the power loss and the voltage ripple.
  • Figure 7 is a timing chart showing the voltage Vx applied by the traditional boost converter shown in Figure 1.
  • Figure 8 is a timing chart showing the voltage Vx applied by the conventional series-parallel circuit shown in Figure 2.
  • the boost converter 1 shown in Figure 3 needs to add one switching element.
  • the boost converter 1 can applies either one of two constant values of the DC bus voltages without the switching.
  • the boost converter 1 can have three-type boost modes 401-403. The switching loss and the current ripple are reduced by means of selecting the best mode of the boost converter 1 shown in Figure 3. Furthermore, the resistive power loss becomes 25% in the parallel mode, because the current flows in parallel.
  • Inverter 2 drives the motor-generator 60 as the traction motor of the vehicle.
  • Boost converter 1 has the mode 401, when motor-generator 60 needs a large motor torque.
  • Boost converter 1 has the mode 401, when motor-generator 6 is rotating at a high speed, too.
  • Boost converter 1 has the mode B, when motor-generator 6 produces a small torque.
  • boost converter 1 has the mode A, when the vehicle is braking at high speed.
  • the output switch 140 is turned on to charge the battery 150 and 150 connected in series to each other.
  • Boost converter 1 has the mode B, when the vehicle is braking at low speed.
  • the output switch 140 is turned on to charge the battery 150 and 150 connected in parallel to each other. Running energy of the vehicle with a low speed can be regenerated.
  • the mode 402 or the mode 404 is employed in a transient period between the mode A and the mode B.
  • FIG 9 shows an electrical energy accumulator 1A employing two EDLCs 4A and 5A, which are electric double layer capacitors.
  • the accumulator 1A has the same circuit topology as the boost converter 1 shown in Figure 3. It is well-known that the boost chopper can be used step-down converter for charging the battery. Accordingly, the accumulator 1A can accumulate electrical energy and outputs the accumulated electrical energy.
  • the mode A When voltages of EDLCs 4A and 5A are small, the mode A is employed.
  • the mode B is employed. However, when accumulator 1A deals a large value of the charging current, the mode B is employed. Similarly, when accumulator 1A deals a large value of the discharging current, the mode A is employed.
  • Figure 10 shows a power conditioner for supplying a generated power of solar cells 4B and 5B to a three-phase grid network 700.
  • the power conditioner includes the boost converter 1, the smoothing capacitor 3 and the three-phase inverter 2.
  • the boost converter 1 has a circuit topology shown in Figure 11.
  • the output switch 140 When the DC bus voltage Vx is in a range between Vb and 2Vb, the output switch 140 is being turned on for a predetermined period in the parallel mode B. After turning-off of the output switch 140, the short-circuit mode C or the mode 404 is executed.
  • FIG. 12 is a circuit diagram of a five-phase power converter 20 for driving a five-phase switched reluctance motor 60 shown in Figure 13.
  • Figure 13 is a schematic diagram for showing five angular positions of a rotor of the Hedershot's 10/8 five-phase SRM.
  • Figure 14 is a timing chart for showing five phase voltages V11--V15 and five phase currents I11-I15 of the five-phase SRM 60.
  • the five-phase SRM has five phase windings 11-15 constituting a stator winding.
  • Each of five phase windings 11-15 is wound on each of stator poles 201A of the stator 201 in turn as shown in Figure 13.
  • the five-phase power converter 20 consists of six transistors 31-34, 35U and 35L and six freewheeling diodes D.
  • the upper transistors 31, 33 and 35U connect the high potential line 6 and the phase windings 11, 13 and 15 respectively.
  • the lower transistors 32, 34 and 35L connects the low potential line 7 and the phase windings 12, 14 and 15 respectively.
  • Each other end of phase windings 11-15 is connected to a neutral line N.
  • a stator core 201 of five-phase 10/8 Hendershot's SRM has ten stator poles 201A, and a rotor core 202 of five-phase 10/8 Hendershot's SRM has eight rotor poles 202A as shown in Figure 13. Accordingly, the stator winding consists of two pair of five phase windings 11-15. Each stator poles is disposed with a constant circumferential pitch.
  • Rotor has two kinds of rotor pole gaps, which are narrow gaps and wide gaps.
  • the narrow gap and the wide gap are disposed alternately between adjacent two rotor poles.
  • a circumferential width of the wide rotor pole gaps is about 150% of a circumferential width of the narrow rotor pole gap.
  • Each angular position of the rotor at each time t1, t2, t3, t4 and t5 is shown in Figures 13 and 14.
  • transistors 32 and 33 are being turned on.
  • a phase voltages V12 and V13 are applied to the phase windings 12 and 13.
  • a phase currents I12 and I13 are supplied to the phase winding 12 and 13.
  • transistors 31 and 35L are being turned on.
  • a phase voltages V11 and V15 are applied to the phase windings 11 and 15.
  • a phase currents I11 and I15 are supplied to the phase winding 11 and 15.
  • transistors 33 and 34 are being turned on.
  • phase voltages V13 and V14 are applied to the phase windings 13 and 14.
  • a phase currents I13 and I14 are supplied to the phase winding 13 and 14.
  • transistors 31 and 32 are being turned on.
  • a phase voltages V11 and V12 are applied to the phase windings 11 and 12.
  • a phase currents I11 and I12 are supplied to the phase windings 11 and 12.
  • transistors 34 and 35U are being turned on.
  • a phase voltages V14 and V15 are applied to the phase windings 14 and 15.
  • a phase currents I14 and I15 are supplied to the phase windings 14 and 15. It should be considered that the phase current I15 in the period from t2 to t3 flows to an opposite direction to the phase current I15 in the period from t5 to t1.
  • one of upper transistors 31, 33 and 35U and one of lower transistors 32, 34 and 35L are turned on at one time and turned off at one time.
  • a potential of the neutral line N is not changed by the turning-on and the turning-off of two transistors at one time. It means that the single-switch-per-phase power converter shown in Figure 12 does not needs known two split capacitors which are required in a conventional split voltage type converter with the single-switch-per-phase topology.
  • each of phase voltages V11-V15 is increased in each transient period Pt, which is a predetermined period just after the previous phase switch is turned off and just after the present switch was turned on.
  • a freewheeling current of the previous phase charges the battery in the transient period Pt.
  • a present phase current increases in the transient period Pt. As the result, the rising of the phase current of the present phase increases quickly, and the freewheeling current is decreased quickly, because the phase voltage is increased as shown in Figure 14.
  • the phase current keeps a predetermined constant value in a constant-current period Pc by means of the PWM-switching.
  • the transient period Pt is shortened by means of applying the increased phase voltage in the transient period Pt.
  • the quick increasing of the phase current and the quick decreasing of the freewheeling current are realized by means of increasing of DC bus voltage Vx in the transient period Pt.
  • the boost converter 1 can change the amplitude of the DC bus voltage Vx in accordance with a required value of the motor torque, too.
  • FIG. 15 is a schematic cross-section showing the nine-phase SRM having two sets of four U-shaped rotor pole segments 201-204.
  • a stator 100 has a stator core 101 having two sets of nine stator poles 1-9, which are coupled to a stator core back 102.
  • Two sets of nine phase windings 11-19 are wound on the two sets of nine stator poles 1-9.
  • a rotor core 200 press-fixed to an axis 206 has two sets of four U-shaped rotor poles 201-204.
  • the four U-shaped rotor poles 201-204 coupled to a rotor core back 205 has eight rotor poles 21-28.
  • Each circumferential width of inner rotor gaps Wrs is narrower than each circumferential width of outer rotor gaps Wrl.
  • Each circumferential width of stator poles Wsp is mostly equal to each circumferential width of stator pole gaps Wsg.
  • Figures 16 and 17 are schematic diagrams for showing nine angular positions of the rotor of the nine-phase SRM.
  • Figure 18 is a circuit topology of the nine-phase power converter 20.
  • Figure 19 is a timing chart for showing nine phase voltages V1-V9 applied to the nine-phase SRM.
  • the nine-phase power converter 20 for driving the nine-phase SRM essentially has same operation as the five-phase power converter shown in Figure 12.
  • the power coveter 300 has five upper transistors 31, 33, 35, 37 and 39U for switching the phase windings 11, 13, 15, 17 and 19.
  • the power coveter 300 further has five lower transistors 32, 34, 36, 38 and 39L for switching the phase windings 12, 14, 16, 18 and 19. It is same that the final phase winding 19 is connected to a half bridge consisting of one upper transistors and one lower transistor.
  • Figure 19 shows excitation periods of nine phases by means of applying phase voltages V1-V9.
  • Phase voltage V1 is applied to phase winding 11.
  • Phase voltage V2 is applied to phase winding 12.
  • Phase voltage V3 is applied to phase winding 13.
  • Phase voltage V4 is applied to phase winding 14.
  • Phase voltage V5 is applied to phase winding 15.
  • Phase voltage V6 is applied to phase winding 16.
  • Phase voltage V7 is applied to phase winding 17.
  • Phase voltage V8 is applied to phase winding 18.
  • Phase voltage V9 is applied to phase winding 19.
  • each transient period one pair of one upper transistor and one lower transistor is turned on, and another pair of another upper transistor and another lower transistor is turned off, Furthermore, the DC bus voltage Vx applied to the nine-phase power converter is increased in the transient period, As the result, the transient period is shortened.
  • phase currents I6 and I7 are supplied to the phase windings 16 and 17 at the time point t2, because the phase voltages V6 and V7 are applied to the phase windings 16 and 17, It means that the current ripple at the time point t2 is reduced, because the phase currents I6 and I7 are flowing in the transient period near the time point t2.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

Un objet de la présente invention est de fournir un convertisseur continu-continu d'amplification qui est en mesure de changer en douceur un rapport de tension entre la tension d'entrée et une tension de sortie dans une large gamme. Deux paires constituées d'une bobine de réactance et d'une batterie sont connectées au moyen d'un commutateur parallèle. Le commutateur parallèle et une paire constituée de la bobine de réactance et de la batterie sont court-circuités par le premier commutateur parallèle. Le commutateur parallèle et l'autre paire constituée de la bobine de réactance et de la batterie sont court-circuités par le second commutateur parallèle. Le moteur à réluctance commuté est doté d'une période transitoire tandis qu'un courant de roue libre circule à partir d'un enroulement de phase du moteur à réluctance commuté. Dans une première moitié de la période transitoire, le convertisseur continu-continu d'amplification applique une tension d'amplification sur le convertisseur en pont.
PCT/JP2010/006167 2010-02-01 2010-10-18 Convertisseur continu-continu d'amplification et moteur à réluctance commuté alimenté au moyen de celui-ci WO2012053027A1 (fr)

Priority Applications (2)

Application Number Priority Date Filing Date Title
PCT/JP2010/006167 WO2012053027A1 (fr) 2010-10-18 2010-10-18 Convertisseur continu-continu d'amplification et moteur à réluctance commuté alimenté au moyen de celui-ci
PCT/JP2010/006674 WO2011092774A1 (fr) 2010-02-01 2010-11-12 Convertisseur élévateur continu-continu et convertisseur électrique alimenté par celui-ci

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/JP2010/006167 WO2012053027A1 (fr) 2010-10-18 2010-10-18 Convertisseur continu-continu d'amplification et moteur à réluctance commuté alimenté au moyen de celui-ci

Publications (1)

Publication Number Publication Date
WO2012053027A1 true WO2012053027A1 (fr) 2012-04-26

Family

ID=45974768

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/JP2010/006167 WO2012053027A1 (fr) 2010-02-01 2010-10-18 Convertisseur continu-continu d'amplification et moteur à réluctance commuté alimenté au moyen de celui-ci

Country Status (1)

Country Link
WO (1) WO2012053027A1 (fr)

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103516205A (zh) * 2012-06-20 2014-01-15 本田技研工业株式会社 电源装置
CN103660983A (zh) * 2012-09-21 2014-03-26 本田技研工业株式会社 电源装置
WO2018001512A1 (fr) 2016-07-01 2018-01-04 Arcelik Anonim Sirketi Appareil ménager avec module de puissance présentant une durée de roue libre réduite
WO2018141394A1 (fr) 2017-02-03 2018-08-09 Arcelik Anonim Sirketi Appareil électroménager à mécanisme de commande sans capteur de moteur cc sans balai
WO2020035969A1 (fr) * 2018-08-14 2020-02-20 田中　正一 Alimentation électrique en courant continu
CN111416558A (zh) * 2020-03-17 2020-07-14 江苏新安电器股份有限公司 一种增强开关磁阻发电机性能的改进型独立励磁变换器

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5111095A (en) * 1990-11-28 1992-05-05 Magna Physics Corporation Polyphase switched reluctance motor
JP2003324988A (ja) * 2002-05-09 2003-11-14 Nissan Motor Co Ltd リラクタンスモータの駆動装置
JP2010193700A (ja) * 2008-08-25 2010-09-02 Suri-Ai:Kk スイッチドリラクタンスモータ装置

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5111095A (en) * 1990-11-28 1992-05-05 Magna Physics Corporation Polyphase switched reluctance motor
JP2003324988A (ja) * 2002-05-09 2003-11-14 Nissan Motor Co Ltd リラクタンスモータの駆動装置
JP2010193700A (ja) * 2008-08-25 2010-09-02 Suri-Ai:Kk スイッチドリラクタンスモータ装置

Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103516205A (zh) * 2012-06-20 2014-01-15 本田技研工业株式会社 电源装置
US8994212B2 (en) 2012-06-20 2015-03-31 Honda Motor Co., Ltd. Electric power supply apparatus
CN103660983A (zh) * 2012-09-21 2014-03-26 本田技研工业株式会社 电源装置
DE102013218517A1 (de) * 2012-09-21 2014-03-27 Honda Motor Co., Ltd. Energieversorgungsvorrichtung
US9373999B2 (en) 2012-09-21 2016-06-21 Honda Motor Co., Ltd. Power supply device
WO2018001512A1 (fr) 2016-07-01 2018-01-04 Arcelik Anonim Sirketi Appareil ménager avec module de puissance présentant une durée de roue libre réduite
WO2018141394A1 (fr) 2017-02-03 2018-08-09 Arcelik Anonim Sirketi Appareil électroménager à mécanisme de commande sans capteur de moteur cc sans balai
WO2020035969A1 (fr) * 2018-08-14 2020-02-20 田中　正一 Alimentation électrique en courant continu
JPWO2020035969A1 (ja) * 2018-08-14 2021-08-10 田中　正一 直流電源
CN111416558A (zh) * 2020-03-17 2020-07-14 江苏新安电器股份有限公司 一种增强开关磁阻发电机性能的改进型独立励磁变换器

Similar Documents

Publication Publication Date Title
US8981705B2 (en) PM brushless motor drive circuit topology and control
Chang et al. An integrated driving/charging switched reluctance motor drive using three-phase power module
US7151364B2 (en) DC/DC converter and program
US9742334B2 (en) Electric motor system for vehicles and method of adjusting coil winding number of electric motor for vehicles
US9843278B2 (en) Power conversion system and control method thereof
WO2012053027A1 (fr) Convertisseur continu-continu d'amplification et moteur à réluctance commuté alimenté au moyen de celui-ci
US11159114B2 (en) Electronic transmission system
WO2011092774A1 (fr) Convertisseur élévateur continu-continu et convertisseur électrique alimenté par celui-ci
JPWO2009157097A1 (ja) 同期モータ駆動電源装置
CN104953845A (zh) 电力变换装置
US20120206076A1 (en) Motor-driving apparatus for variable-speed motor
CN110383639B (zh) 旋转电机系统
Ye et al. Power electronic converters for 12/8 switched reluctance motor drives: A comparative analysis
JP4784242B2 (ja) 電力変換システムおよびこれをを有する電動車両
Patel et al. Analysis on multilevel inverter powertrains for E-transportation
Pittermann et al. Converters for switched reluctance motor-topology comparison
Singh et al. Integrated battery charger with delta connected BLDC motor for electric vehicle applications
WO2012143968A1 (fr) Survolteur
JP2011259571A (ja) モータ駆動装置
Wang et al. High frequency bidirectional isolated matrix converter for AC-motor drives with model predictive control
Shah et al. Integrated power converter with G2V and V2G capabilities for 4-phase SRM drive based EV application
Huseini et al. Development of an integrated Switched-Reluctance Motor drive with battery charging capability for electric vehicle propulsion system
CN110677080B (zh) 一种基于混合储能单元的无刷直流电机系统控制方法
DE102012203415A1 (de) Ladeschaltung für elektrisches Antriebssystem und Verfahren zum Laden von Energiespeicherzellen in einem elektrischen Antriebssystem
Ngo et al. A predictive torque control strategy for interior permanent magnet synchronous motors driven by a three-level simplified neutral point clamped inverter

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 10858586

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

32PN Ep: public notification in the ep bulletin as address of the adressee cannot be established

Free format text: NOTING OF LOSS OF RIGHTS PURSUANT TO RULE 112(1)EPC DATED 30.07.2013

122 Ep: pct application non-entry in european phase

Ref document number: 10858586

Country of ref document: EP

Kind code of ref document: A1