WO2011020737A1 - A direct current-direct current converter - Google Patents

A direct current-direct current converter Download PDF

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Publication number
WO2011020737A1
WO2011020737A1 PCT/EP2010/061594 EP2010061594W WO2011020737A1 WO 2011020737 A1 WO2011020737 A1 WO 2011020737A1 EP 2010061594 W EP2010061594 W EP 2010061594W WO 2011020737 A1 WO2011020737 A1 WO 2011020737A1
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WO
WIPO (PCT)
Prior art keywords
direct current
power supply
current power
voltage
switched
Prior art date
Application number
PCT/EP2010/061594
Other languages
French (fr)
Inventor
De Hong Xu
Min Chen
Na SU
Original Assignee
Siemens Aktiengesellschaft
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Siemens Aktiengesellschaft filed Critical Siemens Aktiengesellschaft
Publication of WO2011020737A1 publication Critical patent/WO2011020737A1/en

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1582—Buck-boost converters

Definitions

  • the present invention relates to a direct current-direct current converter.
  • buck/boost circuits have been designed. Although early buck/boost circuits realized the function whereby the output voltage can be either increased or reduced relative to the input voltage, the input voltage and the output voltage are in polarities opposite to each other, such buck/boost circuits are not suitable to applications for electric vehicles.
  • bidirectional buck/boost direct current-direct current converter are considerable, and when it is applied to
  • the object of the present invention is to provide a direct current-direct current converter capable of reducing the fluctuations in the input and output currents.
  • a direct current-direct current converter comprises a main circuit and a control module, wherein said main circuit comprises: a first capacitor; first, second, third and fourth switching transistors each with a reversed diode connected in parallel, wherein a serial circuit formed by said first and third switching transistors is in parallel connection with said first capacitor, and a serial circuit formed by said second and fourth switching transistors is in parallel connection with said first capacitor; first and second inductors, wherein one terminal of said first inductor is connected to a first direct current power supply and the other terminal of said first inductor is connected to a point between said first and third switching transistors in said serial circuit of said first and third switching transistors, and one terminal of said second inductor is connected to a second direct current power supply, and the other terminal of said second inductor is connected to a point between said second and fourth switching transistors in said serial circuit of said second and fourth switching transistors, and said control module controls the operating states of said first, second, third and fourth switching transistors
  • a direction control signal representing the direction in which electrical energy flows in said direct current-direct current converter and the voltage detection signals of said first direct current power supply and said second direct current power supply.
  • Fig. 1 is a schematic diagram illustrating a bidirectional buck/boost direct current-direct current converter in the prior art
  • Fig. 2 is a schematic structural diagram illustrating a direct current-direct current converter according to an embodiment of the present invention
  • Fig. 3 is a schematic structural diagram illustrating a control module according to an embodiment of the present invention.
  • Fig. 4 is a schematic structural diagram illustrating a hardware-implemented control module according to an
  • Fig. 5 is a schematic diagram illustrating the operating process of the direct current-direct current converter in the case that the operating mode thereof is in the forward direction and ul > u2 according to an embodiment of the present invention
  • Fig. 6 is a schematic diagram illustrating the operating process of the direct current-direct current converter in the case that the operating mode thereof is in the forward direction and ul ⁇ u2 according to an embodiment of the present invention
  • Fig. 7 is a schematic diagram illustrating the operating process of the direct current-direct current converter in the case that the operating mode thereof is in the backward direction and ul > u2 according to an embodiment of the present invention.
  • Fig. 8 is a schematic diagram illustrating the operating process of the direct current-direct current converter in the case that the operating mode thereof is in the backward direction and ul ⁇ u2 according to an embodiment of the present invention.
  • Fig. 2 is a schematic structural diagram illustrating the direct current-direct current converter according to an embodiment of the present invention.
  • a direct current-direct current converter 100 comprises a main circuit 110 and a control module 120.
  • the main circuit 110 comprises four switching
  • transistors S1-S4 each connected to a reversed diode in parallel, three capacitors C0-C2, and two inductors L1-L2.
  • the switching transistors Sl, S2, S3 and S4 are respectively in parallel connection with the reversed diodes Dl, D2, D3 and D4.
  • the switching transistor Sl is in serial connection with S3, and the serial circuit formed by the switching transistor Sl and S3 connected in serial is in parallel with the capacitor CO.
  • the switching transistor S2 is in serial connection with S4, and the serial circuit formed by the switching transistor S2 and S4 connected in serial is in parallel with the capacitor CO.
  • the switching transistors S1-S4 are isolated-gate transistors, however, the present invention is not limited to the case that the switching transistors S1-S4 are isolated-gate transistors, in fact, the switching transistors S1-S4 can also be power field effect transistors, power bipolar transistors or other types of controllable switching
  • One terminal of the inductor Ll is connected to a point between the switching transistors Sl and S3 in the serial circuit formed by the switching transistors Sl and S3, while the other terminal of the inductor Ll is connected to a direct current power supply ul .
  • One terminal of the inductor L2 is connected to a point between the switching transistor S2 and S4 in the serial circuit formed by the switching transistors S2 and S4, while the other terminal of the inductor L2 is connected to a direct current power supply u2.
  • the capacitor Cl is in parallel connection with the direct current power supply ul
  • the capacitor C2 is in parallel connection with the direct current power supply u2.
  • the control module 120 is used for controlling the operating states of the switching transistors S1-S4 (either in a switched-on or a switched-off state) according to a direction control signal and the voltage detection signals of the direct current power supplies ul and u2, or, according to a direction control signal, the voltage detection signals of the direct current power supplies ul and u2, and the current detection signal of the inductor Ll or L2.
  • the switching transistors S1-S4 either in a switched-on or a switched-off state
  • direction control signal indicates the direction in which the electrical energy flows in the direct current-direct current converter 100, wherein the flowing direction in which the electrical energy flows from the direct current power supply ul to the direct current power supply u2 is referred to as the forward direction and the flowing direction in which the electrical energy flows from the direct current power supply u2 to the direct current power supply ul is referred to as the backward direction.
  • Fig. 3 is a schematic structural diagram illustrating the control module according to an embodiment of the present invention.
  • the control module 120 comprises a pulse-width modulated (PWM) signal generating unit 1202, a mode selecting unit 1204 and a drive unit 1206.
  • PWM pulse-width modulated
  • the pulse-width modulated signal generating unit 1202 is used for generating a pulse-width modulated signal.
  • the pulse-width modulated signal generating unit 1202 can
  • the pulse-width modulated signal generating unit 1202 can use an existing method, such as the pulse-width modulation method based on the voltage single-loop proportional-integral-derivative (PID) control, to generate the pulse-width modulated signal.
  • PID proportional-integral-derivative
  • the pulse-width modulated signal generating unit 1202 can use an existing method, such as the pulse-width modulation method based on the voltage- current dual-loop control, to generate the pulse-width modulated signal.
  • the mode selecting unit 1204 is used for receiving the direction control signal, the voltage detection signal of the direct current power supply ul and the voltage detection signal of the direct current power supply u2, comparing the relative magnitudes between the received voltage detection signals of the direct current power supplies ul and u2, and selecting the operating mode of the direct current-direct current converter 100 according to the received direction control signal and the comparison result.
  • the operating mode of the direct current-direct current converter 100 is selected to be in the forward direction with the voltage of the direct current power supply ul being greater than that of the direct current power supply u2 (forward direction and ul > u2) .
  • the operating mode of the direct current-direct current converter 100 is selected to be in the forward direction with the voltage of the direct current power supply ul being less than that of the direct current power supply u2 (forward direction and ul ⁇ u2) .
  • the operating mode of the direct current-direct current converter 100 is selected to be in the backward direction with the voltage of the direct current power supply ul being greater than that of the direct current power supply u2 (backward direction and ul > u2) .
  • the operating mode of the direct current-direct current converter 100 is selected to be in the backward direction with the voltage of the direct current power supply ul being less than that of the direct current power supply u2 (backward direction mode and ul ⁇ u2) .
  • the drive unit 1206 is used for outputting respectively corresponding drive signals to each of the switching
  • transistors S1-S4 of the main circuit 110 according to the operating mode selected by the mode selecting unit 1204 and the pulse-width modulated signal generated by the pulse-width modulated signal generating unit 1202, so as to drive the switching transistors S1-S4 in the switched-on state or the switched-off state.
  • the drive unit 1206 outputs to the switching transistors Sl, S3 and S4 respectively the drive signals representing switching-off so as to drive the switching transistors Sl, S3 and S4 in the switched-off state, and outputs to the
  • switching transistor S2 the pulse-width modulated signal generated by the pulse-width modulated signal generating unit 1202 as the drive signal representing alternately switching- on and switching-off, so as to drive the switching transistor S2 alternately in the switched-on state and the switched-off state.
  • the drive unit 1206 When the operating mode selected by the mode selecting unit 1204 is in the forward direction and ul ⁇ u2, the drive unit 1206 outputs to the switching transistors Sl and S4 respectively the drive signals representing switching-off so as to drive the switching transistors Sl and S4 in the switched-off state, outputs to the switching transistor S2 the drive signal representing switching-on so as to drive the switching transistor S2 in the switched-on state, and outputs to the switching transistor S3 the pulse-width modulated signal generated by the pulse-width modulated signal
  • the drive unit 1206 When the operating mode selected by the mode selecting unit 1204 is in the backward direction and ul > u2, the drive unit 1206 outputs to the switching transistors S2 and S3 respectively the drive signals representing switching-off so as to drive the switching transistors S2 and S3 in the switched-off state, outputs to the switching transistor Sl the drive signal representing switching-on so as to drive the switching transistor Sl in the switched-on state, and outputs to the switching transistor S4 the pulse-width modulated signal generated by the pulse-width modulated signal
  • the drive unit 1206 When the operating mode selected by the mode selecting unit 1204 is in the backward direction and ul ⁇ u2, the drive unit 1206 outputs to the switching transistors S2, S3 and S4 respectively the drive signal representing switching-off so as to drive the switching transistors S2, S3 and S4 in the switched-off state, and outputs to the switching transistor Sl with the pulse-width modulated signal generated by the pulse-width modulated signal generating unit 1202 as the drive signal representing alternately switching-on and switching-off, so as to drive the switching transistor Sl alternately in the switched-on state and the switched-off state.
  • control module 120 can be implemented by way of software, hardware or a combination of software and hardware.
  • Fig. 4 is a schematic structural diagram illustrating a hardware-implemented control module according to an
  • the control module 120 comprises a sampling part 2010, a pulse- width control part 2020, a mode selecting part 2030 and a logic control and drive part 2040.
  • the sampling part 2010 and the pulse-width control part 2020 form the pulse- width modulated signal generating unit 1202, the mode
  • the pulse-width control part 2020 generates the pulse-width modulated signal by using the pulse-width modulation method based on the voltage-current dual-loop (a voltage inner loop and a current outer loop) control, with the voltage detection signals of the direct current power supply ul or u2 and the current detection signal of the inductor Ll or L2 as the control values .
  • the sampling part 2010 comprises a sampling controller 5, which has four input terminals for acquiring the current detection signal A of the inductor Ll, the voltage detection signal B of the direct current power supply ul, the voltage detection signal C of the direct current power supply u2, and the current detection signal D of the inductor L2; and two output terminals, Pl and P2.
  • the output terminal Pl is used for outputting the voltage detection signal B or C
  • the output terminal P2 is used for outputting the current
  • the pulse-width control part 2020 comprises a first subtracter 6, a first PID controller 7, a limiting controller 8, a second subtracter 9, a second PID controller 10 and a pulse-width modulator 11.
  • the first subtracter 6 is used for calculating the difference value between the signal from the output terminal Pl of the sampling controller 5 and a reference voltage E.
  • the first subtracter 6 has two input terminals and one output terminal, in which one of the two input terminals of the first subtracter 6 is connected to the output terminal Pl of the sampling controller 5, the other input terminal receives the reference voltage E, and the output terminal outputs the calculated difference value.
  • the first PID controller 7 is used for carrying out a PID control on the difference value outputted from the first subtracter 6.
  • the first PID controller 7 has one input terminal and one output terminal, wherein the input terminal of the first PID controller 7 is connected to the output terminal of the first subtracter 6.
  • the limiting controller 8 is used for limiting the output value of the first PID controller 7 to be within a predefined range.
  • the limiting controller 8 has one input terminal and one output terminal, in which the input terminal of the limiting controller 8 is connected to the output terminal of the first PID controller 7.
  • the second subtracter 9 is used for calculating the difference value between the value from the output terminal of the limiting controller 8 and the signal from the output terminal P2 of the sampling controller 5.
  • subtracter 9 has two input terminals and one output terminal, in which one of the two input terminals of the second
  • the subtracter 9 is connected to the output terminal of the limiting controller 8, and the other input terminal of the second subtracter 9 is connected to the output terminal P2 of the sampling controller 5.
  • the second PID controller 10 is used for carrying out a PID control on the difference value outputted by the second subtracter 9.
  • the second PID controller 10 has one input terminal and one output terminal. In this case, the input terminal of the second controller 10 is connected to the output terminal of the second subtracter 9.
  • the pulse-width modulator 11 is used for generating a pulse modulating signal by using the signal outputted by the second PID controller 10.
  • the pulse-width modulator 11 has one input terminal and one output terminal. In this case, the input terminal of the pulse-width modulator 11 is connected to the output terminal of the second PID controller 10, and the pulse-width modulator 11 outputs to the drive part 2040 (the drive unit 1206) the pulse-width modulated signal generated by itself via its output terminal.
  • the pulse-width modulator 11 can be implemented by using, for example, a pulse-width modulation (PWM) control chip UC3525, and the first subtracter 6, the first PID controller 7, the limiting controller 8, the second subtracter 9 and the second controller 10 can be implemented either by using, for example, commonly used circuits
  • PWM pulse-width modulation
  • DSP digital signal processor
  • MCU microcontroller unit
  • the mode selecting part 2030 comprises a voltage
  • comparator 12 and a mode logic control circuit 13.
  • the voltage comparator 12 has two input terminals and one output terminal. In this case, the two input terminals of the voltage comparator 12 receive respectively the voltage detection signal B of the direct current power supply ul and the voltage detection signal C of the direct current power supply u2.
  • the voltage comparator 12 compares the relative magnitudes between the received voltage detection signals B and C, and outputs the comparison result via its output terminal, in which the comparison result is either B being greater than C or B being less than C.
  • the mode logic control circuit 13 has two input
  • one of the input terminals of the mode logic control circuit 13 is connected to the output terminal of the voltage comparator 12, and the other input terminal of the mode logic control circuit 13 receives a direction control signal F.
  • the mode logic control circuit 13 selects the operating mode of the direct current-direct current converter 100 according to the received direction control signal F and the comparison result from the voltage comparator 12, and outputs the operating mode signal representing the selected operating mode via its four output terminals.
  • the mode control logic circuit 13 selects the operating mode of the direct current-direct current converter 100 in the forward direction and ul > u2, and outputs the operating mode signal representing the forward direction and ul > u2 via its first output terminal; when the direction control signal F indicates the forward direction and the comparison result from the voltage comparator 12 is that B is less than C, the mode control logic circuit 13 selects the operating mode of the direct current-direct current converter 100 in the forward direction and ul ⁇ u2, and outputs the operating mode signal representing the forward direction and ul ⁇ u2 via its second output terminal; when the direction control signal F indicates the backward direction and the comparison result from the voltage comparator 12 is that B is greater than C, the mode control logic circuit 13 selects the operating mode of the direct current-direct current converter 100 in the backward direction and ul > u2, and outputs the operating mode signal representing the backward direction and ul > u2 via its third output
  • the comparator 12 can be implemented either by using, for example, commonly used circuits
  • the mode logic control circuit 13 can be any type of circuitry, or by using a digital signal processor (DSP) or a microcontroller unit (MCU) .
  • DSP digital signal processor
  • MCU microcontroller unit
  • logic circuits such as AND gates, NOT gates, and so on.
  • the logic control and drive part 2040 is implemented as a circuit, referred to herein as a logic control and drive circuit 14, which has five input terminals and four output terminals.
  • the five input terminals of the logic control and drive circuit 14 are respectively connected to the four output terminals of the mode logic control circuit 13 and the output terminal of the pulse-width
  • the logic control and drive circuit 14 outputs corresponding drive signals respectively to the four
  • switching transistors S1-S4 according to the operating mode signal from the mode logic control circuit 13 and the pulse- width modulated signal from the pulse-width modulator 11, so as to drive the switching transistors S1-S4 in a switched-on state or in a switched-off sate.
  • the logic control and drive circuit 13 can be any logic control and drive circuit 13.
  • logic circuits such as AND gates, NOT gates, and so on, and gate-driver chips corresponding to the switching transistors.
  • Figs 5-8 are schematic diagrams respectively
  • ugsl to ugs4 are respectively the drive signals outputted by the control module 120 to the gates of the switching
  • transistors S1-S4, uO is the voltage waveform of the
  • intermediate capacitor CO, uLl and uL2 are respectively the voltage waveforms across the two terminals of the inductors Ll, L2, and iLl and iL2 are respectively the waveforms of the currents flowing through the inductors Ll and L2.
  • switching transistor S2 and the diode D4 are alternately switched-on in phase 1 and phase 2, and the capacitor CO releases energy in phase 1 and stores energy in phase 2.
  • the switching transistors Sl and S4 are kept in the switched-off state, the switching transistor S2 is kept in the switched-on state, and the switching transistor S3 operates with a certain duty cycle.
  • the switching transistor S3 and the diode Dl are alternately switched-on in phase 1 and phase 2, and the capacitor CO releases energy in phase 1 and stores energy in phase 2.
  • the switching transistors S2 and S4 are kept in the switched-off state, the switching transistor Sl is kept in the switched-on state, and the switching transistor S4 operates with a certain duty cycle.
  • the switching transistor S4 and the diode D2 are alternately switched-on in phase 1 and phase 2, and the capacitor CO releases energy in phase 1 and stores energy in phase 2.
  • the switching transistors S2, S3 and S4 are kept in the switched-off state, the reversely shunted diode D2 is kept in the switched-on state, and the switching transistor Sl operates with a certain duty cycle.
  • the switching transistor Sl and the diode D3 are alternately switched-on in phase 1 and phase 2, and the capacitor CO releases energy in phase 1 and stores energy in phase 2.
  • the pulse- width control part 2020 utilizes the pulse-width modulation method based on the voltage inner loop and current outer loop control to generate the pulse-width modulated signals
  • the present invention is not limited to this.
  • the pulse-width control part 2020 can also utilize the pulse-width modulation method based on voltage outer loop and current inner loop control to generate the pulse-width modulated signals.
  • the output terminal Pl of the sampling controller 5 outputs the current detection signal A of the inductor Ll or the current detection signal D of the inductor L2
  • the output terminal P2 of the sampling controller 5 outputs the voltage detection signal B of the direct current power supply ul or the voltage detection signal C of the direct current power supply u2
  • the first subtracter 6 does not receive the reference voltage E but receives a reference current.
  • the main circuit 110 comprises the capacitor Cl in parallel connection with the direct current power supply ul and the capacitor C2 in parallel connection with the direct current power supply u2
  • the present invention is not limited to this. In other embodiments of the present invention, it is also possible for the main circuit 110 not to comprise the

Abstract

The present invention relates to a direct current-direct current converter comprising a main circuit and a control module, wherein the main circuit comprises: a first capacitor; first to fourth switching transistors each with a reversed diode connected in parallel, wherein a serial circuit formed by the first and the third switching transistors is in parallel connection with the first capacitor, and a serial circuit formed by the second and the fourth switching transistors is in parallel connection with the first capacitor; first and second inductors, wherein one terminal of the first inductor is connected to a first direct current power supply and the other terminal thereof is connected to a point between the first and the third switching transistors in the serial circuit of the first and the third switching transistors, one terminal of the second inductor is connected to a second direct current power supply and the other terminal thereof is connected to a point between the second and the fourth switching transistors in the serial circuit of the second and the fourth switching transistors, and the control module controls the operating states of the first to the fourth switching transistors according to a direction control signal and the voltage detection signals of the first direct current power supply and the second direct current power supply. This direct current-direct current converter is capable of reducing the fluctuations of input and output currents.

Description

Description A direct current-direct current converter Technical field
The present invention relates to a direct current-direct current converter.
Background art
Traditional boost circuits are only applicable to situations where the output voltage is higher than the input voltage while traditional buck circuits are only applicable to situations in which the output voltage is lower than the input voltage, therefore, in situations where it is required that the output voltage be either lower than or higher than the input voltage, neither traditional boost circuits nor traditional buck circuits are applicable.
For this reason, buck/boost circuits have been designed. Although early buck/boost circuits realized the function whereby the output voltage can be either increased or reduced relative to the input voltage, the input voltage and the output voltage are in polarities opposite to each other, such buck/boost circuits are not suitable to applications for electric vehicles.
In this case, a bidirectional buck/boost direct current- direct current converter as shown in Fig. 1 is proposed, with its output voltage in positive polarity. However, the
fluctuations in the input and output currents of this
bidirectional buck/boost direct current-direct current converter are considerable, and when it is applied to
rechargeable batteries, the current fluctuations will affect the safety and the service life of the batteries.
In view of the above problems in the prior art, the object of the present invention is to provide a direct current-direct current converter capable of reducing the fluctuations in the input and output currents.
A direct current-direct current converter according to the embodiments of the present invention comprises a main circuit and a control module, wherein said main circuit comprises: a first capacitor; first, second, third and fourth switching transistors each with a reversed diode connected in parallel, wherein a serial circuit formed by said first and third switching transistors is in parallel connection with said first capacitor, and a serial circuit formed by said second and fourth switching transistors is in parallel connection with said first capacitor; first and second inductors, wherein one terminal of said first inductor is connected to a first direct current power supply and the other terminal of said first inductor is connected to a point between said first and third switching transistors in said serial circuit of said first and third switching transistors, and one terminal of said second inductor is connected to a second direct current power supply, and the other terminal of said second inductor is connected to a point between said second and fourth switching transistors in said serial circuit of said second and fourth switching transistors, and said control module controls the operating states of said first, second, third and fourth switching transistors
according to a direction control signal representing the direction in which electrical energy flows in said direct current-direct current converter and the voltage detection signals of said first direct current power supply and said second direct current power supply.
Description of the accompanying drawings
The features, characteristics and advantages of the present invention will become more apparent by way of the detailed description hereinbelow in conjunction with the accompanying drawings. In the drawings: Fig. 1 is a schematic diagram illustrating a bidirectional buck/boost direct current-direct current converter in the prior art;
Fig. 2 is a schematic structural diagram illustrating a direct current-direct current converter according to an embodiment of the present invention;
Fig. 3 is a schematic structural diagram illustrating a control module according to an embodiment of the present invention;
Fig. 4 is a schematic structural diagram illustrating a hardware-implemented control module according to an
embodiment of the present invention;
Fig. 5 is a schematic diagram illustrating the operating process of the direct current-direct current converter in the case that the operating mode thereof is in the forward direction and ul > u2 according to an embodiment of the present invention;
Fig. 6 is a schematic diagram illustrating the operating process of the direct current-direct current converter in the case that the operating mode thereof is in the forward direction and ul < u2 according to an embodiment of the present invention;
Fig. 7 is a schematic diagram illustrating the operating process of the direct current-direct current converter in the case that the operating mode thereof is in the backward direction and ul > u2 according to an embodiment of the present invention; and
Fig. 8 is a schematic diagram illustrating the operating process of the direct current-direct current converter in the case that the operating mode thereof is in the backward direction and ul < u2 according to an embodiment of the present invention.
Exemplary embodiments
Hereinbelow, each of the embodiments of the present invention will be described in detail in conjunction with the accompanying drawings . Fig. 2 is a schematic structural diagram illustrating the direct current-direct current converter according to an embodiment of the present invention. As shown in Fig. 2, a direct current-direct current converter 100 comprises a main circuit 110 and a control module 120.
The main circuit 110 comprises four switching
transistors S1-S4, each connected to a reversed diode in parallel, three capacitors C0-C2, and two inductors L1-L2.
In this case, the switching transistors Sl, S2, S3 and S4 are respectively in parallel connection with the reversed diodes Dl, D2, D3 and D4. The switching transistor Sl is in serial connection with S3, and the serial circuit formed by the switching transistor Sl and S3 connected in serial is in parallel with the capacitor CO. The switching transistor S2 is in serial connection with S4, and the serial circuit formed by the switching transistor S2 and S4 connected in serial is in parallel with the capacitor CO. In Fig. 2, the switching transistors S1-S4 are isolated-gate transistors, however, the present invention is not limited to the case that the switching transistors S1-S4 are isolated-gate transistors, in fact, the switching transistors S1-S4 can also be power field effect transistors, power bipolar transistors or other types of controllable switching
components .
One terminal of the inductor Ll is connected to a point between the switching transistors Sl and S3 in the serial circuit formed by the switching transistors Sl and S3, while the other terminal of the inductor Ll is connected to a direct current power supply ul .
One terminal of the inductor L2 is connected to a point between the switching transistor S2 and S4 in the serial circuit formed by the switching transistors S2 and S4, while the other terminal of the inductor L2 is connected to a direct current power supply u2. The capacitor Cl is in parallel connection with the direct current power supply ul, and the capacitor C2 is in parallel connection with the direct current power supply u2.
The control module 120 is used for controlling the operating states of the switching transistors S1-S4 (either in a switched-on or a switched-off state) according to a direction control signal and the voltage detection signals of the direct current power supplies ul and u2, or, according to a direction control signal, the voltage detection signals of the direct current power supplies ul and u2, and the current detection signal of the inductor Ll or L2. Here, the
direction control signal indicates the direction in which the electrical energy flows in the direct current-direct current converter 100, wherein the flowing direction in which the electrical energy flows from the direct current power supply ul to the direct current power supply u2 is referred to as the forward direction and the flowing direction in which the electrical energy flows from the direct current power supply u2 to the direct current power supply ul is referred to as the backward direction.
Fig. 3 is a schematic structural diagram illustrating the control module according to an embodiment of the present invention. As shown in Fig. 3, the control module 120 comprises a pulse-width modulated (PWM) signal generating unit 1202, a mode selecting unit 1204 and a drive unit 1206. The pulse-width modulated signal generating unit 1202 is used for generating a pulse-width modulated signal. The pulse-width modulated signal generating unit 1202 can
generate the pulse-width modulated signals both with the voltage detection signal of the direct current power supply ul or u2 as the control value, and with the voltage detection signal of the direct current power supply ul or u2 and the current detection signal of the inductor Ll or L2 as the control values. When the voltage detection signal of the direct current power supply ul or u2 is used as the control value to
generate the pulse-width modulated signal, the pulse-width modulated signal generating unit 1202 can use an existing method, such as the pulse-width modulation method based on the voltage single-loop proportional-integral-derivative (PID) control, to generate the pulse-width modulated signal. When the voltage detection signal of the direct current power supply ul or u2 and the current detection signal of the inductors Ll or L2 are used as the control values to generate the pulse-width modulated signal, the pulse-width modulated signal generating unit 1202 can use an existing method, such as the pulse-width modulation method based on the voltage- current dual-loop control, to generate the pulse-width modulated signal.
The mode selecting unit 1204 is used for receiving the direction control signal, the voltage detection signal of the direct current power supply ul and the voltage detection signal of the direct current power supply u2, comparing the relative magnitudes between the received voltage detection signals of the direct current power supplies ul and u2, and selecting the operating mode of the direct current-direct current converter 100 according to the received direction control signal and the comparison result.
Particularly, when the received direction control signal indicates the forward direction and the comparison result indicates that the voltage detection signal of the direct current power supply ul is greater than the voltage detection signal of the direct current power supply u2, the operating mode of the direct current-direct current converter 100 is selected to be in the forward direction with the voltage of the direct current power supply ul being greater than that of the direct current power supply u2 (forward direction and ul > u2) . When the received direction control signal indicates the forward direction and the comparison result indicates that the voltage detection signal of the direct current power supply ul is less than the voltage detection signal of the direct current power supply u2, the operating mode of the direct current-direct current converter 100 is selected to be in the forward direction with the voltage of the direct current power supply ul being less than that of the direct current power supply u2 (forward direction and ul < u2) .
When the received direction control signal indicates the backward direction and the comparison result indicates that the voltage detection signal of the direct current power supply ul is greater than the voltage detection signal of the direct current power supply u2, the operating mode of the direct current-direct current converter 100 is selected to be in the backward direction with the voltage of the direct current power supply ul being greater than that of the direct current power supply u2 (backward direction and ul > u2) .
When the received direction control signal indicates the backward direction and the comparison result indicates that the voltage detection signal of the direct current power supply ul is less than the voltage detection signal of the direct current power supply u2, the operating mode of the direct current-direct current converter 100 is selected to be in the backward direction with the voltage of the direct current power supply ul being less than that of the direct current power supply u2 (backward direction mode and ul< u2) .
The drive unit 1206 is used for outputting respectively corresponding drive signals to each of the switching
transistors S1-S4 of the main circuit 110 according to the operating mode selected by the mode selecting unit 1204 and the pulse-width modulated signal generated by the pulse-width modulated signal generating unit 1202, so as to drive the switching transistors S1-S4 in the switched-on state or the switched-off state.
Particularly, when the operating mode selected by the mode selecting unit 1204 is in the forward direction and ul > u2, the drive unit 1206 outputs to the switching transistors Sl, S3 and S4 respectively the drive signals representing switching-off so as to drive the switching transistors Sl, S3 and S4 in the switched-off state, and outputs to the
switching transistor S2 the pulse-width modulated signal generated by the pulse-width modulated signal generating unit 1202 as the drive signal representing alternately switching- on and switching-off, so as to drive the switching transistor S2 alternately in the switched-on state and the switched-off state.
When the operating mode selected by the mode selecting unit 1204 is in the forward direction and ul < u2, the drive unit 1206 outputs to the switching transistors Sl and S4 respectively the drive signals representing switching-off so as to drive the switching transistors Sl and S4 in the switched-off state, outputs to the switching transistor S2 the drive signal representing switching-on so as to drive the switching transistor S2 in the switched-on state, and outputs to the switching transistor S3 the pulse-width modulated signal generated by the pulse-width modulated signal
generating unit 1202 as the drive signal representing
alternately switching-on and switching-off, so as to drive the switching transistor S3 alternately in the switched-on state and the switched-off state.
When the operating mode selected by the mode selecting unit 1204 is in the backward direction and ul > u2, the drive unit 1206 outputs to the switching transistors S2 and S3 respectively the drive signals representing switching-off so as to drive the switching transistors S2 and S3 in the switched-off state, outputs to the switching transistor Sl the drive signal representing switching-on so as to drive the switching transistor Sl in the switched-on state, and outputs to the switching transistor S4 the pulse-width modulated signal generated by the pulse-width modulated signal
generating unit 1202 as the drive signal representing
alternately switching-on and switching-off, so as to drive the switching transistor S4 alternately in the switched-on state and the switched-off state.
When the operating mode selected by the mode selecting unit 1204 is in the backward direction and ul < u2, the drive unit 1206 outputs to the switching transistors S2, S3 and S4 respectively the drive signal representing switching-off so as to drive the switching transistors S2, S3 and S4 in the switched-off state, and outputs to the switching transistor Sl with the pulse-width modulated signal generated by the pulse-width modulated signal generating unit 1202 as the drive signal representing alternately switching-on and switching-off, so as to drive the switching transistor Sl alternately in the switched-on state and the switched-off state.
It should be understood by those skilled in the art that, the control module 120 can be implemented by way of software, hardware or a combination of software and hardware.
Fig. 4 is a schematic structural diagram illustrating a hardware-implemented control module according to an
embodiment of the present invention. As shown in Fig. 4, the control module 120 comprises a sampling part 2010, a pulse- width control part 2020, a mode selecting part 2030 and a logic control and drive part 2040. Here, the sampling part 2010 and the pulse-width control part 2020 form the pulse- width modulated signal generating unit 1202, the mode
selecting part 2030 corresponds to the mode selecting unit 1204, and the logic control and drive part 2040 corresponds to the drive unit 1206. In this embodiment, the pulse-width control part 2020 generates the pulse-width modulated signal by using the pulse-width modulation method based on the voltage-current dual-loop (a voltage inner loop and a current outer loop) control, with the voltage detection signals of the direct current power supply ul or u2 and the current detection signal of the inductor Ll or L2 as the control values .
The sampling part 2010 comprises a sampling controller 5, which has four input terminals for acquiring the current detection signal A of the inductor Ll, the voltage detection signal B of the direct current power supply ul, the voltage detection signal C of the direct current power supply u2, and the current detection signal D of the inductor L2; and two output terminals, Pl and P2. The output terminal Pl is used for outputting the voltage detection signal B or C, and the output terminal P2 is used for outputting the current
detection signal A or D.
The pulse-width control part 2020 comprises a first subtracter 6, a first PID controller 7, a limiting controller 8, a second subtracter 9, a second PID controller 10 and a pulse-width modulator 11.
The first subtracter 6 is used for calculating the difference value between the signal from the output terminal Pl of the sampling controller 5 and a reference voltage E.
The first subtracter 6 has two input terminals and one output terminal, in which one of the two input terminals of the first subtracter 6 is connected to the output terminal Pl of the sampling controller 5, the other input terminal receives the reference voltage E, and the output terminal outputs the calculated difference value.
The first PID controller 7 is used for carrying out a PID control on the difference value outputted from the first subtracter 6. The first PID controller 7 has one input terminal and one output terminal, wherein the input terminal of the first PID controller 7 is connected to the output terminal of the first subtracter 6. The limiting controller 8 is used for limiting the output value of the first PID controller 7 to be within a predefined range. The limiting controller 8 has one input terminal and one output terminal, in which the input terminal of the limiting controller 8 is connected to the output terminal of the first PID controller 7.
The second subtracter 9 is used for calculating the difference value between the value from the output terminal of the limiting controller 8 and the signal from the output terminal P2 of the sampling controller 5. The second
subtracter 9 has two input terminals and one output terminal, in which one of the two input terminals of the second
subtracter 9 is connected to the output terminal of the limiting controller 8, and the other input terminal of the second subtracter 9 is connected to the output terminal P2 of the sampling controller 5. The second PID controller 10 is used for carrying out a PID control on the difference value outputted by the second subtracter 9. The second PID controller 10 has one input terminal and one output terminal. In this case, the input terminal of the second controller 10 is connected to the output terminal of the second subtracter 9.
The pulse-width modulator 11 is used for generating a pulse modulating signal by using the signal outputted by the second PID controller 10. The pulse-width modulator 11 has one input terminal and one output terminal. In this case, the input terminal of the pulse-width modulator 11 is connected to the output terminal of the second PID controller 10, and the pulse-width modulator 11 outputs to the drive part 2040 (the drive unit 1206) the pulse-width modulated signal generated by itself via its output terminal.
In this case, the pulse-width modulator 11 can be implemented by using, for example, a pulse-width modulation (PWM) control chip UC3525, and the first subtracter 6, the first PID controller 7, the limiting controller 8, the second subtracter 9 and the second controller 10 can be implemented either by using, for example, commonly used circuits
constructed by corresponding operational amplifiers, or by using a digital signal processor (DSP) or a microcontroller unit (MCU) .
The mode selecting part 2030 comprises a voltage
comparator 12 and a mode logic control circuit 13.
The voltage comparator 12 has two input terminals and one output terminal. In this case, the two input terminals of the voltage comparator 12 receive respectively the voltage detection signal B of the direct current power supply ul and the voltage detection signal C of the direct current power supply u2. The voltage comparator 12 compares the relative magnitudes between the received voltage detection signals B and C, and outputs the comparison result via its output terminal, in which the comparison result is either B being greater than C or B being less than C.
The mode logic control circuit 13 has two input
terminals and four output terminals. In this case, one of the input terminals of the mode logic control circuit 13 is connected to the output terminal of the voltage comparator 12, and the other input terminal of the mode logic control circuit 13 receives a direction control signal F. The mode logic control circuit 13 selects the operating mode of the direct current-direct current converter 100 according to the received direction control signal F and the comparison result from the voltage comparator 12, and outputs the operating mode signal representing the selected operating mode via its four output terminals. Particularly, when the direction control signal F indicates the forward direction and the comparison result from the voltage comparator 12 is that B is greater than C, the mode control logic circuit 13 selects the operating mode of the direct current-direct current converter 100 in the forward direction and ul > u2, and outputs the operating mode signal representing the forward direction and ul > u2 via its first output terminal; when the direction control signal F indicates the forward direction and the comparison result from the voltage comparator 12 is that B is less than C, the mode control logic circuit 13 selects the operating mode of the direct current-direct current converter 100 in the forward direction and ul < u2, and outputs the operating mode signal representing the forward direction and ul < u2 via its second output terminal; when the direction control signal F indicates the backward direction and the comparison result from the voltage comparator 12 is that B is greater than C, the mode control logic circuit 13 selects the operating mode of the direct current-direct current converter 100 in the backward direction and ul > u2, and outputs the operating mode signal representing the backward direction and ul > u2 via its third output terminal; and when the direction control signal F indicates the backward direction and the comparison result from the voltage comparator 12 is that B is less than C, the mode control logic circuit 13 selects the operating mode of the direct current-direct current converter 100 in the backward direction and ul < u2, and outputs the operating mode signal representing the backward direction and ul < u2 via its fourth output terminal.
In this case, the comparator 12 can be implemented either by using, for example, commonly used circuits
constructed by corresponding operational amplifiers, or by using a digital signal processor (DSP) or a microcontroller unit (MCU) . The mode logic control circuit 13 can be
implemented by using, for example, logic circuits such as AND gates, NOT gates, and so on.
The logic control and drive part 2040 is implemented as a circuit, referred to herein as a logic control and drive circuit 14, which has five input terminals and four output terminals. In this case, the five input terminals of the logic control and drive circuit 14 are respectively connected to the four output terminals of the mode logic control circuit 13 and the output terminal of the pulse-width
modulator 11, and the four output terminals of the logic control and drive circuit 14 are respectively connected to the gates of the four switching transistors S1-S4 of the main circuit 110. The logic control and drive circuit 14 outputs corresponding drive signals respectively to the four
switching transistors S1-S4 according to the operating mode signal from the mode logic control circuit 13 and the pulse- width modulated signal from the pulse-width modulator 11, so as to drive the switching transistors S1-S4 in a switched-on state or in a switched-off sate.
The logic control and drive circuit 13 can be
implemented by using, for example, logic circuits, such as AND gates, NOT gates, and so on, and gate-driver chips corresponding to the switching transistors.
Figs 5-8 are schematic diagrams respectively
illustrating the operation processes of the direct current- direct current converter in various operating modes according to an embodiment of the present invention. In Figs 5 to 8, ugsl to ugs4 are respectively the drive signals outputted by the control module 120 to the gates of the switching
transistors S1-S4, uO is the voltage waveform of the
intermediate capacitor CO, uLl and uL2 are respectively the voltage waveforms across the two terminals of the inductors Ll, L2, and iLl and iL2 are respectively the waveforms of the currents flowing through the inductors Ll and L2.
As shown in Fig. 5, when the operating mode of the direct current-direct current converter is in the forward direction and ul > u2, the switching transistors Sl, S3 and S4 are kept in the switched-off state, the reversely shunted diode Dl is kept in the switched-on state, and the switching transistor S2 operates with a certain duty cycle. The
switching transistor S2 and the diode D4 are alternately switched-on in phase 1 and phase 2, and the capacitor CO releases energy in phase 1 and stores energy in phase 2.
As shown in Fig. 6, when the operating mode of the direct current-direct current converter is in the forward direction and ul < u2, the switching transistors Sl and S4 are kept in the switched-off state, the switching transistor S2 is kept in the switched-on state, and the switching transistor S3 operates with a certain duty cycle. The switching transistor S3 and the diode Dl are alternately switched-on in phase 1 and phase 2, and the capacitor CO releases energy in phase 1 and stores energy in phase 2.
As shown in Fig. 7, when the operating mode of the direct current-direct current converter is the backward direction and ul > u2, the switching transistors S2 and S4 are kept in the switched-off state, the switching transistor Sl is kept in the switched-on state, and the switching transistor S4 operates with a certain duty cycle. The switching transistor S4 and the diode D2 are alternately switched-on in phase 1 and phase 2, and the capacitor CO releases energy in phase 1 and stores energy in phase 2.
As shown in Fig. 8, when the operating mode of the direct current-direct current converter is in the backward direction and ul < u2, the switching transistors S2, S3 and S4 are kept in the switched-off state, the reversely shunted diode D2 is kept in the switched-on state, and the switching transistor Sl operates with a certain duty cycle. The switching transistor Sl and the diode D3 are alternately switched-on in phase 1 and phase 2, and the capacitor CO releases energy in phase 1 and stores energy in phase 2.
It should be appreciated by those skilled in the art that, although in the above-described embodiments the pulse- width control part 2020 utilizes the pulse-width modulation method based on the voltage inner loop and current outer loop control to generate the pulse-width modulated signals, the present invention, however, is not limited to this. In other embodiments of the present invention, the pulse-width control part 2020 can also utilize the pulse-width modulation method based on voltage outer loop and current inner loop control to generate the pulse-width modulated signals. In this case, the output terminal Pl of the sampling controller 5 outputs the current detection signal A of the inductor Ll or the current detection signal D of the inductor L2, the output terminal P2 of the sampling controller 5 outputs the voltage detection signal B of the direct current power supply ul or the voltage detection signal C of the direct current power supply u2, and the first subtracter 6 does not receive the reference voltage E but receives a reference current. It should be appreciated by those skilled in the art that, although in the above-described embodiments the main circuit 110 comprises the capacitor Cl in parallel connection with the direct current power supply ul and the capacitor C2 in parallel connection with the direct current power supply u2, the present invention, however, is not limited to this. In other embodiments of the present invention, it is also possible for the main circuit 110 not to comprise the
capacitors Cl and C2. It should be appreciated by those skilled in the art that, various variations and modifications can be made to each of the embodiments of the present invention without departing from the spirit of the present invention, and all these variations and modifications should fall into the protective scope of the present invention. Therefore, the protective scope of the present invention is to be defined by the attached claims.

Claims

Claims
1. A direct current-direct current converter,
comprising:
a main circuit, wherein said main circuit comprises: a first capacitor;
first, second, third and fourth switching transistors each with a reversed diode connected in parallel, wherein a serial circuit formed by said first and third switching transistors is in parallel connection with said first capacitor, and a serial circuit formed by said second and fourth switching transistors is in parallel connection with said first capacitor;
first and second inductors, wherein one terminal of said first inductor is connected to a first direct current power supply, the other terminal of said first inductor is connected to a point between said first and third switching transistors in said serial circuit formed by said first and third switching transistors, and one terminal of said second inductor is connected to a second direct current power supply, and the other terminal of said second inductor is connected to a point between said second and fourth switching transistors in said serial circuit formed by said second and fourth switching transistors; and
a control module for controlling the operating states of said first, second, third and fourth switching transistors according to a direction control signal representing the direction in which the electrical energy flows in said direct current-direct current converter and the voltage detection signals of said first direct current power supply and said second direct current power supply.
2. The direct current-direct current converter as claimed in claim 1, wherein said control module further comprises :
a pulse-width modulated signal generating unit for generating a pulse-width modulated signal by using a corresponding pulse-width modulation method with the voltage detection signal of said first direct current power supply or said second direct current power supply as a control value; a mode selecting unit for selecting the operating mode of said direct current-direct current converter according to the relative magnitude between said first direct current power supply and said second direct current power supply and said direction control signal; and
a drive unit for driving said first, second, third and fourth switching transistors into a switched-on state or a switched-off state according to said selected operating mode and said generated pulse-width modulated signal.
3. The direct current-direct current converter as claimed in claim 2, wherein
said pulse-width modulated signal generating unit is further used for generating the pulse-width modulated signal by using the corresponding pulse-width modulation method, with the voltage detection signal of said first direct current power supply or said second direct current power supply and the current detection signal of said first
inductor or said second inductor as the control values.
4. The direct current-direct current converter as claimed in claim 2 or 3, wherein
said mode selecting unit is further used for selecting the operating mode of said direct current-direct current converter to be in a forward direction and the voltage of said first direct current power supply to be greater than the voltage of said second direct current power supply, when the voltage detection signal of said first direct current power supply is greater than the voltage detection signal of said second direct current power supply and said direction control signal indicates that the electrical energy in said direct current-direct current converter is flowing from said first direct current power supply to said second direct current power supply.
5. The direct current-direct current converter as claimed in claim 2 or 3, wherein
said mode selecting unit is further used for selecting the operating mode of said direct current-direct current converter in the forward direction and the voltage of said first direct current power supply to be less than the voltage of said second direct current power supply, when the voltage detection signal of said first direct current power supply is less than the voltage detection signal of said second direct current power supply and said direction control signal indicates that the electrical energy in said direct current- direct current converter is flowing from said first direct current power supply to said second direct current power supply.
6. The direct current-direct current converter as claimed in claim 2 or 3, wherein
said mode selecting unit is further used for selecting the operating mode of said direct current-direct current converter to be in a backward direction and the voltage of said first direct current power supply to be greater than the voltage of said second direct current power supply, when the voltage detection signal of said first direct current power supply is greater than the voltage detection signal of said second direct current power supply and said direction control signal indicates that the electrical energy in said direct current-direct current converter is flowing from said second direct current power supply to said first direct current power supply.
7. The direct current-direct current converter as claimed in claim 2 or 3, wherein
said mode selecting unit is further used for selecting the operating mode of said direct current-direct current converter in the backward direction mode and the voltage of said first direct current power supply to be less than the voltage of said second direct current power supply, when the voltage detection signal of said first direct current power supply is less than the voltage detection signal of said second direct current power supply and said direction control signal indicates that the electrical energy in said direct current-direct current converter is flowing from said second direct current power supply to said first direct current power supply.
8. The direct current-direct current converter as claimed in claim 2 or 3, wherein
said drive unit is further used for driving said first, third and fourth switching transistors in the switched-off state and said second switching transistor to be alternately in the switched-on state and the switched-off state by using said generated pulse-width modulated signal, when said selected operating mode is in the forward direction and the voltage of said first direct current power supply is greater than the voltage of said second direct current power supply.
9. The direct current-direct current converter as claimed in claim 2 or 3, wherein
said drive unit is further used for driving said first and fourth switching transistors to be in the switched-off state, said second switching transistor to be in the
switched-on state, and said third switching transistor to be alternately in the switched-on state and the switched-off state by using said generated pulse-width modulated signal, when said selected operating mode is in the forward direction mode and the voltage of said first direct current power supply is less than the voltage of said second direct current power supply.
10. The direct current-direct current converter as claimed in claim 2 or 3, wherein
said drive unit is further used for driving said second and third switching transistors to be in the switched-off state, said first switching transistor to be in the switched- on state, and said fourth switching transistor to be
alternately in the switched-on state and the switched-off state by using said generated pulse-width modulated signal, when said selected operating mode is in the backward
direction and the voltage of said first direct current power supply is greater than the voltage of said second direct current power supply.
11. The direct current-direct current converter as claimed in claim 2 or 3, wherein
said drive unit is further used for driving said second, third and fourth switching transistors to be in the switched- off state and said first switching transistor to be
alternately in the switched-on state and the switched-off state by using said generated pulse-width modulated signal, when said selected operating mode is in the backward
direction and the voltage of said first direct current power supply is less than the voltage of said second direct current power supply.
12. The direct current-direct current converter as claimed in claim 3, wherein said pulse-width modulated signal generating unit further comprises:
a sampling controller having four input terminals and two output terminals, wherein the four input terminals of said sampling controller respectively receive the current detection signals of said first and second inductors and the voltage detection signals of said first and second direct current power suppliers, and the two output terminals of said sampling controller respectively output the current detection signal of said first inductor or said second inductor and the voltage detection signal of said first direct current power supply or said second direct current power supply;
a first subtracter having two input terminals and one output terminal, wherein one of the input terminals of said first subtracter is connected to one of the two output terminals of said sampling controller, and the other input terminal of said first subtracter receives a reference voltage or a reference current; a first proportional-integral-derivative controller having one input terminal and one output terminal, wherein the input terminal of said first proportional-integral- derivative controller is connected to the output terminal of said first subtracter;
a limiting controller having one input terminal and one output terminal, wherein the input terminal of said limiting controller is connected to the output terminal of said first proportional-integral-derivative controller;
a second subtracter having two input terminals and one output terminal, wherein one of the input terminals of said second subtracter is connected to the other output terminal of said two output terminals of said sampling controller, and the other input terminal of said second subtracter is
connected to the output terminal of said limiting controller; a second proportional-integral-derivative controller having one input terminal and one output terminal, wherein the input terminal of said second proportional-integral- derivative controller is connected to the output terminal of said second subtracter; and
a pulse-width modulator having one input terminal and one output terminal, wherein the input terminal of said pulse-width modulator is connected to the output terminal of said second proportional-integral-derivative controller, and said pulse-width modulator outputs to said drive unit the pulse-width modulated signal generated by itself via its output terminal .
13. The direct current-direct current converter as claimed in claim 2 or 3, wherein said mode selecting unit further comprises:
a voltage comparator for comparing the relative
magnitude between the voltage detection signal of said first direct current power supply and the voltage detection signal of said second direct current power supply, and for
outputting the comparison result; and
a mode logic control circuit for selecting the operating mode of said direct current-direct current converter according to said direction control signal and the comparison result from said voltage comparator, and for outputting to said drive unit an operating mode signal indicating said selected operating mode.
14. The direct current-direct current converter as claimed in claim 2 or 3, wherein said drive unit is
implemented as a circuit.
15. The direct current-direct current converter as claimed in claim 1, wherein said main circuit further comprises a second capacitor and a third capacitor, with said second capacitor being in parallel connection with the first direct current power supply, and said third capacitor being in parallel connection with the second direct current power supply.
PCT/EP2010/061594 2009-08-21 2010-08-10 A direct current-direct current converter WO2011020737A1 (en)

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