WO2010098174A1

WO2010098174A1 - Power circuit

Info

Publication number: WO2010098174A1
Application number: PCT/JP2010/051352
Authority: WO
Inventors: 正史加瀬; 太朗中臺; 謙治加藤
Original assignee: 株式会社光波
Priority date: 2009-02-24
Filing date: 2010-02-01
Publication date: 2010-09-02
Also published as: JP2010200428A; JP5616028B2

Abstract

Provided is a power circuit capable of supplying an output voltage lower than or higher than an input voltage to a direct-current load utilizing a simple circuit configuration without any special circuitry being provided. The power circuit (10) is equipped with a power supply circuit which has a transformer (Tr), a rectifying diode (D1), a primary capacitor (C1) and a secondary capacitor (C2), and with a switching element (Q). An LED series circuit (40) is driven by a direct current from the primary capacitor (C1) when the switching element (Q) is on, and is driven by a direct current from the secondary capacitor (C2) when the switching element (Q) is off. The primary capacitor (C1) is charged by the transformer (Tr) when the switching element (Q) is off.

Description

Power circuit

The present invention relates to a power supply circuit, and more particularly to a power supply circuit capable of obtaining a stable desired output voltage.

Conventionally, there is an LED lighting device provided with a boost type power factor correction circuit (for example, see Patent Document 1). In the conventional LED lighting device described in Patent Document 1, a power supply voltage from an AC power supply is converted into a DC voltage, and then the DC voltage is boosted and supplied to an LED load.

JP 2004-327152 A

However, since the power factor correction circuit in the conventional LED lighting device described in Patent Document 1 is a step-up type, a DC voltage lower than the power supply voltage cannot be obtained. Therefore, when driving the LED load with a DC voltage lower than the power supply voltage, a circuit for stepping down the voltage to the drive voltage of the LED load is required after the boost type power factor correction circuit. As a result, the circuit configuration becomes complicated, and the number of components increases, resulting in an increase in manufacturing cost.

Accordingly, the present invention has been made to solve the above-described conventional problems, and its specific purpose is to supply an output voltage lower or higher than the input voltage to the DC load without providing a special circuit. An object of the present invention is to provide a power circuit that can be realized.

[1] In order to achieve the above object, according to the present invention, a switch circuit that is turned on and off based on the first and second switch signals, and electric power that supplies a direct current to a DC load by turning the switch circuit on and off A power supply circuit; and a control circuit that outputs the first and second switch signals to the switch circuit, wherein the power supply circuit is electrically connected based on a direct current from a rectifier circuit when the switch circuit is on. A storage circuit that stores energy and outputs a direct current based on the stored electrical energy; a first capacitor connected in series with the direct current load and charged by the direct current from the storage circuit; A second capacitor disposed in parallel with the DC load and charged by the DC current from the storage circuit, the DC load being connected to the switch. The power supply is driven by a direct current from the storage circuit and the first capacitor when the circuit is on, and is driven by a direct current from the second capacitor when the switch circuit is off. In the circuit.
[2] In the invention described in [1], the storage circuit charges the first capacitor when the switch circuit is off.
[3] In the invention described in [1] above, the first capacitor is connected between a connection point between the negative electrode terminal of the second capacitor and the negative electrode terminal of the DC load and the first capacitor. A reverse current prevention diode is connected to prevent a direct current from flowing from the first capacitor to the second capacitor.

The present invention can supply an output voltage lower or higher than the input voltage to the DC load with a simple circuit configuration without providing a special circuit.

1 is a circuit diagram schematically showing a configuration example of a power supply circuit according to a first embodiment of the present invention. FIG. 2 is a block diagram schematically showing a configuration example of a control IC applied to the power supply circuit shown in FIG. 1. It is a block diagram which shows the other structural example of control IC roughly. It is a circuit diagram which shows roughly the example of 1 structure of the power supply circuit which is 2nd Embodiment based on this invention.

10 power supply circuit 11 commercial AC power supply 20 rectifier circuit 21 diode bridge 22, C3 capacitor 30 PFC circuit 31 control IC
32 Inverting amplifier 33 Error amplifier 34 Multiplier 35 Comparator 36 Flip-flop 37 Driver 38 Zero

current detector

40, 42 LED series circuit 41 LED
C1 Primary capacitor C2 Secondary capacitor D1 Rectifier diodes D2 and D4 Backflow prevention diode D3 Charging diode Q Switching elements R1 to R15 Resistance Tr Transformer Tr1 First winding Tr2 Second winding

Hereinafter, preferred embodiments of the present invention will be specifically described with reference to the accompanying drawings.

[First Embodiment]
(Configuration of power supply circuit)
In FIG. 1, reference numeral 10 denotes a constant current power supply circuit (hereinafter referred to as a power supply circuit). The basic configuration of the power supply circuit 10 includes a rectifier circuit 20 and a power factor control circuit (PFC circuit) 30 that improves the power factor of the DC voltage converted by the rectifier circuit 20. The constant current load connected to the output terminal of the PFC circuit 30 is not particularly limited, but is a lighting device such as an organic EL or LED. For example, a plurality of light emitting diodes (LEDs) 41,. An LED series circuit 40 connected in series is illustrated.

(Configuration of rectifier circuit)
As shown in FIG. 1, the rectifier circuit 20 includes a diode bridge 21 formed of four diodes. The rectifier circuit 20 performs full-wave rectification on the AC voltage input from the commercial AC power supply 11 through the input terminal and converts the AC voltage into a DC voltage. This DC voltage is supplied to the PFC circuit 30 through the output terminal of the rectifier circuit 20.

(Configuration of PFC circuit)
A PFC circuit 30 shown in FIG. 1 is a circuit that generates a constant output voltage by stepping up or down an input voltage to a desired voltage. MOSFET) Q, primary capacitor C1, backflow prevention diode D2, secondary capacitor C2, and control IC 31. In the illustrated example, a power supply circuit is configured by the ripple current removing capacitor 22, the transformer Tr, the rectifier diode D1, the primary capacitor C1, the backflow prevention diode D2, and the secondary capacitor C2. The transformer Tr, the primary capacitor C1, and the secondary capacitor C2 constitute an accumulation circuit. The DC voltage whose power factor has been improved by the PFC circuit 30 is output to the LED series circuit 40 through the output terminal.

As shown in FIG. 1, the control IC 31 is composed of an integrated circuit that improves the power factor by aligning the input voltage from the rectifier circuit 20 and the waveform of the input current flowing through the switching element Q. This type of control IC 31 is not particularly limited. For example, it is possible to use a circuit made into an IC for suppressing harmonic current or improving power factor, such as FA5500 and FA5501 manufactured by Fuji Electric Co., Ltd. it can. According to the illustrated example, the control IC 31 includes a power supply voltage input VCC terminal, a ground connection GND terminal, a feedback signal input FB terminal, a switching drive OUT terminal, and a switching current detection IS terminal. A ZCD terminal for zero current detection and a MUL terminal for voltage input proportional to the full-wave rectified voltage are shown. The control IC 31 generates a control pulse based on input signals to the VCC terminal, FB terminal, MUL terminal, IS terminal, and ZCD terminal. The power factor is improved by changing the magnitude of the output current in accordance with the time during which the switching element Q that is on / off controlled by the control pulse is turned on.

As shown in FIG. 1, a capacitor C3 is connected between the VCC terminal and the GND terminal of the control IC 31. One end of the capacitor C3 is connected to the auxiliary power supply voltage VCC, and the other end of the capacitor C3 is connected to the ground. A positive terminal (+) of the rectifier circuit 20 is connected between one end of the capacitor C3 and the auxiliary power supply voltage VCC via a resistor R1. A connection point between the resistor R1 and the capacitor C3 is connected to the second winding Tr2 of the transformer Tr via a backflow preventing diode D4.

Between the positive terminal of the rectifier circuit 20 and the GND terminal of the control IC 31, as shown in FIG. 1, a voltage dividing resistor composed of resistors R2 and R3 is connected. The output of the voltage dividing resistor is connected to the MUL terminal of the control IC 31. A sine wave full-wave rectified voltage (voltage waveform proportional to the absolute value voltage of the commercial AC power supply 11) obtained by dividing the full-wave rectified voltage of the rectifier circuit 20 with resistors R2 and R3 is input to the MUL terminal. This prevents the generation of lowering and harmonic current.

In the power supply circuit 10, a single transformer Tr is interposed as shown in FIG. The transformer Tr is provided with a first winding Tr1 and a second winding Tr2. One end of the first winding Tr1 is connected to the positive terminal of the rectifier circuit 20. The other end of the first winding Tr1 is connected to one end (negative terminal) of the LED series circuit 40 through a series circuit including a rectifier diode D1, a primary capacitor C1, and a backflow prevention diode D2. A charging diode D3 is connected to one end of the first winding Tr1 and a connection point between the primary capacitor C1 and the cathode of the backflow prevention diode D2. When the switching element Q is in the OFF state, the primary capacitor C1 is charged by circulating current through the closed circuit of the rectifier diode D1, the primary capacitor C1, the charging diode D3, and the primary winding Tr1 of the transformer Tr.

As shown in FIG. 1, the reverse current prevention diode D2 prevents the charging current to the primary capacitor C1 from flowing backward. A secondary capacitor C2 is connected in parallel with the LED series circuit 40 between the anode of the backflow prevention diode D2 and the negative terminal of the rectifier circuit 20. The drain of the switching element Q is connected to the connection point of the rectifier diode D1 and the primary capacitor C1. The source of the switching element Q is connected to the ground via a current detection resistor R4. The connection point of the source of the switching element Q and the resistor R4 is connected to the IS terminal of the control IC 31 via the resistor R5, and detects the switching current of the switching element Q. The gate of the switching element Q is connected to the OUT terminal of the control IC 31 via the resistor R6.

As shown in FIG. 1, the second winding Tr2 of the transformer Tr is electrically insulated from the primary winding Tr1. One end of the second winding Tr2 is connected to the ground. The other end of the second winding Tr2 is connected to the ZCD terminal of the control IC 31 via a resistor R7, and the value of the current flowing through the transformer Tr is detected. When the switching element Q changes from the on state to the off state, a current flows through the secondary winding Tr2 by a voltage proportional to the induced voltage of the first winding Tr1 induced in the secondary winding Tr2. When it is detected that the current of the transformer Tr has returned to zero based on the voltage from the second winding Tr2, the switching element Q is turned on.

As shown in FIG. 1, a series circuit composed of resistors R8, R9, and R10 is connected to one end (positive terminal) of the secondary capacitor C2. An inverting input terminal of the inverting amplifier 32 is connected to a connection point between the resistor R9 and the resistor R10. The resistors R9 and R10 constitute a current detection circuit that detects a current flowing through the LED series circuit 40. The divided voltage value at the connection point between the resistor R9 and the resistor R10 is amplified with a predetermined amplification factor by the inverting amplifier 32, and is input to the FB terminal of the control IC 31 as a current detection value. Feedback control is performed in order to make the current of the LED series circuit 40 constant by the detected current value. Although not shown, one end of the resistor R10 opposite to the resistor R9 side is connected to an offset voltage for operating the inverting amplifier 32.

(Power circuit operation)
Next, the operation of the power supply circuit 10 will be described with reference to FIGS. The control IC 31 shown in FIG. 2 mainly includes an error amplifier 33, a multiplier (MUL) 34, a comparator 35, a flip-flop 36, a driver 37, and a zero current detector 38. Now, when the commercial AC power supply 11 is applied to the power supply circuit 10, the power supply voltage from the commercial AC power supply 11 is supplied to the rectifier circuit 20. After full-wave rectification by the rectifier circuit 20, the full-wave rectified direct current is supplied to the PFC circuit 30. A direct current is supplied to the control IC 31 to start the operation, and a gate voltage is applied to the switching element Q.

In FIG. 1, when the switching element Q is in the ON state, a switching current flows to the ground through the switching element Q. The current energy at that time is accumulated in the first winding Tr1 of the transformer Tr. Thereafter, when the switching element Q is turned off, the inflow of current to the first winding Tr1 is stopped, and the current energy accumulated in the first winding Tr1 is released through the rectifier diode D1, and is supplied to the primary capacitor C1. Accumulated. The primary capacitor C1 functions as a first output power supply when the switching element Q is in an on state. The current energy stored in the primary capacitor C1 is released, and a current flows in the closed circuit of the switching element Q, the secondary capacitor C2, and the primary capacitor C1 to supply a charging current to the secondary capacitor C2, and the switching element Q, LED A current flows in the closed circuit of the series circuit 40, the backflow prevention diode D2, and the primary capacitor C1.

On the other hand, the output of the voltage dividing resistor composed of the resistors R9 and R10 which are current detection circuits of the LED series circuit 40 is input to the inverting input terminal of the inverting amplifier 32 as shown in FIGS. The inverting amplifier 32 amplifies the phase-inverted voltage to a predetermined amplification factor. The amplified voltage is supplied to the inverting input terminal of the error amplifier 33 in the control IC 31 through the FB terminal of the control IC 31.

In the error amplifier 33, as shown in FIGS. 1 and 2, the voltage input to the FB terminal of the control IC 31 is compared with the reference voltage Vref, and a voltage having a level corresponding to the error voltage with respect to the reference voltage Vref is amplified by a predetermined amount. Amplify to rate. The amplified error voltage is output to the multiplier 34 in the control IC 31.

As shown in FIGS. 1 and 2, the multiplier 34 is supplied with the divided output voltage from the rectifier circuit 20 through the MUL terminal of the control IC 31, and multiplies the output voltage by the output voltage from the error amplifier 34. Voltage is generated. The voltage of the multiplier 34 is output to the inverting input terminal of the comparator 35 in the control IC 31 as a current target value of the switching current. The output voltage of the multiplier 34 has a waveform similar to the full-wave rectification waveform, and the amplitude is a voltage proportional to the current flowing through the LED series circuit 40 (the discharge amount of the primary capacitor C1).

In the comparator 35, as shown in FIGS. 1 and 2, the voltage converted by the current detection resistor R4 of the switching element Q is compared with the voltage from the multiplier 34, and the pulse width-modulated pulse is obtained. appear. The output of the comparator 35 is supplied to the reset terminal R of the flip-flop 36 in the control IC 31. The output of the comparator 35 is power amplified by a driver 37 in the control IC 31 and drives the gate of the switching element Q. The switching element Q controls the on-time of the switching element Q by the pulse signal modulated by the pulse width generated by the comparator 35 and also controls the current flowing through the first winding Tr1 of the transformer Tr. Thus, constant current control can be performed so that the reference voltage Vref of the error amplifier 33 and the divided voltage from the secondary capacitor C2 are equal.

When the voltage converted by the current detection resistor R4 of the switching element Q becomes larger than the output voltage of the multiplier 34, the output of the comparator 35 is inverted and the flip-flop 36 is reset. When the switching element Q is turned off, the charging diode D3 becomes conductive, and the current flowing through the transformer Tr flows into the primary capacitor C1 through the rectifier diode D1. This current flows in the closed circuit of the primary capacitor C1, the charging diode D3, and the primary winding Tr1 of the transformer Tr, and the primary capacitor C1 is charged. Since the current flowing through the primary winding Tr1 is directly supplied to the primary capacitor C1, a voltage obtained by adding the coil voltage of the primary winding Tr1 to the full-wave rectified voltage of the rectifier circuit 20 is supplied to the primary capacitor C1. Thus, an output voltage lower than the input voltage can be supplied to the LED series circuit 40. On the other hand, in the ON state of the switching element Q, the electrical energy is charged from the primary capacitor C1 to the secondary capacitor C2, and a current flows through the closed circuit of the LED series circuit 40 and the secondary capacitor C2. The secondary capacitor C2 functions as a second output power source when the switching element Q is in an off state.

The fact that the current flowing through the primary winding Tr1 of the transformer Tr has become zero is detected by the secondary winding Tr2 of the transformer Tr and the zero current detector 38. When the zero current detector 38 detects that the current flowing through the primary winding Tr1 has become zero, the flip-flop 36 is set and the switching element Q is turned on.

By repeating the above operation, the average value of the current flowing through the primary winding Tr1 of the transformer Tr becomes equal to the voltage waveform of the commercial AC power supply 11, and improvement of the power factor and suppression of harmonic current can be realized.

By setting the voltage input to the FB terminal to a predetermined value suitable for driving the LED series circuit 40 with respect to the reference voltage Vref of the error amplifier 33, the LED series having a higher voltage specification than the voltage of the commercial AC power supply 11 is set. The power supply circuit 10 suitable for driving the circuit 40 or driving the LED series circuit 40 having a lower voltage specification than the voltage of the commercial AC power supply 11 is obtained. In FIG. 2, when the voltage input to the FB terminal is set smaller than the reference voltage Vref of the error amplifier 33, the output voltage of the multiplier 34 increases, and the pulse width of the pulse signal generated from the comparator 35 increases. The on-time during which the switching element Q is on-controlled increases, and the amount of charge charged to the primary capacitor C1 increases. As a result, the power supply circuit 10 that drives the LED series circuit 40 having a higher voltage specification than the voltage of the commercial AC power supply 11 can be effectively used.

On the other hand, if the voltage input to the FB terminal is set to be larger than the reference voltage Vref of the error amplifier 33, the output voltage of the multiplier 34 is lowered and the pulse width of the pulse signal generated from the comparator 35 is reduced. The ON time during which the switching element Q is ON-controlled is shortened, and the amount of charge to the primary capacitor C1 is reduced. As a result, the power supply circuit 10 that drives the LED series circuit 40 having a lower voltage specification than the voltage of the commercial AC power supply 11 can be effectively used.

[Modification of control IC]
FIG. 3 schematically shows another configuration example of the control IC. In FIG. 3, the difference from the first embodiment is that the output voltage from the error amplifier 33 is supplied to the comparator 35 via the multiplier (MUL) 34 in the first embodiment. In this modification, the output voltage from the error amplifier 33 is directly supplied to the comparator 35. In addition, the same member name and code | symbol are attached | subjected to the member substantially the same as the said 1st Embodiment. Therefore, a detailed description of substantially the same members as those in the first embodiment is omitted.

As shown in FIG. 3, the control IC 31 in this modified example inputs the voltage converted by the resistors R9 and R10 to the inverting input terminal of the inverting amplifier 32, and applies the reference voltage Vref to the non-inverting input terminal of the error amplifier 33. input. The output of the error amplifier 33 is compared with the voltage converted by the current detection resistor 4 of the switching element Q by the comparator 35. The output of the comparator 35 is output via the flip-flop 36 and the driver 37, and drives the gate of the switching element Q.

When the voltage converted by the current detection resistor 4 of the switching element Q becomes larger than the output voltage of the error amplifier 33, the output of the comparator 35 is inverted to reset the flip-flop 36, and the switching element Q is turned off. To. When the zero current detector 38 detects that the current flowing through the primary winding Tr1 has become zero, the flip-flop 36 is set and the switching element Q is turned on. By repeating this operation, the current flowing through the LED series circuit 40 is kept constant, and the LED series circuit 40 having a voltage higher than the voltage of the commercial AC power supply 11 is driven or has a voltage lower than the voltage of the commercial AC power supply 11. A voltage suitable for driving the LED series circuit 40 is output.

In the first embodiment and the modification, the voltage converted by the resistors R9 and R10 is supplied to the inverting input terminal of the inverting amplifier 32 and the inverting input terminal of the error amplifier 33 through the FB terminal of the control IC 31. However, the present invention is not limited to this. In the present invention, for example, the voltage converted by the resistors R9 and R10 is input to the error amplifier 33 through the FB terminal of the control IC 31 without using the inverting amplifier 32 according to the polarity of the FB terminal of the control IC 31. Of course, the structure which does may be sufficient.

[Second Embodiment]
FIG. 4 schematically shows a configuration example of the power supply circuit according to the second embodiment. In the figure, the substantially same members as those in the first embodiment are given the same member names and symbols. Therefore, a detailed description of substantially the same members as those in the first embodiment is omitted.

The power supply circuit 10 according to the second embodiment is different from the first embodiment in that a constant voltage power supply circuit is used as a power supply for the LED 41. According to the illustrated example, a series circuit composed of resistors R11 and R12 is connected in parallel to a constant voltage load composed of an LED series circuit 42 connected to a resistor R15 between output terminals of the power supply circuit 10. A series circuit including resistors R13 and R14 is connected to a connection point between the resistors R11 and R12. The inverting input terminal of the inverting amplifier 32 is connected to the connection point of the resistors R13 and R14. The resistors R11 to R14 constitute a voltage detection circuit that detects a voltage applied to a constant voltage load. The divided voltage value at the connection point of the resistors R13 and R14 is input to the FB terminal of the control IC 31 through the inverting amplifier 32.

In the second embodiment, as in the first embodiment, the control IC 31 shown in FIG. 2 or 3 can be used effectively. By setting the voltage input to the FB terminal to a predetermined value suitable for driving the LED series circuit 40 with respect to the reference voltage Vref of the error amplifier 33, an output lower than the input voltage is provided without providing an expensive circuit. A voltage or a high output voltage can be supplied to the LED series circuit 40.

Even in the second embodiment, the voltage converted by the resistors R13 and R14 is input to the inverting input terminal of the inverting amplifier 32 and the inverting terminal of the error amplifier 33 through the FB terminal of the control IC 31. Although the configuration is illustrated, the present invention is not limited to this. For example, the voltage converted by the resistors R13 and R14 is not converted to the voltage of the control IC 31 without using the inverting amplifier 32 according to the polarity of the FB terminal of the control IC 31. The configuration may be such that the error amplifier 33 is input through the FB terminal.

As is clear from the above description, in each of the illustrated examples, when the switching element Q is on, electrical energy is accumulated based on the direct current from the rectifier circuit 20, and the direct current is output based on the accumulated electrical energy. Although the configuration in which the single transformer Tr is provided in the power supply circuit as the storage circuit to be performed is illustrated, for example, a configuration in which a single coil is provided in the power supply circuit may be used. In each of the illustrated examples, the critical mode control method is illustrated in which the switching element Q is controlled to be turned on when the current flowing through the transformer Tr becomes zero. However, the current flowing through the transformer Tr is prevented from becoming zero. The present invention can also be applied to a continuous current mode control system to be controlled, and the initial object of the present invention can be sufficiently achieved. Moreover, in each said example of illustration, although the power supply circuit of the illuminating device was illustrated, this invention is not limited to this. In the case of a constant current load, the present invention can be effectively used as a power circuit for driving a DC motor such as an air conditioner, a refrigerator, a ventilation fan or a pump, for example. In the case of a constant voltage load, For example, it can be used as a general-purpose DC voltage power source. Therefore, the present invention is not limited to the above embodiments and modifications, and various design changes can be made within the scope described in each claim.

Claims

A switch circuit that is turned on and off based on the first and second switch signals;
A power supply circuit for supplying a direct current to a direct current load by turning on and off the switch circuit;
A control circuit for outputting the first and second switch signals to the switch circuit;
The power supply circuit includes:
When the switch circuit is on, the storage circuit stores electrical energy based on the direct current from the rectifier circuit, and outputs direct current based on the stored electrical energy;
A first capacitor connected in series with the DC load and charged by the DC current from the storage circuit;
A second capacitor disposed in parallel with the DC load and charged by the DC current from the storage circuit;
The DC load is driven by a direct current from the storage circuit and the first capacitor when the switch circuit is on, and is driven by a direct current from the second capacitor when the switch circuit is off. A power supply circuit characterized by that.
The power storage circuit according to claim 1, wherein the storage circuit charges the first capacitor when the switch circuit is off.
Preventing a direct current from flowing from the first capacitor to the second capacitor between the connection point between the negative electrode terminal of the second capacitor and the negative electrode terminal of the DC load and the first capacitor. 2. A power supply circuit according to claim 1, further comprising a backflow prevention diode connected thereto.