WO2009047174A1 - Circuit and method for double peak current control - Google Patents
Circuit and method for double peak current control Download PDFInfo
- Publication number
- WO2009047174A1 WO2009047174A1 PCT/EP2008/063097 EP2008063097W WO2009047174A1 WO 2009047174 A1 WO2009047174 A1 WO 2009047174A1 EP 2008063097 W EP2008063097 W EP 2008063097W WO 2009047174 A1 WO2009047174 A1 WO 2009047174A1
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- WO
- WIPO (PCT)
- Prior art keywords
- peak current
- circuit
- power switch
- switching circuit
- control circuit
- Prior art date
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Classifications
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
- H05B41/285—Arrangements for protecting lamps or circuits against abnormal operating conditions
- H05B41/2851—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
- H05B41/2856—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against internal abnormal circuit conditions
Definitions
- the present invention relates to a circuit and method for control the peak current passing through the switch tube during ignition of a lamp.
- Ignition of a lamp requires a sufficiently high voltage.
- the driving frequency of the switch tube shifts towards the resonance frequency, a high voltage will be generated across the resonant capacitor.
- the resonance voltage and the resonance current will not be limited, resulting in unsafe influence on the power switch tube and the output of the ballast.
- the existing solution to this problem is merely measuring the current passing through the lower switch tube in the half-bridge circuit.
- the current choke is saturated to a certain extent, however, such method of detecting the single peak current value cannot effectively and timely limit the current in the oscillating circuit. As a result, the ignition voltage becomes too high and the life of the lamp is affected.
- the present invention provides a method that can effectively control the ignition voltage. Even if the lamp current choke becomes saturated, the peak current in the switch tube can still be controlled, and the ignition voltage is kept stable.
- a double peak current control circuit is provided for controlling the peak current flowing through the power switch tubes S 1 and S2 of the oscillating circuit in the ballast.
- Said double peak current control circuit comprises: an integrated control circuit for driving power switch tubes Sl and S2; a RC oscillating network for controlling the driving frequency, said RC oscillating network being connected to the input terminal of the integrated control circuit; a first divider circuit connected in series between the power switch tube S2 and the ground, for detecting the peak current flowing through the power switch tube S2; and a first switching circuit, by triggering to turn on said first switching circuit, the resistive value in the RC oscillating network is regulated, and the triggering turning on signal of said first switching circuit being provided by the first divider circuit.
- the double peak current control circuit further comprises a second divider circuit and a second switching circuit.
- the second divider circuit is connected in series to the power switch tube S 1 through the power part circuit in the ballast so as to detect the peak current flowing through the power switch tube Sl.
- the second switching circuit is connected in parallel to the first switching circuit, and the resistive value in the RC oscillating network can also be regulated by triggering to turn on said second switching circuit, and the triggering turning on signal of said second switching circuit is provided by the second divider circuit.
- the power switch tubes S 1 and S2 are directly or indirectly driven by the two outputs of the integrated control circuit.
- the triggering turning on signals of the first and second switching circuits can respectively be used to accelerate the generation of the negative edge of the output of the integrated control circuit, thereby indirectly turning off the power switch tubes Sl and S2.
- the first switching circuit and the second switching circuit are respectively triggered to be turned on to immediately turn off power switch tubes S 1 and S2.
- the second switching circuit In a half cycle, if the peak current flowing through the power switch tube S 1 is more than enough, the second switching circuit will be triggered to be turned on to increase the charging current and discharging current of capacitor C 1 in the RC oscillating network. In another half cycle, if the peak current flowing through the power switch tube S2 is more than enough, the first switching circuit will be triggered to be turned on to increase the charging current and discharging current of capacitor Cl; thus the output frequency of the integrated control circuit is increased to limit the peak current flowing through the power switch tubes Sl and S2.
- the resistor in the RC oscillating network can be integrated into the integrated control circuit.
- first switching circuit and the second switching circuit can be implemented as signal switch tubes, small signal bipolar junction transistors or small signal metallic oxide semiconductor field effect transistor, and any switching circuits that can be integrated into an integrated circuit.
- a method for double peak current control for controlling the peak current flowing through the power switch tubes S 1 and S2 of the oscillating circuit in the ballast.
- Said method comprises the following steps: driving the power switch tubes Sl and S2 through the integrated control circuit; the RC oscillating network connected to the input terminal of the integrated control circuit controlling the driving frequency; the first divider circuit connected in series between the power switch tube S2 and the ground detecting the peak current flowing through the power switch tube S2; and the first divider circuit providing triggering turning on signal to the first switching circuit, and regulating the resistive value in the RC oscillating network by triggering to turn on said first switching circuit, thereby controlling the peak current flowing through the power switch tube S2.
- Said method further comprises: a second divider circuit connected in series to the power switch tube Sl through the power part circuit in the ballast detecting the peak current flowing through the power switch tube S 1 ; a second switching circuit connecting in parallel to the first switching circuit, to which the second divider circuit provides triggering turning on signal, and the resistive value in the RC oscillating network can also be regulated by triggering to turn on the second switching circuit, thereby controlling the peak current flowing through the power switch tube S 1.
- the double peak current control circuit of the present invention is more effective than the single peak current control circuit, especially in real applications where the power part circuit might suffer from nonlinearities.
- Fig. 1 shows the circuit of the present invention for use in an electronic ballast.
- Fig. 1 shows the circuit of the present invention for realizing double peak current control.
- Fig. 1 shows two power switch tubes Sl and S2, which are directly or indirectly driven by the two outputs OUTl and OUT2 of the integrated control circuit Ul.
- the frequency driving the power switch tubes Sl and S2 are directly or indirectly driven by the two outputs OUTl and OUT2 of the integrated control circuit Ul.
- the effective resistive value between the input RT and the ground can be regulated by the signal switch tubes S3 and S4.
- the signal switch tubes S3 and S4 The signal switch tubes
- the power part circuit comprises a DC block capacitor, a resonant capacitor, a lamp load, and a current choke used to limit current Il and 12.
- the resistance of the divider voltage can be appropriately regulated to ensure that voltage Icp*R9*R8/(R7+R8) and voltage Icp*R6*R5/(R4+R5) are respectively equal to the turning on thresholds of the signal switch tubes S3 and S4.
- signal switch tube S3 will be triggered to be turned on to increase the charging current and discharging current for capacitor Cl which is the oscillating capacitor of the integrated control circuit Ul.
- the peak current of the current 12 is more than Icp
- signal switch tube S4 will be triggered to be turned on to increase the charging current and discharging current for capacitor C 1.
- the whole duty of the cycle will be shorter, which means the frequency of outputs OUTl and 0UT2 will be increased.
- the increased frequency will limit the peak current of current Il and 12, thus the ignition voltage will be limited.
- the signal switch tubes S3 and S4 are kept off and the oscillating frequency will ramp down again, resulting in the increase in current Il and 12.
- it is a closed negative feedback control loop, which keeps ignition voltage within a defined range.
- the signal switch tubes S3 and S4 are triggered respectively to push the charging current and discharging current of the oscillator to be higher to increase driving frequency, so as to limit the increase of current Il and 12.
- the triggering turning on signals of signal switch tubes S3 and S4 can respectively be used to accelerate generation of the negative edge of the outputs OUTl and 0UT2 so as to indirectly turn off the power switch tubes Sl and S2.
- Such double peak current control circuit also works well.
- the signal switch tubes S3 and S4 are respectively triggered to immediately turn off the power switch tubes S 1 and S2 to limit the increase of current Il and 12.
- the signal switch tubes S3 and S4 can also be replaced by any kind of analog components, such as small signal BJT (small signal bipolar junction transistor), small signal MOSFET (small signal metallic oxide semiconductor field effect transistor), and so on.
- small signal BJT small signal bipolar junction transistor
- small signal MOSFET small signal metallic oxide semiconductor field effect transistor
- Such double peak current control circuit can also be used in full digital oscillators.
Abstract
The present invention relates to a circuit and method for double peak current control. In the present invention, the power switch tubes S1 and S2 are driven through the integrated control circuit (U1); the RC oscillating network connected to the input terminal of the integrated control circuit (U1) controls the driving frequency; the resistive value in the RC oscillating network is regulated by the first switching circuit (S4) and the second switching circuit (S3); the divider circuit for detecting the peak current flowing through the power switch tubes S1 and S2 provides triggering turning on signal to the first switching circuit (S4) and the second switching circuit (S3); and driving frequency is controlled by triggering to turn on the first switching circuit (S4) and the second switching circuit (S3), so as to limit the peak current flowing through the power switch tubes S1 and S2. The double peak current control circuit of the present invention is more effective than the single peak current control circuit, especially in real applications where the power part circuit might suffer from nonlinearities.
Description
Circuit and Method for Double Peak Current Control
Technical Field
The present invention relates to a circuit and method for control the peak current passing through the switch tube during ignition of a lamp.
Background Art
Ignition of a lamp requires a sufficiently high voltage. When the driving frequency of the switch tube shifts towards the resonance frequency, a high voltage will be generated across the resonant capacitor. Without a control circuit, the resonance voltage and the resonance current will not be limited, resulting in unsafe influence on the power switch tube and the output of the ballast.
The existing solution to this problem is merely measuring the current passing through the lower switch tube in the half-bridge circuit. When the current choke is saturated to a certain extent, however, such method of detecting the single peak current value cannot effectively and timely limit the current in the oscillating circuit. As a result, the ignition voltage becomes too high and the life of the lamp is affected.
Summary of the Invention
The present invention provides a method that can effectively control the ignition voltage. Even if the lamp current choke becomes saturated, the peak current in the switch tube can still be controlled, and the ignition voltage is kept stable.
According to one aspect of the invention, a double peak current control circuit is provided for controlling the peak current flowing through the power switch tubes S 1 and S2 of the oscillating circuit in the ballast. Said double peak current control circuit comprises: an integrated control circuit for driving power switch tubes Sl and S2; a RC oscillating network for controlling the driving frequency, said RC oscillating network being connected to the input terminal of the integrated control circuit; a first divider circuit connected in series between the power switch tube S2 and the ground, for detecting the peak current flowing through the power switch tube S2; and a first switching circuit, by triggering to turn on said first switching circuit, the resistive value in the RC oscillating network is regulated, and the triggering turning on signal of said first switching circuit being provided by the first divider circuit. The double peak current control circuit further comprises a second divider circuit and a second switching circuit. The second divider circuit is connected in series to the power switch tube S 1 through the power part circuit in the ballast so as to detect the peak current flowing through the power switch tube Sl. The second switching circuit is connected in parallel to the first switching circuit, and the resistive value in the RC oscillating network can also be regulated by triggering to turn on said second switching circuit, and the triggering turning on signal of said second switching circuit is provided by the second divider circuit.
In the double peak current control circuit of the present invention, the power switch tubes S 1 and S2 are directly or indirectly driven by the two outputs of the integrated control circuit. Wherein the triggering turning on signals of the first and second switching circuits can respectively be used to accelerate the generation of the negative edge of the output of the integrated control circuit, thereby indirectly turning off the power switch tubes Sl and S2. Alternatively, when the peak current flowing through the power switch tubes Sl and S2 reaches a certain high level, the first
switching circuit and the second switching circuit are respectively triggered to be turned on to immediately turn off power switch tubes S 1 and S2.
In a half cycle, if the peak current flowing through the power switch tube S 1 is more than enough, the second switching circuit will be triggered to be turned on to increase the charging current and discharging current of capacitor C 1 in the RC oscillating network. In another half cycle, if the peak current flowing through the power switch tube S2 is more than enough, the first switching circuit will be triggered to be turned on to increase the charging current and discharging current of capacitor Cl; thus the output frequency of the integrated control circuit is increased to limit the peak current flowing through the power switch tubes Sl and S2.
In an alternative, the resistor in the RC oscillating network can be integrated into the integrated control circuit.
In another alternative, the first switching circuit and the second switching circuit can be implemented as signal switch tubes, small signal bipolar junction transistors or small signal metallic oxide semiconductor field effect transistor, and any switching circuits that can be integrated into an integrated circuit.
According to another aspect of the present invention, a method for double peak current control is provided for controlling the peak current flowing through the power switch tubes S 1 and S2 of the oscillating circuit in the ballast. Said method comprises the following steps: driving the power switch tubes Sl and S2 through the integrated control circuit; the RC oscillating network connected to the input terminal of the integrated control circuit controlling the driving frequency; the first divider circuit connected in series between the power switch tube S2 and the ground
detecting the peak current flowing through the power switch tube S2; and the first divider circuit providing triggering turning on signal to the first switching circuit, and regulating the resistive value in the RC oscillating network by triggering to turn on said first switching circuit, thereby controlling the peak current flowing through the power switch tube S2. Said method further comprises: a second divider circuit connected in series to the power switch tube Sl through the power part circuit in the ballast detecting the peak current flowing through the power switch tube S 1 ; a second switching circuit connecting in parallel to the first switching circuit, to which the second divider circuit provides triggering turning on signal, and the resistive value in the RC oscillating network can also be regulated by triggering to turn on the second switching circuit, thereby controlling the peak current flowing through the power switch tube S 1.
The double peak current control circuit of the present invention is more effective than the single peak current control circuit, especially in real applications where the power part circuit might suffer from nonlinearities.
Description of the Drawing
Fig. 1 shows the circuit of the present invention for use in an electronic ballast.
Preferred Embodiments
In the present invention, effective control on the peak current flowing through both power switch tubes Sl and S2 in the oscillating circuit is realized by increasing the divider circuits for detecting the peak current flowing through the power switch tube S 1. Fig. 1 shows the circuit of the present invention for realizing double peak current control.
Fig. 1 shows two power switch tubes Sl and S2, which are directly or
indirectly driven by the two outputs OUTl and OUT2 of the integrated control circuit Ul. The frequency driving the power switch tubes Sl and
52 is determined through the value of the resistor connected to the input RT of the integrated control circuit Ul and the value of the capacitor connected to the input CT of the integrated control circuit Ul. The effective resistive value between the input RT and the ground can be regulated by the signal switch tubes S3 and S4. The signal switch tubes
53 and S4 can be triggered to be turned on by a part of the divider circuit for detecting the peak current of current Il and 12 flowing through the power switch tubes Sl and S2.
In every half cycle, current Il passes through the power part circuit and is detected by resistor R9; and in the other half cycle, current 12 passes through the power part circuit and is detected by resistor R6. The power part circuit comprises a DC block capacitor, a resonant capacitor, a lamp load, and a current choke used to limit current Il and 12.
It is assumed that the peak current is kept to be about Icp, an appropriate ignition voltage will be generated. When current Il and 12 are increased up to Icp with the shifting of the driving frequency of the switch tube, the voltages across resistors R9 and R6 are respectively Icp*R9 and Icp*R6. The series circuit of resistors R4 and R5 is connected in parallel to resistor R6, thus providing the triggering turning on signal to signal switch tube S4 through the voltage divided by resistor R5. The series circuit of resistors R7 and R8 is connected in parallel to resistor R6, thus providing the triggering turning on signal for signal switch tube S3 through the voltage divided by resistor R8. The resistance of the divider voltage can be appropriately regulated to ensure that voltage Icp*R9*R8/(R7+R8) and voltage Icp*R6*R5/(R4+R5) are respectively equal to the turning on thresholds of the signal switch tubes S3 and S4.
In this case, in a half cycle, if the peak current of current Il is more than Icp, signal switch tube S3 will be triggered to be turned on to increase the charging current and discharging current for capacitor Cl which is the oscillating capacitor of the integrated control circuit Ul. In the other half cycle, likewise, if the peak current of the current 12 is more than Icp, signal switch tube S4 will be triggered to be turned on to increase the charging current and discharging current for capacitor C 1. Therefore, the whole duty of the cycle will be shorter, which means the frequency of outputs OUTl and 0UT2 will be increased. The increased frequency will limit the peak current of current Il and 12, thus the ignition voltage will be limited. When the peak current of current Il and 12 is lower than Icp with increased frequency, the signal switch tubes S3 and S4 are kept off and the oscillating frequency will ramp down again, resulting in the increase in current Il and 12. Hence, it is a closed negative feedback control loop, which keeps ignition voltage within a defined range. As a conclusion, when the peak current of current Il and 12 reaches a certain high level, the signal switch tubes S3 and S4 are triggered respectively to push the charging current and discharging current of the oscillator to be higher to increase driving frequency, so as to limit the increase of current Il and 12.
If the integrated control circuit Ul integrates resistors Rl and R2 and the signal switch tubes S3 and S4, such double peak current control circuit can work well too.
The triggering turning on signals of signal switch tubes S3 and S4 can respectively be used to accelerate generation of the negative edge of the outputs OUTl and 0UT2 so as to indirectly turn off the power switch tubes Sl and S2. Such double peak current control circuit also works well. As a second conclusion, when the peak current of current Il and 12 reaches a certain high level, the signal switch tubes S3 and S4 are
respectively triggered to immediately turn off the power switch tubes S 1 and S2 to limit the increase of current Il and 12.
The signal switch tubes S3 and S4 can also be replaced by any kind of analog components, such as small signal BJT (small signal bipolar junction transistor), small signal MOSFET (small signal metallic oxide semiconductor field effect transistor), and so on.
Such double peak current control circuit can also be used in full digital oscillators.
Although the present invention is described in conjunction with the drawing as the above, it is not limited to such descriptions, but various modifications can be made thereto within the scope disclosed by the appended claims.
Claims
1. A double peak current control circuit for controlling the peak current flowing through the power switch tubes Sl and S2 of the oscillating circuit in the ballast, said double peak current control circuit comprises: an integrated control circuit (Ul) for driving power switch tubes Sl and S2; a RC oscillating network for controlling the driving frequency, said RC oscillating network being connected to the input terminal of the integrated control circuit (Ul); a first divider circuit (R4, R5, R6) connected in series between the power switch tube S2 and the ground, for detecting the peak current flowing through the power switch tube S2; and a first switching circuit (S4), by triggering to turn on said first switching circuit (S4), the resistive value in the RC oscillating network is regulated, and the triggering turning on signal of said first switching circuit (S4) being provided by the first divider circuit (R4, R5, R6), characterized in that said double peak current control circuit further comprises a second divider circuit (R7, R8, R9) and a second switching circuit (S3); the second divider circuit (R7, R8, R9) is connected in series to the power switch tube S 1 through the power part circuit in the ballast so as to detect the peak current flowing through the power switch tube Sl; the second switching circuit (S3) is connected in parallel to the first switching circuit (S4), and the resistive value in the RC oscillating network can also be regulated by triggering to turn on said second switching circuit (S3), and the triggering turning on signal of said second switching circuit (S3) is provided by the second divider circuit (R7, R8, R9).
2. The double peak current control circuit according to claim 1, characterized in that the power switch tubes Sl and S2 are directly or indirectly driven by the two outputs (OUTl, OUT2) of the integrated control circuit (Ul).
3. The double peak current control circuit according to claim 2, characterized in that the triggering turning on signals of the first switching circuit (S4) and the second switching circuit (S3) can respectively be used to accelerate the generation of the negative edge of the output (OUTl, 0UT2) of the integrated control circuit (Ul), thereby indirectly turning off the power switch tubes Sl and S2; or when the peak current flowing through the power switch tubes Sl and S2 reaches a certain high level, the first switching circuit (S4) and the second switching circuit (S3) are respectively triggered to be turned on to immediately turn off power switch tubes Sl and S2.
4. The double peak current control circuit according to claim 3, characterized in that in a half cycle, if the peak current flowing through the power switch tube Sl is more than enough, the second switching circuit (S3) will be triggered to be turned on to increase the charging current and discharging current of capacitor Cl in the RC oscillating network; in another half cycle, if the peak current flowing through the power switch tube S2 is more than enough, the first switching circuit (S4) will be triggered to be turned on to increase the charging current and discharging current of capacitor Cl; thus the output frequency of the integrated control circuit (Ul) is increased to limit the peak current flowing through the power switch tubes Sl and S2.
5. The double peak current control circuit according to one of claims 1-4, characterized in that the resistor in the RC oscillating network can be integrated into the integrated control circuit (Ul).
6. The double peak current control circuit according to one of claims 1-4, characterized in that the first switching circuit (S4) and the second switching circuit (S3) can be implemented as signal switch tubes, small signal bipolar junction transistors or small signal metallic oxide semiconductor field effect transistor, as well as any switching circuits that can be integrated into an integrated circuit.
7. The double peak current control circuit according to one of claims 1-4, characterized in that said double peak current control circuit can also be used in full digital oscillators.
8. A method for double peak current control, which is used to controll the peak current flowing through the power switch tubes S 1 and S2 of the oscillating circuit in the ballast, said method comprises the following steps: driving the power switch tubes Sl and S2 through the integrated control circuit (Ul); the RC oscillating network connected to the input terminal of the integrated control circuit (Ul) controlling the driving frequency; the first divider circuit (R4, R5, R6) connected in series between the power switch tube S2 and the ground detecting the peak current flowing through the power switch tube S2; and the first divider circuit (R4, R5, R6) providing triggering turning on signal to the first switching circuit (S4), and regulating the resistive value in the RC oscillating network through triggering to turn on said first switching circuit (S4), thereby controlling the peak current flowing through the power switch tube S2, characterized in that said method further comprises: a second divider circuit (R7, R8, R9) connected in series to the power switch tube Sl through the power part circuit in the ballast detecting the peak current flowing through the power switch tube Sl; a second switching circuit
(S3) connecting in parallel to the first switching circuit (S4), to which the second divider circuit (R7, R8, R9) provides triggering turning on signal, and the resistive value in the RC oscillating network can also be regulated by triggering to turn on the second switching circuit (S3), thereby controlling the peak current flowing through the power switch tube S 1.
9. The method for double peak current control according to claim 8, characterized in that the power switch tubes Sl and S2 are directly or indirectly driven by the two outputs (OUTl, OUT2) of the integrated control circuit (Ul).
10. The method for double peak current control according to claim 9, characterized in that the triggering turning on signals of the first switching circuit (S4) and the second switching circuit (S3) can respectively be used to accelerate the generation of the negative edge of the output (OUTl, OUT2) of the integrated control circuit (Ul), thereby indirectly turning off the power switch tubes Sl and S2; or when the peak current flowing through the power switch tubes Sl and S2 reaches a certain high level, the first switching circuit (S4) and the second switching circuit (S3) are respectively triggered to be turned on to immediately turn off power switch tubes Sl and S2.
11. The method for double peak current control according to claim 10, characterized in that in a half cycle, if the peak current flowing through the power switch tube Sl is more than enough, the second switching circuit (S3) will be triggered to be turned on to increase the charging current and discharging current of capacitor Cl in the RC oscillating network; in another half cycle, if the peak current flowing through the power switch tube S2 is more than enough, the first switching circuit (S4) will be triggered to be turned on to increase the charging current and discharging current of capacitor Cl; thus the output frequency of the integrated control circuit (Ul) is increased to limit the peak current flowing through the power switch tubes Sl and S2.
12. The method for double peak current control according to one of claims 8-11, characterized in that the resistor in the RC oscillating network can be integrated into the integrated control circuit (Ul).
13. The method for double peak current control according to one of claims 8-11, characterized in that the first switching circuit (S4) and the second switching circuit (S3) can be implemented as signal switch tubes, small signal bipolar junction transistors or small signal metallic oxide semiconductor field effect transistor, as well as any switching circuits that can be integrated into an integrated circuit.
14. The method for double peak current control according to one of claims 8-11, characterized in that said method for double peak current control can also be used in full digital oscillators.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN200710162238.4 | 2007-10-08 | ||
| CNA2007101622384A CN101409971A (en) | 2007-10-08 | 2007-10-08 | Dual peak current controlled circuit and method |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| WO2009047174A1 true WO2009047174A1 (en) | 2009-04-16 |
Family
ID=40225163
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| PCT/EP2008/063097 WO2009047174A1 (en) | 2007-10-08 | 2008-09-30 | Circuit and method for double peak current control |
Country Status (2)
| Country | Link |
|---|---|
| CN (1) | CN101409971A (en) |
| WO (1) | WO2009047174A1 (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE102011084274A1 (en) * | 2011-10-11 | 2013-04-11 | Bag Engineering Gmbh | Method and device for monitoring current peaks in an electronic ballast |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101954893A (en) * | 2010-10-14 | 2011-01-26 | 上海中科深江电动车辆有限公司 | Soft-start device of electromobile |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO1983002537A1 (en) * | 1982-01-15 | 1983-07-21 | Vossough, Eshan | Electronic high frequency controlled device for operating gas discharge lamps |
| US6008593A (en) * | 1997-02-12 | 1999-12-28 | International Rectifier Corporation | Closed-loop/dimming ballast controller integrated circuits |
| WO2002078405A2 (en) * | 2001-03-27 | 2002-10-03 | Koninklijke Philips Electronics N.V. | Panic protection from fault conditions in power converters |
| WO2003098790A1 (en) * | 2002-05-15 | 2003-11-27 | Philips Intellectual Property & Standards Gmbh | Circuit arrangement for a resonant converter and method of operating said converter |
| WO2003103117A2 (en) * | 2002-05-31 | 2003-12-11 | Parra Jorge M Sr | Self-oscillating constant-current gas discharge device lamp driver and method |
| US20070096662A1 (en) * | 2005-11-03 | 2007-05-03 | International Rectifier Corporation | Ballast control circuit |
| DE102006061357A1 (en) * | 2006-12-22 | 2008-06-26 | Infineon Technologies Austria Ag | Method for controlling a fluorescent lamp |
-
2007
- 2007-10-08 CN CNA2007101622384A patent/CN101409971A/en active Pending
-
2008
- 2008-09-30 WO PCT/EP2008/063097 patent/WO2009047174A1/en active Application Filing
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO1983002537A1 (en) * | 1982-01-15 | 1983-07-21 | Vossough, Eshan | Electronic high frequency controlled device for operating gas discharge lamps |
| US6008593A (en) * | 1997-02-12 | 1999-12-28 | International Rectifier Corporation | Closed-loop/dimming ballast controller integrated circuits |
| WO2002078405A2 (en) * | 2001-03-27 | 2002-10-03 | Koninklijke Philips Electronics N.V. | Panic protection from fault conditions in power converters |
| WO2003098790A1 (en) * | 2002-05-15 | 2003-11-27 | Philips Intellectual Property & Standards Gmbh | Circuit arrangement for a resonant converter and method of operating said converter |
| WO2003103117A2 (en) * | 2002-05-31 | 2003-12-11 | Parra Jorge M Sr | Self-oscillating constant-current gas discharge device lamp driver and method |
| US20070096662A1 (en) * | 2005-11-03 | 2007-05-03 | International Rectifier Corporation | Ballast control circuit |
| DE102006061357A1 (en) * | 2006-12-22 | 2008-06-26 | Infineon Technologies Austria Ag | Method for controlling a fluorescent lamp |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE102011084274A1 (en) * | 2011-10-11 | 2013-04-11 | Bag Engineering Gmbh | Method and device for monitoring current peaks in an electronic ballast |
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| Publication number | Publication date |
|---|---|
| CN101409971A (en) | 2009-04-15 |
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