WO2004109928A1 - Frequency synthesizer and radio communication device - Google Patents

Frequency synthesizer and radio communication device Download PDF

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Publication number
WO2004109928A1
WO2004109928A1 PCT/JP2004/008005 JP2004008005W WO2004109928A1 WO 2004109928 A1 WO2004109928 A1 WO 2004109928A1 JP 2004008005 W JP2004008005 W JP 2004008005W WO 2004109928 A1 WO2004109928 A1 WO 2004109928A1
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WIPO (PCT)
Prior art keywords
frequency
ratio
switching
noise peak
voltage
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PCT/JP2004/008005
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French (fr)
Japanese (ja)
Inventor
Fumio Ito
Kenji Takahashi
Katsuyuki Sato
Takashi Enoki
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Matsushita Electric Industrial Co., Ltd.
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Application filed by Matsushita Electric Industrial Co., Ltd. filed Critical Matsushita Electric Industrial Co., Ltd.
Publication of WO2004109928A1 publication Critical patent/WO2004109928A1/en

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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
    • H03L7/00—Automatic control of frequency or phase; Synchronisation
    • H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
    • H03L7/08—Details of the phase-locked loop
    • H03L7/085—Details of the phase-locked loop concerning mainly the frequency- or phase-detection arrangement including the filtering or amplification of its output signal
    • H03L7/093—Details of the phase-locked loop concerning mainly the frequency- or phase-detection arrangement including the filtering or amplification of its output signal using special filtering or amplification characteristics in the loop
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
    • H03L7/00—Automatic control of frequency or phase; Synchronisation
    • H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
    • H03L7/08—Details of the phase-locked loop
    • H03L7/10—Details of the phase-locked loop for assuring initial synchronisation or for broadening the capture range
    • H03L7/107—Details of the phase-locked loop for assuring initial synchronisation or for broadening the capture range using a variable transfer function for the loop, e.g. low pass filter having a variable bandwidth
    • H03L7/1075—Details of the phase-locked loop for assuring initial synchronisation or for broadening the capture range using a variable transfer function for the loop, e.g. low pass filter having a variable bandwidth by changing characteristics of the loop filter, e.g. changing the gain, changing the bandwidth
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
    • H03L7/00—Automatic control of frequency or phase; Synchronisation
    • H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
    • H03L7/16—Indirect frequency synthesis, i.e. generating a desired one of a number of predetermined frequencies using a frequency- or phase-locked loop
    • H03L7/18—Indirect frequency synthesis, i.e. generating a desired one of a number of predetermined frequencies using a frequency- or phase-locked loop using a frequency divider or counter in the loop

Definitions

  • the present effort is suitable for a frequency synthesizer, for example, to be applied to a wireless communication device corresponding to a plurality of wireless communication systems.
  • FIG. 1 is a block diagram showing the configuration of a conventional frequency synthesizer (see Japanese Patent Application Laid-Open No. 7-170181 (FIG. 1)).
  • the oscillation output f r is output from the voltage controlled oscillation circuit 1 1, PLL (Phase Locked Loop ) 1 2 phase comparison between the criteria signal f ref is performed, the voltage loop filter is proportional to the phase difference
  • the loop filter 13 has a cascade-connected lag-lead filter 13A and a low-pass filter 13B.
  • the loop filter 13 supplies the control voltage S1 that has passed only the lag-lead filter 13A to the input terminal P1 of the analog switch SW1. Further, the control voltage S 2 passed through both the lag-lead filter 13 A and the low-pass filter 13 B is applied to the input terminal P 2 of the analog switch SW 1 and the differential absolute ⁇ circuit 14.
  • the differential absolute value circuit 14 controls switching of the analog switch SW1 using the switching signal S3.
  • the analog switch SW1 switches the switch according to the switching signal S3 output from the differential absolute value circuit 14. Specifically, when the switching signal S 3 indicates that high-speed lockup is prioritized, the control voltage S l, that is, the input terminal P 1 is selected, and the switching signal S 3 sets a high CN ratio. Give priority Is selected, the control voltage S2, that is, the input terminal P2 is selected.
  • the control voltage selected by the analog switch SW 1 is supplied to the voltage-controlled oscillation circuit 11 via a voltage follower 15 for preventing the influence of a load change from affecting the voltage-controlled oscillation circuit 11. .
  • the conventional frequency synthesizer is to readiness to the phase difference between the oscillation output f r and the reference signal f ref of the voltage controlled oscillation circuit, and controls the oscillation conditions of the voltage controlled oscillation circuit, high-speed lock-up and high CN The ratio is compatible.
  • the required CN ratio Carrier to Noise Ratio
  • a frequency synthesizer corresponding to each system must be provided, which leads to an increase in the scale of the device.
  • the frequency synthesizer forms a signal that does not satisfy the required CN ratio, the reception sensitivity characteristics will deteriorate, making it impossible to make and receive calls in a weak electric field area, and the communication quality will deteriorate. Disclosure of the invention
  • An object of the present invention is to provide a small frequency synthesizer and a wireless communication device corresponding to each received signal when a different CN ratio is required for each received signal.
  • the above object is achieved by preparing a plurality of loop filters for realizing each CN ratio corresponding to a signal transmitted from a communication partner, and switching the loop filter according to the transmitted signal.
  • Figure 1 is a block diagram showing the configuration of a conventional frequency synthesizer
  • FIG. 2 is a block diagram showing a configuration of the frequency synthesizer according to Embodiment 1 of the present invention
  • Fig. 3 is a diagram showing the CN ratio vs. frequency characteristics of the output signal of the frequency synthesizer.
  • FIG. 4 is a block diagram showing a configuration of a frequency synthesizer according to Embodiment 2 of the present invention.
  • FIG. 5 is a block diagram showing a configuration of a frequency synthesizer according to Embodiment 3 of the present invention.
  • FIG. 2 is a block diagram showing a configuration of the frequency synthesizer according to Embodiment 1 of the present invention.
  • a mode angle analyzer 101 analyzes which communication method among a plurality of wireless communication methods is used, based on a signal transmitted from a communication partner.
  • the analysis method is to multiply the received signal by a predetermined spreading code
  • demodulation is used to identify the CDMA method and other methods.
  • the analysis result that is, information indicating the communication method used for communication is notified to the control unit 102.
  • the control unit 102 includes a first frequency divider 104, a second frequency divider 105, and a switching unit 107 according to the communication method during communication notified from the mode analysis unit 101. Control.
  • the mode analysis unit 101 and the control unit 102 function as control means.
  • the reference signal generator 103 generates a signal serving as a reference of a frequency at which the frequency synthesizer can oscillate, and outputs the generated reference signal to the first frequency divider 104.
  • the first frequency divider 104 changes the frequency division ratio based on the control of the control unit 102, and divides the frequency of the reference signal output from the reference signal generator 103 with the changed frequency division ratio. Go around.
  • the frequency-divided signal is output to the phase comparator 106.
  • the second frequency divider 105 changes the frequency division ratio based on the control of the control unit 102, and divides the frequency of the reference signal output from the voltage controlled oscillator 109 at the changed frequency division ratio. I do.
  • the frequency-divided signal is output to the phase comparator 106.
  • the phase comparator 106 compares the phase of the signal output from the first frequency divider 104 with the phase of the signal output from the second frequency divider 105, and calculates a voltage (control voltage) proportional to the phase difference. Voltage) to the switching unit 107.
  • the switching unit 107 supplies the voltage supplied from the phase comparator 106 to one of the loop filters 108-1 to 108-N based on the control of the control unit 102.
  • the noise peak frequencies ⁇ are set so as to correspond to the CN ratios required in a plurality of wireless communication systems, respectively.
  • the obtained voltage is smoothed (averaged), and a DC voltage obtained by smoothing is applied to the voltage-controlled oscillator 109.
  • the noise peak frequency ⁇ is a factor that affects the CN ratio because it determines the frequency at which noise peaks appear when averaging the voltage, and is determined by the capacitance of the capacitor that constitutes the loop filter.
  • the C ⁇ ratio of the averaged signal can be set as the CN ratio corresponding to the signal transmitted from the communication partner.
  • the voltage controlled oscillator 109 oscillates a signal having a frequency corresponding to the DC voltage given from any of the loop filters 108-1 to 108-N, and outputs a signal having a CN ratio corresponding to the wireless communication system under communication. .
  • FIG. 3 is a diagram showing a CN ratio versus frequency characteristic in an output signal of the frequency synthesizer.
  • the horizontal axis represents frequency
  • the vertical axis represents CN ratio.
  • the solid line indicates the wireless communication system A
  • the dotted line indicates the wireless communication system B
  • the dashed line indicates the wireless communication system C.
  • the frequency f A is used, CN ratio and CN A is required.
  • the radio communications system B the frequency I beta is used, CN ratio is required CN B
  • the radio communications system C the frequency f c is employed, CN ratio when CN C is required I do.
  • the figure below shows the CN ratio versus frequency characteristics of the loop filter corresponding to the CN ratio and frequency required in each wireless communication system, and the noise peak of the loop filter is adjusted to achieve the desired CN ratio.
  • Frequency ⁇ n is set. As shown in Fig. 3, it can be seen that it is necessary to switch each loop filter to satisfy all the frequencies and CN ratios required in each communication method.
  • the mode analysis unit 101 analyzes which wireless communication system is performing communication based on the signal transmitted from the communication partner, and notifies the control unit 102 of the analysis result.
  • the control unit 102 controls the first frequency divider 104, the second frequency divider 105, and the switching unit 107 in accordance with the wireless communication scheme currently being communicated. More specifically, the control unit 102 stores a communicable communication method, a frequency division ratio, and loop filter switching information in association with each other, and stores a frequency division ratio and a frequency corresponding to the communication method under communication.
  • the switching information is output as control information.
  • the reference signal output from the reference signal generator 103 is frequency-divided by the control information output from the control unit 102, that is, the frequency division ratio corresponding to the communication system under communication.
  • the signal output from the voltage controlled oscillator 109 is divided by the frequency division ratio according to the control information of the control unit 102. It is. The divided signals are output to the phase comparator 106.
  • the phase comparator 106 calculates the phase difference between the signals output from the first frequency divider 104 and the second frequency divider 105, and outputs a voltage (control voltage) corresponding to the phase difference. Is done.
  • the voltage corresponding to this phase difference is supplied to the voltage-controlled oscillator 109 via any one of the switching unit 107 and the loop filter 108-1-1 to 108-1N, and the voltage is adjusted so that the phase difference disappears. Controls the control oscillator 109.
  • the switching unit 107 based on the switching information notified from the control unit 102 (here, the switching information indicates the loop filter 108-1), the switching unit 107 supplies the switching unit 106 with the phase comparator 106. The applied voltage is supplied to the loop filter 108-8-1.
  • the noise peak frequency ⁇ n corresponding to the communication system currently in communication is set, and the voltage applied from the switching unit 107 is filtered (smoothed) and filtered.
  • the applied DC voltage is applied to the voltage controlled oscillator 109.
  • the voltage-controlled oscillator 109 oscillates a frequency corresponding to the voltage given from the loop filter 108-1, and forms a signal having a CN ratio and a frequency required by the communication system during communication. As a result, good communication quality can be ensured in each communication method.
  • a loop filter for realizing a CN ratio required in a plurality of wireless communication systems is prepared, and by switching to a loop filter according to a communication system in communication, a plurality of loop filters are provided. It is possible to realize a single frequency synthesizer corresponding to the communication system, to reduce the size of the device, and to avoid deterioration of the communication quality in each communication system.
  • FIG. 4 is a block diagram showing a configuration of a frequency synthesizer according to Embodiment 2 of the present invention. However, parts in FIG. 4 common to FIG. 2 are denoted by the same reference numerals as in FIG. 2, and detailed description thereof will be omitted.
  • FIG. 4 differs from FIG. 2 in that the mode analysis unit 101 is changed to a transmission rate analysis unit 301, and that the loop filter 108-8 This is the point where 1 08—N is changed to a loop filter 3 0 2—1 to 3 0 2—N.
  • the transmission rate analysis unit 301 analyzes the transmission rate of the signal transmitted from the communication partner based on the information included in the signal.
  • the transmission rate changes, for example, according to the bandwidth of the signal, and the CN ratio changes according to the bandwidth. Specifically, when the transmission rate is high, the bandwidth is wide and the CN ratio tends to decrease. Conversely, when the transmission rate is low, the bandwidth is narrow and the CN ratio tends to improve.
  • the specified communication system is notified to the control unit 102. Note that the transmission rate angle analyzer 301 and the controller 102 function as control means.
  • the noise peak frequency ⁇ n is set in each of the loop filters 302-1 to 300 -N so as to realize a CN ratio corresponding to a predetermined transmission rate. Is smoothed (averaged), and the DC voltage obtained by smoothing is applied to the voltage-controlled oscillator 109.
  • a plurality of loop filters for realizing a CN ratio corresponding to the transmission rate of a signal transmitted from a communication partner are prepared, and a loop filter corresponding to the transmission rate during communication is prepared.
  • FIG. 5 is a block diagram showing a configuration of a frequency synthesizer according to Embodiment 3 of the present invention.
  • FIG. 5 differs from FIG. 2 in that the mode analysis unit 101 is changed to the adaptive modulation analysis unit 401, and the loop filters 108-1-1 to 108-N are replaced with the loop filter 400-2. This is the point changed to 1-402-N.
  • Adaptive modulation analysis section 401 analyzes which modulation scheme the signal transmitted from the communication partner has been transmitted based on information included in the signal.
  • the CN ratio tends to decrease when the modulation level is high (for example, 16 Q AM), and the CN ratio when the modulation level is low (for example, QPSK). Tend to improve.
  • the specified communication system is notified to the control unit 102.
  • the adaptive modulation analysis unit 401 and the control unit 102 function as control means.
  • the noise peak frequency ⁇ n is set in each of the loop filters 402-1 to 402 -N so as to realize a CN ratio corresponding to a predetermined modulation method (modulation multi-level number).
  • the voltage supplied from the switching unit 107 is smoothed (averaged), and the smoothed DC voltage is supplied to the voltage controlled oscillator 109.
  • a plurality of loop filters for realizing the CN ratio corresponding to the modulation method of the signal transmitted from the communication partner are prepared, and the loop filter according to the modulation method during communication is prepared.
  • a frequency synthesizer includes: a first frequency divider for dividing a reference frequency at a desired frequency division ratio; an oscillator for oscillating a frequency according to a control voltage; and a frequency oscillating by the oscillator.
  • a second frequency dividing means for dividing the frequency by a desired frequency dividing ratio; and a phase comparing means for generating a control voltage corresponding to a phase difference of the frequency divided by the first frequency dividing means and the second frequency dividing means.
  • a plurality of loop filters each having a different noise peak frequency that determines a frequency at which a noise peak appears when filtering the control voltage generated by the phase comparing means.
  • a configuration is provided that includes: a switching unit that performs the switching; and a control unit that monitors a signal transmitted from the communication partner and controls the switching unit based on a monitoring result.
  • the oscillation peak frequency is determined by setting the noise peak frequency.
  • the stage can oscillate a signal having a frequency corresponding to the signal transmitted from the communication partner, and can set the signal to a desired CN ratio. As a result, even if a different CN ratio is required for each signal transmitted from the communication partner, a single frequency synthesizer corresponding to each signal can be realized, thereby avoiding deterioration of speech quality. The size of the device can be reduced.
  • the plurality of loop filters are configured to set a noise peak frequency according to a different wireless communication system
  • the control unit determines which one of the plurality of wireless communication systems is a wireless communication system. It is configured to detect whether or not the switching unit is used, and to control the switching unit based on the detection result.
  • a frequency synthesizer corresponding to a plurality of wireless communication systems is provided. Can be realized by one, and the size of the device can be reduced.
  • the plurality of loop filters are set to noise peak frequencies corresponding to different transmission rates, and the control unit detects a transmission rate of a signal transmitted from a communication partner.
  • a configuration is employed in which the switching means is controlled based on the detection result.
  • a frequency synthesizer corresponding to a plurality of transmission rates is provided. Can be realized by one, and the size of the device can be reduced.
  • the plurality of loop filters may set a noise peak frequency according to a different modulation scheme, and the control unit 1 may detect a modulation scheme of a signal transmitted from a communication partner.
  • a configuration for controlling the switching means based on the result is adopted.
  • a plurality of loop filters for realizing a CN ratio corresponding to the modulation scheme of the signal are switched according to the modulation scheme during communication, A single frequency synthesizer that supports a plurality of modulation schemes can be realized, and the scale of the device can be reduced.
  • a wireless communication apparatus includes a first frequency dividing means for dividing a reference frequency by a desired frequency dividing ratio, an oscillating means for oscillating a frequency according to a control voltage, and a frequency oscillated by the oscillating means.
  • a second frequency dividing means for dividing the frequency by a desired frequency dividing ratio; and a phase comparing means for generating a control voltage corresponding to a phase difference between the frequencies divided by the first frequency dividing means and the second frequency dividing means.
  • a plurality of loop filters each having a different noise peak frequency for determining a frequency at which a noise peak appears when filtering the control voltage generated by the phase comparing means; and switching between the loop filters.
  • a control means for monitoring a signal transmitted from a communication partner and controlling the switching means based on a monitoring result.
  • the noise peak frequency is an element that affects the CN ratio of the signal oscillated by the oscillating means. While oscillating a signal of the corresponding frequency, the signal can be set to a desired CN ratio. As a result, even if a different CN ratio is required for each signal transmitted from the communication partner, a single frequency synthesizer corresponding to each signal can be realized, thereby avoiding deterioration of speech quality. The size of the device can be reduced.
  • a loop filter for realizing each CN ratio corresponding to a signal transmitted from a communication partner is prepared, and the loop filter is switched according to the transmitted signal.
  • the present invention is suitable for use in, for example, a wireless communication device supporting a plurality of wireless communication systems.

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Abstract

Loop filters (108-1 to 108-N) respectively have noise peak frequencies ωn set so as to correspond to the CN ratio requested by a plurality of radio communication methods. A control section (102) switches to a loop filter corresponding to the radio communication method analyzed to be currently in communication by a mode analysis section (101). The loop filters are used to filter the control voltage in accordance with a phase difference between a reference signal output from a reference signal generator (103) and a signal output from a voltage control oscillator (109). The control voltage after subjected to the filtering controls the oscillation condition of the voltage control oscillator (109). Thus, when a different CN ratio is requested for each of the reception signals, it is possible to provide a small-size frequency synthesizer and a radio communication device corresponding to each of the reception signals.

Description

明 細 書 周波数シンセサイザ及び無線通信装置 技術分野  Description Frequency synthesizer and wireless communication device Technical field
本努明は、 周波数シンセサイザに関し、 例えば、 複数の無線通信方式に対応 する無線通信装置に適用するに好適である。 背景技術  The present effort is suitable for a frequency synthesizer, for example, to be applied to a wireless communication device corresponding to a plurality of wireless communication systems. Background art
図 1は、 従来の周波数シンセサイザの構成を示すプロック図である （特開平 7-170181号公報 （第 1図） 参照） 。 この図において、 発振出力 f rが 電圧制御発振回路 1 1から出力され、 P L L (Phase Locked Loop) 1 2で基 準信号 f r e f との位相比較が行われ、 位相差に比例する電圧がループフィルタFIG. 1 is a block diagram showing the configuration of a conventional frequency synthesizer (see Japanese Patent Application Laid-Open No. 7-170181 (FIG. 1)). In this figure, the oscillation output f r is output from the voltage controlled oscillation circuit 1 1, PLL (Phase Locked Loop ) 1 2 phase comparison between the criteria signal f ref is performed, the voltage loop filter is proportional to the phase difference
1 3に与えられる。 Given to 13
ループフィルタ 13は、 カスケ一ド接続されたラグリードフィルタ 13 Aと ローパスフィルタ 13 Bとを備えている。 ループフィルタ 13は、 ラグリード フィルタ 13 Aのみを通過したコントロール電圧 S 1をアナログスィツチ S W1の入力端子 P 1に与える。 また、 ラグリードフィルタ 13 A及びローパス フィルタ 13 Bの双方を通過したコントロール電圧 S 2をアナログスィツチ SW1の入力端子 P 2及び微分絶対 ^ίίί回路 14に与える。  The loop filter 13 has a cascade-connected lag-lead filter 13A and a low-pass filter 13B. The loop filter 13 supplies the control voltage S1 that has passed only the lag-lead filter 13A to the input terminal P1 of the analog switch SW1. Further, the control voltage S 2 passed through both the lag-lead filter 13 A and the low-pass filter 13 B is applied to the input terminal P 2 of the analog switch SW 1 and the differential absolute ίίί circuit 14.
微分絶対値回路 14は、 ループフィルタ 1 3から与えられたコント口ール電 圧 S 2が変化すると、切り替え信号 S 3を用いてアナログスィッチ SW1の切 り替え制御を行う。  When the control voltage S2 supplied from the loop filter 13 changes, the differential absolute value circuit 14 controls switching of the analog switch SW1 using the switching signal S3.
アナログスィツチ SW1は、微分絶対値回路 14から出力される切り替え信 号 S 3に応じてスィッチを切り替える。 具体的には、 切り替え信号 S 3が高速 ロックアップを優先させることを示す場合には、 コントロール電圧 S l、 すな わち、 入力端子 P 1を選択し、 切り替え信号 S 3が高 CN比を優先させること を示す場合には、コントロール電圧 S 2、すなわち、入力端子 P 2を選択する。 アナログスィッチ S W 1で選択されたコント口ール電圧は、負荷変動による 影響が電圧制御発振回路 1 1に及ぶのを防止するためのボルテージフォロワ 1 5を介して電圧制御発振回路 1 1に与えられる。 The analog switch SW1 switches the switch according to the switching signal S3 output from the differential absolute value circuit 14. Specifically, when the switching signal S 3 indicates that high-speed lockup is prioritized, the control voltage S l, that is, the input terminal P 1 is selected, and the switching signal S 3 sets a high CN ratio. Give priority Is selected, the control voltage S2, that is, the input terminal P2 is selected. The control voltage selected by the analog switch SW 1 is supplied to the voltage-controlled oscillation circuit 11 via a voltage follower 15 for preventing the influence of a load change from affecting the voltage-controlled oscillation circuit 11. .
このように、 従来の周波数シンセサイザは、 電圧制御発振回路の発振出力 f rと基準信号 f r e f との位相差に即応して、電圧制御発振回路の発振条件を制御 し、 高速ロックアップと高 C N比を両立させている。 Thus, the conventional frequency synthesizer is to readiness to the phase difference between the oscillation output f r and the reference signal f ref of the voltage controlled oscillation circuit, and controls the oscillation conditions of the voltage controlled oscillation circuit, high-speed lock-up and high CN The ratio is compatible.
ところで、 近年、 G S M (Global System for Mobile Communications) 方 式や P D C (Personal Digital Cellular) 方式、 さらには C D MA (Code Division Multiple Access)方式などの複数の無線通信方式に対応した通信装置 が検討され、 上述した周波数シンセサイザを適用することも考えられる。  By the way, in recent years, communication devices that support multiple wireless communication systems such as the GSM (Global System for Mobile Communications) system, the PDC (Personal Digital Cellular) system, and the CDMA (Code Division Multiple Access) system have been studied. It is also conceivable to apply the frequency synthesizer described above.
し力 しながら、 上述した従来の周波数シンセサイザでは、 複数の無線通信方 式に対応した通信装置に適用する場合、各無線通信方式で要求される E b/N。 However, in the above-mentioned conventional frequency synthesizer, when applied to a communication device corresponding to a plurality of wireless communication systems, E b / N required for each wireless communication system.
(ビットエネルギーとノイズの比） が異なることや、 通信方式によっては伝送 帯域幅（伝送量） が異なることなどから、要求される C N比（Carrier to Noise Ratio) も通信方式によって異なるため、 各通信方式に対応する周波数シンセ サイザをそれぞれ設けなければならず、 装置規模の増大を招いてしまう。  (Ratio between bit energy and noise) and transmission bandwidth (transmission amount) depending on the communication method, etc., the required CN ratio (Carrier to Noise Ratio) differs depending on the communication method. A frequency synthesizer corresponding to each system must be provided, which leads to an increase in the scale of the device.
また、 複数の無線通信方式のうち、 最も高い C N比が要求される通信方式に 合わせた周波数シンセサイザを設けることが考えられるが、 このような周波数 シンセサイザを実現するのは困難であり、 実現したとしても回路規模が増大し てしまう。  In addition, it is conceivable to provide a frequency synthesizer that matches the communication system that requires the highest CN ratio among multiple wireless communication systems.However, it is difficult to realize such a frequency synthesizer. However, the circuit scale also increases.
ここでは、 異なる C N比が要求される例として、 複数の無線通信方式に対応 する周波数シンセサイザについて説明したが、 受信信号ごとに異なる C N比が 要求される場合に上述した問題が生じると考えられる。  Here, a frequency synthesizer corresponding to a plurality of wireless communication systems has been described as an example in which different CN ratios are required. However, it is considered that the above-described problem occurs when a different CN ratio is required for each received signal.
なお、 周波数シンセサイザが要求される C N比を満たさない信号を形成した 場合には、 受信感度特性が劣化し、 弱電界エリアでは発着呼が行えなくなった り、 通話品質が劣化したりする。 発明の開示 If the frequency synthesizer forms a signal that does not satisfy the required CN ratio, the reception sensitivity characteristics will deteriorate, making it impossible to make and receive calls in a weak electric field area, and the communication quality will deteriorate. Disclosure of the invention
本発明の目的は、 受信信号ごとに異なる C N比が要求される場合、 各受信信 号に対応する小型の周波数シンセサイザ及び無線通信装置を提供することで あ  An object of the present invention is to provide a small frequency synthesizer and a wireless communication device corresponding to each received signal when a different CN ratio is required for each received signal.
上記目的は、 通信相手から送信された信号に対応する各 C N比を実現するた めのループフィルタを複数用意し、 送信された信号に応じてループフィルタを 切り替えることにより達成される。 図面の簡単な説明  The above object is achieved by preparing a plurality of loop filters for realizing each CN ratio corresponding to a signal transmitted from a communication partner, and switching the loop filter according to the transmitted signal. BRIEF DESCRIPTION OF THE FIGURES
図 1は、 従来の周波数シンセサイザの構成を示すプロック図、  Figure 1 is a block diagram showing the configuration of a conventional frequency synthesizer,
図 2は、 本発明の実施の形態 1に係る周波数シンセサイザの構成を示すプロ ック図、  FIG. 2 is a block diagram showing a configuration of the frequency synthesizer according to Embodiment 1 of the present invention,
図 3は、周波数シンセサイザの出力信号における C N比対周波数特性を示す 図、  Fig. 3 is a diagram showing the CN ratio vs. frequency characteristics of the output signal of the frequency synthesizer.
図 4は、本発明の実施の形態 2に係る周波数シンセサイザの構成を示すプロ ック図、 及び、  FIG. 4 is a block diagram showing a configuration of a frequency synthesizer according to Embodiment 2 of the present invention, and
図 5は、本発明の実施の形態 3に係る周波数シンセサイザの構成を示すプロ ック図である。 発明を実施するための最良の形態  FIG. 5 is a block diagram showing a configuration of a frequency synthesizer according to Embodiment 3 of the present invention. BEST MODE FOR CARRYING OUT THE INVENTION
以下、 本発明の実施の形態について図面を用いて説明する。  Hereinafter, embodiments of the present invention will be described with reference to the drawings.
(実施の形態 1 )  (Embodiment 1)
図 2は、本 明の実施の形態 1に係る周波数シンセサイザの構成を示すプロ ック図である。 この図において、 モード角军析部 1 0 1は、 通信相手から送信さ れた信号に基づいて、 複数の無線通信方式のうち、 いずれの通信方式が用いら れているかを解析する。 解析の方法は、 受信した信号に所定の拡散符号を乗算 し、 復調することにより、 C DMA方式とそれ以外の方式であることを特定す ることなどが考えられる。 解析結果、 すなわち、 通信に用いられている通信方 式を示す情報は制御部 1 0 2に通知される。 FIG. 2 is a block diagram showing a configuration of the frequency synthesizer according to Embodiment 1 of the present invention. In this figure, a mode angle analyzer 101 analyzes which communication method among a plurality of wireless communication methods is used, based on a signal transmitted from a communication partner. The analysis method is to multiply the received signal by a predetermined spreading code However, it is conceivable that demodulation is used to identify the CDMA method and other methods. The analysis result, that is, information indicating the communication method used for communication is notified to the control unit 102.
制御部 1 0 2は、 モード解析部 1 0 1から通知された通信中の通信方式に応 じて、 第 1分周器 1 0 4、 第 2分周器 1 0 5及び切替部 1 0 7を制御する。 な お、 モード解析部 1 0 1及び制御部 1 0 2は制御手段として機能する。  The control unit 102 includes a first frequency divider 104, a second frequency divider 105, and a switching unit 107 according to the communication method during communication notified from the mode analysis unit 101. Control. The mode analysis unit 101 and the control unit 102 function as control means.
基準信号発生器 1 0 3は、 周波数シンセサイザが発振可能な周波数の基準と なる信号を発生し、 発生した基準信号を第 1分周器 1 0 4に出力する。  The reference signal generator 103 generates a signal serving as a reference of a frequency at which the frequency synthesizer can oscillate, and outputs the generated reference signal to the first frequency divider 104.
第 1分周器 1 0 4は、 制御部 1 0 2の制御に基づいて分周比を変更し、 変更 した分周比で基準信号発生器 1 0 3から出力された基準信号の周波数を分周 する。 分周された信号は、 位相比較器 1 0 6に出力される。  The first frequency divider 104 changes the frequency division ratio based on the control of the control unit 102, and divides the frequency of the reference signal output from the reference signal generator 103 with the changed frequency division ratio. Go around. The frequency-divided signal is output to the phase comparator 106.
第 2分周器 1 0 5は、 制御部 1 0 2の制御に基づいて分周比を変更し、 変更 した分周比で電圧制御発振器 1 0 9から出力された基準信号の周波数を分周 する。 分周された信号は、 位相比較器 1 0 6に出力される。  The second frequency divider 105 changes the frequency division ratio based on the control of the control unit 102, and divides the frequency of the reference signal output from the voltage controlled oscillator 109 at the changed frequency division ratio. I do. The frequency-divided signal is output to the phase comparator 106.
位相比較器 1 0 6は、 第 1分周器 1 0 4から出力された信号と第 2分周器 1 0 5から出力された信号との位相比較を行い、 位相差に比例する電圧 （制御電 圧） を切替部 1 0 7に与える。  The phase comparator 106 compares the phase of the signal output from the first frequency divider 104 with the phase of the signal output from the second frequency divider 105, and calculates a voltage (control voltage) proportional to the phase difference. Voltage) to the switching unit 107.
切替部 1 0 7は、 位相比較器 1 0 6から与えられた電圧を、 制御部 1 0 2の 制御に基づいてループフィルタ 1 0 8— 1〜1 0 8— Nのいずれかに与える。 ループフィルタ 1 0 8— 1〜 1 0 8— Nは、複数の無線通信方式で要求され る C N比にそれぞれ対応するように雑音ピーク周波数 ω ηが設定されており、 切替部 1 0 7から与えられた電圧を平滑 （平均化） し、 平滑して得られた直流 電圧を電圧制御発振器 1 0 9に与える。 雑音ピーク周波数 ω ηは、 電圧を平均 化する際に雑音のピークが現れる周波数を決定するため、 C N比に影響を与え る要素であり、ループフィルタを構成するコンデンサの容量などによって決定 される。 すなわち、 雑音ピーク周波数 ω ηの設定により、 平均化された信号の C Ν比を通信相手から送信された信号に対応する C N比とすることができる。 電圧制御発振器 109は、 ループフィルタ 108— 1〜108—Nのいずれ かから与えられた直流電圧に応じた周波数の信号を発振し、 通信中の無線通信 方式に対応する C N比の信号を出力する。 The switching unit 107 supplies the voltage supplied from the phase comparator 106 to one of the loop filters 108-1 to 108-N based on the control of the control unit 102. In the loop filters 108-1-1 to 108-N, the noise peak frequencies ωη are set so as to correspond to the CN ratios required in a plurality of wireless communication systems, respectively. The obtained voltage is smoothed (averaged), and a DC voltage obtained by smoothing is applied to the voltage-controlled oscillator 109. The noise peak frequency ωη is a factor that affects the CN ratio because it determines the frequency at which noise peaks appear when averaging the voltage, and is determined by the capacitance of the capacitor that constitutes the loop filter. That is, by setting the noise peak frequency ωη, the CΝ ratio of the averaged signal can be set as the CN ratio corresponding to the signal transmitted from the communication partner. The voltage controlled oscillator 109 oscillates a signal having a frequency corresponding to the DC voltage given from any of the loop filters 108-1 to 108-N, and outputs a signal having a CN ratio corresponding to the wireless communication system under communication. .
図 3は、 周波数シンセサイザの出力信号における CN比対周波数特性を示す 図である。 この図において、 横軸を周波数、 縦軸を CN比として示している。 また、 実線が無線通信方式 Aを、 点線が無線通信方式 Bを、 .一点鎖線が無線通 信方式 Cをそれぞれ示しているものとする。 ここで、 例えば、 無線通信方式 A では、 周波数 f Aが用いられ、 CN比は CNAが要求されるとする。 同様に、 無 線通信方式 Bでは、周波数 ίΒが用いられ、 CN比は CNBが要求され、 無線通 信方式 Cでは、周波数 f cが用いられ、 CN比は CNCが要求されるとする。 各 無線通信方式において要求される C N比及ぴ周波数に対応するループフィル タでそれぞれの CN比対周波数特性を示すと図のようになり、所望の CN比と なるように、 ループフィルタの雑音ピーク周波数 ω nが設定されている。 図 3 が示すように、各通信方式において要求される周波数と CN比を全て満たすに は、 それぞれのループフィルタを切り替える必要があることが分かる。 FIG. 3 is a diagram showing a CN ratio versus frequency characteristic in an output signal of the frequency synthesizer. In this figure, the horizontal axis represents frequency, and the vertical axis represents CN ratio. It is assumed that the solid line indicates the wireless communication system A, the dotted line indicates the wireless communication system B, and the dashed line indicates the wireless communication system C. Here, for example, in the wireless communication system A, the frequency f A is used, CN ratio and CN A is required. Similarly, in the radio communications system B, the frequency I beta is used, CN ratio is required CN B, the radio communications system C, the frequency f c is employed, CN ratio when CN C is required I do. The figure below shows the CN ratio versus frequency characteristics of the loop filter corresponding to the CN ratio and frequency required in each wireless communication system, and the noise peak of the loop filter is adjusted to achieve the desired CN ratio. Frequency ω n is set. As shown in Fig. 3, it can be seen that it is necessary to switch each loop filter to satisfy all the frequencies and CN ratios required in each communication method.
次に、 上記構成を有する周波数シンセサイザの動作について説明する。 モー ド解析部 101では、 通信相手から送信された信号に基づいて、 いずれの無線 通信方式で通信が行われているかの解析が行われ、 解析結果が制御部 102に 通知される。 制御部 102では、 現在通信中の無線通信方式に応じた制御が第 1分周器 104、 第 2分周器 105及び切替部 107に対して行われる。 具体 的には、 制御部 102には通信可能な通信方式と分周比、 ループフィルタの切 替情報がそれぞれ対応付けられて記憶されており、 通信中の通信方式に対応す る分周比及び切替情報が制御情報として出力される。  Next, the operation of the frequency synthesizer having the above configuration will be described. The mode analysis unit 101 analyzes which wireless communication system is performing communication based on the signal transmitted from the communication partner, and notifies the control unit 102 of the analysis result. The control unit 102 controls the first frequency divider 104, the second frequency divider 105, and the switching unit 107 in accordance with the wireless communication scheme currently being communicated. More specifically, the control unit 102 stores a communicable communication method, a frequency division ratio, and loop filter switching information in association with each other, and stores a frequency division ratio and a frequency corresponding to the communication method under communication. The switching information is output as control information.
第 1分周器 104では、 基準信号発生器 103から出力された基準信号が制 御部 102から出力された制御情報、 すなわち、 通信中の通信方式に対応する 分周比で分周される。 同様に、 第 2分周器 105では、 電圧制御発振器 109 から出力された信号が制御部 102の制御情報にしたがった分周比で分周さ れる。 分周された各信号は位相比較器 1 0 6に出力される。 In the first frequency divider 104, the reference signal output from the reference signal generator 103 is frequency-divided by the control information output from the control unit 102, that is, the frequency division ratio corresponding to the communication system under communication. Similarly, in the second frequency divider 105, the signal output from the voltage controlled oscillator 109 is divided by the frequency division ratio according to the control information of the control unit 102. It is. The divided signals are output to the phase comparator 106.
位相比較器 1 0 6では、 第 1分周器 1 0 4及び第 2分周器 1 0 5から出力さ れた信号の位相差が求められ、位相差に応じた電圧（制御電圧）が出力される。 この位相差に応じた電圧は切替部 1 0 7、 ループフィルタ 1 0 8— 1〜 1 0 8 一 Nのいずれかをそれぞれ介して電圧制御発振器 1 0 9に与えられ、位相差が なくなるよう電圧制御発振器 1 0 9を制御する。  The phase comparator 106 calculates the phase difference between the signals output from the first frequency divider 104 and the second frequency divider 105, and outputs a voltage (control voltage) corresponding to the phase difference. Is done. The voltage corresponding to this phase difference is supplied to the voltage-controlled oscillator 109 via any one of the switching unit 107 and the loop filter 108-1-1 to 108-1N, and the voltage is adjusted so that the phase difference disappears. Controls the control oscillator 109.
.切替部 1 0 7では、 制御部 1 0 2から通知された切替情報 （ここでは、 切替 情報がループフィルタ 1 0 8— 1を示すとする） に基づいて、 位相比較器 1 0 6から与えられた電圧がループフィルタ 1 0 8— 1に与えられる。  In the switching unit 107, based on the switching information notified from the control unit 102 (here, the switching information indicates the loop filter 108-1), the switching unit 107 supplies the switching unit 106 with the phase comparator 106. The applied voltage is supplied to the loop filter 108-8-1.
ループフィルタ 1 0 8 _ 1は、現在通信中の通信方式に対応する雑音ピーク 周波数 ω nが設定されており、切替部 1 0 7から与えられた電圧をフィルタリ ング （平滑） し、 フィルタリ グされた直流電圧を電圧制御発振器 1 0 9に与 る。  In the loop filter 1 08 _ 1, the noise peak frequency ω n corresponding to the communication system currently in communication is set, and the voltage applied from the switching unit 107 is filtered (smoothed) and filtered. The applied DC voltage is applied to the voltage controlled oscillator 109.
電圧制御発振器 1 0 9では、ループフィルタ 1 0 8— 1から与えられた電圧 に応じた周波数が発振され、 通信中の通信方式で要求される C N比及び周波数 の信号が形成される。 これにより、 各通信方式において良好な通話品質を確保 することができる。  The voltage-controlled oscillator 109 oscillates a frequency corresponding to the voltage given from the loop filter 108-1, and forms a signal having a CN ratio and a frequency required by the communication system during communication. As a result, good communication quality can be ensured in each communication method.
このように本実施の形態によれば、複数の無線通信方式で要求される C N比 を実現するためのループフィルタを用意し、 通信中の通信方式に応じたループ フィルタに切り替えることにより、複数の通信方式に対応した周波数シンセサ ィザを 1つで実現することができ、 装置規模の削減を図ることができると共に、 各通信方式において通話品質の劣化を回避することができる。  As described above, according to the present embodiment, a loop filter for realizing a CN ratio required in a plurality of wireless communication systems is prepared, and by switching to a loop filter according to a communication system in communication, a plurality of loop filters are provided. It is possible to realize a single frequency synthesizer corresponding to the communication system, to reduce the size of the device, and to avoid deterioration of the communication quality in each communication system.
(実施の形態 2 )  (Embodiment 2)
図 4は、 本発明の実施の形態 2に係る周波数シンセサイザの構成を示すブロ ック図である。 ただし、 図 4が図 2と共通する部分には、 図 2と同一の符号を 付し、 その詳しい説明は省略する。 図 4が図 2と異なる点は、 モード解析部 1 0 1を伝送レート解析部 3 0 1に変更した点と、ループフィルタ 1 0 8— 1〜 1 0 8— Nをループフィルタ 3 0 2— 1〜3 0 2— Nに変更した点である。 伝送レート解析部 3 0 1は、 通信相手から送信された信号がどれだけの伝送 レートで送信されたのかを、 前記信号に含まれる情報に基づいて解析する。 伝 送レートは、 例えば、 信号の帯域幅によって変化し、 また帯域幅に応じて C N 比も変化するものである。 具体的には、 伝送レートが高い場合には帯域幅が広 く、 C N比が低下する傾向にある。 逆に、 伝送レートが低い場合には帯域幅が 狭く、 C N比が向上する傾向にある。 特定された通信方式は制御部 1 0 2に通 知される。 なお、 伝送レート角罕析部 3 0 1及び制御部 1 0 2は、 制御手段とし て機能する。 FIG. 4 is a block diagram showing a configuration of a frequency synthesizer according to Embodiment 2 of the present invention. However, parts in FIG. 4 common to FIG. 2 are denoted by the same reference numerals as in FIG. 2, and detailed description thereof will be omitted. FIG. 4 differs from FIG. 2 in that the mode analysis unit 101 is changed to a transmission rate analysis unit 301, and that the loop filter 108-8 This is the point where 1 08—N is changed to a loop filter 3 0 2—1 to 3 0 2—N. The transmission rate analysis unit 301 analyzes the transmission rate of the signal transmitted from the communication partner based on the information included in the signal. The transmission rate changes, for example, according to the bandwidth of the signal, and the CN ratio changes according to the bandwidth. Specifically, when the transmission rate is high, the bandwidth is wide and the CN ratio tends to decrease. Conversely, when the transmission rate is low, the bandwidth is narrow and the CN ratio tends to improve. The specified communication system is notified to the control unit 102. Note that the transmission rate angle analyzer 301 and the controller 102 function as control means.
また、 ループフィルタ 3 0 2— 1〜3 0 2— Nは、 それぞれ所定の伝送レー トに対応する C N比を実現するように雑音ピーク周波数 ω nが設定されてお り、 切替部 1 0 7から与えられた電圧を平滑 （平均化） し、 平滑して得られた 直流電圧を電圧制御発振器 1 0 9に与える。  The noise peak frequency ω n is set in each of the loop filters 302-1 to 300 -N so as to realize a CN ratio corresponding to a predetermined transmission rate. Is smoothed (averaged), and the DC voltage obtained by smoothing is applied to the voltage-controlled oscillator 109.
このように本実施の形態によれば、 通信相手から送信された信号の伝送レー トに対応する C N比を実現するためのループフィルタを複数用意し、 通信中の 伝送レートに応じたループフィルタに切り替えることにより、複数の伝送レー トに対応した周波数シンセサイザを.1つで実現することができ、 装置規模の削 減を図ることができると共に、 各通信方式において通話品質の劣化を回避する ことができる。  As described above, according to the present embodiment, a plurality of loop filters for realizing a CN ratio corresponding to the transmission rate of a signal transmitted from a communication partner are prepared, and a loop filter corresponding to the transmission rate during communication is prepared. By switching, it is possible to realize a single frequency synthesizer that supports multiple transmission rates, reduce the size of the equipment, and avoid deterioration in speech quality in each communication method. it can.
(実施の形態 3 )  (Embodiment 3)
図 5は、 本発明の実施の形態 3に係る周波数シンセサイザの構成を示すプロ ック図である。 ただし、 図 5が図 2と共通する部分には、 図 2と同一の符号を 付し、 その詳しい説明は省略する。 図 5が図 2と異なる点は、 モード解析部 1 0 1を適応変調解析部 4 0 1に変更した点と、ループフィルタ 1 0 8— 1〜1 0 8— Nをループフィルタ 4 0 2— 1〜4 0 2—Nに変更した点である。 適応変調解析部 4 0 1は、 通信相手から送信された信号がいずれの変調方式 で送信されたのかを、 前記信号に含まれる情報に基づいて解析する。 変調方式 と C N比にも対応関係があり、 変調多値数が高い場合 （例えば、 1 6 Q AM) では C N比が低下する傾向にあり、変調多値数が低い場合（例えば、 Q P S K) では C N比が向上する傾向にある。 特定された通信方式は制御部 1 0 2に通知 される。 なお、 適応変調解析部 4 0 1及び制御部 1 0 2は、 制御手段として機 能する。 FIG. 5 is a block diagram showing a configuration of a frequency synthesizer according to Embodiment 3 of the present invention. However, parts in FIG. 5 common to FIG. 2 are denoted by the same reference numerals as in FIG. 2, and detailed description thereof will be omitted. FIG. 5 differs from FIG. 2 in that the mode analysis unit 101 is changed to the adaptive modulation analysis unit 401, and the loop filters 108-1-1 to 108-N are replaced with the loop filter 400-2. This is the point changed to 1-402-N. Adaptive modulation analysis section 401 analyzes which modulation scheme the signal transmitted from the communication partner has been transmitted based on information included in the signal. Modulation method And the CN ratio, the CN ratio tends to decrease when the modulation level is high (for example, 16 Q AM), and the CN ratio when the modulation level is low (for example, QPSK). Tend to improve. The specified communication system is notified to the control unit 102. The adaptive modulation analysis unit 401 and the control unit 102 function as control means.
また、 ループフィルタ 4 0 2— 1〜4 0 2— Nは、 それぞれ所定の変調方式 (変調多値数） に対応する C N比を実現するように雑音ピーク周波数 ω nが設 定されており、 切替部 1 0 7から与えられた電圧を平滑 （平均化） し、 平滑し て得られた直流電圧を電圧制御発振器 1 0 9に与える。  The noise peak frequency ω n is set in each of the loop filters 402-1 to 402 -N so as to realize a CN ratio corresponding to a predetermined modulation method (modulation multi-level number). The voltage supplied from the switching unit 107 is smoothed (averaged), and the smoothed DC voltage is supplied to the voltage controlled oscillator 109.
このように本実施の形態によれば、通信相手から送信された信号の変調方式 に対応する C N比を実現するためのループフィルタを複数用意し、通信中の変 調方式に応じたループフィルタに切り替えることにより、複数の変調方式に対 応した周波数シンセサイザを 1つで実現することができ、装置規模の削減を図 ることができると共に、各通信方式において通話品質の劣化を回避することが できる。  As described above, according to the present embodiment, a plurality of loop filters for realizing the CN ratio corresponding to the modulation method of the signal transmitted from the communication partner are prepared, and the loop filter according to the modulation method during communication is prepared. By switching, a single frequency synthesizer that supports multiple modulation schemes can be realized, reducing the size of the device and avoiding degradation in call quality in each communication scheme. .
本発明の周波数シンセサイザは、 基準周波数を所望の分周比で分周する第 1 分周手段と、 制御電圧に応じた周波数を発振する発振手段と、 前記発振手段に よつて発振された周波数を所望の分周比で分周する第 2分周手段と、 前記第 1 分周手段及び前記第 2分周手段により分周された周波数の位相差に応じた制 御電圧を生成する位相比較手段と、 前記位相比較手段によって生成された制御 電圧をフィルタリングする際に雑音のピークが現れる周波数を決定する雑音 ピーク周波数がそれぞれ異なるように設定された複数のループフィルタと、 前 記ループフィルタの切り替えを行う切替手段と、 通信相手から送信された信号 を監視し、 監視結果に基づいて前記切替手段を制御する制御手段と、 を具備す る構成を採る。  A frequency synthesizer according to the present invention includes: a first frequency divider for dividing a reference frequency at a desired frequency division ratio; an oscillator for oscillating a frequency according to a control voltage; and a frequency oscillating by the oscillator. A second frequency dividing means for dividing the frequency by a desired frequency dividing ratio; and a phase comparing means for generating a control voltage corresponding to a phase difference of the frequency divided by the first frequency dividing means and the second frequency dividing means. And a plurality of loop filters each having a different noise peak frequency that determines a frequency at which a noise peak appears when filtering the control voltage generated by the phase comparing means. A configuration is provided that includes: a switching unit that performs the switching; and a control unit that monitors a signal transmitted from the communication partner and controls the switching unit based on a monitoring result.
この構成によれば、杂集音ピーク周波数は発振手段で発振された信号の C N比 に影響を与える要素であることから、 雑音ピーク周波数の設定により、 発振手 段は、 通信相手から送信された信号に対応する周波数の信号を発振しつつ、 当 該信号を所望の C N比とすることができる。 これにより、 前記通信相手から送 信された信号ごとに異なる C N比が要求される場合でも、 各信号に対応する周 波数シンセサイザを 1つで実現することができ、 通話品質の劣化を回避すると 共に、 装置規模の削減を図ることができる。 According to this configuration, since the peak sound frequency is an element that affects the CN ratio of the signal oscillated by the oscillating means, the oscillation peak frequency is determined by setting the noise peak frequency. The stage can oscillate a signal having a frequency corresponding to the signal transmitted from the communication partner, and can set the signal to a desired CN ratio. As a result, even if a different CN ratio is required for each signal transmitted from the communication partner, a single frequency synthesizer corresponding to each signal can be realized, thereby avoiding deterioration of speech quality. The size of the device can be reduced.
本発明の周波数シンセサイザは、 上記構成において、 前記複数のループフィ ルタは、 異なる無線通信方式に応じた雑音ピーク周波数が設定され、 前記制御 手段は、複数の無線通信方式のうちいずれの無線通信方式が用いられているか を検出し、 検出結果に基づいて前記切替手段を制御する構成を採る。  In the frequency synthesizer of the present invention, in the above configuration, the plurality of loop filters are configured to set a noise peak frequency according to a different wireless communication system, and the control unit determines which one of the plurality of wireless communication systems is a wireless communication system. It is configured to detect whether or not the switching unit is used, and to control the switching unit based on the detection result.
この構成によれば、複数の無線通信方式で要求される C N比を実現するため の複数のループフィルタを、 通信中の通信方式に応じて切り替えることにより、 複数の無線通信方式に対応した周波数シンセサイザを 1つで実現することが でき、 装置規模の削減を図ることができる。  According to this configuration, by switching a plurality of loop filters for realizing a CN ratio required by a plurality of wireless communication systems according to a communication system being communicated, a frequency synthesizer corresponding to a plurality of wireless communication systems is provided. Can be realized by one, and the size of the device can be reduced.
本発明の周波数シンセサイザは、 上記構成において、 前記複数のループフィ ルタは、 異なる伝送レートに応じた雑音ピーク周波数が設定され、 前記制御手 段は、 通信相手から送信された信号の伝送レートを検出し、 検出結果に基づい て前記切替手段を制御する構成を採る。  In the frequency synthesizer of the present invention, in the above configuration, the plurality of loop filters are set to noise peak frequencies corresponding to different transmission rates, and the control unit detects a transmission rate of a signal transmitted from a communication partner. A configuration is employed in which the switching means is controlled based on the detection result.
この構成によれば、 前記信号の伝送レートに対応する C N比を実現するため の複数のループフィルタを、 通信中の伝送レートに応じて切り替えることによ り、複数の伝送レートに対応した周波数シンセサイザを 1つで実現することが でき、 装置規模の削減を図ることができる。  According to this configuration, by switching a plurality of loop filters for realizing a CN ratio corresponding to the transmission rate of the signal according to a transmission rate during communication, a frequency synthesizer corresponding to a plurality of transmission rates is provided. Can be realized by one, and the size of the device can be reduced.
本発明の周波数シンセサイザは、 上記構成において、 前記複数のループフィ ルタが、 異なる変調方式に応じた雑音ピーク周波数が設定され、 前記制御手段 1 通信相手から送信された信号の変調方式を検出し、 検出結果に基づいて前 記切替手段を制御する構成を採る。  In the frequency synthesizer of the present invention, in the above-described configuration, the plurality of loop filters may set a noise peak frequency according to a different modulation scheme, and the control unit 1 may detect a modulation scheme of a signal transmitted from a communication partner. A configuration for controlling the switching means based on the result is adopted.
この構成によれば、 前記信号の変調方式に対応する C N比を実現するための 複数のループフィルタを、 通信中の変調方式に応じて切り替えることにより、 複数の変調方式に対応した周波数シンセサイザを 1つで実現することができ、 装置規模の削減を図ることができる。 According to this configuration, a plurality of loop filters for realizing a CN ratio corresponding to the modulation scheme of the signal are switched according to the modulation scheme during communication, A single frequency synthesizer that supports a plurality of modulation schemes can be realized, and the scale of the device can be reduced.
本発明の無線通信装置は、 基準周波数を所望の分周比で分周する第 1分周手 段と、 制御電圧に応じた周波数を発振する発振手段と、 前記発振手段によって 発振された周波数を所望の分周比で分周する第 2分周手段と、 前記第 1分周手 段及び前記第 2分周手段により分周された周波数の位相差に応じた制御電圧 を生成する位相比較手段と、 前記位相比較手段によつて生成された制御電圧を フィルタリングする際に雑音のピークが現れる周波数を決定する雑音ピーク 周波数がそれぞれ異なるように設定された複数のループフィルタと、 前記ルー プフィルタの切り替えを行う切替手段と、 通信相手から送信された信号を監視 し、 監視結果に基づいて前記切替手段を制御する制御手段と、 を具備する構成 を採る。  A wireless communication apparatus according to the present invention includes a first frequency dividing means for dividing a reference frequency by a desired frequency dividing ratio, an oscillating means for oscillating a frequency according to a control voltage, and a frequency oscillated by the oscillating means. A second frequency dividing means for dividing the frequency by a desired frequency dividing ratio; and a phase comparing means for generating a control voltage corresponding to a phase difference between the frequencies divided by the first frequency dividing means and the second frequency dividing means. A plurality of loop filters each having a different noise peak frequency for determining a frequency at which a noise peak appears when filtering the control voltage generated by the phase comparing means; and switching between the loop filters. And a control means for monitoring a signal transmitted from a communication partner and controlling the switching means based on a monitoring result.
この構成によれば、雑音ピーク周波数は発振手段で発振された信号の C N比 に影響を与える要素であることから、 雑音ピーク周波数の設定により、 発振手 段は、 通信相手から送信された信号に対応する周波数の信号を発振しつつ、 当 該信号を所望の C N比とすることができる。 これにより、 前記通信相手から送 信された信号ごとに異なる C N比が要求される場合でも、 各信号に対応する周 波数シンセサイザを 1つで実現することができ、 通話品質の劣化を回避すると 共に、 装置規模の削減を図ることができる。  According to this configuration, the noise peak frequency is an element that affects the CN ratio of the signal oscillated by the oscillating means. While oscillating a signal of the corresponding frequency, the signal can be set to a desired CN ratio. As a result, even if a different CN ratio is required for each signal transmitted from the communication partner, a single frequency synthesizer corresponding to each signal can be realized, thereby avoiding deterioration of speech quality. The size of the device can be reduced.
以上説明したように、 本宪明によれば、 通信相手から送信された信号に対応 する各 C N比を実現するためのループフィルタをそれぞれ用意し、 送信された 信号に応じてループフィルタを切り替えることにより、複数の無線通信方式で 要求されるそれぞれの C N比に対応する周波数シンセサイザを 1つで実現す ることができ、 装置規模の削減を図ることができると共に、 各通信方式におい て通話品質の劣化を回避することができる。  As described above, according to the present invention, a loop filter for realizing each CN ratio corresponding to a signal transmitted from a communication partner is prepared, and the loop filter is switched according to the transmitted signal. As a result, it is possible to realize a single frequency synthesizer corresponding to each CN ratio required by multiple wireless communication systems, reduce the size of the equipment, and improve the communication quality in each communication system. Deterioration can be avoided.
本明細書は、 2 0 0 3年 6月 5日出願の特願 2 0 0 3— 1 6 1 2 7 0に基づ くものである。 この内容をここに含めておく。 産業上の利用可能性 This description is based on Japanese Patent Application No. 2003-161620 filed on June 5, 2003. This content is included here. Industrial applicability
本発明は、 例えば、 複数の無線通信方式に対応する無線通信装置に用いる 好適である。  The present invention is suitable for use in, for example, a wireless communication device supporting a plurality of wireless communication systems.

Claims

請求の範囲 The scope of the claims
1 . 基準周波数を所望の分周比で分周する第 1分周手段と、  1. first frequency dividing means for dividing the reference frequency by a desired frequency dividing ratio;
制御電圧に応じた周波数を発振する発振手段と、  Oscillating means for oscillating a frequency according to the control voltage;
前記発振手段によって発振された周波数を所望の分周比で分周する第 2分 周手段と、  Second frequency dividing means for dividing the frequency oscillated by the oscillating means at a desired frequency dividing ratio;
前記第 1分周手段及び前記第 2分周手段により分周された周波数の位相差 に応じた制御電圧を生成する位相比較手段と、  Phase comparing means for generating a control voltage corresponding to a phase difference between the frequencies divided by the first frequency dividing means and the second frequency dividing means,
前記位相比較手段によって生成された制御電圧をフィルタリングする際に 雑音のピークが現れる周波数を決定する雑音ピーク周波数がそれぞれ異なる ように設定された複数のループフィルタと、  When filtering the control voltage generated by the phase comparison means, a plurality of loop filters set so that noise peak frequencies that determine a frequency at which a noise peak appears are different from each other,
前記ループフィルタの切り替えを行う切替手段と、  Switching means for switching the loop filter,
通信相手から送信された信号を監視し、 監視結果に基づいて前記切替手段を 制御する制御手段と、  A control unit that monitors a signal transmitted from a communication partner and controls the switching unit based on a monitoring result;
を具備する周波数シンセサイザ。  A frequency synthesizer comprising:
2 . 前記複数のループフィルタは、 異なる無線通信方式に応じた雑音ピーク周 波数が設定され、 2. The plurality of loop filters have noise peak frequencies set according to different wireless communication systems,
前記制御手段は、複数の無線通信方式のうちいずれの無線通信方式が用いら れているかを検出し、 検出結果に基づいて前記切替手段を制御する請求の範囲 1に記載の周波数シンセサイザ。  2. The frequency synthesizer according to claim 1, wherein the control unit detects which wireless communication system among a plurality of wireless communication systems is used, and controls the switching unit based on a detection result.
3 . 前記複数のループフィルタは、 異なる伝送レートに応じた雑音ピーク周波 数が設定され、 3. The plurality of loop filters have noise peak frequencies set according to different transmission rates,
前記制御手段は、 通信相手から送信された信号の伝送レートを検出し、 検出 結果に基づいて前記切替手段を制御する請求の範囲 1に記載 周波数シンセ サイザ。  2. The frequency synthesizer according to claim 1, wherein the control unit detects a transmission rate of a signal transmitted from a communication partner, and controls the switching unit based on a detection result.
4 . 前記複数のループフィルタは、 異なる変調方式に応じた雑音ピーク周波数 が設定され、 4. The plurality of loop filters are set with noise peak frequencies according to different modulation schemes,
前記制御手段は、 通信相手から送信された信号の変調方式を検出し、 検出結 果に基づいて前記切替手段を制御する請求の範囲 1に記載の周波数シンセサ ィザ。 The control means detects a modulation method of a signal transmitted from a communication partner, and detects the result. 2. The frequency synthesizer according to claim 1, wherein said switching means is controlled based on a result.
5 . 基準周波数を所望の分周比で分周する第 1分周手段と、  5. first frequency dividing means for dividing the reference frequency by a desired frequency dividing ratio;
制御電圧に応じた周波数を発振する発振手段と、  Oscillating means for oscillating a frequency according to the control voltage;
前記発振手段によつて発振された周波数を所望の分周比で分周する第 2分 周手段と、  Second frequency dividing means for dividing the frequency oscillated by the oscillating means at a desired frequency dividing ratio;
前記第 1分周手段及び前記第 2分周手段により分周された周波数の位相差 に応じた制御電圧を生成する位相比較手段と、  Phase comparing means for generating a control voltage corresponding to a phase difference between the frequencies divided by the first frequency dividing means and the second frequency dividing means,
前記位相比較手段によって生成された制御電圧をフィルタリングする際に 雑音のピークが現れる周波数を決定する雑音ピーク周波数がそれぞれ異なる ように設定された複数のループフィルタと、  When filtering the control voltage generated by the phase comparison means, a plurality of loop filters set so that noise peak frequencies that determine a frequency at which a noise peak appears are different from each other,
前記ループフィルタの切り替えを行う切替手段と、  Switching means for switching the loop filter,
通信相手から送信された信号を監視し、 監視結果に基づいて前記切替手段を 制御する制御手段と、  A control unit that monitors a signal transmitted from a communication partner and controls the switching unit based on a monitoring result;
を具備する無線通信装置。  A wireless communication device comprising:
PCT/JP2004/008005 2003-06-05 2004-06-02 Frequency synthesizer and radio communication device WO2004109928A1 (en)

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JPH02141127A (en) * 1988-11-22 1990-05-30 Nec Corp Frequency control circuit
JPH02203622A (en) * 1989-02-01 1990-08-13 Nippon Telegr & Teleph Corp <Ntt> Multiple frequency phase locked loop circuit
WO1998047232A1 (en) * 1997-04-14 1998-10-22 Mitsubishi Denki Kabushiki Kaisha Pll frequency synthesizer and portable terminal employing the pll frequency synthesizer

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Publication number Priority date Publication date Assignee Title
JPH02141127A (en) * 1988-11-22 1990-05-30 Nec Corp Frequency control circuit
JPH02203622A (en) * 1989-02-01 1990-08-13 Nippon Telegr & Teleph Corp <Ntt> Multiple frequency phase locked loop circuit
WO1998047232A1 (en) * 1997-04-14 1998-10-22 Mitsubishi Denki Kabushiki Kaisha Pll frequency synthesizer and portable terminal employing the pll frequency synthesizer

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