WO2004032348A1 - Procede de reduction de la gamme dynamique dans un recepteur a large bande - Google Patents

Procede de reduction de la gamme dynamique dans un recepteur a large bande Download PDF

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Publication number
WO2004032348A1
WO2004032348A1 PCT/SG2002/000196 SG0200196W WO2004032348A1 WO 2004032348 A1 WO2004032348 A1 WO 2004032348A1 SG 0200196 W SG0200196 W SG 0200196W WO 2004032348 A1 WO2004032348 A1 WO 2004032348A1
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signal
interference
input
suppressed
digital
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PCT/SG2002/000196
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English (en)
Inventor
Kai Bin Huang
Quee Seng Quek
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Agency For Science, Technlogy And Research
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Priority to PCT/SG2002/000196 priority Critical patent/WO2004032348A1/fr
Priority to AU2002328010A priority patent/AU2002328010A1/en
Publication of WO2004032348A1 publication Critical patent/WO2004032348A1/fr

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
    • H04B1/109—Means associated with receiver for limiting or suppressing noise or interference by improving strong signal performance of the receiver when strong unwanted signals are present at the receiver input

Definitions

  • the present invention relates generally to wideband receivers, and, more specifically, to an adaptive technique for suppressing unwanted signals to reduce the dynamic-range requirement of a digitizer in a wideband receiver.
  • Analog-to-digital conversion remains as the main bottleneck in realising a wideband software radio receiver 100, such as the one illustrated in Fig. 1.
  • the receiver 100 receives signals via an antenna 110.
  • the receiver 100 consists of a wideband radiofrequency (RF) front-end 120, a digitizer or analog-to-digital conversion (ADC) device 130, and a channelization filter 140.
  • the wideband RF front-end 120 processes the received signal from antenna 110.
  • the output of the front-end 120 is digitized by the ADC 130.
  • the digitized output of ADC 130 is filed by the channelization filter 140 to provide a digital signal to a signal processing block (not shown).
  • An example of a relevant wideband receiver is the software-radio receiver described by Kenington, P.B., "Emerging technologies for software radio", Electronics & Communication Engineering Journal, April 1999, pp. 69-83.
  • the stringent dynamic-range requirements for the ADC 130 arises from the fact that the channelization function 140 of the wide-band receiver 100 is carried out digitally.
  • the ADC 130 is hence exposed to wideband radio signals, which may contain strong interfering signals. Such requirements cannot be fulfilled by existing systems.
  • the stringent requirements for ADC dynamic range inhibit the implementation of a wideband receiver.
  • the techniques for solving this problem are related to research areas such as dynamic range reduction in multi-carrier signal processing and interference cancellation.
  • 6,195,537 issued to Allpress et al on February 27, 200 and entitled "Method and apparatus for strong signal suppression in multi-carrier signals” relates to the digitisation of multi-carrier signals.
  • the described system comprises a strong signal suppressor that selectively suppresses stronger signals at certain carriers without affecting weaker signals.
  • the stronger signals have to go through a lengthy sequence of operations. Those signals are firstly coarsely digitized, then are detected by scanning, are scaled, undergo phase correction, subsequently are converted back to the analog domain where a reconstruction operation is carried out, and finally are recombined with the received signal in such a way that the stronger signals are attenuated.
  • U.S. Patent No. 5,826,181 issued to Reed on October 20, 1998 and entitled “Radio frequency noise reduction arrangement” describes a strong interfering signal in the received signal being reconstructed and tracked using a Phase Lock Loop (PLL). Interference suppression is achieved by combining the phase-inverted and scaled PLL output with the original received signal. Since the system of US Patent No. 5,826,181 involves a PLL, the system can only track a narrow-band signal modulated at a single carrier frequency, which is always the signal with the largest power. This scheme does not work if the desired signal is stronger than, or has the same power as, the blocking signals, because the desired signal is locked by the PLL and hence suppressed. Another disadvantage arises when multiple strong blocking signals are present.
  • the PLL may fail to track any of the blocking signals, or the suppression of one of the blocking signals may not be sufficient in reducing the dynamic range of the received signal.
  • U.S. Patent No. 5,694,395 issued to Myer et al on December 2, 1997 and entitled "Method and apparatus for processing multicarrier signals" describes the design of a multi-carrier signal processor. The received signals at different carriers are separated, modified using individual sets of processors, and combined with a delayed version of the received signal. The modification of the signals ensures that the combined signal has a reduced dynamic range.
  • a method for processing an input wideband signal containing a desired signal and a plurality of interfering signals is disclosed.
  • the input wideband signal is split into a first signal for a first signal path and a second signal for a second signal path.
  • the first and second signals are each an analog representation of the input wideband signal.
  • the second signal is digitized to provide a digitized second signal.
  • the desired signal is suppressed in the digitised second signal to provide a plurality of interference-dominant signals.
  • a phase shift is applied to the plurality of interference-dominant signals to provide a plurality of digital, phase-shifted signals through the second path that is substantially the same as a phase shift through the first path.
  • the plurality of digital, phase-shifted signals are converted into analog form to provide a plurality of analog regenerated signals.
  • the plurality of analog regenerated signals from the second signal path and the first signal from the first signal path are combined to provide an interference-suppressed, input wideband signal based on a difference of the plurality of analog regenerated signals and the first signal.
  • the interference-suppressed, wideband input signal may also be digitized to provide a digitised interference-suppressed input signal. Further, the desired signal may be extracted from the digitised interference-suppressed input signal.
  • the suppressing step may be implemented using a digital filter and the extracting step may be implemented using a channelization filter. Further, coefficients of the digital filter and the digital channelization filter may be changed to extract a different desired signal from the digitised interference-suppressed input signal.
  • the phase-shift applying step may be implemented using a phase-shifting circuit.
  • the digitised interference-suppressed input signal may be received and coefficients of the phase shifting circuit may be changed.
  • the digitised interference-suppressed input signal and the plurality of digital, phase- shifted signals may be combined to provide a digitised wideband input signal.
  • a delay through the first path may be made equal to a delay through the second signal path.
  • the amplitude of the second signal may also be controlled.
  • the second signal may further be scaled to provide a scaled second signal that swings over approximately the maximum input range of the digitizing means.
  • the amplitude of the interference-suppressed, input wideband signal may be controlled.
  • the interference- suppressed, input wideband signal may be scaled to provide a scaled interference- suppressed, input wideband signals that swings over approximately the maximum input range of the digitizing means.
  • the phase-shifting applying step may be implemented using an adaptive filter having coefficients that can be constantly updated using a filter-weight-updating algorithm so that variation of the characteristics of the input wideband signal is able to be tracked.
  • a method for processing an input wideband signal containing a desired signal and a plurality of interfering signals is disclosed.
  • An analog interference cancellation signal is subtracted from an input wideband signal to provide an interference-suppressed signal.
  • the interference- suppressed signal is digitized to provide a digitized signal.
  • the desired signal in the digitized signal is suppressed to provide a reference interference signal.
  • the reference interference signal is filtered based on filter parameters from the digitised signal to provide a digital interference cancellation signal.
  • the digital interference cancellation signal is converted into analog form to provide the analog interference cancellation signal.
  • the digital interference cancellation signal and the digitized signal after cancellation may be combined to provide a reconstructed digitized signal for input to the suppressing step. Further, a delay in a signal path for the interference-suppressed signal may be made equal to a delay through a signal path for the reference interference signal from the suppressing step.
  • the desired signal may be extracted from the digitised interference-suppressed signal.
  • the suppressing step may be implemented using a digital filter and the extracting step may be implemented using a digital channelization filter. Further, coefficients of the digital filter and the digital channelization filter may be changed for extracting a different desired signal from the digitized signal.
  • a digitised input wideband signal may be reconstructed from the digitised interference- suppressed signal and the interference cancellation signal.
  • the input wideband signal may be scaled to provide a scaled first signal that swings over approximately the maximum input range for the digitizing step.
  • the interference-suppressed signal may be scaled to provide a scaled interference-suppressed signal that swings over approximately the maximum input range for the digitizing step.
  • Fig. 1 is a block diagram of a wideband software radio receiver
  • Fig. 2 is a block diagram of a system for dynamic range reduction in accordance with an embodiment of the invention
  • Fig. 3 is a block diagram of another system for dynamic range reduction in accordance with an alternate embodiment of the invention.
  • Figs. 4(a), 4(b), and 4(c) are spectral graphs of the spectrum of signals at nodes A, B, and C, respectively, of Fig. 2;
  • Fig. 5 is a block diagram of a simulated system based on GSM standards
  • Fig. 6 is a spectral graph of the power spectrum (dB) of a received signal of a GSM receiver
  • Fig. 7 is a graph depicting a BER comparison (BER vs SNR(dB)) between a feedforward form in accordance with an embodiment of the invention and a conventional approach;
  • Fig. 8 is a graph depicting a BER comparision (BER vs Eb/N 0 (dB)) between the feedforward and feedback forms in accordance with embodiments of the invention.
  • Fig. 2 is a block diagram depicting a dynamic range reduction technique in accordance with an embodiment of the invention.
  • Fig. 3 depicts the technique implemented in a more compact architecture.
  • Has feedforward and feedback forms hereafter.
  • the concept and operation of the architectures are explained mainly based on the feedforward form 200 of Fig. 2, because of its relatively straightforward architecture.
  • a received wideband signal 200 is input at node A to a splitter 210, which provides separate outputs to a subtractor (+ input) 212 and an automatic-gain-control (AGC) circuit 222, labelled AGC2.
  • AGC automatic-gain-control
  • the spectrum of the received wideband signal 210 is depicted in Fig. 4(a).
  • the received signal 200 consists of multiple interfering signals at different carrier frequencies whose power is much larger than a desired signal.
  • the output of subtractor 212 is node C, which is input to another AGC circuit 214, labelled AGCl.
  • the output of AGCl 214 is input to ADCl 216.
  • the received signal 200 split by the splitter 210 is firstly scaled by the AGCl 214 and digitised by ADCl 216 with relatively low resolution.
  • the scaling function of AGCl 214 ensures that the input signal of ADCl 216 occupies the full input range of the ADCl 216.
  • the output of ADCl 216 is coupled to a channelization filter 218 and a control input of an adaptive filter 228.
  • the ADCl 216 can also optionally be coupled to a combiner 232.
  • the output of the adaptive filter 228 is coupled to a digital-to-analog conversion (DAC) circuit 230 and an optionally to another input of the combiner 232.
  • the output of DAC 230 is coupled to the subtractor (- input) 212.
  • the channelization filter 218 and the combiner 232 provide a digitized digital signal 220 and digitized wideband signal 234, respectively.
  • AGC2222 is coupled to ADC2224, which is in turn coupled to a bandstop filter 226.
  • a channel selection module controls the bandstop filter 226 and the channelization filter 218, with an input to each of filters 226 and 218.
  • the output of the bandstop filter 226 is node B, which is provided to the input of the adaptive filter 228.
  • the digitised signal produced by AGC2 222 and ADC2224 is passed through the band- stop filter 226, which attenuates the desired signal and allows the interfering or blocking signal outside of the desired signal band to pass without attenuation. However, the filtering operation introduces phase-shift to the blocking signal as well as to the small residual desired signal, whose existence is due to the non-ideality of the band-stop filter 226.
  • the spectrum of the filtered signal at node B is illustrated in Fig. 4(b), where diagonal-line hatching distinguishes the phase-shifted signals in Fig. 4(b) from the original signals in Fig. 4(a).
  • the phase-shifted blocking signals have to undergo phase-correction before the blocking signals can be subtracted from the received signal.
  • This task is carried out by the adaptive filter 228 indicated in Fig. 2.
  • the operation of the adaptive filter 228 is elaborated hereinafter.
  • the filter 228 is assumed to carry out the task effectively. Therefore, the output of the adaptive filter 228 consists mostly of the interfering signals that are almost in-phase with the original signals at node A of Fig. 2.
  • the output signal from the filter 226 is converted into an analogue signal by a DAC 230. Having synchronous blocking signals at both inputs, the subtractor 212 results in substantial suppression of the interfering signals.
  • AGC2222 serves the same purpose as AGCl 216. Since the strong interfering signals are suppressed, the dynamic range requirements of ADC2 224 are consequently mitigated.
  • the outputs of the ADCl 216 and the adaptive filter 228 can be summed to provide the digitised wideband signal 234 for multiple channel signal processing.
  • the feedback form 300 shown in Fig. 3 is able to suppress strong interfering signals by using only one set of ADC 316 and AGC 312 instead of two in the former.
  • the received wideband signal 210 is input to an AGC circuit 312.
  • the output of the AGC 312 is input to a subtractor (+ input) 314.
  • the other input of the subtractor (- input) is received from the output of a DAC circuit 326.
  • the output of the subtractor is input to an ADC module 316.
  • the received signal 310 is initially scaled by the AGC 312 and digitised by the ADC 314. This AGC 312 ensures that the input signal of the ADC 316 occupies the full input range of the ADC 316.
  • the output of the ADC 316 is input to a channelization filter 320, a combiner 318, and a control input of an adaptive filter 328.
  • the channelization filter produces a digitized desired signal 330.
  • the output of the combiner 318 is provided as input to the bandstop filter 322 and provides a digitized wideband signal 332 as output.
  • the digitised signal from ADC 316 is passed through the band-stop filter 322, which only allows the interfering signals to pass without attenuation.
  • the output of the bandstop filter 322 is provided to the adaptive filter 328.
  • the channel selection module 324 provides a control input to each of the channelization filter 320 and the bandstop filter 322.
  • the adaptive filter 328 provides an input to the DAC 326 and the combiner 318.
  • the adaptive filter 328 in the feedback form 300 phase corrects the interfering signals from the band-stop filter 322.
  • the phase-corrected interfering signals are then converted into an analogue signal by a DAC 326 before the phase-corrected interfering signals are subtracted from the incoming received signal 310 by the subtractor 314.
  • Such a feedback loop suppresses the strong interfering signals in the wideband-received signal 310 before the wideband signal is digitised.
  • the reconstructed interfering signals from the adaptive filter 328 are added back to the suppressed digitised signal by the combiner 318, before being passed through the bandstop filter 322.
  • this feedback form can generate either the digitised wideband signal 332, or the digitised desired signal 330 for further signal processing.
  • the architecture of the adaptive filter 228, 328 in Figs. 2 and 3, respectively, can be a finite-impulse-response (FIR) filter, an infinite-impulse-response (IIR) filter, or a Lattice filter.
  • Popular algorithms such as LMS and RLS (Simon Haykin, Adaptive Filter Theory, 3 rd edition, Prentice Hall, 1996, pp. 367-372 and 566-571) can be used to update the tap weights of the filter.
  • the digitised output of the subtractor is used as the error function (Simon Haykin, Adaptive Filter Theory, 3 rd edition, Prentice Hall, 1996, pp. 370) for tuning the tap weights of the adaptive filter.
  • the tap-weight updating equation of the adaptive filter 228 in the feedforward form 200 shown in Fig. 2 is given as:
  • W_(n + 1) W( ⁇ ) + ⁇ ⁇ u( ⁇ ) • e( ⁇ )
  • W_(ri) , u( ⁇ ) , e( ) denote the vector containing the tap weights of the adaptive filter, the input of the filter, and the output of ADCl 216 at the time instant n respectively; r(t) and a(t) denote the received signal and the DAC 230 output; Tl l ( ⁇ ) and ⁇ 2 (•) represent the combined operations of AGC2 222, ADC2 224, bandstop filter 226, and the combined operations of AGC2 222 and ADC2 224, respectively.
  • the tap- weight updating equation for the feedback form shown in Fig. 3 is similar except TI l (•) and II 2 (-) represent different sets of operations.
  • the channelization filter 218, 320 in both forms 200, 300 extracts the desired signal from the input for further signal processing. Both being digital, the channelization filter 200, 300 and the band-stop filter 226, 322 can be reconfigured by the channel selection block 236, 324 to receive different channels.
  • the feedback form 300 of the technique requires only one set of ADC and AGC. Hence, the latter has more power saving and is more suitable for mobile handset implementation.
  • the two forms also have comparable performance. However, - l i ⁇
  • the AGCs in both forms may be removed for simpler implementation, as long as the signal input to the ADC is not too small to cause significant degradation in the digitizer.
  • the whole system as shown in Figs. 2 and 3 may be replaced by a set of AGC and ADC without affecting the performance severely.
  • Simulations have been carried out to evaluate the performance of the techniques in accordance with the embodiments of the invention. Simulation models have been developed on SPW ® platform and are described hereinafter. Simulation results are also summarised.
  • Fig. 5 is a block diagram illustrating the simulated system 500, including a GSM transmitter 510 and a GSM receiver 550.
  • the GSM transmitter 510 includes a data source 512, GSM frame generator, a differential encoder 516, and a GMSK modulator 518, connected sequentially.
  • the output of the GSM transmitter 510 is provided to an AWGN channel 520.
  • the output of the channel 520 is summed using summer/combiner 530 and a signal from an interfering signal generator 540.
  • a simple AWGN channel has been used in the simulation.
  • the interfering signals are assumed to be GMSK modulated and have the same bandwidth as the desired signal.
  • the interfering signals are modulated at carrier frequencies offset from the desired channel.
  • the output of the combiner 530 is provided to the input of the GSM receiver 550.
  • the GSM receiver 550 includes a digitzation system for dynamic range reduction in accordance with that of Fig. 2 or Fig. 3, a downconverter 554, a phase derotation module 556, a viterbi equalizer 560, and a detector 562, connected sequentially.
  • the output of the phase derotation module 556 is coupled to a channel estimator, which in turn is coupled to another input of the viterbi equalizer 560.
  • the output of the GSM receiver 550 (from detector 562) is recovered data 570.
  • Simulations have been carried out to compare the performance of the proposed digitisation technique and a conventional approach.
  • the simulation model for the conventional approach is the same as that shown in Fig. 5 with the digitisation scheme block 552 replaced with a single ADC instead.
  • Fig. 6 shows the spectrum of the signal received by the GSM receiver 500, which consists of two interfering signals located at 800kHz (-29dB) from the desired signal (-98dB), whose power spectrum density is approximately 64dB stronger than the latter.
  • the BER performance of the feedforward form 200 and the conventional approach is compared in Fig. 7.
  • the feedforward form 200 feedforward
  • ADC conventional approach
  • the BER performance improves when ADC resolution is increased.
  • the improvement is marginal for ADCl resolution above 10 bits.
  • the three curves for the feedforward form 200 corresponding to ADCl of 10, 11, and 12 bits almost overlap with each other, and with the curve corresponding to conventional approach with ADC resolution of 13 bits.
  • Case 2 Fig. 8 shows a comparison between the BER performance of the feedforward and feedback forms 200, 300 in accordance with the embodiments of the invention.
  • ADCl and ADC2 are set at 10 bits and 8 bits, respectively.
  • the ADC is set at 10 bits.
  • the received signal consists of four interfering signals of -33dBm at 2, 2.6, 3, 3.4 MHz frequency offset from the desired signal at - 99dBm.
  • Both the feedforward and feedback forms 200, 300 have similar performance and result in the ADC dynamic range reduction of 3 bits as in Case 1.
  • the method for dynamic range reduction in a wideband receiver in accordance with the embodiments of the invention is a simple solution for the ADC dynamic-range problem in software radio.
  • the technique is able to differentiate a desired signal from interfering signals by employing a bandstop filter centred at the desired carrier frequency. With this added feature, suppression of the interfering signals can be achieved, without distorting the desired signal even when the desired signal has same power as the interfering signals.
  • the dynamic range reduction technique in accordance with the embodiments of the invention has the flexibility of different forms of implementation depending on the hardware requirements. Another important advantage of this technique is its capability of suppressing time- varying interfering signals.
  • embodiments of the invention can adaptively suppress unwanted signals so as to reduce the dynamic-range requirement of the digitizer in a wideband receiver.
  • embodiments of the invention are able to differentiate a desired signal from interfering signals by employing a bandstop filter centred at the desired carrier frequency.
  • an adaptive filter is used in the embodiments of the invention.
  • suppression of the interfering signals is carried out by subtracting the phase-shifted interfering signals from the received signal.
  • the technique is able to suppress time-varying interfering signals.
  • this technique has the flexibility of implementing different forms of architecture depending on the hardware requirements.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Noise Elimination (AREA)

Abstract

L'invention concerne des procédés et des appareils permettant de traiter un signal d'entrée à large bande renfermant un signal recherché et une pluralité de signaux brouilleurs. Dans un procédé, le signal d'entrée à large bande (200) est séparé (210) en un premier signal destiné à un premier parcours de signal et en un second signal destiné à un second parcours de signal. Le second signal est numérisé (224) de manière à fournir un second signal numérisé. Le signal recherché est supprimé (226) dans le second signal numérisé, de manière à fournir des signaux dominants le brouillage. Un déphasage est appliqué (228) aux signaux dominants le brouillage, de manière à fournir une pluralité de signaux numériques déphasés dans le second parcours, le déphasage étant sensiblement égal au déphasage dans le premier parcours. Les signaux numériques déphasés sont convertis (230) en une forme analogique de manière à fournir des signaux analogiques régénérés. La pluralité de signaux analogiques régénérés issus du second parcours de signal et le premier signal sont combinés (212), de manière à fournir un signal d'entrée à large bande exempt de brouillage, en fonction d'une différence entre la pluralité de signaux régénérés analogiques et le premier signal.
PCT/SG2002/000196 2002-08-28 2002-08-28 Procede de reduction de la gamme dynamique dans un recepteur a large bande WO2004032348A1 (fr)

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PCT/SG2002/000196 WO2004032348A1 (fr) 2002-08-28 2002-08-28 Procede de reduction de la gamme dynamique dans un recepteur a large bande
AU2002328010A AU2002328010A1 (en) 2002-08-28 2002-08-28 Method for dynamic range reduction in a wideband receiver

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Cited By (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1769583A1 (fr) * 2004-06-12 2007-04-04 L-3 Integrated Systems Company Systemes et procedes pour conversion analogique-numerique multicanaux
EP1895667A2 (fr) * 2006-08-30 2008-03-05 Broadcom Corporation Récepteur radio et son frontal
WO2010006646A1 (fr) * 2008-07-16 2010-01-21 Signal Processing Devices Sweden Ab Dispositif et procédé de réduction de signal de blocage
US8078130B2 (en) 2008-12-23 2011-12-13 L-3 Communications Integrated Systems L.P. Systems and methods for interference cancellation
US8081946B2 (en) 2008-12-23 2011-12-20 L-3 Communications Integrated Systems L.P. Interference cancellation for reconfigurable direct RF bandpass sampling interference cancellation
WO2013017975A1 (fr) * 2011-07-29 2013-02-07 Telefonaktiebolaget L M Ericsson (Publ) Procédé et dispositif pour un échantillonnage itératif à l'aveugle d'un signal à large bande
WO2017039819A1 (fr) * 2015-09-04 2017-03-09 Raytheon Company Appareil et procédé d'annulation sélective de signal
EP3240197A1 (fr) * 2016-04-28 2017-11-01 Nxp B.V. Circuits récepteurs avec voie de signal feedforward
FR3128600A1 (fr) * 2021-10-25 2023-04-28 Thales Numériseur radiofréquence à dynamique augmentée

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3938153A (en) * 1974-08-16 1976-02-10 The United States Of America As Represented By The Secretary Of The Navy Sidelobe canceller system
SU794706A1 (ru) * 1978-11-27 1981-01-07 Минский радиотехнический институт Синтезатор частот
JPH06338871A (ja) * 1993-05-31 1994-12-06 Victor Co Of Japan Ltd スペクトル拡散復調装置
US5694395A (en) * 1994-09-30 1997-12-02 Lucent Technologies, Inc. Method and apparatus for processing multicarrier signals
US5826181A (en) * 1996-05-18 1998-10-20 Northern Telecom Limited Radio frequency noise reduction arrangement
US6195537B1 (en) * 1997-09-25 2001-02-27 Lucent Technologies, Inc. Method and apparatus for strong signal suppression in multi-carrier signals

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3938153A (en) * 1974-08-16 1976-02-10 The United States Of America As Represented By The Secretary Of The Navy Sidelobe canceller system
SU794706A1 (ru) * 1978-11-27 1981-01-07 Минский радиотехнический институт Синтезатор частот
JPH06338871A (ja) * 1993-05-31 1994-12-06 Victor Co Of Japan Ltd スペクトル拡散復調装置
US5694395A (en) * 1994-09-30 1997-12-02 Lucent Technologies, Inc. Method and apparatus for processing multicarrier signals
US5826181A (en) * 1996-05-18 1998-10-20 Northern Telecom Limited Radio frequency noise reduction arrangement
US6195537B1 (en) * 1997-09-25 2001-02-27 Lucent Technologies, Inc. Method and apparatus for strong signal suppression in multi-carrier signals

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
DATABASE WPI Derwent World Patents Index; Class U23, AN 1981-3766D *
PATENT ABSTRACTS OF JAPAN *

Cited By (17)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1769583A4 (fr) * 2004-06-12 2008-01-16 L 3 Integrated Systems Co Systemes et procedes pour conversion analogique-numerique multicanaux
EP1769583A1 (fr) * 2004-06-12 2007-04-04 L-3 Integrated Systems Company Systemes et procedes pour conversion analogique-numerique multicanaux
EP1895667A2 (fr) * 2006-08-30 2008-03-05 Broadcom Corporation Récepteur radio et son frontal
EP1895667A3 (fr) * 2006-08-30 2014-05-14 Broadcom Corporation Récepteur radio et son frontal
US8494100B2 (en) 2008-07-16 2013-07-23 Signal Processing Devices Sweden Ab Device and method for blocking-signal reduction
WO2010006646A1 (fr) * 2008-07-16 2010-01-21 Signal Processing Devices Sweden Ab Dispositif et procédé de réduction de signal de blocage
US8078130B2 (en) 2008-12-23 2011-12-13 L-3 Communications Integrated Systems L.P. Systems and methods for interference cancellation
US8081946B2 (en) 2008-12-23 2011-12-20 L-3 Communications Integrated Systems L.P. Interference cancellation for reconfigurable direct RF bandpass sampling interference cancellation
WO2013017975A1 (fr) * 2011-07-29 2013-02-07 Telefonaktiebolaget L M Ericsson (Publ) Procédé et dispositif pour un échantillonnage itératif à l'aveugle d'un signal à large bande
US8885783B2 (en) 2011-07-29 2014-11-11 Telefonaktiebolaget L M Ericsson (Publ) Method and device for iterative blind wideband sampling
WO2017039819A1 (fr) * 2015-09-04 2017-03-09 Raytheon Company Appareil et procédé d'annulation sélective de signal
KR20180049035A (ko) * 2015-09-04 2018-05-10 레이데온 컴퍼니 선택적 신호 제거를 위한 장치 및 방법
KR102044816B1 (ko) 2015-09-04 2019-11-14 레이데온 컴퍼니 선택적 신호 제거를 위한 장치 및 방법
EP3240197A1 (fr) * 2016-04-28 2017-11-01 Nxp B.V. Circuits récepteurs avec voie de signal feedforward
US10164807B2 (en) 2016-04-28 2018-12-25 Nxp B.V. Receiver circuits
FR3128600A1 (fr) * 2021-10-25 2023-04-28 Thales Numériseur radiofréquence à dynamique augmentée
WO2023072906A1 (fr) * 2021-10-25 2023-05-04 Thales Numériseur radiofréquence à dynamique augmentée

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