WO2004010606A1 - Procede et appareil permettant de recevoir une sttd a ponderation adaptative - Google Patents
Procede et appareil permettant de recevoir une sttd a ponderation adaptative Download PDFInfo
- Publication number
- WO2004010606A1 WO2004010606A1 PCT/CN2003/000513 CN0300513W WO2004010606A1 WO 2004010606 A1 WO2004010606 A1 WO 2004010606A1 CN 0300513 W CN0300513 W CN 0300513W WO 2004010606 A1 WO2004010606 A1 WO 2004010606A1
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- module
- receiver
- receiving
- signal
- space
- Prior art date
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
Definitions
- the present invention relates to space-time transmit diversity reception techniques, and more particularly to a reception method and system based on adaptive weighted space-time transmit diversity. Background of the invention
- WCDMA Wideband Code Division Multiple Access
- 3G third generation
- multiple diversity methods such as multipath diversity, spatial diversity, and antenna diversity can be used.
- ML Maximum Likelihood
- STTD Space Time Transmit Diversity
- the diversity technique is to perform simple space-time coding on the information to be transmitted, and then divide the space-time encoded signal into two paths, and respectively send them to two independent transmission channels for transmission according to equal energy criteria, correspondingly, the receiving end Signals from two independent transmit channels are received separately and processed according to the maximum likelihood principle.
- the conventional STTD transmit diversity technique cannot achieve the performance upper bound.
- the applicant proposes a transmit-diversity technique based on space-time coding and adaptive weighting.
- the core idea is that the transmitter receives the fading amplitude characteristics of the current two-way radio channel according to the received from the feedback channel. Information, recalculate the appropriate transmit power weight value, and redistribute the transmit energy.
- the implementation structure is shown in Figure 1.
- reference numeral 100 denotes information to be transmitted, where s 2 is two transmission symbols in the same space time coding block; 101 is a space time coding module, 102 is a feedback signal processing module, and 103 is an optimal weight calculation module.
- 104 is a feedback channel
- 105 is a transmit power distribution module
- 106 is a transmit antenna array having two antennas, indicating that two independent transmit channels are respectively transmitted through antennas AnU and Ant2
- Rec is a receiver based on maximum likelihood ( The receiver of the ML) principle
- 107 is a maximum likelihood receiving module.
- the diversity method includes at least the following steps: a.
- the transmitting end transmits the symbols to be transmitted with one input block for each two input symbols, and performs space-time coding according to a certain rule to output two signals;
- the transmitting end adjusts the current transmit power value of the two transmit antennas in real time according to the currently given transmit power weight value while keeping the total transmit power unchanged; the transmit antenna array will go through the current transmit power value.
- the time-coded output signal is transmitted from the two independent antennas;
- the receiver at the receiving end estimates the fading characteristics of the two wireless channels according to the current received signal, and encodes the fading amplitude characteristics of the two wireless channels to the transmitting end; d.
- the transmitting end receives and obtains from the feedback channel
- the current characteristic information of the fading amplitude of the two channels of the wireless channel is calculated according to formula (1), and the new adaptive weight value of the transmission power of the two channels is calculated, and the transmission power is adjusted according to the weight value.
- the received signal of the same space-time coded block can be expressed as:
- r 2 are the received signals of the same space-time coding block, respectively! ⁇ And! ⁇ respectively represents the fading factor from the two transmit antennas to the receive antenna radio channel
- S 2 is the transmit symbol in the same space-time coded block
- ⁇ ! and w 2 are the transmit power weights of the two transmit channels at the transmitting end, respectively.
- the receiver mainly performs functions such as maximum likelihood reception and decoding.
- the S 2 decision variable calculated by the maximum likelihood receiving technique is directly used for decoding.
- the decision variables of S! and S 2 are:
- the main purpose of the present invention is to provide an adaptive weighted space-time transmit diversity receiving method, which can further improve the receiving process of adaptive weighted space-time diversity, and avoid the increase of adaptive weighting operation. Signal interference caused, which in turn improves system performance.
- Another object of the present invention is to provide a system for implementing an adaptive weighted space-time transmit diversity receiving method, which can improve the performance of a receiver in an adaptive weighted space-time transmit diversity system, thereby improving the overall performance of the system, and
- the design is simple and easy to implement.
- a method for receiving adaptive weighted space-time transmit diversity includes at least:
- the receiver After receiving the signal from the transmitting end, the receiver first calculates the intermediate value of the decision variable of each signal by using the maximum likelihood principle;
- the intermediate value of the decision variable is calculated by the linear transformation according to the given linear transformation matrix and its coefficients, and the final decision variable value of each signal is calculated as the input of the subsequent processing module.
- the step a further comprises: the receiver detects the received input signal in units of space-time coding blocks, and outputs two intermediate values of the decision variables each time.
- Step b further includes: pre-setting a linear transformation matrix, and pre-calculating a linear transformation.
- the linear transformation matrix coefficient is related to the implementation form of the adaptive weighted space-time transmit diversity, and can be determined by the adaptive weight value and the wireless channel fading amplitude characteristic; and the adaptive weight value and the transmitting end used for calculating the linear transformation matrix coefficient The weight values currently in use are fully synchronized.
- Step b further includes: transmitting the final decision variable value to a decoding module in the receiver for decoding processing.
- a system for implementing the above adaptive weighted space-time transmit diversity receiving method including at least Space-time coding module, transmit antenna array with two antennas, transmit power distribution module, feedback channel, feedback signal processing module and optimal weight calculation module, and maximum likelihood receiver module in receiver receiver, the key is: receiving The receiver of the terminal further includes a linear transformation module;
- the maximum likelihood receiving module of the receiver receives and processes the signal from the transmitting end, outputs the intermediate value of the decision variable to the linear transform module for linear transformation, and the processed decision variable continues to be sent to the subsequent processing module of the receiver, the subsequent processing module at least Includes a decoding module.
- the key to the present invention is: adding line line conversion processing at the receiving end based on adaptive weighted space-time transmit diversity to remove inter-signal interference generated during the calculation of the transmit power weight and improve system performance.
- the information about the radio channel fading amplitude obtained by the receiver itself and the calculation method of the optimal weight based on the space-time coding adaptive weighted closed-loop transmit diversity technique after the maximum likelihood receiving module, a simple first step is added.
- the linear transformation (LT, Linear Transform) removes the cross terms in the adaptive weight calculation by linear transformation processing, thereby avoiding the signal interference generated by the cross terms, and greatly improving the reception performance of the transmission diversity; and the linear transformation and The use of space-time coding adaptive weighted transmit diversity technology can greatly improve the overall performance of the system.
- the invention only needs to add a linear transformation module to the receiver at the receiving end, and the system modification of the prior art is small, and the system performance is further improved on the original basis, and the structure design is simple and easy to implement.
- FIG. 1 is a schematic structural diagram of a system structure of an existing adaptive weighted space-time transmit diversity
- FIG. 2 is a schematic structural diagram of a system for adaptive weighted space-time transmit diversity according to the present invention
- FIG. 3 is a schematic diagram of the present invention and existing space-time transmit diversity, A schematic diagram of performance comparison of adaptive weighted space-time transmit diversity. Mode for carrying out the invention
- the system includes a space time coding module 101, a feedback signal processing module 102, an optimal weight calculation module 103, a feedback channel 104, and a transmit power allocation.
- the feedback channel 104 is configured to output information about the current wireless channel characteristics from the receiver; the feedback signal processing module 102 is configured to receive information about the current wireless channel characteristics from the feedback channel, and perform mapping processing; the optimal weight calculation module 103, according to the relevant wireless channel characteristic information from the feedback receiving module 102, calculate the transmit power weight of the two transmit channels; the transmit power allocation module 105 is configured to adjust the transmit power values of the different antennas according to the received transmit power weight; The antenna array 106 sends the output encoded by the space time coding module 101 through two independent antennas according to the current transmit power value.
- the linear transform module 108 is configured to receive the output of the maximum likelihood receiving module 107, calculate a linear transform matrix coefficient based on the adaptive weight calculation method, and linearly transform the input with the matrix.
- the present invention first follows the normal pole by the maximum likelihood receiving module 107.
- the N2003/000513 large likelihood principle detects the received input signal from the transmitting end in units of space-time coded blocks.
- each channel after space-time coding contains a copy of the information, but the form and order are different.
- the one space-time coding block actually refers to two copies of the two-way signal information. Therefore, the receiver
- two signals are received, and a copy of the two pieces of information is jointly processed according to formula (4), and the intermediate value of each of the two decision variables is output to the linear transformation module 108.
- the intermediate value of the decision variable can be expressed as:
- coefficients A and B can also be expressed in other forms, or determined by other factors, depending primarily on the implementation of the adaptive weighted space-time transmit diversity implementation.
- calculating a linear transformation matrix coefficients A and B are adaptive weight transmitter is currently using weight values Wl, w 2, namely: to ensure that the weight value is calculated transformation matrix coefficients weighting value transmitter currently used fully Synchronization, in turn, makes the linear transformation process work better, thereby improving the overall performance of the system.
- the base station determines the relative delay between the uplink and the downlink, according to the fixed relative delay. Guaranteed weight synchronization.
- Another method is that the receiver uses the downlink common pilot channel and the dedicated pilot channel to estimate the weight actually used by the current transmitter, and uses the weight value to perform signal demodulation and transform matrix system calculation at the receiving end.
- the specific implementation process of the method is as follows: the channel fading factor hph 2 is estimated through the common pilot channel, and then The pilot channel is estimated! ⁇ and w 2 *h 2 , thereby obtaining the weight value actually used by the current transmitter
- this value is the weight value calculated according to the weight formula at the previous moment, and then the demodulation process is continued with this value and the transformation matrix coefficients are calculated.
- the linear transform module 108 can calculate the linear transform matrix coefficients A and B represented by the formula (5), and then according to the formula (6).
- the linear transformation matrix shown is a linear transformation of the decision variable intermediate value (r 2 ) output by the maximum likelihood receiving module 107:
- the result of the linear transformation is output by the linear transform module 108, and sent as a final decision variable to a subsequent processing module in the receiver, such as a decoding module, to perform subsequent processing such as decoding in a conventional manner.
- a subsequent processing module in the receiver such as a decoding module
- the average signal to noise ratio (SNR) corresponding to the decision variable can be obtained as:
- the present invention increases by an average of 1.55 dB compared with the performance of ordinary STTD transmit diversity, and increases by an average of 0.7 to 0.8 dB compared with the performance of adaptively weighted STTD transmit diversity.
- FIG. 3 is a schematic diagram showing the performance comparison between the present invention and the existing space-time transmit diversity and the existing adaptive weighted space-time transmit diversity, wherein the abscissa represents the decibel (dB) number of the signal-to-noise ratio (Eb/No), and the ordinate Indicates the original bit error rate, curve 31 is the performance curve of ordinary STTD transmit diversity, curve 32 is the performance curve of STTD transmit diversity after adding adaptive weighted adjustment transmit power, curve 33 is the performance of STTD transmit diversity after adding linear transform process for the present invention curve. It can be seen from the comparison of the three curves that when the bit error rate is the same, the signal-to-noise ratio of the adaptive weighted transmit diversity of the linear transform process is increased compared with the other two cases.
- the value is low, that is, when the bit error rate is the same, the signal required by the signal of the invention has the lowest transmission power; from another point of view, when the signal-to-noise ratio of the three curves is the same, the receiving end increases the adaptation of the linear transformation process.
- the bit error rate of the weighted transmit diversity is significantly lower than the other two cases. Obviously, the overall performance of the transmit diversity system of the present invention is higher.
- the present invention is applicable not only to the aforementioned adaptive weighted space-time transmit diversity method and structure proposed by the applicant, but also to other various adaptive weighted space-time transmit diversity techniques implemented by different approaches, the idea of the present invention is applicable,
- the corresponding linear transform coefficients will be different for different implementations of adaptive weighted space-time transmit diversity techniques.
Landscapes
- Engineering & Computer Science (AREA)
- Computer Networks & Wireless Communication (AREA)
- Signal Processing (AREA)
- Radio Transmission System (AREA)
Description
一种自适应加权空时发射分集的接收方法及其系统
技术领域
本发明涉及空时发射分集接收技术， 尤指一种基于自适应加权空时 发射分集的接收方法及其系统。 发明背景
在第三代（ 3G )移动通信系统的宽带码分多址（ WCDMA, Wideband Code Division Multiple Access )制式中， 由于同一小区中不同的用户和 邻近小区的不同用户在同一时间内共享同一段频段， 因此， 用户彼此之 间存在干扰， 这些干扰限制了系统容量和信息传送速率。 为了提高系统 容量， 可釆用多种分集方法， 如多径分集、 空间分集以及天线分集等技 术。 在采用分集技术的系统内， 同一信息内容存在有多 不同形式的独 立拷贝，接收机接收这些独立拷贝后 ,通常根据极大似然（ ML, Maximum Likelihood )的原理， 充分利用信息的冗余特性加以处理， 可大大减少传 输信息的误比特率， 并降低无线数据传输所需的能量， 从而减少对用户 间的彼此干扰。 可见， 分集技术能有效地提高系统容量。
在 WCDMA 系统下行链路中， 要实现大容量用户数和高速数据传 送，同样需要采用多种发射分集技术，空时发射分集（STTD, Space Time Transmit Diversity )方法便是其中之一。 该分集技术是将待传送的信息 先进行简单的空时编码， 然后将空时编码后的信号分成两路， 按照相等 能量准则分别送至两路独立的发射通道进行发射， 相应的， 接收端分别 接收来自两路独立发射通道的信号， 并根据极大似然原理进行处理。 但 由于按照平分的方式等分发射能量， 该普通的 STTD发射分集技术无法 达到性能上界。
为了提高空时发射分集的性能， 申请人曽提出一种基于空时编码和 自适应加权的发射分集技术， 其核心思想是发射端根据从反馈信道接收 的有关当前两路无线信道的衰落幅度特性信息， 重新计算合适的发射功 率权重值， 并重新分配发射能量， 其实现结构如图 1所示。 图 1中， 标 号 100表示待传送信息， 其中的 s2为同一空时编码块中的两个发 射符号； 101即为空时编码模块， 102为反馈信号处理模块， 103为最优 权重计算模块， 104为反馈通道， 105为发射功率分配模块， 106为具有 两根天线的发射天线阵， 表示两路独立的发射通道分别通过天线 AnU、 Ant2进行发射； Rec为接收端基于极大似然 （ML )原理的接收机， 107 为极大似然接收模块。
基于图 1所示的系统接收， 该分集方法至少包括以下的步骤： a. 发射端将待发射符号以每两个输入符号为一个单元块，按一定规 则进行空时编码后输出两路信号；
b. 发射端根据当前给定的发射功率权重值，在保持总发射功率不变 的前提下， 分别实时调整两路发射天线的当前发射功率值； 发射天线阵 按当前发射功率值， 将经过空时编码的输出信号从两才艮独立的天线发射 出去；
c 接收端的接收机才艮据当前接收到信号，估计出两路无线信道的衰 落特性， 并将两路无线信道衰落幅度特性经过编码后反馈至发射端； d. 发射端从反馈信道接收并获得当前两路无线信道衰落幅度的特 性信息， 按公式（1 )计算两路发射通道发射功率的新自适应权重值， 并根据该权重值进行发射功率调整。
T/CN2003/000513
在接收端， 同一空时编码块的接收信号可以表示为：
其中， 、 r2分别为同一空时编码块的接收信号， ！^和！^分别表示 从两才 发射天线到接收天线无线信道的衰落因子， S2为同一空时编 码块中的发射符号， ！^和 为接收噪声， ^¥!和 w2分别为发射端两路发 射通道的发射功率权重。
按传统方式， 接收机主要完成极大似然接收和解码等功能， 由极大 似然接收技术计算的 S2判决变量直接用于解码， 此种情况下 S!、 S2 的判决变量为：
= 0】 I hx I2 +w2 I h2 I2 )S{ + {wx一 w2 )h*h2S2* + (h*n, + h2n2 )
( 3 )
+ (h;n2 + h2n*) 从公式（3 ) 可以看出， 由于两路发射通道权重不相等， 将导致 Si 判决变量中出现交叉项 W2»2S2*， 同样， S2判决变量中也将出现类 似的交叉项（w2 - Wl)A 2S 。 随着信号能量的增加， 该交差项的干扰将会 越来越大， 严重影响了接收机的性能。
可见， 如果仅仅采用传统极大似然接收方法， 基于空时编码和自适 应加权的发射分集的性能受到严重的限制， 影响了发射效果。
发明内容
由上述分析可以看出， 本发明的主要目的在于提供一种自适应加权 空时发射分集的接收方法， 使其能进一步完善自适应加权空时分集的接 收处理， 避免因增加自适应加权运算而导致的信号干扰， 进而提高系统 性能。
本发明的另一目的在于提供一种实现自适应加权空时发射分集接 收方法的系统， 使其能改善自适应加权空时发射分集系统中接收机的性 能， 从而提高该系统的整体性能， 且设计简单、 易于实现。
为达到上述目的， 本发明的技术方案是这样实现的：
一种自适应加权空时发射分集的接收方法， 至少包括：
a.接收机接收到来自发射端的信号后，先利用极大似然原理计算出 每路信号的判决变量中间值；
b. 然后该判决变量中间值按给定的线性变换矩阵及其系数，通过线 性变换计算出每路信号的最终判决变量值， 并将该值作为后续处理模块 的输入。
上述过程中， 步驟 a进一步包括： 接收机对接收到的输入信号以空 时编码块为单元进行检测， 且每次输出两个判决变量中间值。
步骤 b进一步包括： 预先设定线性变换矩阵， 并预先计算出线性变. 换矩阵系数。 其中， 该线性变换矩阵系数与自适应加权空时发射分集的 实现形式有关， 可以由自适应权重值和无线信道衰落幅度特性确定； 并 且， 计算线性变换矩阵系数所用的自适应权重值与发射端当前使用的权 重值完全同步。
步骤 b还进一步包括： 将最终判决变量值送入接收机中的解码模块 进行解码处理。
—种实现上述自适应加权空时发射分集接收方法的系统， 至少包括
空时编码模块、 具有两根天线的发射天线阵、 发射功率分配模块、 反馈 通道、 反馈信号处理模块和最优权重计算模块以及接收端接收机中的极 大似然接收模块， 关键是： 接收端的接收机中还进一步包括线性变换模 块；
接收机的极大似然接收模块接收并处理来自发射端的信号， 输出判 决变量中间值给线性变换模块做线性变换， 经处理的判决变量继续送入 接收机的后续处理模块， 该后续处理模块至少包括解码模块。
由上述方案可以看出， 本发明的关键在于： 在基于自适应加权空时 发射分集的接收端增加线线变换处理， 以去除发射功率权重计算过程中 产生的信号间干扰， 提高系统性能。
本发明所提供的自适应加权空时发射分集的接收方法及其系统， 具 有以下的优点和特点：
1 )本发明根据接收机自身获得的有关无线信道衰落幅度信息， 以 及基于空时编码自适应加权闭环发射分集技术最优权重的计算方法， 在 极大似然接收模块后， 增加了一级简单的线性变换 （LT , Linear Transform ), 通过线性变换处理去除自适应权重计算时的交叉项， 从而 避免了交叉项产生的信号干扰， 极大改善了该发射分集的接收性能； 且 该线性变换与基于空时编码自适应加权发射分集技术配合使用， 可大大 提高系统的整体性能。
2 )本发明只需在接收端的接收机中增加一个线性变换模块， 对现 有技术的系统改动艮小 , 系统性能在原有基础上得到了进一步的提高， 结构设计简单且易于实现。
3 )经过仿真试验和理论分析证明， 本发明的方法和系统实现简单、 性能优越， 在信噪比相等的情况下， 误码率比现有 STTD发射分集低很 多； 而且， 在误码率相同的情况下， 本发明要求的信号发射功率更低。
因此， 随着信噪比的提高， 系统获得的性能增益也越大。 附图简要说明
图 1为现有自适应加权空时发射分集的系统组成结构示意图； 图 2为本发明自适应加权空时发射分集的系统组成结构示意图； 图 3为本发明与现有空时发射分集、 现有自适应加权空时发射分集 性能对比的示意图。 实施本发明的方式
下面结合附图及具体实施例对本发明再作进一步详细的说明。
图 2为本发明空时发射分集的系统组成结构示意图， 如图 2所示， 该系统包括空时编码模块 101、 反馈信号处理模块 102、 最优权重计算 模块 103、 反馈通道 104、 发射功率分配模块 105、 具有两根天线的发射 天线阵 106以及接收端接收机中的极大似然接收模块 107, 特别是在接 收端接收机的极大似然接收模块 107之后还包括： 线性变换模块 108。 其中， 反馈通道 104用于输出来自接收机的有关当前无线信道特性的信 息； 反馈信号处理模块 102用于接收来自反馈通道中有关当前无线信道 特性的信息， 并做映射处理； 最优权重计算模块 103则根据来自反馈接 收模块 102的有关无线信道特性信息， 计算出两路发射通道的发射功率 权重; 发射功率分配模块 105用来根据接收到的发射功率权重， 调整不 同天线的发射功率值； 发射天线阵 106则按照当前发射功率值， 将经过 空时编码模块 101编码后的输出经两根独立天线送出。线性变换模块 108 用于接收极大似然接收模块 107的输出， 基于自适应权重的计算方法， 计算出线性变换矩阵系数， 并用该矩阵对输入进行线性变换。
参见图 2所示， 本发明首先由极大似然接收模块 107遵循正常的极
N2003/000513 大似然原理， 对接收到的来自发射端的输入信号以空时编码块为单元进 行检测。 这里， 经过空时编码后的每一路信号均包含信息的一个拷贝， 但形式和顺序不一样， 所说的一个空时编码块实际上是指两路信号信息 的两个拷贝， 因此， 接收机同时接收两路信号， 利用这两个信息的拷贝 按照公式 （4 )进行联合处理， 每次输出两个判决变量的中间值送至线 性变换模块 108 , 该判决变量的中间值可以表示为：
设定：
Α = {Μ>χ \ +w2 \ h2 I2) ( 5 )
5 = (w, - w2 )h1*h2
实际上， 该系数 A和 B还可表示为其它形式， 或由其它因素确定， 主要取决于自适应加权空时发射分集实现形式的不同。
在式 （5 ) 中计算线性变换矩阵系数 A和 B是根据发射端当前所用 的自适应权重值 Wl、 w2, 即： 保证计算变换矩阵系数的权重值与发射机 当前所使用的权重值完全同步， 进而使线性变换处理的效果更好， 从而 提高系统的整体性能。
对于该权重同步的实现， 通常可以采用两种方案： 一种是接收机和 基站在建立连接时， 就确定上行链路和下行链路之间的相对时延， 根据 该固定的相对时延来保证权重同步。 另一种方法是接收机利用下行公共 导频信道和专用导频信道来估计出当前发射机实际使用的权重， 以此权 重值进行接收端的信号解调和变换矩阵系统计算。 该方法具体的实现过 程是这样： 通过公共导频信道估计出信道衰落因子 h p h2, 再通过专用
导频信道估计出 ！^和 w2*h2,从而获得当前发射机实际使用的权重值
Wl > w2, 实际上此值是前一时刻根据权重公式计算出的权重值， 然后以 此值继续解调过程并计算变换矩阵系数。
根据上面所述的公式 （1 ) 以及接收机自身获得的有关无线信道衰 落特性， 线性变换模块 108可计算出公式（5 )所表示的线性变换矩阵 系数 A和 B, 然后按照公式（6 )所示的线性变换矩阵对极大似然接收 模块 107输出的判决变量中间值（ r2 )进行线性变换：
线性变换后的结果由线性变换模块 108输出， 作为最终的判决变量 送至接收机中的后续处理模块， 比如解码模块， 按传统方式进行解码等 后续处理。
根据上述方案可以得到判决变量对应的平均信噪比 SNR为：
SNRW ^≠~ES ( 7 )
σ
根据公式（ 7 )可计算得出， 本发明与普通 STTD发射分集的性能相比 平均增加 1.55dB, 与增加自适应加权的 STTD发射分集性能相比也平均 增加了 0.7~0.8dB。
图 3即为本发明与现有空时发射分集、 现有自适应加权空时发射分 集性能对比的示意图， 其中， 横坐标表示信噪比（Eb/No )的分贝 （dB ) 数， 纵坐标表示原始误码率， 曲线 31为普通 STTD发射分集的性能曲 线， 曲线 32为增加自适应加权调整发射功率后 STTD发射分集的性能 曲线， 曲线 33为本发明增加线性变换处理后 STTD发射分集的性能曲 线。 由三条曲线的比较可以看出， 当误码率相同时， 接收端增加了线性 变换处理的自适应加权发射分集的信噪比值要比其它两种情况信噪比
值低， 也就是说， 误码率相同时， 本发明信号所需的发射功率最低； 从 另一角度来看， 当三条曲线的信噪比相同时， 接收端增加了线性变换处 理的自适应加权发射分集的误码率与其它两种情况相比明显最低， 显而 易见， 本发明发射分集的系统整体性能更高了。
本发明不仅适用于本申请人曾提出的前述自适应加权空时发射分 集方法与綍构， 对于其它各种通过不同途径实现的自适应加权空时发射 分集技术， 本发明的思想均适用， 只是针对各种自适应加权空时发射分 集技术实现的不同， 相应的线性变换系数会有所不同。
以上所述， 仅为本发明的较佳实施例而已， 并非用于限制本发明的保 护范围。
Claims
1、 一种自适应加权空时发射分集的接收方法， 其特征在于该方法 至少包括：
a.接收机接收到来自发射端的信号后，先利用极大似然原理计算出 每路信号的判决变量中间值；
b. 然后该判决变量中间值按照给定的线性变换矩阵及其系数，通过 线性变换计算出每路信号的最终判决变量值 , 并将该值作为后续处理模 块的输入。
2、根据权利要求 1所述的方法，其特征在于步驟 a进一步包括： 接 收机对接收到的输入信号以空时编码块为单元进行检测， 且每次输出两 个判决变量中间值。
3、 根据权利要求 1所述的方法， 其特征在于步骤 b进一步包括： 预先设定线性变换矩阵。
4、 根据权利要求 1所述的方法， 其特征在于步骤 b进一步包括： 预先计算出线性变换矩阵系数。
5、 根据权利要求 1所述的方法， 其特征在于步骤 b进一步包括： 将最终判决变量值送入接收机中的解码模块进行解码处理。
6、 根据权利要求 1或 4所述的方法， 其特征在于： 所述的线性变 换矩阵系数与自适应加权空时发射分集的实现形式有关。
7、 根据权利要求 6所述的方法， 其特征在于： 所述的线性变换矩 阵系数由自适应权重值和无线信道衰落幅度特性确定。
8、 根据权利要求 7所述的方法， 其特征在于： 计算线性变换矩阵 系数所用的自适应权重值与发射端当前使用的权重值完全同步。
9、 一种实现上述自适应加权空时发射分集接收方法的系统， 至少
包括空时编码模块、 具有两根天线的发射天线阵、 发射功率分配模块、 反馈通道、 反馈信号处理模块和最优权重计算模块以及接收端接收机中 的极大似然接收模块, 其特征在于： 接收端的接收机中还进一步包括线 性变换模块；
接收机的极大似然接收模块接收并处理来自发射端的信号， 输出判 决变量中间值给线性变换模块做线性变换， 经处理的判决变量继续送入 接收机的后续处理模块。
10、 根据权利要求 9所述的系统， 其特征在于： 所述的后续处理模 块至少包括解码模块。
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| AU2003252428A AU2003252428A1 (en) | 2002-07-19 | 2003-06-30 | Method and apparatus for receiving an adaptive weight sttd |
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN02125258.0A CN1190092C (zh) | 2002-03-22 | 2002-07-19 | 一种自适应加权空时发射分集的接收方法及其系统 |
| CN02125258.0 | 2002-07-19 |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| WO2004010606A1 true WO2004010606A1 (fr) | 2004-01-29 |
Family
ID=30450059
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| PCT/CN2003/000513 WO2004010606A1 (fr) | 2002-07-19 | 2003-06-30 | Procede et appareil permettant de recevoir une sttd a ponderation adaptative |
Country Status (2)
| Country | Link |
|---|---|
| AU (1) | AU2003252428A1 (zh) |
| WO (1) | WO2004010606A1 (zh) |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP1039658A2 (en) * | 1999-02-26 | 2000-09-27 | Texas Instruments Incorporated | Method of operating a communication circuit |
| CN1348642A (zh) * | 1999-02-22 | 2002-05-08 | 摩托罗拉公司 | 使用发射分集技术的方法和系统 |
| US20020054621A1 (en) * | 2000-10-11 | 2002-05-09 | Mun Geon Kyeong | Apparatus and method for very high performance space-time array reception processing using chip-level beamforming and fading rate adaptation |
| WO2002045294A1 (en) * | 2000-11-29 | 2002-06-06 | Ericsson Inc. | Receiver architecture for transmit diversity in cdma system |
-
2003
- 2003-06-30 WO PCT/CN2003/000513 patent/WO2004010606A1/zh not_active Application Discontinuation
- 2003-06-30 AU AU2003252428A patent/AU2003252428A1/en not_active Abandoned
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1348642A (zh) * | 1999-02-22 | 2002-05-08 | 摩托罗拉公司 | 使用发射分集技术的方法和系统 |
| EP1039658A2 (en) * | 1999-02-26 | 2000-09-27 | Texas Instruments Incorporated | Method of operating a communication circuit |
| US20020054621A1 (en) * | 2000-10-11 | 2002-05-09 | Mun Geon Kyeong | Apparatus and method for very high performance space-time array reception processing using chip-level beamforming and fading rate adaptation |
| WO2002045294A1 (en) * | 2000-11-29 | 2002-06-06 | Ericsson Inc. | Receiver architecture for transmit diversity in cdma system |
Also Published As
| Publication number | Publication date |
|---|---|
| AU2003252428A1 (en) | 2004-02-09 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN108512585B (zh) | 基于功率域非正交多址接入技术的动态协作中继传输方法 | |
| WO2003081836A1 (fr) | Procede de diversite de transmission espace-temps pondere auto-adaptatif et systeme correspondant | |
| US7924949B2 (en) | Advanced multi-sensor processing | |
| Goldsmith et al. | Capacity limits of MIMO channels | |
| US7778147B2 (en) | MIMO communication system using an adaptive transmission mode switching technique | |
| JP4504293B2 (ja) | 複数アンテナを備えた無線通信装置および無線通信システム、無線通信方法 | |
| JP4369128B2 (ja) | 無線通信システム | |
| WO2003009492A1 (fr) | Procede et dispositif de transmission par multiples antennes avec retroaction descendante dans un systeme de communication sans fil | |
| WO2004062132A1 (fr) | Procede et systeme permettant une diversite de transmission en boucle fermee spatio-temporelle adaptative | |
| KR20070072406A (ko) | 무선 통신 시스템의 간섭 제거 방법 및 디바이스 | |
| CN111314935B (zh) | 基于noma-mec系统的下行传输时延最小化的方法 | |
| CN101150343A (zh) | 一种mimo移动通信方法及系统 | |
| WO2006080360A1 (ja) | 通信装置及び通信方法 | |
| Zhang et al. | Linear transmitter precoding design for downlink of multiuser MIMO systems | |
| CN106921418A (zh) | 一种基于非理想信道状态信息的中继协作预编码方法 | |
| WO2001078253A1 (fr) | Procede de traitement de signaux utilise avec un terminal dans un systeme de communication mobile amrc | |
| CN102223170B (zh) | 码分多径信道的序贯多天线选择发送方法 | |
| CN101141232A (zh) | 一种多输入多输出系统中的信号发射方法及信号发射系统 | |
| CN113691287B (zh) | 一种基于平均误比特率约束的大规模mimo系统自适应调制方法 | |
| CN102624498A (zh) | 一种联合分布式空时编码的下行多基站协同系统干扰消除方法 | |
| CN102752071A (zh) | 用于多点协作系统的下行链路预编码方法和中心处理节点 | |
| WO2004010606A1 (fr) | Procede et appareil permettant de recevoir une sttd a ponderation adaptative | |
| Bjerke et al. | Antenna diversity combining schemes for WCDMA systems in fading multipath channels | |
| CN111917522B (zh) | 一种抗干扰宽带单载波空时编码传输方法 | |
| CN109379308B (zh) | 一种基于稀疏感知的自适应空时均衡方法 |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| AK | Designated states |
Kind code of ref document: A1 Designated state(s): AE AG AL AM AT AU AZ BA BB BG BR BY BZ CA CH CO CR CU CZ DE DK DM DZ EC EE ES FI GB GD GE GH GM HR HU ID IL IN IS JP KE KG KP KR KZ LC LK LR LS LT LU LV MA MD MG MK MN MW MX MZ NI NO NZ OM PG PH PL PT RO RU SC SD SE SG SK SL SY TJ TM TN TR TT TZ UA UG US UZ VC VN YU ZA ZM ZW |
|
| AL | Designated countries for regional patents |
Kind code of ref document: A1 Designated state(s): GH GM KE LS MW MZ SD SL SZ TZ UG ZM ZW AM AZ BY KG KZ MD RU TJ TM AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HU IE IT LU MC NL PT RO SE SI SK TR BF BJ CF CG CI CM GA GN GQ GW ML MR NE SN TD TG |
|
| DFPE | Request for preliminary examination filed prior to expiration of 19th month from priority date (pct application filed before 20040101) | ||
| 121 | Ep: the epo has been informed by wipo that ep was designated in this application | ||
| 122 | Ep: pct application non-entry in european phase | ||
| NENP | Non-entry into the national phase |
Ref country code: JP |
|
| WWW | Wipo information: withdrawn in national office |
Country of ref document: JP |