WO2002097960A1 - Convertisseur et son procede de commande - Google Patents

Convertisseur et son procede de commande Download PDF

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Publication number
WO2002097960A1
WO2002097960A1 PCT/SE2002/000975 SE0200975W WO02097960A1 WO 2002097960 A1 WO2002097960 A1 WO 2002097960A1 SE 0200975 W SE0200975 W SE 0200975W WO 02097960 A1 WO02097960 A1 WO 02097960A1
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WO
WIPO (PCT)
Prior art keywords
voltage
valves
current valves
current
semiconductor devices
Prior art date
Application number
PCT/SE2002/000975
Other languages
English (en)
Inventor
Bo Bijlenga
Original Assignee
Abb Ab
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Abb Ab filed Critical Abb Ab
Publication of WO2002097960A1 publication Critical patent/WO2002097960A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4811—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode having auxiliary actively switched resonant commutation circuits connected to intermediate DC voltage or between two push-pull branches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/4837—Flying capacitor converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0095—Hybrid converter topologies, e.g. NPC mixed with flying capacitor, thyristor converter mixed with MMC or charge pump mixed with buck
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/487—Neutral point clamped inverters

Definitions

  • the present invention relates to an apparatus for converting alternating voltage into direct voltage and conversely included in a SVC (Static Var Compensator) with a direct voltage side formed by one or a plurality of capacitors hanging freely, said apparatus comprising a series connection of at least four current valves arranged between two poles, one positive and one negative, of said direct voltage side, said valves each comprising a semiconductor device of turn-off type and a rectifying member connected in anti-parallel therewith, an alternating voltage phase line connected to a first midpoint, called phase output, of the series connection between two current valves while dividing the series connection into equal parts, the two poles of the direct voltage side being put on substantially the same voltage but with opposite signs with respect to a zero voltage level of the direct voltage side, said apparatus comprising a second mid- point between two said current valves of one part of the series connection, which is through a flying capacitor connected to a second midpoint of the other part of the series connection corresponding thereto with respect to the phase output, and an arrangement for
  • the invention is directed to a voltage stiff converter apparatus adapted only for transferring reactive power and being ad- vantageously arranged along high voltage alternating voltage lines for achieving reactive power compensation.
  • the invention is not restricted to any levels of the voltage of the alternating voltage side of the apparatus, of the reactive power the converter apparatus is able to transfer or the number of phases of the alternating voltage side of the apparatus, and it may accordingly very well be designed for the one-phase case, for example for feeding railway vehicles.
  • the invention is particularly, but not exclusively, directed to intermediate and high voltage, i.e. where the peak voltage on the alternating voltage sfde of the apparatus is 10 kV or higher.
  • the apparatus defined in the introduction is a so called multilevel-converter, since it may on said phase output deliver at least three different phase potentials.
  • An advantage of using such so called multi-level-converters with respect to so called two level bridges " , * is that the semiconductor devices of the current valves may be switched with a considerably lower fre- quency for obtaining an alternating voltage of a determined frequency and quality on the alternating voltage phase line, so that the losses of the converter apparatus may be reduced considerably. More exactly, the switching frequency of the semiconductor devices in a three level converter may under said condi- tions be reduced to about ⁇ A.
  • An advantage of using so called flying capacitors for obtaining further voltage levels of the phase output besides the voltage level of the two poles of the direct voltage side with respect to a use of a so called clamping diode is primarily that the semiconductor devices in the latter case have to be controlled in such a way that a non-uniform distribution of switching losses on them will occur, so that in the practice all semiconductor devices have to be dimensioned for being able to take the maximum load to which an individual semiconductor device may be subjected, since otherwise particular considerations have to be taken to the design of each individual semiconductor device when controlling them. This makes the total cost for the semiconductor devices very high, since some of them will in most operation situations be heavily overdimen- sioned.
  • the object of the present invention is to provide a converter apparatus of the type defined in the introduction as well as a method for control thereof, which in at least some respect results in an improved function of such an apparatus with respect to such apparatuses already known, especially enables a reduction of the total switching losses of the semiconductor devices included in the current valves.
  • Another advantage of a lower frequency of the switching of the outer current valves is that in the case of a series connection of semiconductor devices, which is necessary when handling high voltages, this is easier at low switching frequencies, since an unbalance with respect to the voltage held by different semiconductor devices connected in series will then get smaller, so that it is possible to arrange semiconductor devices having a smaller margin between the voltage they may maximally withstand and the average voltage per semiconductor device in the current valve.
  • the apparatus is adapted to control the semiconductor devices of the outer current valves to be turned on and turned off with a frequency being substantially equal to said fundamental frequency, said fundamental frequency being in the order of 40-70 Hz, preferably 50 Hz or 60 Hz, and the arrangement is adapted to turn on and turn off the semiconductor devices of the inner cur- rent valves with a frequency being 15-45 times said fundamental frequency, which usually means 1 -2 kHz.
  • the semiconductor devices and the rectifying members of said cur- rent valves are designed so that the time average of the voltage across the flying capacitor will be a factor 0.2-0.5 times the voltage between the two poles of he direct voltage side, in which it is advantageous that said, factor is less than 0.5. If this factor differs from 0.5 the use of one single flying capacitor and four said current valves would in fact result in a possibility to obtain four different levels of the potential, while in an apparatus according to US 5 737 201 six current valves connected in series and two flying capacitors are required for obtaining four levels, which means a considerable saving of costs with respect to components as well as switching losses with respect to such an apparatus already known, should there be a desire to obtain four levels instead of three.
  • Another advantage of the fact that a higher voltage is applied across the outer current valves than across the inner ones in the blocking state is that the semiconductor devices of the outer current valves do not have to be dimensioned just as large with respect to the ability to withstand voltage so as to withstand the stresses when connecting the converter apparatus to voltage from the alternating voltage side.
  • the clamping capacitors of the direct voltage side hanging freely will namely when connecting the apparatus to voltage be charged " before the flying capacitor.
  • the flying capacitor will thereafter be charged to the nominal voltage thereof thanks to the voltage dividers normally arranged in parallel with the semiconductor devices of turn-off type in the different current valves.
  • the entire voltage between the two direct voltage poles will then during a short period of time be applied across one or the other of the outer current valves before the flying capacitor has been charged.
  • said factor is 1/3.
  • the fact is that the four voltage levels obtainable on the phase output will then be uniformously distributed between the positive and the negative pole voltage, which results in a lower voltage switched, i.e. a lower pulse height step, which reduces the stresses on equipments such as reactors and transformers, connected thereto.
  • the apparatus has a unit adapted to enable so called soft-switching of the semiconductor devices of the inner current valves, i.e. so that no high voltages and high currents are combined in the semiconductor devices in these two valves. It is very advantageous to arrange such a unit exactly where the frequencies are high, since this has the greatest impact on the switching losses. Otherwise expressed, it is chosen to have high frequencies where the losses per switching are very low. Thus, the maximum revenue of the additional costs resulting from such a unit is obtained in this way. , A device of this type gets extremely low switching losses, since the outer current valves switch according to the hard-switching principle with a low frequency and the inner current valves switch according to the soft-switching principle with a high frequency. This embodiment is particularly advantageous in combination with a selection of said factor as being less than 0.5, so that lower voltages have to be handled-by the inner current valves and thereby also by the unit, which thereby may be made smaller and manufactured to a lower cost.
  • the two inner current valves have a snubber capacitor each connected in parallel with said semiconductor device of turn-off type and the unit comprises a resonance circuit for recharging the snubber capacitors of the current valves so as to thereby enable turning on of the semiconductor devices of turn-off type of the current valves at a low voltage thereacross.
  • This is an advantageous way to obtain so called soft-switching of the inner current valves, in which ' a preferred embodiment has a resonance circuit being made of an ARCP-circuit (Auxiliary Resonant Commutation Pole).
  • the two outer valves have a snubber member each, for example a snubber capacitor or a RC-circuit, connected in parallel with said semiconductor devices of turn-off type, so that the time de- rivative- of the voltage across the semiconductor devices of turn- off type is restricted when switching the outer current valves and thereby the capacitive currents in a transformer associated therewith are limited.
  • a snubber member each, for example a snubber capacitor or a RC-circuit
  • said arrangement is adapted to control the semiconductor devices of the current valves and thereby the current valves according to a voltage set value for said phase voltage, and when the voltage set value is located between U dc /2 and (1 -k) x U dc /2, corre- sponding above a first level, to alternatively make the two inner current valves conducting and continuously keep the outer current valve closest to the positive direct voltage pole conducting and the other outer current valve blocked, when the current set value is located between -U C / and (-1+k) x U dc /2, cor- responding to a second level, alternatively make the two inner current valves conducting and continuously keep the current valve closest to the positive direct voltage pole blocked and the opposite outer current valve conducting, and when the current set value is located between said two levels to alternatively make one outer current valve and the inner current valve located on the opposite side of the phase output with respect thereto conducting and at the same time the other outer current valve and the other inner current valve to block and conversely, U dc
  • the arrangement is adapted to control the current valves according to a voltage set value for said phase voltage with the shape of a sine curve having a third tone component or a multiple of third tone components with respect to the fundamental tone of the sine curve added thereto for prolonging the period of time during which the voltage set value is located above said first level and below said second level and the two outer current valves may be located in a fixed position and do not have to be switched.
  • the flanks of the voltage set value are in this way made steeper and the period of time during which the outer cur- rent valves have to be switched is hereby made shorter.
  • the invention also relates to a method for the control of a con- verter apparatus in accordance with the above according to the appended independent method claim. Advantages of this method and of embodiments of this method defined in the appended dependent claims appear without any doubt from the discussion above of preferred embodiments of the converter apparatus according to the invention.
  • the invention also relates to a computer program product as well as a computer readable medium according to the corresponding appended claims. It is easily understood that the method according to the invention defined in the appended set of method claims is well suited to be carried out through program instructions from a processor which may be influenced by a computer program provided with the program steps in question.
  • Fig 1 is a simplified circuit diagram of a converter apparatus according to a first preferred embodiment of the invention
  • Fig 2 is a view corresponding to Fig 1 of a converter apparatus according to a second preferred embodiment of the invention
  • Fig 3 is a view corresponding to Fig 1 of a converter apparatus according to a third preferred embodiment of the invention, which is formed by a minor modification of the converter apparatus according to Fig 2,
  • Figs 4 and 5 illustrate a voltage set value with sine shape and a voltage set value in the form of a sine curve having a third tone component adde Hhereto, respectively, for the voltage between the phase output and an imagined zero voltage level on the di- rect voltage side of the converter apparatus, which is used for pulse width modulation of the converter apparatus, and
  • Fig 6 illustrates schematically what a pulse width modulation pattern based on the voltage set value according to Fig 1 may look like for a converter apparatus according to Fig 1 .
  • Fig 1 Only the part of the converter apparatus connected to one phase of an alternating voltage phase line is shown in Fig 1 , in which the number of phases is normally three, but it is also possible that this constitutes the entire converter apparatus, when this is connected to a one-phase alternating voltage network.
  • the con- verter apparatus is a so-called VSC-converter (Voltage Source Converter), which has four current valves 1 -4 connected in series between the two poles 5, 6, positive and negative, respectively, of a direct voltage side of the apparatus.
  • a so-called coupling capacitor 7 is arranged between the two poles.
  • the voltage between the two poles defined therethrough gets U dc , in which the potentials for the poles get +U dc /2 and -U c /2, respectively.
  • VSC-converter Voltage Source Converter
  • the current valves 1-4 are each constituted by a semiconductor device 8-1 1 of turn-off type, such as an IGBT, GTO or IGCT, and a rectifying member connected in anti-parallel therewith in the form of a rectifying diode 12-15.
  • a semiconductor device 8-1 1 of turn-off type such as an IGBT, GTO or IGCT
  • a rectifying member connected in anti-parallel therewith in the form of a rectifying diode 12-15.
  • a first midpoint 16 which constitutes the phase output of the converter, is connected to an alternating voltage line 19 through an inductor 20.
  • Said series connection is in this way divided into two equal parts with two current valves 1 , 2 and 3, 4, respec- tively, of each such part.
  • a second midpoint 21 between two said current valves of one part of the series connection is through a flying capacitor 22 connected to a second midpoint 23 of the other part of the se- ries connection corresponding to the first one with respect to the phase output.
  • the apparatus has also an arrangement 24 adapted to control the different semiconductor devices of the current valves 1-4 and thereby ensure that said phase output is connected to and receives the same potential as the pole 5, the pole 6 or any of said second midpoints 21 , 23, which for the midpoint 21 means the potential of the pole 6 having the voltage across the capacitor 24 added thereto and the midpoint 23 the voltage of the pole 5 having the voltage across the capacitor 22 subtracted therefrom.
  • the arrangement 24 and the connection thereof is very schematically shown here and a separate such arrangement should in the practice ,be arranged on high potential at each individual current valve and these will receive control signals from a control arrangement arranged on ground level.
  • the current valves are advantageously so designed that the time average of the voltage across the flying capacitor 22 will be a factor 0.2-0.5 the voltage between the two poles of the direct voltage side. This means that when this factor is less than 0.5 a higher voltage will be taken by the outer current valves 1 , 4 than the inner ones in the blocking state at the same time as four different levels are obtainable for the potential of the phase output 16.
  • a voltage set value curve may have such an appearance that it is most advantageous to have such levels being ununiformly distributed, since it results in lower switching losses exactly there.
  • the arrangement is adapted to control the semiconductor device of the current valves in the following way for obtaining a voltage according to the voltage set value curve in question (which the arrangement 24 gets as an input signal) on the phase line 19: the outer valves are controlled to turn off and turn on with a frequency close to the fundamental frequency of the alternating voltage of the alternating voltage phase line 19, which typically may be 50 Hz or 60 Hz, while the two inner current valves 2, 3 are controlled to turn on and turn off with a pulse width modulation pattern being at least an order of magnitude higher than the fundamental frequency, preferably 1 kHz - 2 kHz.
  • Fig 6 Reference is also made to Fig 6.
  • the arrangement 24 is, when the voltage set value is located between U dc /2 and (1 -k) x U dc /2, which corresponds to a value above a first level 25, adapted to alternatively make the two inner current valves 2, 3 conducting and continuously keep the outer current valve 1 closest to the positive direct voltage pole conducting and the other outer current valve 4 blocking.
  • the control arrangement makes alternatively the two inner current valves 2, 3 conducting and keeps the current valve 1 located closest to the positive direct voltage pole blocking and the opposite outer current valve 4 conducting.
  • the control arrangement makes one outer current valve 1 and the inner current valve 3 located on the opposite side of ' the phase output with respect thereto alternatively conducting and at the same time the other outer current valve 4 and the other inner current valve 2 blocking and conversely.
  • the two outer current valves 1 , 4 only switch within the time interval 27, which is located between the intersection points of the voltage set value curve with the two levels 25, 26.
  • a converter apparatus according to. a very preferred embodiment of the invention is shown in Fig 2 and this differs from the one according to Fig 1 by the fact that here a unit 28 for so called soft-switching of the inner current valves 2, 3 is arranged.
  • This unit is formed by snubber capacitors 29, 30 connected in parallel with the respective current valve as well as a resonance circuit for recharging these snubber capacitors for enabling turning on of the semiconductor devices of turn-off type of the current valves at a ⁇ low voltage thereacross.
  • An ARCP-circuit comprises more exactly an auxiliary valve 31 comprising two auxiliary valve circuits 32, 33 connected in series, which each comprises a semiconductor device 34 of turn-off type, such as an IGBT or a GTO, and a rectifying member 35 connected in anti-parallel therewith in the form of a diode, such as a free wheeling diode.
  • the semiconductor devices 34 of turn-off type of the two auxil- iary valve circuits are arranged in opposite polarity with respect to each other.
  • the ARCP-circuit comprises also an inductor 36 connected in series with the auxiliary valve circuits.
  • This auxiliary valve 31 constitutes a bi-directional valve, which may be brought to conduct in one or the other direction. It appears that the flying capacitor is here divided into two capacitors 37, 38, which together hold a voltage according to the factor k mentioned before times the voltage between the poles 5, 6. The function of this resonant circuit may be very briefly described. When for example the inner valve 3 conducts and the current flows from the phase output to the valve and this is controlled to turn off the current flowing into the phase output from the phase line is transferred directly to the two snubber capacitors 29 and 30 and the voltage increases slowly across the current valve 3, so that the current through the semiconductor device will man- age to get low before the voltage gets high and thereby the switching loss gets low.
  • the switching losses of the converter apparatus may be reduced further, at the same time as the cost for the resonance circuit may be made low, should the auxiliary valve circuits 32, 33 only need to handle a low voltage, which is the case when k is less than 0.5, such as 1/3, since the voltage to be handled thereby gets only U c /6-
  • the outer current valves 1 and 4 will in the practice switch with a fundamental tone frequency at normal stable SVC-operation, i.e. when the SVC is connected to an alternating voltage network with a sine shaped voltage and with a demand upon the converter apparatus to deliver a certain reactive power to or from the connecting network.
  • the voltage set value will a longer period of time be present in the voltage interval between the levels 25 and 26 (see Figs 4 and 5). It is then possible to let the valves 1 and 2 switch several times per period.
  • a higher content of harmonics may be transiently ac- cepted.
  • the voltage regulation of the flying capacitor gets simple thanks to the fact that the converter apparatus only operates with reactive power. As seen over half a period of the fundamental tone of the phase current .the charging of the capacitor will be equal to the discharging thereof, so that the capacitor voltage is naturally self-balancing.
  • a converter apparatus according to a third preferred embodiment of the invention is illustrated in Fig 3 and this differs from the one according to Fig 2 by having snubber capacitors 39, 40 connected in parallel also with the two outer current valves 1 , 4, so that the time derivative of the voltage is restricted and thereby the capacitive currents in a connected transformer are limited in connection with switching of the outer current valves 1 , 4.
  • These snubber capacitors could also be replaced by any other snubber member, such as a RC-circuit.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)
  • Inverter Devices (AREA)

Abstract

L'invention concerne un convertisseur de tension alternative en tension directe et inversement, utilisé dans un compensateur statique d'énergie réactive (SVC). Ce convertisseur comprend un côté à tension directe formé par un ou plusieurs condensateurs (7) suspendus, des vannes (1-4) montées en série et un condensateur flottant (22) monté en parallèle avec les deux vannes de courant intermédiaires (2, 3), et un agencement permettant de commander les vannes de courant pour générer un train d'impulsions avec des amplitudes déterminées en fonction d'un type de modulation d'impulsions en durée sur une sortie de phase (16) du dispositif. L'agencement (24) est conçu pour commander les dispositifs semi-conducteurs des vannes de courant intermédiaires (2, 3) afin de les mettre en position de marche ou d'arrêt avec un type de modulation d'impulsions en durée étant au moins d'un ordre de grandeur supérieur à la fréquence fondamentale de la tension alternative d'une ligne à tension alternative (19) reliée à la sortie de phase et pour commander les vannes de courant de sortie (1, 4) afin de les mettre en position de marche ou d'arrêt avec une fréquence sensiblement inférieure à ladite fréquence de modulation d'impulsions en durée et égale ou proche à la gamme de fréquences correspondant à une ou plusieurs fois ladite fréquence fondamentale.
PCT/SE2002/000975 2001-05-30 2002-05-22 Convertisseur et son procede de commande WO2002097960A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
SE0101877-9 2001-05-30
SE0101877A SE522427C2 (sv) 2001-05-30 2001-05-30 Omriktaranordning samt förfarande för styrning av en sådan

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Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2004082115A1 (fr) * 2003-03-14 2004-09-23 Abb Technology Ltd Convertisseur de source de tension et procede associe
WO2016109052A1 (fr) * 2014-12-30 2016-07-07 General Electric Company Procédé et appareil de commande de convertisseur de puissance à commutation logicielle multi-niveaux
EP1972485A3 (fr) * 2007-03-21 2016-08-24 Renk Aktiengesellschaft Agencement de commutation électronique de puissance pour un générateur à champ tournant

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0430044A2 (fr) * 1989-11-22 1991-06-05 Mitsubishi Denki Kabushiki Kaisha Méthode pour la régulation d'un onduleur
US5047913A (en) * 1990-09-17 1991-09-10 General Electric Company Method for controlling a power converter using an auxiliary resonant commutation circuit
WO1999040676A1 (fr) * 1998-01-27 1999-08-12 Abb Ab Convertisseur
EP1087512A2 (fr) * 1999-09-02 2001-03-28 ABBPATENT GmbH Convertisseur multi-points du type ARCP avec condensateurs intermédiaires à tension variable

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0430044A2 (fr) * 1989-11-22 1991-06-05 Mitsubishi Denki Kabushiki Kaisha Méthode pour la régulation d'un onduleur
US5047913A (en) * 1990-09-17 1991-09-10 General Electric Company Method for controlling a power converter using an auxiliary resonant commutation circuit
WO1999040676A1 (fr) * 1998-01-27 1999-08-12 Abb Ab Convertisseur
EP1087512A2 (fr) * 1999-09-02 2001-03-28 ABBPATENT GmbH Convertisseur multi-points du type ARCP avec condensateurs intermédiaires à tension variable

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2004082115A1 (fr) * 2003-03-14 2004-09-23 Abb Technology Ltd Convertisseur de source de tension et procede associe
EP1972485A3 (fr) * 2007-03-21 2016-08-24 Renk Aktiengesellschaft Agencement de commutation électronique de puissance pour un générateur à champ tournant
DE102007013462B4 (de) 2007-03-21 2018-08-09 Renk Ag Leistungselektronische Schaltungsanordnung für eine Drehfeldmaschine
WO2016109052A1 (fr) * 2014-12-30 2016-07-07 General Electric Company Procédé et appareil de commande de convertisseur de puissance à commutation logicielle multi-niveaux
US9467065B2 (en) 2014-12-30 2016-10-11 General Electric Company Method and apparatus for controlling a multilevel soft switching power converter

Also Published As

Publication number Publication date
SE522427C2 (sv) 2004-02-10
SE0101877L (sv) 2002-12-01
SE0101877D0 (sv) 2001-05-30

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