WO2002023704A1 - Circuit d'alimentation en energie destine a un circuit de commande d'un commutateur a semi-conducteur de puissance et procede pour mettre l'energie de commande a disposition d'un commutateur a semi-conducteur de puissance - Google Patents

Circuit d'alimentation en energie destine a un circuit de commande d'un commutateur a semi-conducteur de puissance et procede pour mettre l'energie de commande a disposition d'un commutateur a semi-conducteur de puissance Download PDF

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Publication number
WO2002023704A1
WO2002023704A1 PCT/DE2001/003329 DE0103329W WO0223704A1 WO 2002023704 A1 WO2002023704 A1 WO 2002023704A1 DE 0103329 W DE0103329 W DE 0103329W WO 0223704 A1 WO0223704 A1 WO 0223704A1
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WO
WIPO (PCT)
Prior art keywords
circuit
power semiconductor
voltage
capacitor
semiconductor switch
Prior art date
Application number
PCT/DE2001/003329
Other languages
German (de)
English (en)
Inventor
Benno Weis
Original Assignee
Siemens Aktiengesellschaft
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Siemens Aktiengesellschaft filed Critical Siemens Aktiengesellschaft
Publication of WO2002023704A1 publication Critical patent/WO2002023704A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H02M1/096—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices the power supply of the control circuit being connected in parallel to the main switching element
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
    • H03K2217/0081—Power supply means, e.g. to the switch driver

Definitions

  • the invention relates to a circuit arrangement for the energy supply for a control circuit of a power semiconductor switch with a series circuit electrically connected in parallel from a resistor and a first capacitor, which can be charged via the resistor, and with a parallel circuit from a second capacitor and a power consumer.
  • Power semiconductors offer the possibility of switching high electrical energy (e.g. in the kW or MW range) using a low control energy of a few watts.
  • the provision of control energy for power semiconductors in applications with high voltage is of great importance.
  • a cost-effective solution is the transmission through a transformer.
  • the alternating voltage for the transformer is generated by a switching power supply, for example from the intermediate circuit voltage of a converter for converter drives or from an auxiliary voltage.
  • this conventional solution is only suitable for transmission over relatively low voltage levels, since otherwise the required transformer will be very expensive. Above 40k volts, the problem of partial discharges can hardly be mastered.
  • Another known supply voltage circuit uses optical transmission by means of a laser diode and an energy converter: this solution is very cost-intensive and also has problems with regard to the lifespan of such a supply voltage circuit.
  • the transferable power is also limited to a range below 200mW.
  • Another known supply voltage circuit therefore uses the following principle of decoupling from the connection of the power semiconductor.
  • Such a circuit arrangement is known, for example, from the conference report "Novel Gate Power Supply Circuit Using Snubber Capacitor Energy for Series-Connected GTO Valves", printed in the conference volume EPE'97 Trondheim, pages 1,576 to 1,581.
  • FIG 7 A circuit arrangement for energy supply for a control circuit of a power semiconductor switch according to the preamble of claim 1 is shown in more detail in FIG 7.
  • a capacitor Cb and a resistor Rb form a series circuit 4 and, in conjunction with a diode Db electrically connected at node 6 of the series circuit 4, form a protective circuit 10 of the power semiconductor switch T.
  • the diode Db is closer to the cathode side in the following Overload contactor 11 explained with a parallel circuit 2 of a supply voltage capacitor C s and an electrical load - here in the form of a load resistor R L - electrically connected.
  • a supply voltage U C s drops at the supply voltage capacitor C s and is supplied to the control circuit of the power semiconductor switch T. For reasons of clarity this control circuit is not shown in detail.
  • the protective circuit 10 has the task of limiting the voltage rise to a predetermined value.
  • the voltage rise is limited by the capacitor Cb.
  • this capacitor Cb is discharged via the resistor Rb. Due to the required protective circuit 10, losses in the resistor Rb must be accepted with each switching operation. The power loss that arises is proportional to the switching frequency of the power semiconductor switch T.
  • the current that occurs through the protective circuit .10 of the power semiconductor T is conducted via the supply voltage capacitor C s on the control module (not shown) and charges it.
  • Overcharge protection or a voltage limiter circuit 11 is connected electrically in parallel with the supply voltage capacitor C s . If the supply voltage capacitor C s is overloaded, a protective thyristor TY is ignited, which takes over the wiring current. The thyristor is electrically connected in parallel with the opposite voltage diode D2 in a further series circuit 7 to the supply voltage capacitor C s , the node 8 of this series circuit 7 being electrically connected to the cathode-side connection of the diode Db. The control connection of the thyristor TY is electrically connected to the cathode-side connection of the diode D2 via a Zener diode Z.
  • this object is achieved in that a circuit arrangement for supplying energy for a control circuit of a power semiconductor switch according to the preamble of claim 1 is further developed in that a switching transformation means for transforming the energy stored in the first capacitor to the required voltage level of the second capacitor is provided, which is electrically connected on the input side to the first capacitor and which is electrically connected on the output side to the parallel circuit.
  • a voltage limiting device is arranged electrically in parallel with the first capacitor.
  • a diode which is polarized in the direction of flow is provided, which is preferably arranged between the resistor and the first capacitor or between the node comprising the resistor with the voltage limiting device and the first capacitor.
  • a particularly advantageous voltage limiting device has voltage detection means, a comparison means for comparing a measurement voltage with a reference voltage and a switching means for discharging the capacitor if the reference voltage is exceeded by the measurement voltage.
  • this is achieved in a particularly simple and cost-effective manner in that a voltage divider which is electrically connected in parallel with the first capacitor is used to determine the measurement voltage, which is applied to the non-inverting input of a comparator whose inverting input carries the reference voltage, the output of the comparator controlling a semiconductor switch which is electrically connected in parallel with a resistor to the first capacitor in parallel.
  • the comparison means or the comparator has a hysteresis according to a further advantageous embodiment of the invention.
  • a particularly compact structure can be achieved by the voltage supply of the comparison means or of the comparator from the voltage of the second capacitor, the supply voltage capacitor.
  • the output of the comparator can be electrically connected via a resistor to the connection of the first capacitor on the power semiconductor side.
  • the voltage limiting device has a Zener diode as a measuring means, which triggers a switching means for discharging the supply voltage capacitor.
  • circuit arrangement of the invention operation with pulse blocking and at the same time with greatly minimized power loss is possible by providing a protective circuit device between the power semiconductor switch and the series circuit, in particular by connecting the power semiconductor switch and the series circuit a further series circuit with a third capacitor and a downstream resistor is electrically connected in parallel and a transverse branch connecting the connection points of the two series circuits is provided, which has a diode which is polarized in the direction of flow.
  • a plurality of power semiconductor switches which are electrically connected in series can be operated particularly effectively with a respectively associated circuit arrangement according to the invention for the energy supply for a control circuit of this power semiconductor switch if each power semiconductor switch has a resistor connected in parallel and the electrical series connection of these resistors is used for the static balancing of the reverse voltages of the power semiconductor switches, in that each balancing resistor is used to charge the respective first capacitor of the associated circuit arrangement. It has proven to be particularly advantageous if the switching power supply or the switching regulator is operated with the highest possible input voltage, as a result of which the input current and the power loss associated therewith is minimized.
  • the overall circuit with a plurality of power semiconductor switches electrically connected in series, each with a circuit arrangement according to the invention, can also advantageously be used to transmit electrical energy (HVDC).
  • HVDC electrical energy
  • FIG. 1 shows a circuit arrangement according to the invention
  • FIG. 2 shows the basic structure of a switching power supply
  • FIG. 3 shows a circuit arrangement according to the invention with an additional limiting circuit
  • FIG. 4c shows a modified arrangement of the series diode
  • FIG. 5 shows a circuit arrangement according to the invention with supply from the balancing and an additional circuit
  • FIG. 6 shows a bridge branch of a converter circuit with a number of series connections
  • two 'and FIG. 7 shows a circuit arrangement for energy decoupling from a circuit network according to the prior art
  • a series circuit 1 comprising a resistor R s and a capacitor Cl of the collector-emitter path is electrically connected in parallel to a power semiconductor switch T.
  • the series circuit 1 additionally has a diode D s which is polarized in the direction of flow and which is arranged between the resistor R s and the first capacitor Cl.
  • the diode D s serves to prevent the capacitor Cl from discharging via R s when the power semiconductor T is switched on. It must be able to block the voltage of the capacitor C1.
  • the capacitor Cl is charged by the resistor R s parallel to the power semiconductor.
  • the resistor R s is for applications with a high reverse voltage and thus series circuit of power semiconductor devices anyway balancing the static voltage required (see FIG. 'FIG 6). Besides, one is
  • Parallel circuit 2 is provided from a second capacitor C s and a power consumer R L , which represent the - not shown - control circuit for the power semiconductor T.
  • a switched-mode power supply SNT or another switching trans ormation means is connected electrically in parallel with Cl, which is electrically connected on the output side to the parallel circuit 2 and transforms the energy to the voltage level of C s . This ensures that the load R L is adequately supplied and that R s only the symmetry flow II flows.
  • Switched-mode power supplies are clocked power supplies, i.e. they "chop" a DC voltage. It is essential for the mode of operation of the switched-mode power supply SNT that a semiconductor element, for example a transistor, works exclusively as a switch S. This results in only switching losses and transmission losses, which results in a high efficiency of a clocked power supply compared to others Process results.
  • a rectified input voltage Ucl is chopped by the switch S, which results in an AC voltage Uz of rectangular, trapezoidal or occasionally sinusoidal shape.
  • Regulation via the switch S usually a discrete MOSFET transistor, takes place via a control logic ST either by changing the duty cycle T with a constant frequency of the AC voltage Uz, or by changing the frequency with a fixed or variable duty cycle T.
  • the voltage Uz chopped in this way can be transformed into any other voltage by transmitting the power via a transformer U and rectifying the voltage via a subsequent rectifier G. This results in the desired converted DC voltage, here U C s.
  • the transformer U also serves for a desired network separation.
  • the control loop is closed by feeding this rectified output voltage U C s to a control amplifier RV, which is connected on the output side for potential isolation, for example, to an optocoupler P, via which the control logic. ST is controlled.
  • the voltage profiles of the described components of the switched-mode power supply SNT resulting on the output side are illustrated in the form of a diagram of the voltage U over time t. If a switching power supply is not connected to the mains, but connected to a direct current source, one speaks of a "switching regulator". A simple step-down converter is also possible.
  • Such switching power supplies or switching regulators are characterized, among other things, by a very high degree of efficiency of up to 90%, good control dynamics and voltage constancy as well as low volume and weight.
  • the switched-mode power supply SNT is expediently to be operated with the highest possible input voltage U C ⁇ in order to be able to work with a given power in R L with a minimum input current II. Since - as mentioned - a discrete MOSFET transistor is usually used in the switched-mode power supply SNT, this input voltage is limited to a level of approximately 1500 V. If the reverse voltage of the power semiconductor T1 is below this level, the switched-mode power supply can also be connected in parallel in a series connection directly to the power semiconductor T from FIG.
  • Q denotes the efficiency of the switching power supply.
  • Capacitor voltage Ucl rise This is practically always the case with correct dimensioning, since both the load and the energy fed in change with the operating conditions and the above inequality (1) must be fulfilled at all times.
  • a limiting circuit B for Cl is after the representation according to FIG 3 advantageous. This is connected in parallel to the capacitor C1.
  • FIG. 4a A basic embodiment of the limiting circuit is shown in FIG. 4a.
  • the voltage at Cl is measured via a voltage detection device from a voltage divider 3 with resistors R3, R4.
  • This measuring voltage Um is compared with a reference voltage Uref.
  • the measuring voltage Um is applied to the noninverting input + of a comparator K, the inverting input - leads the reference voltage Uref, the output of the 'comparator K drives a semiconductor switch Tx.
  • the latter is electrically connected in parallel with the capacitor C1 in series with a resistor R2.
  • the switch Tx e.g. a transistor, switched on and C1 discharged via the further resistor R2 electrically connected in series with the switch Tx. If the voltage at Cl drops as a result, the transistor Tx is switched off again.
  • the comparator K is expediently provided with a hysteresis in order to limit the switching frequency of Tx. This can e.g. by switching a part of the output voltage of the comparator to the reference voltage Uref.
  • the voltage supply of the comparator K advantageously takes place from the supply voltage capacitor Cs. Since Cl and thus Cs are still uncharged when the circuit starts up, in this case the comparator K also has no supply voltage.
  • Another resistor R5 which is connected between the output of the comparator K and the emitter of the transistor Tx, reliably switches off the transistor Tx in this operating state. This makes it possible to charge the capacitor C1.
  • the illustration according to FIG. 4b shows a simpler alternative to voltage limitation.
  • the voltage of the supply voltage capacitor Cl is limited here by triggering the switching means Tx via a Zener diode Dxl, which, together with another Zener diode Dx2, both of which are connected in series in the reverse direction, forms a voltage divider 3 'which is connected in parallel with the supply voltage capacitor Cl ,
  • connection point of this voltage divider 3 ' is electrically conductively connected to the control connection of the switching means Tx.
  • the Zener diode Dxl is also connected in series with a resistor Rxl, which limits the current through Dxl.
  • the Zener diode Dx2 limits the voltage at the control input of the switching means Tx, provided that this is a field-controlled component (e.g. a MOSFET or an IGBT).
  • a resistor Rx2 electrically connected in parallel with the Zener diode Dx2 prevents parasitic positive charging of the control connection or gate of Tx.
  • the switching means Tx is a bipolar transistor
  • Zener diode Dx2 is eliminated.
  • the resistor Rx2 then discharges leakage currents from Dxl.
  • FIG. 4c now shows a further advantageous variant of the inclusion of the voltage limiting circuit B.
  • a lower switching frequency of the switching means Tx can be achieved.
  • the switching means Tx and the resistor R2 are electrically connected not only to the supply voltage capacitor Cl, but also to the series diode Ds. This variant is advantageous because when the switching means Tx is switched on, the supply voltage capacitor Cl is not discharged via the resistor R2.
  • FIG. 5 shows a circuit variant which can be used when the principle described according to the invention is to be used, although one additional switch-off relief 10 of the type described at the outset based on the prior art according to FIG.
  • a further series circuit 4 with a further capacitor Cb and a downstream resistor Rb is then electrically connected in parallel between the power semiconductor switch T and the series circuit 1.
  • the connection points 5 and 6 of the two series circuits 1 and 4 are connected by a shunt arm 9 from a diode Db polarized in the direction of flow.
  • the energy from the circuit 10 is then used in addition to the energy from the balancing R s for the supply it. This avoids the disadvantage of the prior art that the circuit only works in pulse mode.
  • the circuit variant shown in FIG. 5 can then also be used when the pulse is inhibited (for example when starting a converter drive).
  • FIG. 6 serves to illustrate the integration of the circuit arrangements according to the invention described above in a converter and the already mentioned problem of balancing.
  • Each circuit breaker is realized by two power semiconductor switches T1, T2 and T3, T4 connected in series. Since only two power semiconductor switches are used here per circuit breaker, there is a series connection number of 'two' for the converter.
  • Each power semiconductor switch Tl to T4 has a free Running diode DFl to DF4 and a resistor R S ⁇ to R s4 on, which is followed by a supply voltage circuit according to the invention, which is used to supply a respective control circuit AI to A4 assigned to the power semiconductor switch Tl to T4.
  • the level of the intermediate circuit voltage U z ⁇ on the input side is limited by the blocking capability of a power semiconductor switch Tl to T4.
  • a voltage U CEI to U CE 4 drops at each power semiconductor switch T1 to T4.
  • the respective voltage U CEI is to U CE4 above each power semiconductor switch Tl to T4 due to the series connection number of, z ⁇ two 'half of the intermediate circuit voltage U.
  • the intermediate circuit voltage U z ⁇ can be designed for twice the operating voltage of a power semiconductor switch Tl to T4.
  • the resistors R s ⁇ to R s4 are used for the static balancing of the blocking voltages U CEI to U CE4 via each power semiconductor switch Tl to T4. If these all block, for example when the DC link voltage U z ⁇ starts up , the load tap L is at a potential of U Z ⁇ / 2. In continuous-off operation, the operating voltage across each circuit breaker Tl to T4 with a series connection number of 'two' is equal to U z ⁇ / 4.
  • the energy for charging the supply voltage capacitor C s can now be obtained from the respective balancing resistor R S ⁇ to R s without a separate connection of the power semiconductor switch Tl to T4 being necessary.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

Afin de minimiser la puissance dissipée dans l'alimentation en énergie d'un circuit de commande pour un commutateur à semi-conducteur de puissance (T), une alimentation à découpage (SNT) ou un autre système de transformation de commutation, dont la sortie est électriquement connectée à un condensateur à tension d'alimentation CS, sont électriquement connectés en parallèle à un condensateur C1 et transforment l'énergie d'entrée au niveau de tension de CS. La charge RL (circuit de commande) est ainsi suffisamment alimentée et seulement le courant d'équilibrage (I1) absolument nécessaire circule à travers la résistance d'équilibrage RS d'un commutateur à semi-conducteur de puissance (T).
PCT/DE2001/003329 2000-09-12 2001-08-30 Circuit d'alimentation en energie destine a un circuit de commande d'un commutateur a semi-conducteur de puissance et procede pour mettre l'energie de commande a disposition d'un commutateur a semi-conducteur de puissance WO2002023704A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE10045093.8 2000-09-12
DE10045093A DE10045093A1 (de) 2000-09-12 2000-09-12 Schaltungsanordnung zur Energieversorgung für eine Ansteuerschaltung eines Leistungshalbleiterschalters und Verfahren zur Bereitstellung der Ansteuerenergie für einen Leistungshalbleiterschalter

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WO2002023704A1 true WO2002023704A1 (fr) 2002-03-21

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WO (1) WO2002023704A1 (fr)

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2013000500A1 (fr) * 2011-06-27 2013-01-03 Abb Technology Ag Bloc d'alimentation permettant de contrôler un interrupteur d'alimentation
EP3285380A1 (fr) * 2016-08-17 2018-02-21 General Electric Technology GmbH Équilibrage de tension pour des convertisseurs de source de tension
WO2019192675A1 (fr) * 2018-04-03 2019-10-10 Siemens Aktiengesellschaft Ensemble circuit et module redresseur ayant des interrupteurs à semi-conducteurs montés en série
WO2020058212A1 (fr) * 2018-09-18 2020-03-26 Siemens Aktiengesellschaft Dispositif de commutation destiné à couper un circuit de courant

Families Citing this family (6)

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FR2843247B1 (fr) * 2002-07-30 2004-11-19 Inst Nat Polytech Grenoble Dispositif d'alimentation d'un element de commande d'un composant electronique de puissance actif.
US8253394B2 (en) 2004-02-17 2012-08-28 Hewlett-Packard Development Company, L.P. Snubber circuit
KR101287711B1 (ko) 2009-06-16 2013-07-19 지멘스 악티엔게젤샤프트 제어 회로를 위한 전력 스위치와 병렬 연결된 전력 공급기
DE202012012080U1 (de) 2012-12-18 2014-03-24 Joachim Baum Energieversorgung Gatesteuerstufe
DE102014213068B4 (de) * 2014-07-04 2020-08-20 Siemens Aktiengesellschaft Schaltungsanordnung und Verfahren für ein Schaltnetzteil
CN104135141B (zh) * 2014-08-15 2017-05-03 上海理工大学 一种用于串联igbt动态均压控制的取能电路

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EP0573836A2 (fr) * 1992-06-10 1993-12-15 Hitachi, Ltd. Convertisseur de puissance électrique
WO1994018687A1 (fr) * 1993-02-01 1994-08-18 Electric Power Research Institute, Inc. Appareil et procede de commutation de niveaux de puissance eleves
EP0868014A1 (fr) * 1997-03-24 1998-09-30 Asea Brown Boveri Ab Convertisseur de haute tension

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US5453665A (en) * 1994-07-20 1995-09-26 Motorola, Inc. Single transistor electronic ballast

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EP0573836A2 (fr) * 1992-06-10 1993-12-15 Hitachi, Ltd. Convertisseur de puissance électrique
WO1994018687A1 (fr) * 1993-02-01 1994-08-18 Electric Power Research Institute, Inc. Appareil et procede de commutation de niveaux de puissance eleves
EP0868014A1 (fr) * 1997-03-24 1998-09-30 Asea Brown Boveri Ab Convertisseur de haute tension

Cited By (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2013000500A1 (fr) * 2011-06-27 2013-01-03 Abb Technology Ag Bloc d'alimentation permettant de contrôler un interrupteur d'alimentation
US8767420B1 (en) 2011-06-27 2014-07-01 Abb Technology Ag Power supply for controlling a power switch
EP3285380A1 (fr) * 2016-08-17 2018-02-21 General Electric Technology GmbH Équilibrage de tension pour des convertisseurs de source de tension
WO2018033434A1 (fr) * 2016-08-17 2018-02-22 General Electric Technology Gmbh Équilibrage de tension de convertisseurs de sources de tension
WO2019192675A1 (fr) * 2018-04-03 2019-10-10 Siemens Aktiengesellschaft Ensemble circuit et module redresseur ayant des interrupteurs à semi-conducteurs montés en série
CN111919386A (zh) * 2018-04-03 2020-11-10 西门子股份公司 具有串联连接的半导体开关的电路装置和变流器模块
US11283440B2 (en) 2018-04-03 2022-03-22 Siemens Energy Global GmbH & Co. KG Circuit arrangement and power converter module having semiconductor switches connected in series
CN111919386B (zh) * 2018-04-03 2024-01-19 西门子能源全球有限公司 具有串联连接的半导体开关的电路装置和变流器模块
WO2020058212A1 (fr) * 2018-09-18 2020-03-26 Siemens Aktiengesellschaft Dispositif de commutation destiné à couper un circuit de courant

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