WO2001063735A1 - Power converter mode transistioning method and apparatus - Google Patents
Power converter mode transistioning method and apparatus Download PDFInfo
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- WO2001063735A1 WO2001063735A1 PCT/US2001/005781 US0105781W WO0163735A1 WO 2001063735 A1 WO2001063735 A1 WO 2001063735A1 US 0105781 W US0105781 W US 0105781W WO 0163735 A1 WO0163735 A1 WO 0163735A1
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- mode
- control device
- linear regulator
- control loop
- current control
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1588—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load comprising at least one synchronous rectifier element
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0045—Converters combining the concepts of switch-mode regulation and linear regulation, e.g. linear pre-regulator to switching converter, linear and switching converter in parallel, same converter or same transistor operating either in linear or switching mode
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention provides a method and apparatus for transitioning a power converter between a switched mode of operation and a linear regulator mode of operation in a single power converter.
- An intermediate mode of operation and associated circuitry is provided that allows the switched mode and linear regulator mode to cooperate to produce a shared power converter output having reduced noise and voltage ripple as compared to a converter that is alternating between switched mode and fully-on modes of operation.
- Figure 1 is a schematic diagram of a switched mode power converter circuit in accordance with the buck topology
- Figure 2 is a schematic diagram of a linear regulator circuit
- Figure 3 is a schematic circuit diagram of a preferred embodiment of the present invention
- Figure 3A is a schematic circuit diagram of a PWM control loop integrator for a preferred embodiment of the present invention.
- Figure 4 is a schematic block diagram of a most preferred embodiment of the present invention in which unwanted effects caused by the presence of a double pole are reduced;
- Figure 5A is a Cartesian bode plot diagram illustrating the open loop frequency response showing double pole effects ;
- Figure 5B is a Cartesian bode plot diagram illustrating the open loop frequency response of a preferred embodiment of the present invention after reduction of the double pole effects ;
- Figure 6A is a state diagram description of transition from switched mode to intermediate modes of operation
- Figure 6B is a state diagram description of transition from switched mode or LDO mode to a second intermediate mode or PWM mode of operation
- Figure 6C is a state diagram description of transition from switched mode or an intermediate mode to LDO mode of operation; and Figure 6D is a state diagram description of transition from LDO mode to an intermediate mode of operation.
- the power requirements of a portable electronic device determine the useful battery life.
- the power requirements of the circuitry comprising a given portable electronic device form a critical engineering design parameter. Advances in the state of the art have resulted in the availability of components capable of operating at increasingly lower voltage and current specifications, but these components require correspondingly tighter tolerances. While allowed to vary within specified tolerances, the voltage requirements of the circuitry of a portable electronic device remain constant over time. This circuit input voltage must remain within the specified tolerances in order for the device circuitry to function reliably.
- the voltage available from the power source such as a battery
- the voltage available from the power source varies over time due to a variety of factors including dissipation over time of the charge maintained by the battery (discharge of the battery causes supply voltage to drop) , temperature and other external environmental conditions, and contact corrosion.
- a power converter device In order to provide a constant supply of voltage to the device circuitry within the specified required tolerances, a power converter device is typically used.
- the power converter takes the power source voltage as an input and converts it to and maintains it at the desired output voltage signal .
- the power converter further typically includes circuitry to regulate the power converter output within the specified device circuitry input voltage tolerances for wide deviations in the power source signal .
- the power converter output signal is said to be in regulation when provided within the specified circuit input voltage tolerances. Because the components of the power converter device also dissipate power, it is desirable that the power converter be designed to function as efficiently as possible in regulating its output. The less efficient (in terms of power dissipation) the power converter, the faster the power source will be dissipated, and the useful life of the portable electronic device for a given battery charge will be shortened proportionately.
- Switch-mode power supplies are used to convert a varying source voltage (such as that provided by a battery power source as it is discharged over time) to a higher or lower controlled voltage output.
- the switching action of the converter converts the DC voltage provided by the power source into an AC signal in the form of a square wave, which is then filtered to remove the high frequency components and create a regulated DC output voltage.
- the control signals are modulated to control the transfer of power from the input of the power converter to its output, and to regulate the output voltage to the desired value.
- switch mode power converter consist of the power switch devices, an inductor and capacitor for energy storage and filtering, and a feedback/control circuit to modulate the switch timing to regulate the output voltage.
- a switch mode power converter can be created by connecting these elements in different configurations.
- a buck converter In order to generate a given output voltage, a buck converter requires a minimum input voltage. If the input voltage is too low, the power converter will not be able to
- Equation 1 The required minimum differential voltage is approximated by Equation 1 :
- the power train elements are the elements through
- Dmax is the maximum duty cycle at which the converter can
- LDO low dropout
- a linear regulator an example of which is shown in Figure 2
- LDO low dropout
- a linear regulator can operate at a smaller input-output differential voltage, often less than lOOmV, depending on the rated output current.
- the efficiency at high differential voltages is poor, but at low differential voltages, the efficiency of a linear regulator can approach that of a switch mode regulator.
- the efficiency of a linear regulator is approximated by equation
- the switch-mode regulator has the advantage of operating at a higher (compared to the linear regulator) efficiency level when the difference between the input and output voltages are large, but cannot operate correctly at low differential voltages.
- the linear regulator has the advantage of operating at a lower differential voltage, but is not as efficient when operating at high differential voltages.
- a switch-mode power converter can operate more efficiently at a higher input-output differential voltage, and a linear regulator can operate more efficiently at a smaller input -output differential voltage, providing a single power converter that includes both modes allows for efficient power conversion for both large and small voltage differentials.
- this is accomplished as follows: When the battery is fully charged, and the battery voltage is high, the combined converter operates in switching mode. As power is pulled from the battery, the battery voltage decreases, and eventually drops below the critical input voltage required for correct operation in switched mode. If the battery voltage drops below this voltage, the output of the converter will drop out of regulation, and the circuitry powered by the converter may fail to function properly.
- the converter according to the present invention switches to the linear mode of operation, and continues to maintain the correct output voltage, extracting more power from the battery and extending the time between required recharge cycles .
- Other power converters approach this goal, but do not implement a true linear regulator mode in a single integrated power converter.
- a power converter can simulate linear regulator mode operation when, for example, the input -output differential voltage becomes too small thus requiring a duty cycle larger then "Dmax. "
- a power converter can implement a mode in which the device "ml" as shown in Figure 1 is switched to its fully “on” state and then maintained in its “on” state, instead of being switched between "on” and “off” states. If the switch ml remains in its "on” state for a duration long enough to reach steady state condition, the output voltage of the converter will be defined by Equation 3.
- Vout Vi n - (R ml * I 0 ut) Equation 3 where: R m ⁇ is the resistance of ml in the "on" state, and I 0 u t is the load current.
- this output voltage is less than or equal to the desired power converter output voltage (which will occur at very small input-output differentials) , then a stable condition results. If, however, the output voltage is above the desired power converter output voltage, then such a converter must cycle between the "switched” and “fully-on” modes of operation in order to regulate the output voltage. In other words, the converter will "switch” for a number of cycles as the output voltage falls below a set point, and then the converter will leave the switch in the "on” state for a period of time as the output voltage is pulled above the set point. The ratio of the time spent in each mode will vary based on input voltage, output voltage, and load current .
- the condition in which the output voltage in the steady-state "fully-on” mode is lower than the desired output voltage corresponds to a required duty cycle greater than 100%.
- the condition in which the converter must alternate between "fully-on” and “switched” modes corresponds to a required duty cycle greater than "Dmax" but less than 100%.
- the ripple voltage on its output is higher than in normal operation in either its "switched” mode or "on” state.
- the converter will generate noise over a range of varying frequencies.
- the frequency of the mode alternating also described as the burst frequency, can fall within the audio range and cause unwanted sound artifacts in the device circuitry due to the mode switching noise .
- FIG. 3 provides a schematic circuit diagram of a preferred embodiment of a converter according to the present invention.
- a converter 100 includes a Low Dropout controller (LDO) 105, a Pulse Width Modulation controller (PWM) 104, current control devices 101-103, a feedback signal 106, a mode controller 109, a reference generator 110, and various passive components including an inductor L, Capacitor C, and resistors Rl and R2.
- LDO Low Dropout controller
- PWM Pulse Width Modulation controller
- the control signal for current control device 102 is controlled by the output of LDO 105.
- the control signal for current control device 103 is controlled by the output of PWM 104.
- the control signal for current control device 101 is controlled by the outputs of LDO 105 or PWM 104.
- Mode controller 109 determines which block has control of current control device 101 at any given time, so that LDO 105 and PWM 104 do not try to control current control device 101 at the same time.
- LDO 105 and PWM 104 determine their respective outputs in response to the voltage differential between a reference signal, provided by reference generator 110, and feedback signal 106.
- the error signal input of feedback signal 106 is determined by stepping down the converter 100 output voltage, Vout , using the series resistor arrangement of Rl and R2 as shown in Figure 3.
- Mode controller 109 includes logic to control the operation of PWM 104 and LDO 105 by controlling the outputs of reference generator 110 and mode control signals to PWM 104 and LDO 105 in order to transition converter 100 between switched and
- PWM 104 further includes a PWM control loop integrator 120 and PWM control logic 125.
- PWM control loop integrator 120 preferably includes an operational amplifier integrator circuit as shown in Figure 3A. Use of an operational amplifier integrator circuit provides for increased DC gain which in turn provides improved steady state accuracy of the PWM control loop.
- PWM control loop integrator 120 resistor and capacitor components may be chosen to shape the frequency response of the feedback circuit to match that of the circuit under control. The time required for the operational amplifier to generate the required voltage across the feedback capacitors of PWM control loop integrator 120 is a function of the capacitor values and the maximum output current of the amplifier.
- Current control devices 101 and 103 are used in a switched mode control loop in which converter 100 produces a DC output voltage, Vout, under PWM 104 control.
- current control devices 101, 102 and 103 are metal oxide semiconductor field effect transistors (MOSFETs) , as indicated by Ml, M2 and M3 , respectively, in Figure 3.
- MOSFET Ml is preferably used as the main switch and MOSFET M3 is preferably used as the synchronous rectifier.
- Current control device 101 is also used as the pass device when converter 100 is in linear regulator mode. Referring again to Figure 3, operation of converter 100 is described as follows. When the input voltage, Vin, from the power source drops below a level necessary for efficient switched mode operation, converter 100 transitions to a linear regulator mode of operation.
- current control devices 101 and 102 are preferably used as pass devices instead of switches .
- the control signals for current control devices 101 and 102 are modulated in an analog fashion to vary the effective resistance of current control devices 101 and 102, thereby controlling the voltage dropped across current control devices 101 and 102.
- the gates of MOSFETs Ml and M2 are modulated in an analog fashion to vary the effective resistance of the devices, thereby controlling the voltage dropped across MOSFETs Ml and M2.
- converter 100 can produce a regulated output voltage, Vout, without alternating between modes of operation. This prevents generation of excessive voltage ripple and noise otherwise associated with alternating between switched and linear modes of operation.
- a single integrated current control device 101 operates as either a switch or a variable resistance device (i.e., a device which can be controlled to drop varying amounts of voltage across the device) in order to support different modes of operation for converter 100.
- the optimum size of MOSFET Ml required for switched mode operation is smaller than that required for linear mode.
- additional MOSFET area needs to be added to reduce the series resistance of the pass device.
- This extra MOSFET is represented by M2.
- the location of the second current control device 102 between the input and the output nodes allows two significant problems to be solved. These two problems can be summarized as: (1) The effect of the pole doublet due to the LC filter, which increases the difficulty of compensating the feedback loop of the linear regulator portion of converter 100; and (2) The delay associated with the stabilization of the PWM control loop integrator 120, which causes large output transients during the transition from linear to switching mode.
- converter 100 requires a inductor L and capacitor C arranged as an LC filter in the switched mode control loop for operation in switched mode operation including, but not limited to, pulse width modulation (PWM) or pulse skipping mode (PSM) .
- PWM pulse width modulation
- PSM pulse skipping mode
- the LC filter is coupled to the LDO 105 feedback loop.
- the inductor L and capacitor C introduce two additional poles into the feedback path of the linear regulator control loop. The presence of these additional poles increases the difficulty of effecting frequency compensation of the linear regulator control loop. In particular, very large capacitor values are required which have as a consequence unacceptable transient response on the control of the output voltage.
- feedback signal 106 includes an error amplifier 107 and a buffer 108.
- Error amplifier 107 receives a raw error signal, which is the stepped down output voltage, Vout, produced from the series resistor arrangement of Rl and R2 , and a reference signal and produces an amplified error signal with amplitude dependent upon the difference between the raw error signal and the reference.
- Buffer 108 receives the amplified error signal from error amplifier 107 and provides a buffered error signal to current control devices 101 and 102. The effect of the two poles introduced by the LC filter is overcome by making feedback signal 106 current flow predominantly through current control device 102 to the exclusion of current control device 101 for the high frequency components of the feedback control signal 106.
- this is accomplished by: (1) Introducing a resistor, Rm, in series with current control device 101 (which is acting as the main power device) , that in combination with the parasitic input shunt capacitance, Cp, of current control device 101, creates a dominant pole, and (2) Coupling current control device 102 to the output of converter 100 after the LC filter.
- resistor Rm is placed in series with the gate of Ml only when Ml is operating in active mode, i.e. not as a switch.
- a stable closed loop configuration is achieved by providing error amplifier 107 with a very low frequency dominant pole in order for the open loop frequency response to reach the unity gain value (OdB) , fu, before encountering the double pole at the resonant frequency, f LC , of the LC filter.
- OdB unity gain value
- the crossover frequency determined by the dominant pole is inversely proportional to the value of the capacitor used for the compensation.
- a relatively higher capacitance C is required to lower the unity gain frequency f with respect to the resonant frequency f LC , as shown in Figure 5A.
- the total required capacitance value to be introduced in order to counteract the effect of the double pole is preferably at least 10 nanofarads.
- a capacitor is added to an IC implementation having the desired capacitance value.
- shunt capacitance increases as the surface area increases (for example, the gate size of the logic implementing current control device 101) .
- IC surface area e.g., Silicon area
- This alternative is therefore limited in terms of practical use because of the prohibitive cost in terms of Silicon area (i.e., "chip real estate" ) .
- external components e.g., external to an IC are used to provide the desired dominant pole at a lower frequency.
- the parasitic capacitance already present from current control device 102 is used to contribute to the total capacitance required, in order to conserve IC surface area.
- the frequency behavior of the open loop gain of this preferred embodiment is shown in Figure 5B .
- converter 100 provides control loop stability with the same phase margin (PM) using compensation capacitors that are orders of magnitude smaller that can be integrated on chip. Further, the transient response of the system is not overly penalized. Finally, the area occupied by the extra transistor M2 is needed anyway, because the optimum size of Ml for switching operation is in general smaller (40%) than the optimum size needed in LDO mode. In a preferred embodiment, this extra area is provided by M2.
- PWM 104 of the switched mode control loop further includes an integrator to increase the DC gain of the system and to improve DC regulation of converter 100.
- the integrator also allows the use of a smaller output filter capacitor, C, than would be possible if only broadband gain was used in the switched mode control loop.
- the presence of the integrator requires a finite amount of time for the PWM 104 error voltage (i.e., the output of PWM control loop integrator 120) to settle to the correct value to regulate the output voltage.
- the error voltage settles to an initial voltage during startup. Once converter 100 is running, the error voltage only needs to move far enough to adjust for line and load variations, which is usually small compared to the overall error voltage range.
- converter 100 When converter 100 switches between linear regulator mode and switched mode, the correct value of the error voltage is indeterminate.
- the switched mode control loop has been disabled, and as a result PWM control loop integrator 120 is not at the correct voltage to correctly regulate the output.
- Converter 100 must slew the error voltage to the correct value before the output will be regulated to the desired voltage. If the error amplifier is designed with the slew rate necessary for this situation it will have a higher slew rate capability (and draw more power) than necessary during normal operation.
- converter 100 of the present invention solves the problem a different way. Instead of switching directly from the linear regulator control loop to the switched mode control loop, converter 100 switches through an intermediate mode in which both the linear regulator control loop and the switched mode control loop share control of the output voltage. Referring again to Figure 3, the transition method of the present invention is described as follows:
- the switched mode loop is enabled, and the linear regulator loop releases control of current control device 101.
- the linear regulator loop continues to regulate the output voltage by retaining control of current control device 102.
- the linear regulator loop can source current into the load, but cannot sink current from it.
- the linear regulator loop can prevent the output from dropping below a set voltage; however, if the switched mode loop drives the output above that voltage, all the linear regulator loop can do is turn off current control device 102.
- PWM 104 of the switched mode control loop is set to regulate to a slightly higher than desired voltage
- LDO 105 of the linear regulator control loop is set to regulate to a slightly lower than desired voltage. This is accomplished by modifying the reference voltage supplied to the two loops.
- the integration capacitor in the switched mode control loop is initially discharged. 2) Once the switched mode control loop is enabled, PWM 104 senses that the output is below the desired voltage and begins to charge the integrator capacitor to raise the error voltage and increase the output power. The linear regulator control loop prevents the output voltage from dropping below its modified setpoint (which is slightly below the modified setpoint of the switched mode control loop) . 3) Eventually, the error voltage reaches the level that corresponds to the output voltage supported by the linear regulator control loop. As the error voltage increases beyond that point, the switched mode control loop takes over from the linear regulator control loop, and the output voltage begins to increase. When the linear regulator control loop sees that the output is above its modified set point, LDO 105 begins to turn off current control device 102.
- the LDO 105 When the switched mode control loop has raised the output voltage far enough above the linear regulator control loop's modified setpoint, the LDO 105 fully turns off current control device 102. A signal from the LDO 105 alerts mode controller 109 that the current through current control device 102 has dropped to zero, indicating that the linear regulator control loop can be shut down, and control can be passed completely to the switched mode control loop. At this point, the PWM 104 integration capacitor has been precharged to the correct value and the error voltage is at the correct level to regulate the output voltage.
- PWM 104 of the switched mode control loop is set to regulate to the correct output voltage.
- mode controller 109 is implemented in accordance with the logic state diagrams described in Figures 6A, 6B, 6C and 6D. Mode transition of converter 100 is accomplished in accordance with state transition logic executed by mode controller 109 and described as follows.
- converter 100 provides a variety of operating modes including primary modes of operation and transition or intermediate modes of operation.
- Primary modes include, but are not limited to, a switched mode (e.g., PWM mode) and a linear regulator mode (i.e., LDO mode) .
- Intermediate modes of operation include, but are not limited to, a "share_PWM” mode and a "share_LDO” mode.
- PWM mode corresponds to the switched mode operation of converter 100.
- PWM mode is characterized by current control device 101 being switched between its "on” and “off” states.
- the output voltage, Vout, of converter 100 is determined by the duty cycle of current control device 101, where duty cycle is defined as the ratio of "on” time to the total switching period.
- PWM mode is controlled by modulating the duty cycle of current control device 101.
- Switched mode operation also includes, without limitation, Pulse Skipping Mode (PSM) , in which current control device 101 is switched at a variable frequency instead of a fixed switching frequency as in PWM mode. Further, current control device 101 may cease to be switched for a certain period of time, at the end of which time switching is resumed.
- PSM mode Vout is controlled by modulating the switching frequency of current control device 101.
- LDO mode corresponds to linear regulator mode as described herein.
- Share_PWM mode is an intermediate mode of operation that defines converter 100 operational state during transitions between PWM and LDO modes.
- PWM 104 regulates converter 100 output voltage to the desired value and LDO 105 cooperates in regulating Vout by preventing Vout from falling below a nominal range.
- LDO 105 prevent Vout from falling below -2% of the desired output voltage. Other ranges are supported as well.
- Share_LDO is an intermediate mode of operation that defines converter 100 operational state during transitions from Share_PWM mode to LDO mode and from PWM to LDO mode.
- LDO 105 regulates converter 100 output voltage to the desired value and PWM 104 ramps down the current flowing through inductor L.
- Transition from PWM mode to LDO mode can be initiated by one of several triggers .
- VinLow Input voltage
- mode controller 109 operating in switched mode, or pulse width modulation (PWM) mode (block 201) , transitions converter 100 operating mode to Share_PWM mode (block 203) or Share_LDO mode (block 205) in response to changes in the states of certain parameters .
- PWM pulse width modulation
- mode controller 209 transitions converter 100 from PWM mode to Share_PWM mode of operation (block 203) .
- the feedback circuit calling for a duty cycle that is larger than (Dmax) that permitted by the switching frequency.
- VinLow 1 when Vin ⁇ 2.3V.
- mode controller 209 transitions converter 100 from PWM mode to Share_LD0 mode.
- the counter increments to 127 clock edges before transitioning control (block 211) .
- the counter prevents unwanted switching due to transients (i.e. , debounce) .
- mode controller 109 operating in Share_PWM mode transitions converter 100 operating mode to PWM mode (block 201) or Share_LDO mode (block 205) in response to changes in the states of certain parameters as follows.
- Share_PWM mode exists to allow the mode control circuit to delay the decision to transition from switching to linear mode. This mode is entered from PWM mode when the MaxDuty condition is detected, and from LDO mode when attempting the transition into PWM mode . Exit from Share_PWM mode is determined as follows:
- VinLow 1 when Vin ⁇ 2.3V.
- mode controller 209 transitions converter 100 from Share PWM mode to Share_LD0 mode.
- the counter counts 15 clock edges before transitioning control (block 233) .
- the counter prevents unwanted switching due to transients (i.e., debounce) .
- mode controller 109 operating in Share_LD0 mode (block 203) transitions converter 100 operating mode to LDO mode (block 223) in response to changes in the states of certain parameters as follows.
- Share_LDO mode exists to allow a smooth transition into LDO mode by ramping down the current in the inductor before giving control of Ml to the linear loop. This creates a predictable condition (the inductor current is always zero when the linear loop gets control of Ml) , and prevents possible damage caused by voltage spikes that may be induced by abrupt changes in inductor current .
- the Noff signal causes entry into LDO mode.
- Blocks 245, 247, 249, 251, and 253 operate as follows: For each switching clock edge in which converter 100 is operating in Share_LD0 mode, a counter is incremented by one (block 247) .
- mode controller 109 sets the states of current control devices 101 and 103 to "off” and “on,” respectively (block 249) .
- LDO 105 retains control of current control device 102.
- LDO 105 retains control of current control device 102, and takes control of current control device 101.
- mode controller 109 operating in LDO mode transitions converter 100 operating mode to Share_PWM mode (block 203) or PSM mode
- mode controller 109 sets the states of current control devices 101 and 103 to "off" and “on,” respectively (block 257) .
- LDO 105 retains control of current control device 102.
- LDO 105 retains control of current control device 102.
- mode controller 109 transitions converter 100 operating mode to Share_PWM mode (block 203) after first enabling the switching clock (block 265) .
- the switching clock signal is present nominally 8 microseconds after being thus enabled.
- the present invention solves several of the problems associated with the implementation of a linear mode of operation in a switched mode converter in that it :
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EP01911124A EP1264390A1 (en) | 2000-02-25 | 2001-02-22 | Power converter mode transistioning method and apparatus |
AU2001238657A AU2001238657A1 (en) | 2000-02-25 | 2001-02-22 | Power converter mode transistioning method and apparatus |
JP2001562812A JP2003525013A (en) | 2000-02-25 | 2001-02-22 | Power converter mode conversion method and device |
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US09/513,339 | 2000-02-25 | ||
US09/513,339 US6229289B1 (en) | 2000-02-25 | 2000-02-25 | Power converter mode transitioning method and apparatus |
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EP (1) | EP1264390A1 (en) |
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Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP4115629B2 (en) * | 1999-05-25 | 2008-07-09 | 本田技研工業株式会社 | Power supply system |
US6246220B1 (en) * | 1999-09-01 | 2001-06-12 | Intersil Corporation | Synchronous-rectified DC to DC converter with improved current sensing |
GB0014344D0 (en) * | 2000-06-13 | 2000-08-02 | Nokia Mobile Phones Ltd | Universal modulation mode tri-amplifier |
DE60030704T2 (en) * | 2000-07-10 | 2007-10-04 | Stmicroelectronics S.R.L., Agrate Brianza | Voltage switching regulator, with a driver circuit of a MOS circuit breaker |
JP3574394B2 (en) * | 2000-10-02 | 2004-10-06 | シャープ株式会社 | Switching power supply |
US6404174B1 (en) * | 2000-10-27 | 2002-06-11 | Adtran, Inc. | Circuit for in-system programming of memory device |
JP3872331B2 (en) * | 2001-03-07 | 2007-01-24 | 富士通株式会社 | DC-DC converter and power supply circuit |
US6310467B1 (en) * | 2001-03-22 | 2001-10-30 | National Semiconductor Corporation | LDO regulator with thermal shutdown system and method |
US6603292B1 (en) * | 2001-04-11 | 2003-08-05 | National Semiconductor Corporation | LDO regulator having an adaptive zero frequency circuit |
US6366070B1 (en) * | 2001-07-12 | 2002-04-02 | Analog Devices, Inc. | Switching voltage regulator with dual modulation control scheme |
US6441597B1 (en) * | 2001-10-31 | 2002-08-27 | Semtech Corporation | Method and apparatus for sensing output inductor current in a DC-to-DC power converter |
US6441598B1 (en) * | 2001-11-05 | 2002-08-27 | Texas Instruments Incorporated | Synchronous rectifier circuit and method of use in switching voltage converter |
US6667602B2 (en) | 2002-03-08 | 2003-12-23 | Visteon Global Technologies, Inc. | Low frequency switching voltage pre-regulator |
US6608521B1 (en) | 2002-05-14 | 2003-08-19 | Texas Instruments Incorporated | Pulse width modulation regulator control circuit having precise frequency and amplitude control |
EP1376295B1 (en) * | 2002-06-17 | 2008-08-13 | Hitachi, Ltd. | Power-supply device |
US6989211B2 (en) * | 2002-06-24 | 2006-01-24 | Delphi Technologies, Inc. | Method and apparatus for controlling a fuel cell system |
US6661211B1 (en) * | 2002-06-25 | 2003-12-09 | Alcatel Canada Inc. | Quick-start DC-DC converter circuit and method |
US6939347B2 (en) * | 2002-11-19 | 2005-09-06 | Conmed Corporation | Electrosurgical generator and method with voltage and frequency regulated high-voltage current mode power supply |
WO2004054076A1 (en) * | 2002-12-10 | 2004-06-24 | Matsushita Electric Industrial Co., Ltd. | Synchronous rectification dc-dc converter power supply |
US6798178B1 (en) * | 2003-03-12 | 2004-09-28 | Semiconductor Components Industries, L.L.C. | Method of forming a power system and structure therefor |
US6781356B1 (en) * | 2003-03-24 | 2004-08-24 | System General Corp. | PWM controller having a modulator for saving power and reducing acoustic noise |
JP2005033888A (en) * | 2003-07-10 | 2005-02-03 | Seiko Instruments Inc | Switching regulator control circuit |
US7760525B2 (en) * | 2003-08-21 | 2010-07-20 | Marvell World Trade Ltd. | Voltage regulator |
US7872454B2 (en) * | 2003-08-21 | 2011-01-18 | Marvell World Trade Ltd. | Digital low dropout regulator |
US7058373B2 (en) * | 2003-09-16 | 2006-06-06 | Nokia Corporation | Hybrid switched mode/linear power amplifier power supply for use in polar transmitter |
JP3763830B2 (en) * | 2003-10-23 | 2006-04-05 | ローム株式会社 | Power supply |
JP4246045B2 (en) * | 2003-12-02 | 2009-04-02 | 株式会社リコー | Power supply circuit and method for raising output voltage of power supply circuit |
JP4493456B2 (en) * | 2003-12-10 | 2010-06-30 | ローム株式会社 | Power supply device and portable device using the same |
CN100552593C (en) * | 2004-02-05 | 2009-10-21 | 美国芯源系统股份有限公司 | Voltage regulator and method thereof |
DE112005000388T5 (en) * | 2004-02-17 | 2007-02-08 | Agere Systems, Inc. | Versatile and intelligent power controller |
US8324872B2 (en) * | 2004-03-26 | 2012-12-04 | Marvell World Trade, Ltd. | Voltage regulator with coupled inductors having high coefficient of coupling |
CN100399689C (en) * | 2004-04-27 | 2008-07-02 | 株式会社理光 | Switching regulator and method for changing output voltages thereof |
US7190152B2 (en) * | 2004-07-13 | 2007-03-13 | Marvell World Trade Ltd. | Closed-loop digital control system for a DC/DC converter |
US7391188B2 (en) * | 2004-08-02 | 2008-06-24 | Jacobs James K | Current prediction in a switching power supply |
US7265601B2 (en) * | 2004-08-23 | 2007-09-04 | International Rectifier Corporation | Adaptive gate drive voltage circuit |
US8058859B2 (en) * | 2004-08-30 | 2011-11-15 | Monolithic Power Systems, Inc. | Pulse frequency modulation methods and circuits |
CN100394200C (en) * | 2004-10-28 | 2008-06-11 | 圆创科技股份有限公司 | Current detection circuit |
JP4832056B2 (en) * | 2004-11-18 | 2011-12-07 | パナソニック株式会社 | High efficiency and high slew rate switching regulator / amplifier |
US7148670B2 (en) | 2005-01-18 | 2006-12-12 | Micrel, Inc. | Dual mode buck regulator with improved transition between LDO and PWM operation |
JP4717449B2 (en) * | 2005-01-19 | 2011-07-06 | セイコーインスツル株式会社 | Switching regulator circuit |
US7805170B2 (en) * | 2005-03-30 | 2010-09-28 | St-Ericsson Sa | System and method for efficient power supply regulation compatible with radio frequency operation |
US7095217B1 (en) * | 2005-03-31 | 2006-08-22 | O2Micro International Limited | Method circuitry and electronic device for controlling a variable output dc power source |
US7064531B1 (en) * | 2005-03-31 | 2006-06-20 | Micrel, Inc. | PWM buck regulator with LDO standby mode |
US20070002596A1 (en) * | 2005-06-29 | 2007-01-04 | Eaton Corporation | Two-stage, wide range power supply for a network protector control relay |
US7521907B2 (en) * | 2006-03-06 | 2009-04-21 | Enpirion, Inc. | Controller for a power converter and method of operating the same |
US7710089B2 (en) * | 2006-03-06 | 2010-05-04 | Texas Instruments Incorporated | Automatic configuration for linear mode of switching power supply |
JP4783195B2 (en) * | 2006-04-18 | 2011-09-28 | パナソニック株式会社 | Buck converter |
US20070290657A1 (en) * | 2006-06-14 | 2007-12-20 | David John Cretella | Circuit and method for regulating voltage |
JP4907275B2 (en) * | 2006-09-01 | 2012-03-28 | 株式会社リコー | Power supply device and operation control method thereof |
US7508179B2 (en) * | 2006-11-06 | 2009-03-24 | Micrel, Incorporated | Dual input prioritized LDO regulator |
TWI335706B (en) * | 2007-01-29 | 2011-01-01 | Richtek Technology Corp | Power supply with high efficiency and low noise |
JP2008206214A (en) * | 2007-02-16 | 2008-09-04 | Ricoh Co Ltd | Switching regulator |
JP5167665B2 (en) * | 2007-03-26 | 2013-03-21 | 富士通セミコンダクター株式会社 | Step-down DC-DC converter control circuit, step-down DC-DC converter and control method therefor |
US7489198B1 (en) | 2007-04-26 | 2009-02-10 | Lockheed Martin Corporation | Linear regulating switch |
US7535183B2 (en) * | 2007-04-27 | 2009-05-19 | Korry Electronics Co. | Apparatus and method to provide a hybrid linear/switching current source, such as for high-efficiency, wide dimming range light emitting diode (LED) backlighting |
US7508177B2 (en) * | 2007-06-08 | 2009-03-24 | Freescale Semiconductor, Inc. | Method and circuit for reducing regulator output noise |
US7868605B1 (en) * | 2007-07-02 | 2011-01-11 | Altera Corporation | Mixed mode power regulator circuitry for memory elements |
US7755341B2 (en) * | 2007-07-05 | 2010-07-13 | Intersil Americas Inc. | Steady state frequency control of variable frequency switching regulators |
US7777465B2 (en) * | 2007-11-15 | 2010-08-17 | Macronix International Co. Ltd | Output transient responsive voltage regulator controlling apparatus and method |
US8072196B1 (en) * | 2008-01-15 | 2011-12-06 | National Semiconductor Corporation | System and method for providing a dynamically configured low drop out regulator with zero quiescent current and fast transient response |
US8258766B1 (en) * | 2008-01-22 | 2012-09-04 | Marvell International Ltd. | Power management system with digital low drop out regulator and DC/DC converter |
US20100060078A1 (en) * | 2008-09-08 | 2010-03-11 | Micrel, Incorporated | Dual Input LDO Regulator With Controlled Transition Between Power Supplies |
US8324876B1 (en) * | 2008-10-31 | 2012-12-04 | Altera Corporation | Unconditional frequency compensation technique on-chip low dropout voltage regulator |
US9716403B2 (en) * | 2008-11-25 | 2017-07-25 | Semiconductor Components Industries, Llc | Battery charger circuit for changing between modes during operation based on temperature and battery voltage and method therefor |
US8203320B2 (en) * | 2009-01-07 | 2012-06-19 | Linear Technology Corporation | Switching mode converters |
CN101989755B (en) * | 2009-07-30 | 2015-03-18 | 立锜科技股份有限公司 | Hybrid charger as well as control circuit and method thereof |
EP2354881A1 (en) | 2010-02-05 | 2011-08-10 | Dialog Semiconductor GmbH | Domino voltage regulator (DVR) |
US8917067B2 (en) * | 2010-03-24 | 2014-12-23 | R2 Semiconductor, Inc. | Assisting an output current of a voltage converter |
US8248044B2 (en) | 2010-03-24 | 2012-08-21 | R2 Semiconductor, Inc. | Voltage regulator bypass resistance control |
US8570011B2 (en) * | 2010-05-07 | 2013-10-29 | Stmicroelectronics S.R.L. | DC-DC converter circuit |
TWI416851B (en) | 2010-06-11 | 2013-11-21 | Wistron Corp | Voltage adjustment module and power supply device |
US8617154B2 (en) * | 2010-06-25 | 2013-12-31 | Covidien Lp | Current-fed push-pull converter with passive voltage clamp |
CN102375464B (en) * | 2010-08-12 | 2014-08-13 | 上海炬力集成电路设计有限公司 | Control method of power management integrated circuit and power management integrated circuit |
JP5727189B2 (en) * | 2010-10-01 | 2015-06-03 | Necエンジニアリング株式会社 | Synchronous rectification type power circuit |
US8552703B2 (en) | 2011-03-04 | 2013-10-08 | Intersil Americas Inc. | Method and apparatus for low standby current switching regulator |
CN102681578B (en) * | 2011-03-15 | 2014-12-17 | 瑞昱半导体股份有限公司 | Voltage adjusting device |
US8933685B2 (en) * | 2011-03-22 | 2015-01-13 | Rf Micro Devices, Inc. | Protection system and method for DC-DC converters exposed to a strong magnetic field |
TWI458241B (en) * | 2011-09-23 | 2014-10-21 | Richtek Technology Corp | Power supply with dynamic dropout control and method thereof |
US8988054B2 (en) * | 2011-12-27 | 2015-03-24 | St-Ericsson Sa | Single feedback loop for parallel architecture buck converter—LDO regulator |
EP2621068B1 (en) * | 2012-01-27 | 2018-08-22 | Dialog Semiconductor GmbH | Bypass control in a DC-to-DC converter |
US8952753B2 (en) * | 2012-02-17 | 2015-02-10 | Quantance, Inc. | Dynamic power supply employing a linear driver and a switching regulator |
JP2013176245A (en) * | 2012-02-27 | 2013-09-05 | Ricoh Co Ltd | Power supply device, image formation device, and power supply method |
US9577523B2 (en) * | 2012-03-01 | 2017-02-21 | Intel Corporation | Dual mode voltage regulator with reconfiguration capability |
KR101387300B1 (en) * | 2012-04-23 | 2014-04-18 | 삼성전기주식회사 | LDO(Low Drop Out Regulator) having phase margin compensation means and phase margin compensation method using the LDO |
US8994347B2 (en) | 2012-06-04 | 2015-03-31 | R2 Semiconductor, Inc. | Assisting a load current of a switching voltage regulator |
US9473023B2 (en) | 2012-08-10 | 2016-10-18 | Texas Instruments Incorporated | Switched mode assisted linear regulator with seamless transition between power tracking configurations |
US9112413B2 (en) * | 2012-08-10 | 2015-08-18 | Texas Instruments Incorporated | Switched mode assisted linear regulator with AC coupling with capacitive charge control |
JP6315834B2 (en) * | 2012-08-10 | 2018-04-25 | 日本テキサス・インスツルメンツ株式会社 | Switched mode assist linear regulator |
US9285812B2 (en) | 2013-02-01 | 2016-03-15 | Allegro Microsystems, Llc | Soft start circuits and techniques |
US9287779B2 (en) | 2013-03-14 | 2016-03-15 | Qualcomm Incorporated | Systems and methods for 100 percent duty cycle in switching regulators |
US9857819B1 (en) * | 2013-03-15 | 2018-01-02 | Maxim Integrated Products, Inc. | System and methods for multi-input switching regulator |
US9256238B1 (en) * | 2013-05-10 | 2016-02-09 | Sridhar Kotikalapoodi | Method and apparatus for fast, efficient, low noise power supply using multiple regulators |
KR101509323B1 (en) * | 2013-08-01 | 2015-04-08 | 단국대학교 산학협력단 | Second battery charging circuit using linear regulator |
CN103731012A (en) * | 2013-11-18 | 2014-04-16 | 青岛盛嘉信息科技有限公司 | Efficient power circuit operating in double modes |
CN104702101A (en) * | 2013-12-10 | 2015-06-10 | 展讯通信(上海)有限公司 | Voltage conversion device and electronic device |
US9606558B2 (en) * | 2014-03-04 | 2017-03-28 | Qualcomm Technologies International. Ltd. | Lower power switching linear regulator |
CN104348359B (en) * | 2014-10-31 | 2017-01-11 | 无锡中感微电子股份有限公司 | DC (Direct Current)-DC adjuster |
US9547322B1 (en) * | 2014-11-13 | 2017-01-17 | Gazelle Semiconductor, Inc. | Configuration modes for optimum efficiency across load current |
US20160190921A1 (en) * | 2014-12-24 | 2016-06-30 | Intel Corporation | Selectable-mode voltage regulator topology |
US20160239036A1 (en) * | 2015-02-12 | 2016-08-18 | Intel Corporation | Dual supply |
US10044263B2 (en) | 2015-03-12 | 2018-08-07 | Microchip Technology Incorporated | Using PMOS power switch in a combination switching and linear regulator |
US9413340B1 (en) * | 2015-05-05 | 2016-08-09 | Fidelix Co., Ltd. | DC-to-DC voltage converter using switching frequency detection |
US10795391B2 (en) * | 2015-09-04 | 2020-10-06 | Texas Instruments Incorporated | Voltage regulator wake-up |
US10320215B2 (en) | 2015-09-25 | 2019-06-11 | Intel Corporation | Apparatus and method for instant on ability |
US9893628B2 (en) * | 2015-10-30 | 2018-02-13 | Apple Inc. | AC-DC power converters with improved voltage output level transitions |
US9733655B2 (en) * | 2016-01-07 | 2017-08-15 | Vanguard International Semiconductor Corporation | Low dropout regulators with fast response speed for mode switching |
US10326296B2 (en) | 2016-02-01 | 2019-06-18 | Qualcomm Incorporated | Dual-phase operation for concurrently charging a battery and powering a peripheral device |
US20170222463A1 (en) * | 2016-02-01 | 2017-08-03 | Qualcomm Incorporated | Duty cycle control for charging a battery |
CN105871180B (en) * | 2016-04-08 | 2018-07-17 | 厦门大学 | A kind of high current CMOS push-pull driver circuits and its control method |
CN106026647A (en) * | 2016-04-29 | 2016-10-12 | 深圳市华芯邦科技有限公司 | Hybrid circuit DC electric energy buck conversion device |
US10534386B2 (en) * | 2016-11-29 | 2020-01-14 | Taiwan Semiconductor Manufacturing Co., Ltd. | Low-dropout voltage regulator circuit |
US9985521B1 (en) * | 2017-04-13 | 2018-05-29 | Nanya Technology Corporation | Voltage system |
TWI654813B (en) | 2017-07-20 | 2019-03-21 | 新唐科技股份有限公司 | Control device and its power conversion circuit |
TWI644193B (en) * | 2017-10-20 | 2018-12-11 | 群光電能科技股份有限公司 | Multi-output control system |
US10218254B1 (en) | 2017-12-13 | 2019-02-26 | Nxp Usa, Inc. | Switching power supply and method for operating a switched-mode power supply |
TWI657651B (en) * | 2018-05-23 | 2019-04-21 | 茂達電子股份有限公司 | Frequency compensation circuit used in dc voltage converter |
TWI673590B (en) * | 2018-07-27 | 2019-10-01 | 威鋒電子股份有限公司 | Multi-port power supply apparatus and operation method thereof |
US11482889B2 (en) * | 2019-01-09 | 2022-10-25 | Integrated Device Technology, Inc. | Wireless power receiver configurable for LDO or buck operation |
JP7173915B2 (en) * | 2019-03-28 | 2022-11-16 | ラピスセミコンダクタ株式会社 | power circuit |
CN110518798A (en) * | 2019-09-02 | 2019-11-29 | 嘉兴飞童电子科技有限公司 | A kind of voiced band noise canceller circuit and method applied to step-down DC/DC converter |
US10790747B1 (en) | 2019-10-07 | 2020-09-29 | Analog Devices International Unlimited Company | Inductor current shunt for mitigation of load dump transients in DC-DC regulators |
US11703897B2 (en) * | 2020-03-05 | 2023-07-18 | Stmicroelectronics S.R.L. | LDO overshoot protection in a cascaded architecture |
US20220247312A1 (en) * | 2021-01-29 | 2022-08-04 | Hassan Ihs | Dc-dc voltage control mode with seamless pfm and load-line operation |
US11394301B1 (en) | 2021-02-15 | 2022-07-19 | Analog Devices, Inc. | Techniques for linear control of inductor current shunt for mitigation of load dump transients in DC-DC regulators |
Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
GB2243961A (en) * | 1990-03-09 | 1991-11-13 | Sunleigh Electrical Developmen | DC-DC Power supply circuit |
US5502369A (en) * | 1991-10-01 | 1996-03-26 | Mitsubishi Denki Kabushiki Kaisha | Stabilized direct current power supply |
US5773966A (en) * | 1995-11-06 | 1998-06-30 | General Electric Company | Dual-mode, high-efficiency dc-dc converter useful for portable battery-operated equipment |
EP0903839A1 (en) * | 1997-09-18 | 1999-03-24 | STMicroelectronics SA | Voltage regulator |
Family Cites Families (13)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS6310214A (en) * | 1986-07-02 | 1988-01-16 | Matsushita Electric Ind Co Ltd | Power supply circuit |
JP2737452B2 (en) * | 1991-05-23 | 1998-04-08 | 日本電気株式会社 | Power system |
JP2712934B2 (en) * | 1991-10-01 | 1998-02-16 | 三菱電機株式会社 | DC stabilized power supply |
US5481178A (en) | 1993-03-23 | 1996-01-02 | Linear Technology Corporation | Control circuit and method for maintaining high efficiency over broad current ranges in a switching regulator circuit |
FR2705506B1 (en) * | 1993-05-21 | 1995-07-07 | Merlin Gerin | Electronic trip device comprising a power control device. |
US5592072A (en) * | 1995-01-24 | 1997-01-07 | Dell Usa, L.P. | High performance dual section voltage regulator |
JPH1098874A (en) * | 1996-09-24 | 1998-04-14 | Sharp Corp | Dc stabilized power supply |
US5945820A (en) | 1997-02-06 | 1999-08-31 | The Board Of Trustees Of The Leland Stanford Junior University | DC-DC switching regulator with switching rate control |
JPH113126A (en) * | 1997-04-17 | 1999-01-06 | Sony Corp | Dc/dc converter |
US5959443A (en) | 1997-11-14 | 1999-09-28 | Toko, Inc. | Controller circuit for controlling a step down switching regulator operating in discontinuous conduction mode |
JPH11353040A (en) * | 1998-04-10 | 1999-12-24 | Matsushita Electric Ind Co Ltd | Power unit |
US5998977A (en) * | 1998-05-27 | 1999-12-07 | Maxim Integrated Products, Inc. | Switching power supplies with linear precharge, pseudo-buck and pseudo-boost modes |
JP3802678B2 (en) * | 1998-05-27 | 2006-07-26 | 富士電機デバイステクノロジー株式会社 | Control method of step-down chopper type DC-DC converter |
-
2000
- 2000-02-25 US US09/513,339 patent/US6229289B1/en not_active Expired - Lifetime
-
2001
- 2001-02-22 WO PCT/US2001/005781 patent/WO2001063735A1/en active Application Filing
- 2001-02-22 JP JP2001562812A patent/JP2003525013A/en active Pending
- 2001-02-22 AU AU2001238657A patent/AU2001238657A1/en not_active Abandoned
- 2001-02-22 EP EP01911124A patent/EP1264390A1/en not_active Withdrawn
Patent Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
GB2243961A (en) * | 1990-03-09 | 1991-11-13 | Sunleigh Electrical Developmen | DC-DC Power supply circuit |
US5502369A (en) * | 1991-10-01 | 1996-03-26 | Mitsubishi Denki Kabushiki Kaisha | Stabilized direct current power supply |
US5773966A (en) * | 1995-11-06 | 1998-06-30 | General Electric Company | Dual-mode, high-efficiency dc-dc converter useful for portable battery-operated equipment |
EP0903839A1 (en) * | 1997-09-18 | 1999-03-24 | STMicroelectronics SA | Voltage regulator |
Also Published As
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US6229289B1 (en) | 2001-05-08 |
EP1264390A1 (en) | 2002-12-11 |
AU2001238657A1 (en) | 2001-09-03 |
JP2003525013A (en) | 2003-08-19 |
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