US6841969B1 - Flux observer in a sensorless controller for permanent magnet motors - Google Patents
Flux observer in a sensorless controller for permanent magnet motors Download PDFInfo
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- US6841969B1 US6841969B1 US10/669,918 US66991803A US6841969B1 US 6841969 B1 US6841969 B1 US 6841969B1 US 66991803 A US66991803 A US 66991803A US 6841969 B1 US6841969 B1 US 6841969B1
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- 230000004907 flux Effects 0.000 title claims abstract description 104
- 230000009466 transformation Effects 0.000 claims abstract description 9
- 230000001360 synchronised effect Effects 0.000 claims abstract description 8
- 230000001052 transient effect Effects 0.000 claims description 14
- 230000001133 acceleration Effects 0.000 description 6
- 230000010354 integration Effects 0.000 description 5
- 230000004044 response Effects 0.000 description 5
- 238000010586 diagram Methods 0.000 description 3
- 230000002441 reversible effect Effects 0.000 description 3
- 230000003313 weakening effect Effects 0.000 description 3
- 238000000034 method Methods 0.000 description 2
- 230000008569 process Effects 0.000 description 2
- 230000002829 reductive effect Effects 0.000 description 2
- 230000001154 acute effect Effects 0.000 description 1
- 230000002411 adverse Effects 0.000 description 1
- 230000003247 decreasing effect Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 230000010363 phase shift Effects 0.000 description 1
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Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/13—Observer control, e.g. using Luenberger observers or Kalman filters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/24—Vector control not involving the use of rotor position or rotor speed sensors
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P2207/00—Indexing scheme relating to controlling arrangements characterised by the type of motor
- H02P2207/05—Synchronous machines, e.g. with permanent magnets or DC excitation
Definitions
- the present invention relates to electric machines, and more particularly to sensorless rotor position estimation for electric machines.
- Open-loop flux observers are used to estimate rotor position in an electric machine such as a permanent magnet (PM) motor.
- the open-loop flux observer is typically called a “sensorless” estimator because the rotor position is inferred rather than measured directly.
- Direct rotor position sensors typically include rotor position transducers (RPTs) or other sensors that sense movement of the rotor.
- RPTs rotor position transducers
- Direct rotor position sensors are typically costly to implement and may tend to reduce the reliability of the electric machine.
- the open-loop flux observer estimates rotor position using stator currents and commanded stator voltages as inputs.
- the open-loop flux observer calculates the back EMF of the electric machine.
- ⁇ r ⁇ ⁇ ⁇ s - ⁇ ( 4 )
- ⁇ dqs s is the stator flux
- the back EMF is integrated to obtain the stator flux linkage in a stationary reference frame (See Equation 1).
- the angular position of the stator flux is usually obtained using the arctangent function (See Equation 2).
- the rotor position information is obtained by subtracting the load angular position ⁇ (See Equation 3) from the stator flux position (See Equation 4).
- an integration function that is set forth in Equation 1 is not used.
- Cascaded low pass filters are typically used to simulate the integration function to avoid integration problems that occur at low stator frequencies.
- Cascaded LPFs also provide improved transient response as compared to a single LPF since faster time constants can be used.
- the conventional open-loop flux observer has several performance problems.
- the cascaded LPFs require electrical speed data, which is not normally available from basic open-loop observers.
- the electrical speed data is used to set the LPF coefficients.
- To generate the electrical speed data a derivative of angular position is generated. The derivative operation tends to be noise sensitive and can create errors in the electrical speed data.
- the electrical speed data is used to compute the coefficients of the cascade LPFs. Errors in the electrical speed data adversely impact LPF characteristics such as gain and phase and may cause instability.
- the conventional open-loop flux observer requires an arctangent function, which can be computationally intensive.
- a control system includes a field oriented controller that receives a torque command and that generates phase voltages for an electric machine including a rotor and a stator.
- a first transformation module receives stator terminal currents and generates d-axis and q-axis stationary frame currents.
- An open loop flux observer receives d-axis and q-axis stationary frame voltage commands and the d and q-axis stationary frame currents.
- the open loop flux observer includes a vector cross product calculator that generates an error signal that is proportional to an angular difference between an estimated stator flux and a computed stator flux and a proportional integral controller that generates an estimated rotor angular position based on the error signal.
- a second transformation module receives the d-axis and q-axis stationary frame currents, and the estimated rotor angular position and generates d-axis and q-axis synchronous reference frame feedback currents that are output to the field oriented controller.
- the electric machine is a permanent magnet electric machine.
- the open loop flux observer includes a d-axis voltage drop calculator that calculates a d-axis stator voltage drop due to stator resistance.
- a q-axis voltage drop calculator calculates a q-axis stator voltage drop due to the stator resistance.
- a first summer generates a d-axis back EMF by calculating a first difference between the d-axis stationary frame voltage command and the d-axis stator voltage drop.
- a second summer generates a q-axis back EMF by calculating a second difference between the q-axis stationary frame voltage command and the q-axis voltage drop.
- the open loop flux observer includes a first low pass filter that receives an electrical angular velocity estimate and the d-axis back EMF and that generates a d-axis stator flux linkage value.
- a second low pass filter receives the electrical angular velocity estimate and the q-axis back EMF and generates a q-axis stator flux linkage value.
- the vector cross product calculator includes a sine function generator that generates a sine value of an estimated stator flux angular position.
- a cosine function generator generates a cosine value of the estimated stator flux angular position.
- a first multiplier multiplies the sine value by the d-axis stator flux value.
- a second multiplier multiplies the cosine value by the q-axis stator flux value.
- a first difference circuit generates an error signal that is based on a difference between the two products, which is also the cross product.
- the open loop flux observer further includes a load angular position circuit that generates a load angular position.
- a derivative calculator calculates a derivative of the load angular position.
- a summing circuit generates a stator flux angular velocity by summing the load angular position derivative and the estimated electrical angular velocity.
- An integrator integrates the stator flux angular velocity to generate a stator flux position.
- a second difference circuit generates the estimated angular rotor position based on a difference between the stator flux position and the load angular position.
- FIG. 1 is a functional block diagram of an open-loop flux observer circuit according to the present invention and a sensorless drive circuit;
- FIG. 2 is a more detailed functional block diagram of the open-loop observer of FIG. 1 ;
- FIG. 3 is a plot illustrating d-axis and q-axis back EMF voltages
- FIG. 4 is a plot illustrating the transient torque response without a feedforward term
- FIG. 5 is a plot illustrating the transient torque response with a feedforward term according to the present invention.
- FIG. 6 is a plot illustrating transient performance during forward acceleration
- FIG. 7 is a plot illustrating transient performance during reverse acceleration.
- the present invention eliminates several problems that are associated with conventional open-loop flux observers.
- the present invention replaces the arctangent function using a vector cross product (VCP) error function and a proportional integral (PI) controller.
- VCP vector cross product
- PI proportional integral
- the open-loop flux observer circuit according to the present invention provides smooth speed estimation data that can be used by the cascade LPFs. Correct system dynamics are maintained by including a derivative of load angular position (d ⁇ /dt) feedforward term in the open-loop flux observer.
- an open-loop flux observer circuit 10 is applied to a sensorless driver for an IPM machine 14 such as a motor or a generator.
- a field-oriented controller 18 receives a torque command Te* and synchronous reference frame feedback currents I ds ⁇ and I qs ⁇ .
- the field-oriented controller 18 generates actual phase voltages 22 that are applied to inputs of the IPM machine 14 .
- Motor phase or stator terminal currents are measured and processed by a 3-phase to 2-phase transformation module 30 .
- the outputs of the transformation module 30 are the stationary frame currents I ds s and I sq s .
- the open-loop flux observer circuit 10 generates an estimated rotor angular position ⁇ r and angular speed w r .
- a stationary to rotating frame transformation module 34 uses the estimated rotor angular position ⁇ r to generate synchronous reference frame feedback currents I ds w and I qs s .
- the synchronous reference frame feedback currents I ds s and I qs s are output to the field-oriented controller module 18 .
- FIG. 2 a detailed block diagram of the open-loop flux observer circuit 10 is shown.
- Stationary frame current I ds s is multiplied by the stator resistance R s using gain block 50 to compute a d-axis stator resistance voltage drop.
- the output of gain block 50 is subtracted from the d-axis stator voltage command V ds s′′ using a summer 54 .
- the output of summer 54 is the d-axis back-EMF ⁇ ds s .
- the d-axis back-EMF is output to cascade LPFs 60 , which use the electrical angular velocity ⁇ e to determine the appropriate coefficients for the cascade LPFs 60 .
- the cascade LPFs 60 integrate the d-axis back-EMF to obtain the d-axis stator flux linkage ⁇ acute over ( ⁇ ) ⁇ ds s .
- Stationary frame current I qs s is multiplied by the stator resistance using gain block 70 to compute the q-axis stator resistance voltage drop.
- the output of gain block 70 is subtracted from the q-axis stator voltage command V qs s* using a summer 74 .
- the output of summer 74 is the q-axis back EMF e qs s .
- the q-axis back EMF is passed to cascade LPFs 80 , which use the electrical angular velocity ⁇ e to determine the appropriate coefficients for the cascade LPFs 80 .
- the cascade LPFs 80 integrate the q-axis back EMF to obtain the q-axis stator flux linkage ⁇ qs s .
- a vector cross product calculator 84 calculates a vector cross product between the observer estimated stator flux angular position unit vector and the computed stator flux vector.
- Block 86 computes the sine of the estimated stator flux angular position ⁇ ⁇ s .
- Block 88 computes the cosine of the estimated stator flux angular position ⁇ ⁇ s .
- Multiplier 90 generates a product of the computed d-axis stator flux and the sine of the estimated stator flux angular position.
- Multiplier 92 generates a product of the computed q-axis stator flux and the cosine of the estimated stator flux angular position.
- Summing junction 94 subtracts the output of block ( 13 ) from the output of block ( 12 ) to generate the error signal ⁇ .
- Error signal ⁇ is input to anti-windup PI controller 100 , whose output is ⁇ e — raw .
- the anti-windup PI controller 100 functions such that ⁇ error goes to zero.
- ⁇ e — raw is passed through low pass filter 104 to produce the estimated electrical angular velocity ⁇ e . This signal is also passed to cascade LPFs 60 and 80 .
- the d ⁇ /dt term can be used in feedforward manner in the open-loop flux observer to improve the torque transient response.
- the load angular position 6 is passed by a load angular position calculator 110 to a derivative generator 112 .
- the output of derivative generator 112 is passed through low pass filter 116 to remove unwanted high frequency noise created by the derivative.
- the output of LPF 116 is scaled with gain block 120 .
- the output of gain block 120 is summed with the output of the anti wind-up PI 100 via summing junction 124 to produce ⁇ ⁇ s , which is fed to integrator 128 , which outputs the estimated stator flux position ⁇ ⁇ s .
- the load angular position ⁇ is calculated by block 110 based on Equation 3 and subtracted from the stator flux position using summing junction 130 to obtain the final rotor position ⁇ r , (see Equation 4).
- FIG. 3 shows the d-axis and q-axis back EMF voltages ⁇ dqs s and resultant computed d and q-axis stator fluxes ⁇ dqs s as calculated by the cascade LPFs.
- the 90° of phase-shift introduced by the integration can be seen in the FIG. 3 .
- the high frequency ripple on ⁇ dqs s is inherent in the design of this IPM motor and is effectively filtered out during the integration process at this speed.
- a step in ⁇ e — est occurs, which should be constant.
- the dynamometer held the speed constant during the torque transient test.
- the estimated electrical speed has a large transient. In reality, the actual rotor speed was held constant, therefore the observer generated the error in the estimated electrical speed.
- FIGS. 6 and 7 Speed transient performance of the proposed open-loop flux observer is shown in FIGS. 6 and 7 .
Abstract
Description
Where Ψdqs s is the stator flux linkage in the stationary reference frame, idqs s is the stator current in the stationary reference frame, Rs is the stator resistance, Ψds s and Ψqs s are the d-axis and q-axis stator flux linkages in the stationary reference frame, Ψds e and Ψqs e are the d-axis and q-axis stator flux linkages in the stationary reference frame, Ψf is the permanent magnet flux linkage, Ld is the d-axis inductance, Lq is the q-axis inductance, ids e and iqs e are synchronous reference frame currents, θ, is the rotor position, θΨs is the angular position of the stator flux and δ is the load angular position.
ε=(cos θΨs +jsin θΨs)×{right arrow over (Ψ)}dqs=|Ψs|sin θerror
ε˜|Ψs|·θerror (5)
Error signal ε is input to
The dδ/dt term can be used in feedforward manner in the open-loop flux observer to improve the torque transient response. The load angular position 6 is passed by a load
Claims (18)
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Cited By (26)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20050029972A1 (en) * | 2003-05-19 | 2005-02-10 | Nobuyuki Imai | Control apparatus for brushless DC motor |
US7109670B1 (en) * | 2005-05-25 | 2006-09-19 | Rockwell Automation Technologies, Inc. | Motor drive with velocity-second compensation |
US20070085499A1 (en) * | 2004-03-12 | 2007-04-19 | Knorr-Bremse Systeme Fuer Nutzfahrzeuge Gmbh | Rotor position detection of a brushless DC motor |
US7211984B2 (en) * | 2004-11-09 | 2007-05-01 | General Motors Corporation | Start-up and restart of interior permanent magnet machines |
US20100109584A1 (en) * | 2008-10-31 | 2010-05-06 | Jeong Hyeck Kwon | Position-sensorless control system and method of operation for a synchronous motor |
EP2264556A1 (en) * | 2009-06-18 | 2010-12-22 | Sanyo Electric Co., Ltd. | Motor control device and motor drive system |
RU2455751C2 (en) * | 2006-10-30 | 2012-07-10 | Бомбардир Транспортацион Гмбх | Control and/or adjustment of three-phase electric energy converter for asynchronous machine operation control |
KR101258087B1 (en) * | 2006-05-03 | 2013-04-25 | 엘지전자 주식회사 | Apparatus and method for controlling high speed driving of sensorless permanent magnet synchoronous mortor |
CN103346726A (en) * | 2013-07-08 | 2013-10-09 | 合肥工业大学 | PMSM stator flux linkage observation method based on extension flux linkage observer |
US20140203754A1 (en) * | 2013-01-24 | 2014-07-24 | Rolls-Royce Plc | Method of controlling an ac machine and controller for controlling an ac machine |
CN104122479A (en) * | 2014-07-29 | 2014-10-29 | 华中科技大学 | Online detection method for open-circuit faults of power tubes of induction-motor vector control system |
US9000699B2 (en) | 2011-11-10 | 2015-04-07 | Whirlpool Corporation | Determination of magnetic flux and temperature of permanent magnets in washing machine motor |
US9106177B2 (en) | 2012-01-05 | 2015-08-11 | GM Global Technology Operations LLC | Method and system for sensorless control of an electric motor |
US20150365029A1 (en) * | 2014-06-16 | 2015-12-17 | Hyundai Motor Company | Sensorless control method for motor and system using the same |
CN106712621A (en) * | 2016-11-15 | 2017-05-24 | 中冶南方(武汉)自动化有限公司 | Device and method for identifying stator resistance of motor |
US20170250641A1 (en) * | 2016-02-26 | 2017-08-31 | Steering Solutions Ip Holding Corporation | Flux estimation for fault tolerant control of pmsm machines for eps |
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US7064504B2 (en) * | 2003-05-19 | 2006-06-20 | Honda Motor Co., Ltd. | Control apparatus for brushless DC motor |
US20050029972A1 (en) * | 2003-05-19 | 2005-02-10 | Nobuyuki Imai | Control apparatus for brushless DC motor |
US20070085499A1 (en) * | 2004-03-12 | 2007-04-19 | Knorr-Bremse Systeme Fuer Nutzfahrzeuge Gmbh | Rotor position detection of a brushless DC motor |
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US7211984B2 (en) * | 2004-11-09 | 2007-05-01 | General Motors Corporation | Start-up and restart of interior permanent magnet machines |
US7109670B1 (en) * | 2005-05-25 | 2006-09-19 | Rockwell Automation Technologies, Inc. | Motor drive with velocity-second compensation |
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