US3840828A - Temperature-stable dielectric resonator filters for stripline - Google Patents

Temperature-stable dielectric resonator filters for stripline Download PDF

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Publication number
US3840828A
US3840828A US00413907A US41390773A US3840828A US 3840828 A US3840828 A US 3840828A US 00413907 A US00413907 A US 00413907A US 41390773 A US41390773 A US 41390773A US 3840828 A US3840828 A US 3840828A
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United States
Prior art keywords
resonator
stripline
resonators
dielectric
conductor
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Expired - Lifetime
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US00413907A
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English (en)
Inventor
D Linn
J Plourde
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AT&T Corp
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Bell Telephone Laboratories Inc
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Application filed by Bell Telephone Laboratories Inc filed Critical Bell Telephone Laboratories Inc
Priority to US00413907A priority Critical patent/US3840828A/en
Priority to CA206,057A priority patent/CA1005536A/en
Application granted granted Critical
Publication of US3840828A publication Critical patent/US3840828A/en
Priority to SE7413536A priority patent/SE400144B/xx
Priority to NLAANVRAGE7414351,A priority patent/NL177641C/xx
Priority to FR7436602A priority patent/FR2251127B1/fr
Priority to GB47668/74A priority patent/GB1485505A/en
Priority to DE2452743A priority patent/DE2452743C2/de
Priority to JP49128154A priority patent/JPS587082B2/ja
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P7/00—Resonators of the waveguide type
    • H01P7/10—Dielectric resonators
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/203—Strip line filters
    • H01P1/20309—Strip line filters with dielectric resonator

Definitions

  • dielectric resonator type filters for stripline. It has been found generally desirable to use dielectric resonators in which the dielectric constant of the material, e.g., titanium dioxide (TiO is at least about 100.
  • TiO titanium dioxide
  • the geometry is uniquely a cylindrical geometry. It is used primarily for coupling from coaxial cable to waveguide; and the only stripline portion thereof is in the coupling from the coaxial cable to the waveguide.
  • the dielectric resonator is used as a part of the coupling arrangement.
  • the problems of accuracy of placement of a dielectric resonator with respect to a stripline are solved -in a manner consistent with good temperature stability and overall compactness by positioning the dielectric resonator over the principal conductor of the stripline and providing precision spacing from the principal conductor in the normal direction by an accurately machined dielectric spacer.
  • FIG. 1 is a pictorial cross-sectional view of the typical prior art arrangement of dielectric resonators with re spect to striplines;
  • FIG. 2 is a pictorial cross-sectional view of a striplin with ground plane and with a dielectric resonator arranged with respectthereto according to our invention
  • FIG. 3 shows curves useful in explaining the characteristics of our invention
  • FIG. 4 shows a modification of the embodiment of FIG. 2, using coupled multiple dielectric resonators shown in pictorial crosssectional view along the stripline;
  • FIG. 5 shows a plan view of the embodiment of FIG.
  • FIGS. 6, 7 and 8 show the filter characteristic for the embodiment of FIGS. 4 and 5;
  • FIGS. 9A and 9B show pictorial plan and elevation views of a pass-band filter employing the invention
  • FIGS. 10A and 108 show a modification of the embodiment of FIGS. 9A and 9B;
  • FIGS. 1 1 and 13 show curves useful in explaining the embodiment of FIGS. 9A and 9B.
  • FIG. 12 is a partial showing of FIG. 9A and setting forth parameters used in the curves of FIG. 11.
  • the dielectric resonator 11 is coupled to the strip line 13 by positioning it on the substrate 12 next to the principal conductor 14.
  • the stripline 13 also includes the dielectric layers 15 and 16, which may be air where desired, and the ground plane 17.
  • the stripline housing width becomes excessive and allows spurious waveguide type modes to propagate, resuiting in undesirable spurious filter responses.
  • a further drawback found with the arrangement of FIG. 1 is that the dielectric resonator 11 is not located at the maximum-coupling position with respect to the principal conductor; and the degree of coupling is extraordinarily sensitive to very minute variations in the lateral center-to-center spacing d between the principal conductors 14 and the resonator 1 1.
  • an arrangement of a dielectric resonator 21 with respect to a stripline 23 as shown in FIG. 2 overcomes the foregoing problems by disposing the dielectric resonator 21 over the principal conductor 24 of the stripline so that in addition to a lateral center-to-center space d the resonator positioning is now characterized by a normal center-to-center spacing h. This normal positioning is determined by a dielectric spacer 25, which may be accurately machined in a separate operation from that of positioning the resonator 21 over the substrate 22.
  • the stripline 23 is shown with its substrate 22 and the additional layer of dielectric material 26 thereunder for structural rigidity. Dielectric layer 26 may be omitted where desired.
  • the ground plane 27 in the vicinity of the resonator 21 encloses the resonator within a metal housing, similar to a section of waveguide, through which a tuning screw 28 is readily inserted.
  • the spacing parameter d is selected for maximum coupling.
  • the coupling is absolutely a maximum with respect to the lateral offset d and is relatively insensitive to small variations in d because the maximum is a broad flat maximum.
  • the increased top ground plane clearance shown in FIG. 2 is provided in the vicinity of dielectric resonators only so that spurious housing reso- I nances are eliminated.
  • the same characteristic impedance as in the preceding and following stripline portions should be maintained throughout the resonator region, for frequencies outside the reject band of the filter.
  • the width of the principal conductor 24 will be altered in the vicinity of resonators such as reso-' nator 21 in order to provide an impedance match along the line at these points and thus avoid spurious reflections along the stripline.
  • the band reject filter comprising dielectric resonator 21 utilizes either a composition material of lithium tantalate and titanium dioxide or, alternatively, uses barium titanate sa mo
  • a lithium tantalate and titanium dioxide composite is disclosed in some detail in the copending patent application of one of us, J. K. Plourde, Ser. No. 317,385 filed Dec. 22, 1972, as-
  • FIG. 3 there are shown curves 31, 32 and 33 of the resonator external Q with respect to the lateral offset spacing d for various values of the normal spacing h.
  • the desirable value of d is in every case at the low part of the curve which corresponds to maximum coupling between the principal conductor 24 and the resonator 21. It will be noted that the resonator and therefore the coupling is insensitive to small variations in d about the preferred value. Because of this fact, the tolerance in d can be relaxed; and only the value h need be accurately controlled. The precise control in the value of h is easily obtained by positioning the resonator 21 on a dielectric spacer 25, such as a Rexolite disc.
  • the height of the resonator 21 was illustratively 0.175 inch and its radius in the horizontal plane was 0.312 inch. It will be noted that, whereas in the prior art configuration the spacing dis significantly greater than the resonator radius, in our configuration the spacing at can be significantly less than the resonator radius with a corresponding reduction of the required lateral dimensions of the housing 27 and a reduction in spurious resonances.
  • each resonator 41, 51 and 61 is provided with its own tuning screw 48, S8, and 68.
  • the entire assembly 43 is shown with the coaxial couplings 69 and 70.
  • FIG. 5 a plane view in section showing principally the configuration of the principal conductor 44 illustrates where the impedance-matching changes in width of the principal conductor occur with respect to the lateral dimensions of the resonators 41, 51 and 61. Specifically, these changes in width are vertically aligned with the resonators.
  • the tuning screws 48, 58 and 68 allow plus frequency tuning when the screw is a conductor or minus frequency tuning when the screw is a dielectric. In other respects the design and operation of the filters of FIG. 4 and 5 follow known principles for dielectric resonators used with stripline.
  • the curves 71, 81 generally show the return loss S i versus frequency; the curves 72, 82 show transmission 21 versus frequency.
  • Characteristics for a filter utilizing Ba Ti O resonators are represented in FIG. 6.
  • the unloaded resonator Q, Q can be calculated giving an approximate value of 6,300.
  • the above Q, value compares well with the undegraded resonator Q of 6,780 verifying that the Q degradation is not significant with this filter configuration.
  • the out-of-band return loss over 3.7 to 4.2 GHZ is 26dB. This parameter is determined by the uniformity of the stripline impedance throughout the filter rather than upon the resonator properties themselves.
  • the peak insertion loss is approximately given by the following equation:
  • Equation 1 gives 104 dB whereas the measured value is 84 dB. M's.
  • Curves 81 and 82, l ul and IS versus frequency for a filter utilizing LiTaO /T i0; composite resonators are given in FIG. 7.
  • the coupling Q QC, omens) /Qo)" -v the Q associated with the dissipation losses external to the resonators is 10,463.
  • the out-of-band return loss is measured at 28 dB. Equation 2 yields a peak insertion loss of 91 dB whereas the measured value is 64 dB.
  • the outof-band insertion loss for the BazTigozo and Li- TaO /TiO filters is 0.10 dB and 0.175 dB, respectively. This parameter is essentially independent of the dielectric resonator properties and depends upon the quality of the transmission line used in the filter.
  • the curve 91 shows the transmission characteristic of the multiple resonator filter versus frequency at 40 Fahrenheit.
  • the same transmission versus frequency characteristic is shown by the displaced curve 92 for a temperature of 141 Fahrenheit.
  • the shift then characteristically was 2.625 MHz. This value is less than the 3.17 MHz value shift predicted from the temperature coefficient of an isolated resonator because of a small compensating effect related to the use of an alumina substrate 42 and the. metal filter housing 47, for the case of use of barium titanate in the resonators 41, 51 and 61.
  • the temperature coefficient of frequency is positive for barium titanate and is negative for alumina and the housing effect.
  • the resonators used in this filter possessed an average temperature coefficient of frequency, 1, 14.3 ppmC.
  • a band-pass filter is formed by positioning one or more resonators in a section of waveguide that is beyond cut-off at the frequen: cies of interest, in the absence of the resonators.
  • the dielectric resonators 103 which are like resonator 21 of FIG. 2 or respectively like resonators 41, 51 and 61 of FIGS. 4 and 5, are spaced apart in housing 101 above stripline 102.
  • the housing 1011 s a section of waveguide, illustratively rectangular, which is beyond cut-off; that is, it will not propagate the frequencies of the intended passband in the absence of resonators 103.
  • the intended pass-band frequencies lie in a band which is centered at the resonant frequencies of the resonators 103. Electromagnetic energy is coupled through the structure from left to right in the drawing. At other frequencies, outside of the pass-band, very little energy is propagated through the structure.
  • FIGS. 9A and 9B show the direct-coupled band-pass filter.
  • the input and output sections of stripline 102 are coupled to the end resonators 103 and the inner ones of the resonators 103 directly couple energy to adjacent resonators.
  • the resonators couplings and hence the filter characteristics are determined by the inter-resonator spacings between the inner resonators as well as the coupling between the end resonators and the input and output striplines.
  • the resonators 103 are disposed over the stripline 102 in the position that is basically off center with respect to at least portions 109 and 110 of the principal conductor 105 of the stripline 102.
  • the resonators 103 are spaced from the principal conductor 105 of the stripline 102 and fromportions 109 and 110 by dielectric spacers, the dielectric spacer 106 being over portion 109, the spacer 107 being over a portion of stripline 102 having no principal conductor within the interior of the housing 10l,'and the spacer 108 being over the portion 110 of stripline 102.
  • the lateral distance between the resonator and the end of the stripline principle conductor is determined such that strong coupling is obtained between the stripline and the end resonator while providing negligible coupling between the stripline and the inner resonators.
  • the direct-coupled band-pass filter of FIGS. 9A and 9B typically yields the best results of the types we have investigated and, in addition, is smaller and simpler than the quarterwave-coupled type described hereinafter.
  • the coupling characteristics between an end resonator and the stripline are set forth in FIG. 11 by curves 121 through 124, in terms of the effective overall, Q of the filter as a function of the spacing A from the resonator edge to principal conductor edge, as shown in FIG. 12.
  • the respective curves 121 through 124 represent the differing spacer thicknesses of spacers 106 through 108 for different filter designs, specifically.
  • the coupling is similar to that used in our band-elimination filters described above in that the lateral offset is adjusted to the position yielding a broad, flat maximum of coupling to the resonant mode of the resonator to be utilized. Most of the. fabrication advantages of our invention and other advantages described above also apply here for that reason.
  • the coupling can be precisely controlled and is a function of the thickness of the dielectric spacers, for example spacers 106 through 108, used to locate the resonators 103 over the stripline.
  • the coupling is relatively insensitive to the lateral off-set with respect to the center conductor.
  • the spacing of the resonators over the center conductor reduces the degradation of the resonator Q due to conductor loss in the bottom ground plane of housing 101.
  • the clearance from the resonator to the top ground plane is sufficient to limit the resonator Q degradation to an acceptable level.
  • the housing width is reduced such that spurious housing resonances are eliminated.
  • FIGS. 10A and 108 A quarterwave-coupled band-pass filter is illustrated in FIGS. 10A and 108.
  • This structure resembles a number of single resonator filters connected in cascade and spaced from one another by odd multiples of a quarterwave length.
  • the filter of FIGS. 10A and 108 can be compared to that of FIGS. 9A and 9B in that the spacing between resonators 103 is about three-fourths of a wavelength between each pair and in that sections of the principal conductor 10S extend between the resonators so that the only portion of stripline 102 free of principal conductor is a small space directly under each of the resonators 103.
  • This configuration is larger and more difficult to fabricate than that of FIGS. 9A and 9B.
  • the filter characteristics may be determined by the coupling to each resonator.
  • dB insertion loss of curve 131 at f0 corresponds to a resonator Q of 3,260.
  • the undegraded resonator Q is approximately 6,000.
  • a microwave circuit comprising a stripline including a planar dielectric substrate and a principal conductor deposited on one surface of said substrate, and means for filtering a portion of the frequencies of microwave radiation'transmitted through said stripline, comprising a dielectric resonator having planar surfaces parallel to the plane of said substrate and having a composition selected for temperature compensation of its resonant frequencies, and a dielectric spacer between said resonator and said conductor, said resonator being offset from symmetrical alignment over said conductor and adapted to support a TE 5 mode of its resonant frequencies, the degree of offset being selected to maximize the degree of coupling of said mode from said stripline to said resonator.
  • a microwave circuit according to claim I in which the composition of the dielectric resonator is selected to have positive coefficient of frequency variation with respect to temperature and the substrate of the stripline and housing effects are selected to have a negative coefficient of frequency variation with respect to temperature.
  • a microwave circuit according to claim 3 including a ground plane having a metallic housing structure about the dielectric resonator, the housing structure being selected to have the opposite coefficient frequency variation with respect to temperature as compared to that possessed by the dielectric resonator.
  • a microwave circuit according to claim 4 including means for" tuning the filter characteristic of the dielectric resonator.
  • a microwave circuit according to claim 1 including a plurality of the dielectric resonators disposed at least partially over the principal conductor and separated by odd multiples of a quarter wavelengths from one another to minimize spurious coupling resonances therebetween, said circuit including a metallic housing structure intruding between said resonators.
  • a microwave circuit according to claim 1 including a waveguide housing that is proportioned to be beyond cut-off for a band of frequencies to be propagated and including a plurality of dielectric resonators disposed within said housing with spacings for mutual coupling therebetween to provide propagation through the housing for the band of frequencies, the stripline comprising a planar dielectric substrate extending completely through the housing and a principal conductor that is broken in at least one region within said housing in proximity to one or more of the resonators.
  • a microwave circuit according to claim 8 in which the principal conductor is terminated under the end resonators of the plurality of resonators and is absent therebetween.
  • a microwave circuit according to claim 8 in which the plurality of dielectric resonators have spacings between adjacent resonators substantially equal to a quarterwave length for the center frequency of the band of frequencies and the principal conductor includes segments extending between adjacent resonators, so that the principal conductor lacks continuity only in a plurality of limited regions respectively adjacent to each of the resonators.

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US00413907A 1973-11-08 1973-11-08 Temperature-stable dielectric resonator filters for stripline Expired - Lifetime US3840828A (en)

Priority Applications (8)

Application Number Priority Date Filing Date Title
US00413907A US3840828A (en) 1973-11-08 1973-11-08 Temperature-stable dielectric resonator filters for stripline
CA206,057A CA1005536A (en) 1973-11-08 1974-07-31 Temperature-stable dielectric resonator filters for stripline
SE7413536A SE400144B (sv) 1973-11-08 1974-10-28 Dielektriskt resonatorfilter
GB47668/74A GB1485505A (en) 1973-11-08 1974-11-04 Microwave circuits with stripline
NLAANVRAGE7414351,A NL177641C (nl) 1973-11-08 1974-11-04 Dielektrisch resonatorfilter.
FR7436602A FR2251127B1 (xx) 1973-11-08 1974-11-04
DE2452743A DE2452743C2 (de) 1973-11-08 1974-11-07 Filter mit einem Streifenleiter
JP49128154A JPS587082B2 (ja) 1973-11-08 1974-11-08 ユウデンタイキヨウシンキフイルタ

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JP (1) JPS587082B2 (xx)
CA (1) CA1005536A (xx)
DE (1) DE2452743C2 (xx)
FR (1) FR2251127B1 (xx)
GB (1) GB1485505A (xx)
NL (1) NL177641C (xx)
SE (1) SE400144B (xx)

Cited By (31)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3973226A (en) * 1973-07-19 1976-08-03 Patelhold Patentverwertungs- Und Elektro-Holding Ag Filter for electromagnetic waves
US4019161A (en) * 1974-09-02 1977-04-19 Hitachi, Ltd. Temperature compensated dielectric resonator device
US4028643A (en) * 1976-05-12 1977-06-07 University Of Illinois Foundation Waveguide having strip dielectric structure
JPS52153359A (en) * 1976-06-14 1977-12-20 Murata Manufacturing Co Dielectric resonator
US4079341A (en) * 1977-03-01 1978-03-14 Bell Telephone Laboratories, Incorporated Microwave oscillator having feedback coupled through a dielectric resonator
DE2802461A1 (de) * 1977-01-21 1978-07-27 Sony Corp Integrierter mikrowellenoszillator
US4124830A (en) * 1977-09-27 1978-11-07 Bell Telephone Laboratories, Incorporated Waveguide filter employing dielectric resonators
US4184133A (en) * 1977-11-28 1980-01-15 Rockwell International Corporation Assembly of microwave integrated circuits having a structurally continuous ground plane
US4241322A (en) * 1979-09-24 1980-12-23 Bell Telephone Laboratories, Incorporated Compact microwave filter with dielectric resonator
US4307352A (en) * 1978-10-17 1981-12-22 Hitachi, Ltd. Micro-strip oscillator with dielectric resonator
US4477785A (en) * 1981-12-02 1984-10-16 Communications Satellite Corporation Generalized dielectric resonator filter
US4484162A (en) * 1981-08-07 1984-11-20 Alps Electric Co., Ltd. Microwave oscillator
US4559490A (en) * 1983-12-30 1985-12-17 Motorola, Inc. Method for maintaining constant bandwidth over a frequency spectrum in a dielectric resonator filter
US4568894A (en) * 1983-12-30 1986-02-04 Motorola, Inc. Dielectric resonator filter to achieve a desired bandwidth characteristic
EP0183485A2 (en) * 1984-11-23 1986-06-04 Tektronix, Inc. Dielectric resonator frequency selective network
US4593460A (en) * 1983-12-30 1986-06-10 Motorola, Inc. Method to achieve a desired bandwidth at a given frequency in a dielectric resonator filter
US4646038A (en) * 1986-04-07 1987-02-24 Motorola, Inc. Ceramic resonator filter with electromagnetic shielding
US4667172A (en) * 1986-04-07 1987-05-19 Motorola, Inc. Ceramic transmitter combiner with variable electrical length tuning stub and coupling loop interface
US4682131A (en) * 1985-06-07 1987-07-21 Motorola Inc. High-Q RF filter with printed circuit board mounting temperature compensated and impedance matched helical resonators
US4940955A (en) * 1989-01-03 1990-07-10 Motorola, Inc. Temperature compensated stripline structure
EP0440334A2 (en) * 1990-01-31 1991-08-07 Gec-Marconi Limited Dielectric resonant oscillator
US5065119A (en) * 1990-03-02 1991-11-12 Orion Industries, Inc. Narrow-band, bandstop filter
WO1992011664A1 (en) * 1990-12-17 1992-07-09 Nokia Telecommunications Oy High-frequency band-pass filter
US5191304A (en) * 1990-03-02 1993-03-02 Orion Industries, Inc. Bandstop filter having symmetrically altered or compensated quarter wavelength transmission line sections
US5235298A (en) * 1989-07-07 1993-08-10 Ngk Spark Plug Co., Ltd. Temperature compensated stripline filter for microwaves
US5391543A (en) * 1991-07-08 1995-02-21 Sumitomo Electric Industries, Ltd. Microwave resonator of compound oxide superconductor material having a tuning element with a superconductive tip
US6011446A (en) * 1998-05-21 2000-01-04 Delphi Components, Inc. RF/microwave oscillator having frequency-adjustable DC bias circuit
EP1001482A1 (en) * 1998-11-09 2000-05-17 Murata Manufacturing Co., Ltd. Resonance device, and oscillator, filter, duplexer, and communication device incorporating same
US6362708B1 (en) 1998-05-21 2002-03-26 Lucix Corporation Dielectric resonator tuning device
US20160301378A1 (en) * 2013-12-16 2016-10-13 Huawei Technologies Co., Ltd. Duplexer and Communications System Having Duplexer
EP3540849A4 (en) * 2016-11-29 2019-11-20 Huawei Technologies Co., Ltd. FILTER AND COMMUNICATION DEVICE

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JPS5423448A (en) * 1977-07-25 1979-02-22 Toshiba Corp Microwave filter
FR2431773A1 (fr) * 1978-07-21 1980-02-15 Thomson Csf Filtre hyperfrequence a resonateurs en dielectrique et materiel pour telecommunications muni d'un tel filtre
FR2511548A1 (fr) * 1981-08-14 1983-02-18 Thomson Csf Filtre coupe-bande a structure coaxiale
JPS58120301A (ja) * 1982-01-12 1983-07-18 Sony Corp 帯域通過フイルタ
JPS60250702A (ja) * 1984-05-25 1985-12-11 Murata Mfg Co Ltd ケ−ス付共振器
JPS6170404U (xx) * 1984-10-12 1986-05-14
JPS61121379U (xx) * 1985-01-16 1986-07-31
JPS61121380U (xx) * 1985-01-16 1986-07-31
EP0235123B1 (en) * 1985-07-08 1991-11-21 Space Systems / Loral, Inc. Narrow bandpass dielectric resonator filter
JPH055689Y2 (xx) * 1985-07-15 1993-02-15
JPS6393201A (ja) * 1986-10-07 1988-04-23 Nec Corp 誘電体共振器帯域フイルタ
GB2234399B (en) * 1989-06-21 1993-12-15 Murata Manufacturing Co Dielectric filter
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Cited By (41)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3973226A (en) * 1973-07-19 1976-08-03 Patelhold Patentverwertungs- Und Elektro-Holding Ag Filter for electromagnetic waves
US4019161A (en) * 1974-09-02 1977-04-19 Hitachi, Ltd. Temperature compensated dielectric resonator device
US4028643A (en) * 1976-05-12 1977-06-07 University Of Illinois Foundation Waveguide having strip dielectric structure
JPS6122481B2 (xx) * 1976-06-14 1986-05-31 Murata Manufacturing Co
JPS52153359A (en) * 1976-06-14 1977-12-20 Murata Manufacturing Co Dielectric resonator
US4136320A (en) * 1976-06-14 1979-01-23 Murata Manufacturing Co., Ltd. Method of constructing dielectric resonator unit and dielectric resonator unit produced thereby
DE2802461A1 (de) * 1977-01-21 1978-07-27 Sony Corp Integrierter mikrowellenoszillator
US4079341A (en) * 1977-03-01 1978-03-14 Bell Telephone Laboratories, Incorporated Microwave oscillator having feedback coupled through a dielectric resonator
US4124830A (en) * 1977-09-27 1978-11-07 Bell Telephone Laboratories, Incorporated Waveguide filter employing dielectric resonators
FR2404316A1 (fr) * 1977-09-27 1979-04-20 Western Electric Co Filtre en guide d'ondes a resonateurs dielectriques
US4184133A (en) * 1977-11-28 1980-01-15 Rockwell International Corporation Assembly of microwave integrated circuits having a structurally continuous ground plane
US4307352A (en) * 1978-10-17 1981-12-22 Hitachi, Ltd. Micro-strip oscillator with dielectric resonator
US4241322A (en) * 1979-09-24 1980-12-23 Bell Telephone Laboratories, Incorporated Compact microwave filter with dielectric resonator
US4484162A (en) * 1981-08-07 1984-11-20 Alps Electric Co., Ltd. Microwave oscillator
US4477785A (en) * 1981-12-02 1984-10-16 Communications Satellite Corporation Generalized dielectric resonator filter
US4559490A (en) * 1983-12-30 1985-12-17 Motorola, Inc. Method for maintaining constant bandwidth over a frequency spectrum in a dielectric resonator filter
US4568894A (en) * 1983-12-30 1986-02-04 Motorola, Inc. Dielectric resonator filter to achieve a desired bandwidth characteristic
US4593460A (en) * 1983-12-30 1986-06-10 Motorola, Inc. Method to achieve a desired bandwidth at a given frequency in a dielectric resonator filter
EP0183485A2 (en) * 1984-11-23 1986-06-04 Tektronix, Inc. Dielectric resonator frequency selective network
EP0183485A3 (en) * 1984-11-23 1987-09-02 Tektronix, Inc. Dielectric resonator frequency selective network
US4682131A (en) * 1985-06-07 1987-07-21 Motorola Inc. High-Q RF filter with printed circuit board mounting temperature compensated and impedance matched helical resonators
US4667172A (en) * 1986-04-07 1987-05-19 Motorola, Inc. Ceramic transmitter combiner with variable electrical length tuning stub and coupling loop interface
US4646038A (en) * 1986-04-07 1987-02-24 Motorola, Inc. Ceramic resonator filter with electromagnetic shielding
US4940955A (en) * 1989-01-03 1990-07-10 Motorola, Inc. Temperature compensated stripline structure
US5235298A (en) * 1989-07-07 1993-08-10 Ngk Spark Plug Co., Ltd. Temperature compensated stripline filter for microwaves
EP0440334A2 (en) * 1990-01-31 1991-08-07 Gec-Marconi Limited Dielectric resonant oscillator
EP0440334A3 (en) * 1990-01-31 1992-07-08 Gec-Marconi Limited Dielectric resonant oscillator
US5065119A (en) * 1990-03-02 1991-11-12 Orion Industries, Inc. Narrow-band, bandstop filter
US5191304A (en) * 1990-03-02 1993-03-02 Orion Industries, Inc. Bandstop filter having symmetrically altered or compensated quarter wavelength transmission line sections
AU653765B2 (en) * 1990-12-17 1994-10-13 Nokia Telecommunications Oy pigh-frequency band-pass filter
WO1992011664A1 (en) * 1990-12-17 1992-07-09 Nokia Telecommunications Oy High-frequency band-pass filter
US5389903A (en) * 1990-12-17 1995-02-14 Nokia Telecommunications Oy Comb-line high-frequency band-pass filter having adjustment for varying coupling type between adjacent coaxial resonators
US5391543A (en) * 1991-07-08 1995-02-21 Sumitomo Electric Industries, Ltd. Microwave resonator of compound oxide superconductor material having a tuning element with a superconductive tip
US6011446A (en) * 1998-05-21 2000-01-04 Delphi Components, Inc. RF/microwave oscillator having frequency-adjustable DC bias circuit
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Also Published As

Publication number Publication date
NL7414351A (nl) 1975-05-12
JPS587082B2 (ja) 1983-02-08
CA1005536A (en) 1977-02-15
SE400144B (sv) 1978-03-13
GB1485505A (en) 1977-09-14
JPS5081043A (xx) 1975-07-01
DE2452743C2 (de) 1987-11-12
SE7413536L (xx) 1975-05-09
NL177641B (nl) 1985-05-17
NL177641C (nl) 1985-10-16
FR2251127B1 (xx) 1978-11-24
DE2452743A1 (de) 1975-05-22
FR2251127A1 (xx) 1975-06-06

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