US3769610A - Voltage controlled variable power divider - Google Patents

Voltage controlled variable power divider Download PDF

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Publication number
US3769610A
US3769610A US00263229A US3769610DA US3769610A US 3769610 A US3769610 A US 3769610A US 00263229 A US00263229 A US 00263229A US 3769610D A US3769610D A US 3769610DA US 3769610 A US3769610 A US 3769610A
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phase
radio frequency
terminal
output ports
hybrid coupler
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US00263229A
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A Savarin
G Rader
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SPACE SYSTEMS/LORAL Inc A CORP OF DELAWARE
Maxar Space LLC
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Philco Ford Corp
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/04—Coupling devices of the waveguide type with variable factor of coupling
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/24—Frequency- independent attenuators
    • H03H7/25—Frequency- independent attenuators comprising an element controlled by an electric or magnetic variable
    • H03H7/253—Frequency- independent attenuators comprising an element controlled by an electric or magnetic variable the element being a diode
    • H03H7/256—Frequency- independent attenuators comprising an element controlled by an electric or magnetic variable the element being a diode the element being a VARACTOR diode
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/48—Networks for connecting several sources or loads, working on the same frequency or frequency band, to a common load or source

Definitions

  • Variable power dividers are well known in the prior art. Typically an input terminal and two (or possibly more) output terminals are involved. Power applied to the input is divided between the output terminals and, by means of a control, the division ratio can be varied. This control is usually of the mechanical variety and ordinarily varies the coupling between inductors or capacitive plates. Electronic control of power dividers has been accomplished using magnetically biased ferrites but typically these devices operate as switches rather than controllable ratio dividers. Electronic switches using varactor diodes are well known and complex switching arrays can be achieved but these devices too operate in the off or on state rather than as controllable ratio power dividers.
  • varactor diodes can be used to increase power-handling capabilities while retaining the desired control function.
  • the power divider is fully reciprocal.
  • a fixed power divider feeds equal signals to two ports of a 90 hybrid.
  • Each signal is subjected to the variable phase action of a reverse biased varactor diode. If each path is subjected to a 45 phase shift the hybrid output ports will contain equalamplitude in-phase signals.
  • the diodes are provided with inverse bias controls so that the phase shift of one is increased as the phase shift of the other is decreased by the same amount. Therefore as one diode approaches a 90 phase shift, the other diode will approach For this condition virtually all of the input power appears at one hybridoutput port.
  • the diode phase shift conditions are reversed the power output is transferred to the other hybrid output. If the diode control signals are correctly shaped, a continuously variable power division ratio can be achieved with the outputs at all ratios being of essentially the same phase.
  • the device is fully reciprocal. If two in-phase signals are applied to the output ports, they will be summed at the input port. The relative weight given to signals applied to the output ports on summing at the input will be a function of the control bias.
  • the two signal channels are each coupled by means of 4-port hybrids to shuntconnected varactor diodes so that multiple diodes can be employed. This permits using as many diodes as required for the desired power handling capabilities.
  • FIG. 1 is a partial schematic block diagram of a voltage controlled variable power divider
  • FIG. 2 is a graph showing the relationship of the control l and control 2 voltages of FIG. 1;
  • FIG. 3 is a graph plotting output of the variable power divider as a function of control 1 bias voltage
  • FIG. 4 is a graph plotting voltage versus time of control signals designed to provide a linear shift of output power as a function of time;
  • FIG. 5 is a partial schematic block diagram of an improved voltage controlled variable power divider
  • FIG. 6 is a showing of stripline construction of the preferred embodiment of FIG. 5.
  • FIG. 6a shows the details of the stripline conductors on the underside of substrate 19 of FIG. 6.
  • FIG. 1 shows a basic variable power divider. While the showing is in part-schematic block-diagram form, the actual circuit could be realized using waveguides, coaxial lines, open wire lines, or strip lines. Strip line construction is preferred because it is compact, rugged, and oflow loss. Also it is easy to fabricate to reasonably high precision.
  • Input device 1 is an equal power divider designed to split the input into equal parts to be applied to the phase shifters.
  • Resistor 2 acts to absorb any signal energy that is not balanced at the equal power divider output.
  • the resistor is desired but not necessary to circuit operation.
  • Equal power inputs are applied to phase shifters 3 and 4, which desirably may comprise varactors or voltage variable capacitor diodes. When a semiconductor junction diode is reverse biased, it presents an almost pure capacitive reactance. The value of reactance increases with increasing reverse bias in a controlled manner. Thus the bias voltages applied to phase shifters 3 and 4 permit control of the value of phase shift.
  • the phase shifters are designed so that they produce a 45 phase shift when their bias voltages are equal.
  • phase shifters are connected to a 3-dB 90 hybrid coupler 5. This device is constituted so that equal outputs occur at output ports 1 and 2 when the input signals are of the same phase. When the inputs are 90 out of phase, all of the output energy appears at one output port, and for the opposite 90 input phase condition all of the output appears at the other port. Thus for the equal bias or 45 phase-shift condition of phase shifters 3 and 4, input port power will be divided equally between output ports 1 and 2. As the diode biases are varied by the voltages applied to the control 1 and control 2 terminals, the power split is varied.
  • FIG. 2 shows the bias voltage relationship of the two phase shifters.
  • the line shows the relative bias requirements to achieve the desired complementary phase shift. It will be noted that the 45 voltage (the equal voltage condition) occurs at about 20 volts.
  • FIG. 3 plots the outputs as a function of control 1 bias voltage. While not shown on this graph, the control 2 bias voltage is operated to be in accord with FIG. 2. It can be seen that the 3-dB point occurs at about 20 volts. For an insertion loss of slightly over ldB the alternate channel attenuation is better than 20 dB (or over 100 times in power).
  • FIG. 4 shows a pair of waveforms designed to operate the variable power divider.
  • control I is at maximum bias while control 2 is at minimum bias.
  • one output port will receive all of the power while the other port is at least 100 times weaker (20dB down).
  • control 1 voltage declines as control 2 voltage increases.
  • Half way through the transfer the two control signals are equal and the two output ports have equal output power.
  • the waveforms are so shaped that the power transfer is a linear function of time. These waveforms are shaped to insureconstant output phase at both output ports.
  • variable power divider of FIG. 1 has been found very useful in amplitude-steered multiple-element antenna arrays. A detailed showing of such an application appears in copending US. Pat. application Ser. No. 263,230 filed June 15, 1972. That application also shows but does not claim the variable power divider of FIG. 1.
  • FIG. 5 shows an improved version of a variable power divider in which the signal energy traverse the varactor diodes is reduced.
  • the diode reactance is shunt connected by means of equal power divider thereby permitting the use of parallel diodes to provide higher power operation.
  • the varactor diodes are not driven into either forward conduction or reverse breakdown.
  • operating biases are typically in the range of about 12 to 40 volts.
  • the equal power divider I and resistor 2 are as shown in FIG. 1, as is output hybrid 5.
  • Two 3dB.90 hybrids 6 and 7 couple energy between theequal power divider l and the output hybrid 5. These hybrids provide means for shunt reactance phase shift control.
  • hybrid 6 four varactor reactance control diodes are connected thereto.
  • Equal power divider 8 connects two varactors 9 and 10 to one port of hybrid 6. Varactor 9 is connected electrically across tuning stub 11 while varactor 10 is connected electrically across tuning stub 12.
  • Capacitor l3 completes the parallel rf connection while blocking the applied d-c bias from ground. Tuning stubs 11 and 12 are adjustable and approximately one-quarter wavelength long.
  • diodes 9 and 10 which are preferably a matched pair.
  • Inductor l4 and capacitor 15 complete a pi network filter designed to eliminate any rf energy from the control 2 line.
  • the diodes are provided with the bias voltage required for 45 or equal output operation and the tuning stubs adjusted for the correct phase shift.
  • a single diode could be connected to each of the lower ports of hybrid 6. This would eliminate the equal power dividers and two of the diodes with their associated tuning stubs and bias supply networks. The single diode and its tuning stub would be connected directly to the hybrid port.
  • FIG. 6 shows how the apparatus of FIG. 5 is set up for stripline fabrication. More specifically, device 17 of FIG. 6 performs the functions of equal power divider 1, output hybrid 5, and coupling hybrids 6 and 7 of FIG. 5, while device. 18 of FIG. 6 comprises the two equal power dividers, associated diodes, and tuning stubs illustrated in the lower portion of FIG. 6.
  • the conductors shown I constitute 1.5 mil thick copper on an insulating substrate 19 which is 11 mils thick.
  • the wide conductors represent 50 ohm impedance lines and are 106 mils across whereas the narrow conductors are 52 mils across and represent 70.7 ohm line impedance.
  • the stripline is two sided with the under side pattern (where not obscured by the presence of the upper side pattern) shown in dotted outline. While not shown, the wiring panel is overlaid on both sides with 58 mil thick dielectric slabs and these are in turn covered with aluminum plates that complete the sandwich and provide the usual ground plane conductors.
  • Resistor 2 is a I00 ohm disk. The assembly is held inside an aluminum frame 21 that mounts 7 coaxial connectors.
  • Connector 22 constitutes a 50-ohm input port while connectors 23 and 24 constitutethe SO-ohm output ports.
  • Connectors 25 and 26 provide coupling with the shunt multiple varactor device 18 of the lower portion of FIG. 6 by way of coaxial cables 33 and 34.
  • a device similar to 18, not illustrated, would be connected to connectors 27 and '28.
  • the two-sided strip line construction of device 17 permits simplified fabrication of the hybrids 5, 6 and 7 of FIG. 5. Details of this construction will be understood if reference is had not only to FIG. 6 but also to FIG. 6a.
  • the latter shows, on a reduced scale, a view from above of the under-side conductors of substrate 19, which conductors, though partially shown in FIG. 6 in'dotted outline, are largely obscured by the presence of the upper-side conductors.
  • Upper-side straight conductor 7a combines with under side straight conductor 7b to provide the coupling supplied by hybrid 7.
  • upper-side straight conductor 5a combines with under-side straight conductor 5b to provide the coupling supplied by hybrid 5.
  • the under-side pattern including conductors 7b and 5b, interconnects connector 27 and output port 24.
  • the coupling supplied by hybrid 6 results from the combination of upper-side conductor 6a and lower-side conductor 6b.
  • Each straight leg of the coupled sections 5, 6, and 7 is made one quarter wavelength long at the operating frequency, hence the term 90 hybrid.
  • coaxial connectors 31 and 32 are mounted on aluminum frame 35 which contains a conducting bottom member to act as a ground plane.
  • the conducting pattern as described above, is 1.5 mil copper but is printed on a 58 mil dielectric substrate 37.
  • Matched diodes 9 and 10 mount between the terminal ends of equal power divider 8.
  • Chip capacitor 13 which is mounted in contact with the ground plane, acts as a d-c blocking r-f bypass capacitor that electrically connects the diodes in parallel with their respective tuning stubs 11 and 12 which are used to resonate the diode circuits.
  • Quarter wavelength wire section 14 provides isolating inductance for the bias feed and is connected to chip bypass capacitor 15, as is shown schematically in FIG. 5. All of the diodes bias connections return to stand off terminal 36 which constitutes the bias control terminal.
  • Another pair of diodes is operated in a similar structure shown in the left half of device 18 so that device 18 contains 4 diodes and their associated circuits.
  • a shield plate covers the exposed face of the varactor section 18 in FIG. 6 and this element ordinarily mounts in close proximity to device 17.
  • the varactor diodes had cutoff frequencies of about 150 GHz, break down voltages of over 50 volts and a zero bias capacitance of about 6 pf. When operated at a 5-watt input level, the maximum insertion loss was only 1.25 dB and the isolation to the off port over20 dB.
  • the control bias ranged between 13 and 34 volts for effective control. The maximum deviation from equal phase was about 7 and appeared at the extreme attenuation value.
  • the power divider showed excellent reciprocal operation at a receiver frequency of 2.030 Gl-Iz.
  • variable capacitance diodes could be used with the value being varied with a controlled magnetic field.
  • variable semiconductor junction capacitor diodes are shown, electrostrictive devices could be used.
  • other equivalent r-f coupling and power distribution devices could be employed. It is intended that the invention be limited only by the following claims:
  • An electronically controlled radio frequency power divider having an input port and two output ports comprising:
  • combining means including a 90 hybrid coupler for combining energy in said two branches, said combining means having two outputs connected to said two output ports the relative magnitudes of which are responsive to the relative phase of said energy in said two branches,
  • phase shifting means in each of said two branches responsive to electronic control said phase shifting means including at least one four-terminal 90 hybrid coupler having two terminals connected in series in said branch and having electronically variable reactances connected to the remaining two terminals, and
  • variable reactances comprise reverse biased semi-conductor diodes connected to said coupler to provide said phase shifting in said branch and biased by said electronic control means.
  • An electronically controlled radio frequency power divider having an input port into which radio frequency energy may be introduced and, under the control of differentially applied control signals, divided differentially between two output ports in such manner that the sum of the powers available from said two output ports is not substantially less than the power introduced at said input port, and the phase difference between the radio frequency energies derived from said output ports remains small over the operating range of said power divider, said power divider comprising:
  • a first four-terminal 90 hybrid coupler having two terminals connected in one of said branch circuits and the other two terminals connected toa first plurality of semiconductor diodes for introducing
  • a second four-terminal hybrid coupler having two terminals connected in the other of said branch circuits and the other two terminals connected to a second plurality of semiconductor diodes for introducing, under the electrical control of a second phase control signal, a phase shift in said other branch, said second phase control signal continuously varying the reverse bias on said second plurality of semiconductor diodes and being differentially related to said first phase control signal, said two branches having equal phase shifts when said first and said .second phase control signals are equal, and
  • a third four terminal 90 hybrid coupler having: one

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US00263229A 1972-06-15 1972-06-15 Voltage controlled variable power divider Expired - Lifetime US3769610A (en)

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Cited By (20)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3955194A (en) * 1973-11-08 1976-05-04 U.S. Philips Corporation Microwave hybrid network producing desired phase difference for use in Doppler radar systems
US3996533A (en) * 1975-07-07 1976-12-07 Lee Chong W High frequency, multi-throw switch employing hybrid couplers and reflection-type phase shifters
US4031488A (en) * 1976-04-05 1977-06-21 The United States Of America As Represented By The Secretary Of The Navy Multiple polarization switch
US4190815A (en) * 1978-03-09 1980-02-26 The United States Of America As Represented By The Secretary Of The Air Force High power hybrid switch
EP0045808A4 (en) * 1980-02-25 1982-07-13 Edward Salzberg MICROWAVE HYBRID COUPLERS.
EP0101941A3 (en) * 1982-07-28 1985-03-13 Textron Inc. High speed high power step attenuator method and apparatus
US4559489A (en) * 1983-09-30 1985-12-17 The Boeing Company Low-loss radio frequency multiple port variable power controller
US4636755A (en) * 1984-07-26 1987-01-13 Motorola, Inc. High-ratio, isolated microwave branch coupler with power divider, phase shifters, and quadrature hybrid
EP0742602A3 (en) * 1995-05-12 1998-03-11 Trw Inc. Monolithic multi-function balanced switch and phase shifter
US20030076198A1 (en) * 2001-08-23 2003-04-24 Ems Technologies, Inc. Microstrip phase shifter
US20040090286A1 (en) * 2002-11-08 2004-05-13 Ems Technologies, Inc. Variable power divider
US20050017822A1 (en) * 2002-11-08 2005-01-27 Ems Technologies, Inc. Variable power divider
US20050030248A1 (en) * 2003-08-06 2005-02-10 Kathrein-Werke Kg, Antenna arrangement
US20050030249A1 (en) * 2003-08-06 2005-02-10 Kathrein-Werke Kg Antenna arrangement and a method in particular for its operation
US20070035361A1 (en) * 2005-08-12 2007-02-15 Martien Rijssemus Signal splitter
US7557675B2 (en) 2005-03-22 2009-07-07 Radiacion Y Microondas, S.A. Broad band mechanical phase shifter
EP2950449A1 (en) * 2014-05-28 2015-12-02 Alcatel Lucent Attenuator
US10181627B2 (en) 2015-08-19 2019-01-15 Honeywell International Inc. Three-port variable power divider
CN112187205A (zh) * 2020-08-20 2021-01-05 电子科技大学 一种任意相差输出的功分滤波网络
CN116318013A (zh) * 2023-03-23 2023-06-23 深圳市资福医疗技术有限公司 一种功率分配调节装置、阻抗调节方法及功率调节方法

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5467063A (en) * 1993-09-21 1995-11-14 Hughes Aircraft Company Adjustable microwave power divider
CN106876854A (zh) * 2017-04-07 2017-06-20 西南应用磁学研究所 低损耗宽带大比例不等分径向功率分配器

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3184691A (en) * 1961-11-29 1965-05-18 Bell Telephone Labor Inc Branching hybrid coupler network useful for broadband power-dividing, duplexing and frequency separation

Cited By (26)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3955194A (en) * 1973-11-08 1976-05-04 U.S. Philips Corporation Microwave hybrid network producing desired phase difference for use in Doppler radar systems
US3996533A (en) * 1975-07-07 1976-12-07 Lee Chong W High frequency, multi-throw switch employing hybrid couplers and reflection-type phase shifters
US4031488A (en) * 1976-04-05 1977-06-21 The United States Of America As Represented By The Secretary Of The Navy Multiple polarization switch
US4190815A (en) * 1978-03-09 1980-02-26 The United States Of America As Represented By The Secretary Of The Air Force High power hybrid switch
EP0045808A4 (en) * 1980-02-25 1982-07-13 Edward Salzberg MICROWAVE HYBRID COUPLERS.
EP0101941A3 (en) * 1982-07-28 1985-03-13 Textron Inc. High speed high power step attenuator method and apparatus
US4559489A (en) * 1983-09-30 1985-12-17 The Boeing Company Low-loss radio frequency multiple port variable power controller
US4636755A (en) * 1984-07-26 1987-01-13 Motorola, Inc. High-ratio, isolated microwave branch coupler with power divider, phase shifters, and quadrature hybrid
EP0742602A3 (en) * 1995-05-12 1998-03-11 Trw Inc. Monolithic multi-function balanced switch and phase shifter
US20030076198A1 (en) * 2001-08-23 2003-04-24 Ems Technologies, Inc. Microstrip phase shifter
US7233217B2 (en) 2001-08-23 2007-06-19 Andrew Corporation Microstrip phase shifter
US6788165B2 (en) 2002-11-08 2004-09-07 Ems Technologies, Inc. Variable power divider
US7221239B2 (en) 2002-11-08 2007-05-22 Andrew Corporation Variable power divider
US20050017822A1 (en) * 2002-11-08 2005-01-27 Ems Technologies, Inc. Variable power divider
US20040090286A1 (en) * 2002-11-08 2004-05-13 Ems Technologies, Inc. Variable power divider
WO2004045017A1 (en) * 2002-11-08 2004-05-27 Ems Technologies, Inc. Variable power divider
US20050030249A1 (en) * 2003-08-06 2005-02-10 Kathrein-Werke Kg Antenna arrangement and a method in particular for its operation
US7038621B2 (en) 2003-08-06 2006-05-02 Kathrein-Werke Kg Antenna arrangement with adjustable radiation pattern and method of operation
US20050030248A1 (en) * 2003-08-06 2005-02-10 Kathrein-Werke Kg, Antenna arrangement
US7557675B2 (en) 2005-03-22 2009-07-07 Radiacion Y Microondas, S.A. Broad band mechanical phase shifter
US20070035361A1 (en) * 2005-08-12 2007-02-15 Martien Rijssemus Signal splitter
US7746194B2 (en) * 2005-08-12 2010-06-29 Technetix Group Limited Signal splitter/combiner for reducing noise ingress and cable television network incorporating plurality of same
EP2950449A1 (en) * 2014-05-28 2015-12-02 Alcatel Lucent Attenuator
US10181627B2 (en) 2015-08-19 2019-01-15 Honeywell International Inc. Three-port variable power divider
CN112187205A (zh) * 2020-08-20 2021-01-05 电子科技大学 一种任意相差输出的功分滤波网络
CN116318013A (zh) * 2023-03-23 2023-06-23 深圳市资福医疗技术有限公司 一种功率分配调节装置、阻抗调节方法及功率调节方法

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GB1424267A (en) 1976-02-11
FR2189935A1 (enrdf_load_html_response) 1974-01-25
DE2329747A1 (de) 1974-01-03
FR2189935B1 (enrdf_load_html_response) 1978-06-30
JPS4952551A (enrdf_load_html_response) 1974-05-22
CA983131A (en) 1976-02-03
NL7308123A (enrdf_load_html_response) 1973-12-18

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