US3450980A - Oscillating switch regulator - Google Patents

Oscillating switch regulator Download PDF

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Publication number
US3450980A
US3450980A US598821A US3450980DA US3450980A US 3450980 A US3450980 A US 3450980A US 598821 A US598821 A US 598821A US 3450980D A US3450980D A US 3450980DA US 3450980 A US3450980 A US 3450980A
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transistor
voltage
switch
output
capacitor
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Arnold L Betton
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Northrop Grumman Guidance and Electronics Co Inc
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Litton Systems Inc
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators

Definitions

  • a regulating power supply for regulating an input source voltage to provide a DC output voltage of a predetermined level including a transistor switch and a filter connected between the input and output with an error signal being generated by comparing output voltage variations with a reference voltage, the error signal actuating a bistable device to a first or second stable state to generate a first or second control signal depending upon the output voltage being above or below the predetermined level, the control signals so generated controlling the transistor switch conductivity or non-conductivity to maintain the predetermined voltage level.
  • This invention relates to a regulating power supply and more particularly to a step-down DC to DC switch regulater.
  • Pulsewidth modulated switching regulators which operate on the principal of time-ratio control are one such type known in the prior art.
  • a time-ratio control power supply a constant output voltage is obtained by Varying the duration of the conducting time of a series switching transistor connected between the load and the source voltage to produce a pulse train with a constant average valve.
  • the conducting time of the series switch transistor is controlled by an error signal which is developed by sampling the output voltage.
  • the error signal is a measure of the difference between the actual output voltage and a desired output voltage level. In typical applications.
  • the rise time of the gating pulses from the commutating circuitry is longer than the minimum interval needed to drive the .series transistor switch out of its state of saturated conduction, thus limiting the maximum eiliciency of this type of power supply.
  • the present invention overcomes the above and other disadvantages of the pulse-width modulated switching regulators of the prior art by providing a series switching transistor and commutating circuitry which, according to the basic concept of the invention, operate at a higher elficency since pulses are provided by the commutating circuitry which have a shortened rise time and thus gate the series switching transistor out of conduction in a minimal time.
  • the regulated power supplies of the invention employ an inverting amplifier which is coupled between the output of a first transistor in a bistable multivibrator and the series switching transistor and which is operative to gate the memori switching transistor out of conduction when the first transistor of the multivibrator goes into conduction.
  • Another object of the invention is to provide a regulated power supply which filters a variable width pulse train from a commutated series switch to provide an output voltage proportional to the average amplitude of the pulse train.
  • Yet another object of the invention is to provide a switching regulator which is rapidly caused to change its state of conduction by control circuitry having a minimal power loss.
  • FIG. 2 is a circuit diagram of a second embodiment of the invention.
  • FIG. 3 illustrates waveforms attendant during the cycle of regulation.
  • a constant output voltage is produced in two stages.
  • transistor switch 12 is actuable to provide constant amplitude pulses of controlled width.
  • a filter comprising inductance 16, capacitor 21 and diode 18, operates to smooth the pulse train.
  • the positive unregulated potential at input terminal is applied to the collector of transistor switch 12.
  • Transistor switch 12 is driven in and out of conduction by gating pluses applied to its base emitter junction, thereby alternately forward biasing and reverse biasing the junction. The transistor conducts when the base-emitter junction is forwarded biased and the collector-base junction is reverse biased. When both junctions are reverse biased, no conduction takes place except for leakage current.
  • Transistor switch 12 is gated in response to an error signal which is, in turn, responsive to variations in the output voltage.
  • the output from the switch a pulsating DC voltage, is applied to inductance 16.
  • Diode 18 is connected to the emitter of transistor 12 and to inductance 16 with a polarity as shown in FIG. 1.
  • Capacitor 2'1 is connected to the other terminal of inductance 16 and to output terminal 23.
  • a positive output potential is obtained at terminal 22 by shunting output terminal 23 to ground terminal 24.
  • a negative output voltage at terminal 23 may be had by connecting terminal 22 to ground terminal 24.
  • capacitor 20 is connected from the emitter of transistor 12 to output terminal 23 to reduce RFI by decreasing the reverse recovery current through diode 18
  • Complementary error signals proportional to deviations in the output voltage from a desired level are developed by dual transistor amplifier 28 and are amplified in a second difference amplifier comprising transistors 40 and 42.
  • a reference potential which is independent of variations in the output voltage, is supplied to the base of transistor 28A by a reference voltage network comprising resistors 30, Zener diode 32 and variable resistor 34. Resistor 30 and variable resistor 34 are connected in series from output terminal 22 to output terminal 24. Zener diode 32 is connected between the junction of resistor 30 and variable resistor 34 to output terminal 24.
  • variable resistor 24 The voltage across variable resistor 24 is a constant value, independent of fluctuations in the output voltage, because of the characteristics of Zener diode 32.
  • the voltage at the adjustable tap of variable resistor 34 a reference voltage variable over particular range, is applied to the base of difference amplifier 28A.
  • Resistor 36 is connected between the common emitters of difference amplifier 28 and output terminal 24.
  • the amount of emitter-base current in transistor 28 is a function of the resistance of resistor 36.
  • a signal responsive to variations in the output voltage is applied to the base of difference amplifier 28B through a sensing network comprising Zener diode 26 and resistor 38. Zener d ode 26 and re i to 38 are connected in se ie between output terminal 22 and output terminal 24.
  • the output signals from difference amplifier 28, a pair of complimentary error signals, are applied to a linear amplifier comprising transistors 40 and 42.
  • the collector of the amplifier 28A is connected to the base of transistor 40; the collector of amplifier 28B to the base of transistor 42.
  • the emitters of transistors 40 and 42 are connected in common.
  • Resistor 44 is connected between the common emitters of transistors 40 and 42 and output terminal 24.
  • the amount of emitter-base current in transistors 40 and 42 is a function of the resistance of resistor 44.
  • Resistor 46 is connected between input terminal 10 and the base of transistor 40. Recall that the unregulated DC source voltage is applied to input terminal 10. This unregulated source voltage less the voltage drop across resistor 46 is applied to the collector of amplifier 28A. Variations in current flow through resistor 46 caused by fluctuations in the base-collector current of difference amplifier 28A drive the base of transistor 40. Resistor 46 also sets the collector-base bias current for transistor 40.
  • Resistor 48 is connected between the unregulated DC source voltage at input terminal 10 and the base of transistor 48. Its functions are similar to those of resistor 46. Thus a pair of complimentary amplified error signals are provided at the collectors of transistors 40 and 42.
  • Amplifier 64 and a bistable multivibrator comprising transistors 50 and 52, control conduction through transistor switch 12 in response to the pair of error signals received from transistors 40 and 42.
  • the error signals are transmitted from the collectors of transistors 40 and 42 by connections to the bases of transistors 50 and 52 respectively.
  • the emitters of transistors 50 and 52 are connected to the source voltage at input terminal 10.
  • the base to emitter junctions of transistors 50 and 52 supply current paths to the source for the collector currents-of transistors 40 and 42 respectively.
  • each stage is alternately conducting and is in an opposite state of conduction from the other stage.
  • Transistors 50 and 52 are alternately driven into conduction by the error signals applied to their bases.
  • Resistor 56 provides a current path to the negative input terminal 11 for the collector current of transistor 50.
  • diode 62 and resistor 60 complete the circuit for the collector current of transistor 52.
  • Capacitor 54 is connected from the collector of transistor 50 to the base of 52.
  • Capacitor 58 is connected from the junction of resistor 60 and diode 62 to the base of transistor 50.
  • Capacitors 54 and 58 provide the cross coupling between transistors 50 and 52 which is necessary to cutoff one stage when the other starts conducting. For'example, when transistor 50 begins conducting capacitor 54 discharges into the base of transistor 52. This current flow reverse biases the baseemitter junction of transistor 52 thereby driving transistor '52 out of conduction.
  • capacitor 58 discharges into the base of transistor 50 thereby driving transistor 50 out of conduction as a result of transistor 52 beginning to conduct.
  • the frequency at which the multivibrator changes stage is a function of the charging time of the capacitors 54 and 58. This frequency is primarily determined by the amount of collector current in transistors 40 and 42. Because these collector currents vary as a function of the fluctuations in the output voltage at output terminal 22, the conducting time of transistors 50 and 52 will also be a function of the output voltage.
  • the collector of transistor 52 is connected to the base of transistor switch 12. Each time that the error signal at the base of transistor 52 drives transistor 52 into conduction, the potential at the collector of transistor 52 approaches the positive potential at input terminal 10. This fast rising positive potential is applied at the base of transistor switch 12 for actuating transistor switch 12 into conduction.
  • switching amplifier 64 drives transistor switch 12 out of conduction each time that transistor 50 is driven into conduction by the error signal appearing at the base of transistor 50.
  • Capacitor 66 is connected between the base of switching amplifier 64 and the collector of transistor 50.
  • the collector of transistor 64 is coupled to the base of transistor switch 12.
  • the emitter of transistor 64 is connected to a bias network comprising capacitor 68, diode 70, resistor 72, and capacitor 74.
  • the sharp positive rise in voltage appearing at the collector of transistor 50 when transistor 50 begins to conduct is transmitted by capacitor 66 to the base of transistor amplifier 64. This fast rising positive pulse drives transistor amplifier '64 into conduction. Recall that transistor 52 will be driven out of conduction when transistor 50 goes into conduction.
  • Diode 62 isolates the collector of transistor 52 from capacitor 58. This has the effect of making the time required to actuate transistor switch 12 out of conduction a function of the sharp negative pulse appearing at the collector of transistor 64 rather than a function of the rate at which capacitor 58 discharges.
  • the network comprising capacitor 68, diode 70, resistor 72 and capacitor 74 is a bias circuit for transistor 64.
  • Capacitor 68 is connected from the emitter of transistor 64 to input terminal 11. Capacitor 68 rapidly discharges when amplifier 64 conducts.
  • Resistor 72 and capacitor 74 are connected in series from input terminal 11 to the emitter of transistor switch 12.
  • Diode 70 is connected between the emitter of transistor 64 and the common connection between resistor 72 and capacitor 74. It will be recalled that transistor 64 was driven into conduction in order to cut-01f transistor switch 12 sharply. When transistor switch 12 ceases to conduct capacitor 74 negatively charges into capacitor 68. Charging capacitor 68 with a negative voltage drives transistor switching amplifier 64 out of conduction thereby readying it'for the next cycle.
  • the reference voltage supplied to the base of difference amplifier 28 is obtained from the unregulated DC source potential at input terminal 10.
  • a voltage divider network is connected between input terminals and 11.
  • This voltage divider comprises the resistive network of resistors 76, 78 and 80 connected in series with Zener diode 82. Because of the characteristics of Zener diode 82 the voltage at the junction of the diode and the resistors remains constant.
  • This constant voltage supplies a second voltage divider network connected between this junction and input terminal 11.
  • This second voltage divider network comprises resistor 84 connected in series with the parallel network of capacitor 86, Zener diode 32 and variable resistor 34.
  • a constant voltage which is variable over a certain range is available at the top of variable resistor 34.
  • This embodiment of the invention is used when the desired output voltage is too low to supply the reference voltage needed for proper operation of difference amplifier 28.
  • a stepdown DC to DC voltage conversion is accomplished by rapidly opening and closing switch 12 which is connected to a source voltage.
  • the output of switch 12 is a pulsating DC voltage that is nearly equal to the source voltage when the switch is on and zero when the switch is off.
  • the average value of the output voltage of switch 12 is proportional to the input voltage and to the ratio of conducting time of switch 12 to total operating time.
  • the use of a diode 18 shunting the switch and an inductance 16 in series with the switch provides a path for the load current when switch 12 is opened and thus permits continuous current flow.
  • the output voltage to the load is maintained at a predetermined level by actuating switch 12 in response to an error signal which is a measure of the deviation of the output voltage from the predetermined level.
  • the error signal is produced by comparing the output voltage with a reference voltage in differential amplifier 28. If the output voltage drops below the desired value,
  • the error signal will turn switch 12 on; and, likewise, if the output voltage rises above the desired value, the error signal will turn switch 12 off.
  • the average value of the output voltage at output terminal 22 remains constant.
  • the switching action cannot occur at the instant the output voltage deviates above or below the desired value because of the delay in actuating circuitry and in the transistor switch itself.
  • the time delay in the switching action results in a slight overshoot or undershoot of the output voltage.
  • the output voltage varies in a small bandwidth about the desired level.
  • the principal of actuation utilized in the various embodiments of the invention is pulse-width modulation.
  • Switch 12 will conduct only so long as the output voltage is less than the desired value and, conversely, it will remain off as long as the output voltage is greater than the desired value.
  • Important factors which determine the efiiciency of the power supply include the power consumed by the switch in changing state and the power consumed by the circuitry which performs the commutating action.
  • the power lost in switching is a function of the time required to perform the switching action. According to the concept of the invention commutating circuitry is employed which requires minimum power to turn the switch off in a minimum time.
  • a step-down time-ratio control converter is capable of controlling a load voltage from a low value to a level nearly as high as that of the supply voltage.
  • the minimum input voltage necessary to operate a supply such as that shown in FIG. 1 is equal to the sum of the voltage drops across the load, inductance 16 and transistor switch 12.
  • the input voltage should be from two to six times higher than the output voltage.
  • the vlaue of input voltage which results in the most efficient operation of the supply may be'determined by experimentation.
  • the average load voltage E load over a repetitive time interval is related to the source voltage E in as follows:
  • T is a total conducting time of the switch and T is the total non-conducting time of the switch.
  • Diode 18, as shown in FIG. 1, provides a path for the load current when transistor switch 12 is non-conducting. This permits inductance 16' to sustain the DC load current during the half-cycle transistor switch 12 is off.
  • transistor switch 12 When transistor switch 12 is conducting, the current flow creates a magnetic field in inductance 16 and charges capacitor 21.
  • transistor switch 12 is off the collapsing magnetic field of inductance 16 and the charge stored in capacitor 21 sustain current flow through the load, inductance 16 and diode 18. Because the average voltage across inductance 16 is zero, the voltage drop across inductance 16 is not a factor in the expression for the average output voltage at terminal 22.
  • Diode 18 must be connected with the proper polarity to permit current flow during the off half-cycle and block flow during the on half-cycle. Thus, there is available at terminal 22 an output voltage with a magnitude dependent upon the level of the source voltage and the duty cycle of transistor switch 12.
  • Inductance 16 and capacitor 21 produce a steady DC output voltage from a pulsating input voltage.
  • the output voltage at terminal 22 is a function of the voltage drop across inductance 16, is in turn, a function of the rate of change of current through inductance 16. This means that the output voltage at terminal 22 will vary because of the changing current in inductance 16
  • transistor switch 12 were switched on for a period of continuous operation.
  • the division of the source voltage across the load and inductance 16 would be determined by the initial flow of current. After a length of time determined by the time constant of inductance .16, the current flow would have created a magnetic field, charged capacitor 21 and reached a steady state value.
  • Regulation is accomplished by actuating switch 12 so that the output voltage varies in a narrow bandwidth about a predetermined level. Actuation is conventionally accomplished by comparing the output voltage and the reference voltage in a difference amplifier to develop an error voltage, applying the error voltage to a bistable multivibrator to change its state when the output voltage rises above and falls below the reference voltage, and gating the series switch with the output of one stage of the multivibrator. Of course, the transistor switch cannot be made to instantly change its state of conduction when the output voltages rise above or fall below the desired value. Time delays occur in the commutating circuitry and in the time required to turn the series switch on or off. According to the concept of the invention, diode 62 and amplifier 64 operate to decrease the time required by the bistable multivibrator, which comprises transistors 50 and 52, to switch transistor switch 12 out of conduction in response to an error signal.
  • a reference voltage is developed by applying the output voltage across resistor 30 and Zener diode 32.
  • the breakdown characteristics of the Zener diode are such that the voltage across the diode 32 is constant and independent of the variations in the output voltage.
  • a voltage which fluctuates in proportion to the output voltage at terminal 22 is developed by connecting Zener diode 26 and resistor 38 across the output terminals 22 and 24. Again the voltage drop across the Zener diode remains constant. Zener diode 26 functions to provide an offset voltage so that the output voltage may be very variable down to zero volts.
  • the inputs to the bases of difference amplifier 28 are the constant voltage available at resistor 34 and the fluctuating voltage across resistor 38.
  • a pair of complementary error signals which represent the difference between the output voltage and the reference voltage, appear at the collectors of difference amplifier 28. These signals provide inputs to the bases of a second differential amplifier comprising transistors 40 and 42. The linearly amplified, inverted pair of error signals appear at the collectors of transistors 40 and 42.
  • bistable multivibrator comprising transistors 50 and 52 and of amplifier 64.
  • the pair of inverted error signals at the collectors of transistors 40 and 42 drive the bases of transistors 50 and 52.
  • one stage is conducting while the other is cutoff.
  • the states of conduction in transistors 50 and 52 will reverse in response to a negative going error signal to the base of the PNP transistor which is non-conducting.
  • transistor 40 is non-conducting and transistor 52 is conducting.
  • transistor 50 conducts, its collector voltage approaches the source voltage at its emitter.
  • the positive going pulse which appears at the collector of transistor 50 as it begins to conduct is coupled to the base of transistor 52.
  • Transistor 52 had been conducting.
  • the bistable multivibrator has reversed its states of conduction.
  • the output pulses from one state of a bistable multivibrator are coupled to a series switch to gate the switch on and off.
  • the positive going signal which appears at the collector of transistor 52 when transistor 52 begins to conduct is used to drive transistor switch '12 into conduction.
  • Transistor 52 will quickly go into conduction in response to an error signal at its base.
  • IWheII transistor 52 is cut off by a signal coupled from transistor 50 the fall time of the negative going signal at the collector of transistor 52 is determined by the time constant of coupling capacitor 58.
  • the negative going voltages at the collector of transistor 52 are isolated from capacitor 58 by diode 62.
  • the diode isolates the collector of transistor 52 fromthe capacitor during the half-cycle when transistor 52 goes out of conduction but does not effect the half-cycle when transistor 52 conducts.
  • Positive pulses from the collector of transistor 52 are coupled through diode 62 and capacitor 58 to the "base of transistor 50.
  • a negative going signal to rapidly switch transistor 12 out of conduction is provided by amplifier 64.
  • Amplifier 64 is driven by the fast rising positive going pulse from the collector of transistor 50 which exists when transistor 50 goes into conduction. The pulse is amplified and inverted in amplifier 64. The drive signal appearing at the collector of amplifier 64 more quickly gates transistor switch 12 out of conduction than would a signal from transistor 52 because it has a shorter fall time and reaches a more negative voltage level.
  • FIG. 3a illustrates the constant reference voltage which is applied to one base of differential amplifier 28. Assume that transistor switch 12 is conducting.
  • FIG. 3b depicts voltage variations at the base of transistor 28B. The voltage variations at this base junction are the output voltage at terminal 22. During the time that transistor switch 12 is conducting the output voltage rises in magnitude. Note that FIG. 3b ShOlWS the sample voltage rising above the level of the reference voltage. The sample voltage continues to rise throughout the time required to gate transistor switch 12 and plus the time required for transistor 12 to cease conduction.
  • FIGS. 3c and 3d portray difference voltages which appear at the collectors of amplifiers 28A and 28B, respectively, and at the base connections of amplifiers 40 and 42, respectively. These signals are amplified by transistors 40 and 42.
  • the pair of complementary error signals which appear at the collectors of transistors 40 and 42 are shown in FIGS. 32 and 3 respectively. Note that the error signals vary from a high state to a low state and vice versa in response to the sample voltage, as shown in FIG. 3b, rising above and falling below the level of the error voltage. At this time the collector voltage of amplifier 40, as shown in FIG. 3e, falls to a less positive value.
  • This voltage is applied to the base of transistor 50 which is cut off during the time transistor switch 12 is conducting.
  • the negative going signal from transistor 40 will cause the bistable multivibrator to reverse its state in the following manner.
  • the negative going signal from transistor 40 charges capacitor 58.
  • Transistor 50- begins to conduct as the base-emitter junction becomes forward biased. Refer to FIG. 3g for the waveform of the collector voltage of transistor 50. During the time transistor 50 was off capacitor 54 was charged. As transistor 50 rapidly begins to conduct, capacitor 54 discharges into the base emitter junction of transistor 52, thereby turning transistor 52 oif.
  • the positive going pulse at the collector of transistor 50 is also applied to the base of amplifier 64, as seen in FIG. 3m. This pulse drives the base of amplifier 64 to a less negative potential.
  • FIG. 312 shows that the common connection of the collector of amplifier 64, the collector of transistor 52 and the base of switch 12 falls to a negative potential. During the period switch 12 was conducting the base voltage had been at a level very close to the value of the input voltage at terminal 10. Amplifier 64 conducts for a very short period to remove energy from the base junction of transistor switch 12, thereby rapidly gating transistor switch 12 out of conduction. As shown in FIG. 3 j the emitter voltage of switch 12 falls from a high value to .a slightly negative one. In FIG.
  • capacitor 74 held a positive charge during the interval the sample voltage was rising because transistor switch 12 was conducting. As the emitter of transistor switch 12 falls to a slightly negative value, a negative pulse is transmitted by capacitor 74 through forward-biased diode 70 to charge capacitor 68 negatively. Thus, the bias network comprising capacitor 74, resistor 72, and diode 70 has readied capacitor 68 for the next cycle of operation.
  • the sample voltage shown in FIG. 3b peaks and begins to decrease because transistor switch 12 has now ceased to conduct.
  • the voltage at the junction of diode 62 and capacitor 58' is shown in FIG. 3k.
  • the positive going voltage at the collector of transistor 52 carries the base of transistor switch 12 to a positive value thereby gating it back into conduction.
  • the emitter voltage of switch 12 increases from a slightly negative value to a value approaching that of the source voltage as switch 12 goes back into conduction. At this point the cycle starts anew.
  • the sample voltage as shown in FIG. 3b rises during the interval that transistor switch 12 conducts.
  • a regulating power supply for regulating an input source voltage to provide a DC output voltage of predetermined voltage level, said regulating power supply comprising:
  • switch means connected between said input and said output terminal and selectively actuable for establishing either a conductive or non-conductive connection therebetween;
  • bistable device coupled to said output terminal and responsive to the output voltage thereon for switching to a first stable state whenever the output voltage rises above the predetermined voltage level and for switching to a second stable state whenever the output voltage falls below the predetermined voltage level, said bistable device producing a first fast rising output signal whenever it switches to one of its stable states and producing a second separate fast rising output signal whenever it switches to the other of its stable states;
  • said second means for actuating said switch means includes an inverting amplifier for inverting the second output signal and for actuating said switch means with the inverted second output signal to establish a non-conductive connection.
  • a regulating power supply for regulating an input voltage to provide a DC output voltage of predetermined voltage level, said regulating power supply comprising:
  • switch means for selectively applying the source voltage to said output terminal, said switch means being connected between said input terminal and said output terminal, and being selectively conductive or nonconductive therebetween in response to application to said switch of predetermined first and second gating signals;
  • comparing means coupled to receive the reference voltage and the output voltage, for producing a signal proportional to the dilference between the reference voltage and the output voltage
  • bistable device having a first and second stage, said first and second stages being connected to said comparing means to receive the difference signal, said first stage being responsive to the difference signal for producing a first fast rising output signal whenever the output voltage falls below the predetermined voltage level and said second stage being responsive to the difference signal for producing a sec ond separate fast rising output signal whenever the output voltage rises above the predetermined voltage level;
  • first means connected between said first stage of said bistable device and said switch means for coupling the first output signal to said switch means to serve as the first gating signal
  • inverting means connected between said second stage of said bistable device and said switch means and responsive to the second output signal for producing the second gating signal and applying the second gating signal to said switch means.
  • a regulating power supply for regulating an input source voltage to provide a DC output voltage of predetermined voltage level, said regulating power supply comprising:
  • a switching transistor for producing unidirectional voltage pulses, said switching transistor being connected to said input terminal and being selectively conductive or non-conductive in response to application to said switching transistor of predetermined first and second gating signals;
  • a filter for smoothing the unidirectional voltage pulses said filter being connected between said switching transistor and said output terminal;
  • a difference amplifier coupled to receive the reference voltage and the output voltage for producing a signal proportional to the difference between the reference voltage and the output voltage
  • bistable multivibrator having a first and second stage, said first and second stages being connected to said difference amplifier to receive the difference signal
  • said first stage being responsive to the difference signal for producing a first fast rising output signal whenever the output voltage falls below the predetermined voltage level and said second stage being responsive to the difference signal for producing a second separate fast rising output signal whenever the output voltage rises above the predetermined voltage level;
  • first means connected said first stage of said bistable multivibrator and said switching transistor for coupling the first output signal to said switching transistor to serve as the first gating signal;
  • said transistor amplifier includes a capacitor for normally biasing said transistor amplifier out of conduction until said transistor amplifier receives said second output signal.
  • said transistor amplifier includes an RC network for charging said capacitor, said network being connected between the output of said switching transistor and said capacitor.
  • said means for producing a reference voltage includes a network comprising a resistor and Zener diode, said resistor being connected to said input terminal and said Zener diode being connected to said resistor.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Electronic Switches (AREA)
  • Oscillators With Electromechanical Resonators (AREA)
US598821A 1966-12-02 1966-12-02 Oscillating switch regulator Expired - Lifetime US3450980A (en)

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US59882166A 1966-12-02 1966-12-02

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US (1) US3450980A (enrdf_load_stackoverflow)
JP (1) JPS4815247B1 (enrdf_load_stackoverflow)
GB (1) GB1209168A (enrdf_load_stackoverflow)
NL (1) NL6715848A (enrdf_load_stackoverflow)

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CN110448288A (zh) * 2018-05-07 2019-11-15 奥拉健康公司 用于低功率应用的光检测器电路的布置结构，以及对应方法和计算机程序产品

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JPS51143943A (en) * 1975-06-06 1976-12-10 Yosuke Horii Heating apparatus
JPS5544200U (enrdf_load_stackoverflow) * 1979-10-05 1980-03-22

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US3219911A (en) * 1960-08-26 1965-11-23 United Aircraft Corp Overload protection circuit
US3286157A (en) * 1961-04-20 1966-11-15 Cit Alcatel Device for the stabilization of d.c. voltage
US3300689A (en) * 1962-12-21 1967-01-24 Westinghouse Canada Ltd Voltage sensing circuit

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Publication number Priority date Publication date Assignee Title
US2776420A (en) * 1954-11-01 1957-01-01 Rca Corp Transistor indicator circuits
US3219911A (en) * 1960-08-26 1965-11-23 United Aircraft Corp Overload protection circuit
US3286157A (en) * 1961-04-20 1966-11-15 Cit Alcatel Device for the stabilization of d.c. voltage
US3300689A (en) * 1962-12-21 1967-01-24 Westinghouse Canada Ltd Voltage sensing circuit

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN110448288A (zh) * 2018-05-07 2019-11-15 奥拉健康公司 用于低功率应用的光检测器电路的布置结构，以及对应方法和计算机程序产品

Also Published As

Publication number Publication date
DE1588496B2 (de) 1972-10-12
JPS4815247B1 (enrdf_load_stackoverflow) 1973-05-14
DE1588496A1 (de) 1971-05-13
NL6715848A (enrdf_load_stackoverflow) 1968-06-04
GB1209168A (en) 1970-10-21

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