US20010038541A1 - Drive and power supply with phase shifted carriers - Google Patents
Drive and power supply with phase shifted carriers Download PDFInfo
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- US20010038541A1 US20010038541A1 US09/827,652 US82765201A US2001038541A1 US 20010038541 A1 US20010038541 A1 US 20010038541A1 US 82765201 A US82765201 A US 82765201A US 2001038541 A1 US2001038541 A1 US 2001038541A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/483—Converters with outputs that each can have more than two voltages levels
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
- H02P27/14—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation with three or more levels of voltage
Abstract
Description
- This application claims the benefit of U.S. Provisional patent application No. 60/195,080, filed Apr. 6, 2000.
- 1. Field of the Invention
- This invention relates to pulse-width modulation in a multi-level power supply. Such a power supply applies readily to motor drive and power supply applications that utilize inverters or cells with low-voltage rated semi-conductors to produce high voltages or high currents.
- 2. Description of Prior Art
- Pulse-width-modulation (PWM) is commonly used in inverters for variable speed drives and power supplies and other applications. Single inverters use a single triangular carrier to generate the PWM signals for controlling the semiconductor devices. On the other hand, multi-level inverters, such as the one disclosed in U.S. Pat. No. 5,625,545 (Hammond) use multiple, phase-shifted triangular carriers to improve the output waveform to the load. Hammond suggests the use of N phase-shifted carriers, where each carrier is phase-shifted from its neighbors by 180°/N and where N is the number of ranks per phase (i.e., the number of series-connected inverters per phase). Thus, for a three phase system there are a total of 3N cells. With the assignment of phase shifts disclosed in Hammond, the three cells in a given rank (i.e., one cell from each phase) share the same triangular carrier.
- FIG. 1 shows the power circuit of a cell, such as was disclosed in U.S. Pat. No. 5,625,545 (Hammond). Each cell receives power from a three-phase source. The diode-bridge rectifier converts the input ac voltage to a substantially constant dc voltage that is supported by capacitors connected across the rectifier output. The output stage is an H-Bridge inverter that consists of two poles, a left pole and a right pole, each with two devices. The inverter transforms the dc voltage across the dc capacitors to an ac output using PWM of the semiconductor devices. This invention is an improvement on Hammond that relates to the switching of these devices; hence, only the output stage of these cells will be discussed hereinafter.
- The two devices in a particular pole receive complementary gating signals; i.e. when the upper device is gated ON, the lower device is gated OFF and vice versa. In this description we define the pole-gating signal to be a means of describing the gating signals of both the (upper and lower) devices in that pole. When the pole-gating signal is high, the upper device is gated ON and the lower device is gated OFF, and vice versa. The gating signals for a pole are determined by comparing the voltage command with the triangular carrier, while the gating signals for the other pole are determined by comparing the same voltage command with the negated triangular carrier. This is shown in FIG. 2 where the output of each pole is shown separately. The cell output is the difference of the two gating signals scaled by the DC voltage.
- The cell output voltage has three levels, each of which corresponds to a different voltage at the output terminals of the cell. These levels are described below.
- 1. The HIGH level corresponds to an output voltage equal to +Vdc, where Vdc is the total dc bus voltage supported by the capacitors.
- 2. The ZERO level corresponds to zero voltage at the output of the cell. 3. The LOW level corresponds to an output voltage equal to −Vdc. Thus the cell output is different from a six-switch inverter (that is traditionally utilized in low voltage drives) that has only two-levels in the output phase voltage waveform. A circuit topology that results in an output waveform with more than two levels is considered as a multi-level topology.
- FIG. 3 shows the three-phase voltage references and triangular carrier that are required by Hammond to generate the PWM signals for one rank of cells (i.e., one cell from each phase). Note that the same triangular carrier (and its negated counterpart) is used for all the three cells in the rank. From this figure, it can also be observed that there are distinct 60° intervals (or ⅙th of the period of the phase-voltage command as shown in FIG. 3) during which two phase-voltage commands have the same magnitude but opposite signs. These intervals are marked at the top of FIG. 3. For example, the comment |A|=|B| in the first interval, means that the voltage commands for phases A and B have the same magnitude during that interval. During these intervals the transition (i.e., switching) of one cell's left pole gating signal coincides with the transition of the second cell's right pole gating signal. This is because both the carrier signal and its inverted value are used in generating the left pole and right pole gating signals for every cell (or H-bridge inverter). The result is a simultaneous change in opposite directions of the outputs of two cells that receive phase-voltage commands with equal magnitudes. This leads to an undesirable step of twice the cell dc bus voltage in the line-to-line voltage. Moreover, these steps occur when the output line-to-line voltage of the power supply is going through its peak value. FIG. 3 also shows examples of instances (encircled) where the outputs of two cells from different phases change state simultaneously. This process repeats every 60° in the two phases that have equal magnitudes of phase voltage command values.
- The total output voltage of each phase of the power supply is generated by the addition of all the cell output voltages in that phase. As described earlier, the cells in a given phase receive phase-shifted triangular carriers to increase the number of voltage levels in the output voltage waveform. The number of levels in the line-to-line output voltage waveform is given by (4N+1), where N is the number of ranks in the power supply.
TABLE 1 Phase shift (in degrees) of carriers in a 9-cell Power Supply based on Hammond. Cells in rank 1 are assumed to have a phase shiftof zero. Rank #\Phase A B C 1 0 0 0 2 60 60 60 3 120 120 120 - A power supply with a total of 9-cells (i.e., three phases with three cells per phase, or N=3) is considered as an example. The phase shift for each cell is shown in Table 1. According to Hammond, all cells in a given rank receive the same carrier. FIG. 4 shows the total phase voltage of one phase of the power supply. Notice that there are 13 distinct levels in the line-to-line output voltage. The effect of a simultaneous change in opposite directions of the outputs of two cells that receive phase-voltage commands with equal magnitudes can be clearly seen in the voltage waveform. Double steps are observed at the peak of the voltage waveform. Such effects increase the peak output voltage applied to the load. In addition, when long cables are used between the power supply and the load, these double steps are amplified at the load terminals by travelling wave effects resulting in increased voltage distortion. Also shown in FIG. 4 is an output current waveform that results when a 9-cell power supply is connected to a motor with low leakage inductance. A motor such as this is considered to amplify the effect of harmonics for comparison purposes.
- It would therefore be desirable to eliminate the simultaneous changes of the gate signals in the cells to eliminate or reduce the double steps observed in the line to-line voltage at the peak of the voltage waveform.
- This invention presents a new modulation technique for multi-level inverters that generate an AC output. The resulting drive waveforms exhibit lower peak voltages and reduced harmonic distortion. The result is an improvement in the characteristics of the voltage and current waveforms over Hammond.
- In the proposed method, the number of phase-shifted carriers equals the total number of series-connected cells. In other words, if there are a total of 3N cells for a three-phase power converter, with N cells in each phase, then 3N phase-shifted carriers are used, one for each inverter, with the phase shift between neighboring carriers being 180°/3N. Such an assignment of phase shifts prevents the cells within a given rank from switching simultaneously when the phase voltage commands have equal magnitudes. This avoids the double steps on the peak of the output line-to-line voltage waveform.
- As a comparison with the 9-cell Power Supply considered earlier, the phase shifts with the proposed method are shown in Table 2. FIG. 5 shows the three-phase voltage references and triangular carriers that are required to generate the PWM signals for one rank of cells. Note that the triangular carriers for the cells (and their negated counterparts) are phase-shifted from their neighbors. This results in cell output changes that are close with respect to one another but are not simultaneous. Regions “X” and “Y” in FIG. 5 are time-expanded in FIG. 6 to show the non-simultaneous transitions more clearly.
TABLE 2 Phase shift (in degrees) of carriers in each cell of 9-cell Power Supply per this invention. Phase A in cell group 1 is assumed to have a phase shift of zero.Rank #\Phase A B C 1 0 20 40 2 60 80 100 3 120 140 160 - The improved drive voltage and current waveforms for a 9-cell power supply are shown in FIG. 7. Notice that the number of levels in the output voltage waveforms are still the same, but there is a distinct improvement in the voltage waveform as compared to that in FIG. 4. The calculated total harmonic distortion (THD) in the voltage is 16.5% as compared to 20.9% with Hammond's method. The current waveform also appears to have lower ripple and correspondingly lower distortion. This is supported by the THD of 4.7% as compared to 6.1% with the method proposed by Hammond.
- Time-expanded views of line-to-line voltage waveforms from prior art and the proposed method are compared in FIG. 8. With the proposed method, double-steps are completely avoided when the line-to-line voltage is near its peak. However, double steps do appear in the region around zero voltage, though there are fewer such transitions as compared to those obtained with the method proposed in prior art. Fewer harmonic components are observed with the proposed method when the harmonic spectra of the two voltage waveforms are considered. FIG. 9 only shows harmonics above 1000 Hz in order to focus on the differences in the spectra.
- FIG. 10 shows experimental waveforms of line-to-line voltage and load current for a 12-cell power supply operating an AC motor with the proposed modulation method. The voltage waveform shows that double peaks are avoided near the peak as described above.
- The proposed method is not meant to be limited to the exemplary circuit topology considered herein, but can be applied to other multi-level topologies wherein cells are connected in series to obtain higher voltages, or wherein cells are connected in parallel to obtain higher currents. Nor is the method limited to those topologies disclosed in Hammond.
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US6954366B2 (en) | 2003-11-25 | 2005-10-11 | Electric Power Research Institute | Multifunction hybrid intelligent universal transformer |
US7050311B2 (en) | 2003-11-25 | 2006-05-23 | Electric Power Research Institute, Inc. | Multilevel converter based intelligent universal transformer |
US20090302682A1 (en) * | 2008-05-30 | 2009-12-10 | Siemens Energy & Automation, Inc. | Method and system for reducing switching losses in a high-frequency multi-cell power supply |
US20120113695A1 (en) * | 2010-11-08 | 2012-05-10 | Ingeteam Technology, S.A. | Control method for converting power, and electronic power converter adapted to carry out said method |
CN102983771A (en) * | 2012-07-13 | 2013-03-20 | 中电普瑞科技有限公司 | Pulse width modulation method for modularization multi-level converter |
KR20130110287A (en) * | 2012-03-29 | 2013-10-10 | 엘에스산전 주식회사 | Apparatus for controlling multilevel inverter |
WO2013091938A3 (en) * | 2011-12-20 | 2013-12-12 | Robert Bosch Gmbh | System and method for controlling an energy storage device |
CN104052325A (en) * | 2014-06-05 | 2014-09-17 | 上海交通大学 | Design method of cascading multi-level inverter with minimized wide-range voltage distortion |
WO2014206704A1 (en) * | 2013-06-27 | 2014-12-31 | Siemens Aktiengesellschaft | Converter assembly having multi-step converters connected in parallel and method for controlling said multi-step converters |
CN106953536A (en) * | 2016-06-02 | 2017-07-14 | 哈尔滨工程大学 | A kind of many level sinusoidal pulse width modulation methods |
US20220077762A1 (en) * | 2019-01-04 | 2022-03-10 | Siemens Aktiengesellschaft | Reducing input harmonic distortion in a power supply |
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JP4641124B2 (en) * | 2001-08-02 | 2011-03-02 | 本田技研工業株式会社 | Multiple coupled inverter device |
US20070223258A1 (en) * | 2003-11-25 | 2007-09-27 | Jih-Sheng Lai | Multilevel converters for intelligent high-voltage transformers |
US20070230226A1 (en) * | 2003-11-25 | 2007-10-04 | Jih-Sheng Lai | Multilevel intelligent universal auto-transformer |
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US7508147B2 (en) * | 2005-05-19 | 2009-03-24 | Siemens Energy & Automation, Inc. | Variable-frequency drive with regeneration capability |
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