UA86190C2 - Closed-loop rate control for data transmission on multichannel communication system - Google Patents

Abstract

Closed-loop rate conlrol for data transmission on multiple parallel channels is provided. An inner loop estimates the channel conditions for a communication link and selects a suitable data rate for each of the multiple parallel channels based on the channel estimates. For each parallel channel, a received SNR is computed based on the channel estimates, an operating SNR is computed based on the received SNR and an SNR offset for the parallel channel, and the data rate is selected based on the operating SNR for the parallel channel and a set of required SNRs for a set of data rates supported by the system. An outer loop estimates the quality of data transmissions received on the multiple parallel channels and adjusts the operation of the inner loop. For example, the SNR offset for each parallel channel is adjusted based on the status of packets received on that parallel channel.

Description

own modes on the downlink and uplink communication lines in the TOU system with MIMO-OBM;

Figure 8 shows the sequence of operations for selecting Me transmission modes for M5 broadband eigenmodes;

9A and 98 show an access point and a user terminal in an LLP system with MIMO-OBM for downlink and uplink transmission, respectively;

Fig. 10 shows the transmission subsystem;

Fig. 11 shows the receiving subsystem; and

12A and 128 show exemplary timing diagrams for closed-loop speed control for downlink and uplink, respectively.

The word "exemplary" is used in this patent document to mean "one that serves as an example, instance, or illustration." Any embodiment or design described in this patent document as "exemplary" is not necessarily to be construed as superior or advantageous over other embodiments or designs.

As used in this patent specification, the expression "rate control" defines the procedure for regulating the data transfer rate of each of the parallel channels based on channel conditions. The data rate for each parallel channel is determined by the transmission mode selected for use on that parallel channel. Rate control can thus be successfully accomplished by controlling the transmission modes used for multiple parallel channels.

Fig. 1 shows a block diagram of a transmitter 110 and a receiver 150 in a multi-channel communication system 100 with closed-loop rate control for Me parallel channels, where Me » 1.Ms parallel channels can be formed in various ways, as described below. For downlink transmission (base station to mobile object), transmitter 110 is an access point, receiver 150 is a user terminal, first link 148 is a downlink (ie, direct line) , and the second link 152 is an uplink (ie, a reverse link). For uplink transmission, transmitter 110 is a user terminal, receiver 150 is an access point, and the first and second links are uplinks and downlinks, respectively.

At the transmitter 110, the transmission (TX) data processing device 120 receives the Ms data streams, one stream for each of the Ms parallel channels. Each parallel channel is associatively associated with a well-defined transmission mode that is indicative of a plurality of transmission parameters to be used for such parallel channel. The transmission mode may be an indication of (or may be associatively associated with) a particular data rate, a particular coding scheme or coding rate (the ratio of the length of the initial data block to the length of its encoded representation), a particular compression scheme, and so on, to be used for data transmission. An exemplary set of transmission modes is provided below in Table 2. For each parallel channel, the data rate is specified by the data rate control, the coding scheme is specified by the coding control, and the modulation scheme is specified by the modulation control. These adjustments are provided by controller 130 and are made based on the transmission mode selected for each parallel channel using feedback information received from receiver 150 and possibly other information (eg, channel estimates) received by transmitter 110.

TX data processing device 120 encodes, compresses, and modulates each data stream according to the transmission mode selected for its parallel channel to provide a corresponding stream of modulation symbols. TX data processing device 120 provides Ms modulation symbol streams for Ms data streams. Transmission unit 122 (TMTE) then processes the Me modulation symbol streams in a system-defined manner. For example, the transmission unit 122 may perform OBJOM processing for an OBM system, spatial processing for an MIMO system, or both of its spatial OBM processing for an MMO-OEOM system (which is a MIMO system using OBM).

A control signal is also transmitted to assist the receiver 150 in performing a number of functions such as estimation, capture, frequency and time synchronization, coherent channel demodulation, and so on. The transmission unit 122 multiplexes the symbols of the control signal with the modulation symbols for each parallel channel, processes the multiplexed symbols and provides the modulated signals to each antenna used for data transmission. Each modulated signal is then transmitted via the first communication line 148 to the receiver 150. The first communication line 148 distorts each modulated signal according to the frequency response of a particular channel and additionally corrupts the modulated signal (1) with additive Gaussian noise (normally distributed noise), which has Mo dispersion and (2) possibly by mutual interference from other transmitters.

At the receiver 150, the transmitted signal(s) is received by one or more antennas, and the received signal from each antenna is provided to a receiver (ACU) unit 160. The receiver unit 160 conditions and digitizes each received signal to provide a corresponding stream of counts. The receiving unit 160 further processes the readings in a manner that is complementary to that performed by the transmitting unit 122 to provide Ms streams of "reconstructed" signals that are estimates of the Ms streams of modulated symbols sent by the transmitter 110.

The receiver (AX) data processing device 162 then processes the Mc recovered symbol streams according to the Mc transmission modes selected for the Mc parallel channels to obtain the Mc decoded data streams, which are estimates of the Mc data streams sent by the transmitter 110. Processing by the AX processing device 162 data may include demodulation, decompression and decoding. The input data processing device 162 may additionally provide the status of each received data packet and/or decoder metrics for each decoded data stream.

The receiving unit 160 provides control symbols of the channel evaluation device 164 received on the Ms parallel channels. The channel estimator 164 processes these received control symbols to obtain channel estimates for the Mo parallel channels. Channel estimates may include, for example, gain estimates, Mo noise variance estimates, and so on. The noise variance Mo, which is the minimum noise level observed at the receiver 150, includes channel noise, receiver circuit noise, mutual interference

(ie, crosstalk) from other transmitting entities, and so on.

Transmission mode selection device (TM) 166 receives channel estimates from channel evaluation device 164 and possibly packet status and/or decoder metrics from TX data processing device 162 . The transmission mode selection device 166 calculates the 5MA operating level for each of the Mo parallel channels based on channel estimates and 5MA compensation for such parallel channel. The transmission mode selection device 166 then selects the appropriate transmission mode for each parallel channel based on the 5MA operating level and the external circuit information for the parallel channel. The choice of transmission mode is described in detail below.

The controller 170 receives the Me selected transmission modes, from TM 1 to TM Ms, from the transmission mode selection device 166 and the status of the packet from the AX data processing device (not shown). The controller 170 then composes the feedback information for the transmitter 110. The feedback information may include Me selected transmission modes for the Mc parallel channels, messages (ASK) and/or negative messages (MAC) for received data packets, a control signal and/or other information. The feedback information is then sent over the second communication line 152 to the transmitter 110. The transmitter 110 uses the feedback information to adjust the Me processing of the data streams sent to the receiver 150. For example, the transmitter 110 can adjust the data rate, coding scheme , the modulation scheme or any combination thereof for each of the Ms data streams sent over the Ms parallel channels of the receiver 150.

The feedback information is used to increase the efficiency of the system by enabling data to be transmitted at the best known settings supported by the first line 148 of communication.

In the embodiment shown in FIG. 1, channel evaluation and transmission mode selection are performed by receiver 150, and Me transmission modes selected for the Mc parallel channels are sent back to transmitter 110. In other embodiments, channel evaluation and transmission mode selection can be performed (1) by transmitter 110 based on feedback information received from receiver 150 and/or other information received by transmitter 110, or (2) jointly by both transmitter 110 and receiver 150.

2 shows a block diagram of an embodiment of a closed-loop speed control mechanism 200 that includes an inner loop 210 that operates in conjunction with another outer loop 220. For simplicity, the operation of the inner loop 210 and the outer loop 220 is shown for only one parallel channel x at Fig. 2. In general, the same processing can be performed independently for each of the Me parallel channels.

For internal circuit 210, channel estimator 164x evaluates channel conditions for parallel channel x and provides channel estimates (eg, channel gain estimates and minimum noise estimates). Selection device 174 within selection device 166bx calculates the received 5MA for parallel channel x based on (1) channel estimates from channel estimation device 164x and (2) 5MA compensation and/or transmission mode adjustment for parallel channel x from device 172 quality assessment. For clarity, the received 5MA is symbolically shown as provided by the channel estimator 164x of the selection device 174 in FIG. 2 . Selector 174 then selects a transmission mode for parallel channel x based on the received information as described below. The selected transmission mode for parallel channel x is included in the feedback information sent by the controller 170 to the transmitter. At the transmitter, the controller 130 accepts the selected transmission mode for the parallel channel x and determines the adjustment of the data transfer rate, coding and modulation for the parallel channel x. The data is then processed in accordance with this regulation by the TX device 120x data processing, additionally multiplexed with control signal symbols and brought to the required state by the transmission unit 122x, and sent to the receiver. Channel evaluation and transmission mode selection can be performed periodically at scheduled times, whenever changes are detected in the communication line, only when necessary (for example, before or during data transmission) or at other times.

The external circuit 220 evaluates the quality of data transmission received on the parallel channel uh, and adjusts the operation of the internal circuit 210 for the parallel channel x. The received data symbols for the parallel channel x are processed by the VX data processing device 162x, and the status of each received packet on the parallel channel x and/or decoder metrics are provided to the quality evaluation device 172. Decoder metrics may include coded symbol error rate (SER), coded power metric, modified Yamomoto metric (for a convolutional decoder), minimum or average log similarity ratio (AI) among bits in a decoded packet (for a fast decoder), and so on.

Coded 5EV is the frequency of occurrence of errors among symbols received from the receiving unit 160 and coded symbols that are received by means of processing (for example, transcoding, remodulation, and so on) of the decoded data from the AX-device 162 of data processing. The modified Yamomoto metric serves as a confidence indicator of the decoded data and is derived from the difference between the selected (best) lattice path for convolutional decoding and the next closest lattice path. The minimum or average IIA can also be used as an indication of confidence in the decoded data. These decoder metrics, which serve as an indication of confidence in the quality of transmission of data received on parallel channel x, are known in the art.

The outer loop 220 may provide various types of information that is used to regulate the operation of the inner loop 210. For example, the outer loop 220 may provide 5MA compensation for each parallel channel. The 5MA compensation is used in the calculation of the operating 5MA for the parallel channel as described below. The operating 5MV is then provided to the correspondence table (OT) 176 and used to select the transmission mode over the parallel channel. 5MA compensation thus affects the selection of the transmission mode.

The outer loop 220 may also provide for setting the transmission mode for each parallel channel.

This setting may instruct the internal circuit 210 to select a transmission mode with a lower data rate for the parallel channel. The transfer mode setting directly affects the transfer mode selection. 5MA compensation and transmission mode adjustment are two mechanisms for controlling the operation of the inner loop 210. The outer loop 220 may also be designed to provide other types of adjustments to the inner loop 210. For simplicity, only the SMA compensation and transmission mode adjustment are described below. The external circuit 220 can adjust the 5MA compensation and/or transmission mode in various ways, some of which are described below.

In a first embodiment, the ZMA compensation and/or transmission mode for each parallel channel is adjusted based on the packet errors detected for the data stream received on such parallel channel.

A data stream can be transmitted in packets, blocks, frames, or some other data unit. (For simplicity, a packet is used in this patent document instead of a data unit.) Each packet may be encoded with an error-detecting code (eg, a cyclic redundancy check (CRC) code) that enables the receiver to detect whether the packet has been decoded correctly or with an error Each parallel channel can be associatively associated with a specific target packet error rate (PER) (eg, PER 195). The quality evaluation device 172 receives the status of each received packet and the target

REVA for parallel channel x, and adjusts the 5MA compensation for parallel channel x accordingly.

For example, 5MA compensation for parallel channel x can be initialized to zero at the beginning of data transmission on parallel channel x. The 5MA compensation can subsequently be reduced by AWOM for each good packet and increased by ACR for each bad packet, where LOM and DOR can be selected based on the target REA and the desired time constant (response time) for the outer loop. The 5MA offset is typically a positive value or zero, but can also be a negative value (eg to account for the high initial value of the 5MA being accepted). Alternatively or additionally, the quality evaluation device 172 may provide an indication to set the transmission mode for parallel channel x to the next lower data rate, for example, if a sequence of packet errors is detected on parallel channel x.

The ZMA compensation and/or transmission mode adjustment from the quality evaluation device 172 is used by the selection device 174 to select the transmission mode for parallel channel x.

In a second embodiment, the 5MA compensation and/or transmission mode for each parallel channel is configured based on the decoder metrics for that parallel channel. Decoder metrics for each parallel channel can be used to evaluate the quality of data transmission received on that parallel channel. If a particular decoder metric for a given parallel channel is worse than the threshold value selected for such metric, then the 5MA compensation and/or transmission mode for such parallel channel may be adjusted accordingly.

In a third embodiment, the ZMA compensation and/or transmission mode for each parallel channel is adjusted based on the received 5MA and the required 5MA for such parallel channel. The received 5MA for each parallel channel can be determined based on the received control signal symbols for that parallel channel. The system may support multiple transmission modes (such as those shown in Table 2), and each supported transmission mode requires a different minimum 5MA to achieve the target REN. The quality evaluation device 172 can determine the permissible deviation of 5MA for parallel channel x, which is the difference between the received 5MA and the required 5MA for parallel channel x. If the allowable deviation of 5MA for the parallel channel x is a negative value, then the transmission mode can be set to the next lower data rate.

The third variant of implementation can also be used for a constructive solution, with the help of which the packet is demultiplexed and transmitted through multiple parallel channels. If a packet is received in error, it may not be possible to determine (from the received packet alone) which parallel channel(s) is the cause of the packet being received in error. If no other information is available, it may be necessary to adjust the Ms 5MA compensations and/or Ms transmission modes for all Ms parallel channels, for example so that the next lower data rate is used for each parallel channel. This can result in an excessive amount of reduction in the overall data transfer rate. However, using a third embodiment, the parallel channel with the smallest deviation of 5MA can be accepted as the packet that caused the error, and the transmission mode for this parallel channel can be set to the next lower data rate.

The outer circuit may also adjust the operation of the inner circuit in other ways, and this is within the scope of the invention. In general, the outer loop operates at a speed that may be higher or lower than the inner loop speed. For example, the setting of 5MA compensation by the external circuit may depend on many received packets. The outer loop can also adjust the data rate within the regularly scheduled calculations of the inner loop. Thus, depending on its specific design and mode of operation, the outer circuit typically has a greater influence on the operation of the inner circuit for longer data transfers. For pulsating gears, the outer loop may have little or no effect on the operation of the inner loop.

Fig.3 shows a block diagram of the sequence of operations 300 for the transmission of Ms data streams over Ms parallel channels, using Ms transmission modes selected by closed-loop speed control.

Sequence 300 operations can be implemented as shown in Fig. 1 and 2. In the initial position, the receiver estimates the channel gain and the minimum noise level, Mo, for Mo parallel channels (step 312).

The receiver then selects a transmission mode for each of the Mo parallel channels based on gain estimates, noise floor estimates, and outer loop information (if applicable) for each parallel channel (step 314). The external loop information may include 5MA compensation or setting the transmission mode for each of the Mo parallel channels. The transmission mode selection is described below. The receiver sends the Ms of selected transmission modes for the Ms of parallel channels as feedback information to the transmitter (step 316).

The transmitter encodes and modulates the Me streams of data according to the Mco of the selected transmission modes (received from the receiver) to provide the Me streams of modulation symbols (step 322). The transmitter then processes and transmits the Ms streams of modulation symbols over the Ms parallel channels of the receiver (step 324).

The receiver processes the data signals that are transmitted, received on Ms parallel channels from the transmitter and receives Me streams of reconstructed symbols (step 332). The receiver further processes the Me streams of reconstructed symbols according to the Mc selected transmission modes to obtain the Mc streams of decoded data (step 334). The receiver also evaluates the quality of data transmission received on each of Me parallel channels,

for example, based on packet status, decoder metrics, 5MAs received, and so forth (step 336). The receiver then provides information to the outer loop for each of the Me parallel channels based on the estimated quality for data transmission received on that parallel channel (step 338). In Figure 3, steps 312 to 324, inclusive, can be considered as part of the inner circuit, and steps 332 to 338, inclusive, can be considered as part of the outer circuit.

Fig.4 shows a block diagram of an exemplary sequence of operations 400 that can be performed for an external circuit. The status of the data packets received on each of the Mc parallel channels is obtained and used to adjust the 5MA compensation and/or transmission mode for that parallel channel (step 412). Decoder metrics for each of the Ms parallel channels can also be obtained and used to tune

ZMA-compensation and/or transmission mode for such parallel channel (step 414). The received 5MA for each of the Mc parallel channels can also be obtained for each parallel channel and used to calculate the 5MA tolerance for that parallel channel. The 5MA tolerances for the Me parallel channels can be used to adjust the transmission modes for the parallel channels if packet errors are detected (step 416). The external circuit can implement any of or any combination of stages shown in Fig. 4, depending on its defined design solution.

The closed-loop rate control techniques described in this patent document can be used for various types of multi-channel communication systems having multiple parallel channels that can be used for data transmission. For example, these technologies can be used for systems with TOM, systems with EOM, OBM-oriented systems, systems with MIMO, systems with MIMO that use OROM (ie, systems with MIMO-OROM), and so on.

A system with TOM can transmit data in frames, each of which can be of a specific time duration. Each frame can include multiple (Mtv) segments, which can be assigned different segment attributes. Mt parallel channels can be formed by Mt segments in each frame, where

MeeMtv. Each of the Mc parallel channels can include one or several segments. Multiple channels are considered "parallel" even if they are not transmitted simultaneously.

A ROM system can transmit data in (Mev) frequency subbands, which can be arbitrarily spaced at intervals. Each of the Mc parallel channels can be formed using Mev subbands, where Mo-Mev. Each of the MC parallel channels can include one or several sub-bands.

A BOTH system uses BOTH to effectively segment the full frequency range of the system into multiple (Me) orthogonal subbands, which may also be referenced as tone, composite, and frequency channels. Each subband is associatively associated with a corresponding carrier that can be modulated by data. MS parallel channels can be formed using Me subbands, where

Me-Me. MO of parallel channels are formed using MC of disjoint sets from one or more subbands. The Mc sets are disaggregated so that each of the Me subbands is assigned to only one set (and thus one parallel channel), if at all. A system with OROM can be considered as a special type of system with a computer.

A MIMO system uses multiple (Mt) transmit antennas and multiple (Mv) receive antennas for data transmission and is designated as a (Mt, Mv) system. MIMO channel, formed with the help of Mt transmission and

It has receiving antennas, composed of spatial channels that can be used for data transmission, where

Mestip (Mt, Mv). The number of spatial channels is determined by the characteristic matrix H of the channel, which describes the relationship between Mt transmitting and Mav receiving antennas. For simplicity, the following description assumes that the characteristic matrix H is full-rank. In this case, the number of spatial channels is set as

Me-MteMv. Mo of parallel channels can be formed using Me of spatial channels, where MosMv.

Each of Me parallel channels can include one or multiple spatial channels.

A system with MIMO-OBM has Me spatial channels for each of Me subbands. Mc parallel channels can be formed using Me spatial channels, each of Me subbands, where

MeMeeMa. Each of the Mc parallel channels may include one or multiple spatial channels from one or multiple subbands (ie, any combination of spatial channels and subbands). For systems with MIMO and with MIMO-ORM, Ms of parallel channels can also be formed using Mt transmission antennas, where Mo-Mt. Each of the Mc parallel channels can be associatively connected to one or more transmission antennas for data transmission.

For systems with MIMO and with ORB, data can be transmitted over Mz spatial channels in different ways.

For a system with MIMO with partial channel state information (partial C5I), data is transmitted over Me spatial channels without any spatial processing at the transmitter and with spatial processing at the receiver. For MIMO systems with full C5I, data is transmitted over Me spatial channels with spatial processing at both the transmitter and the receiver. For full C5I MIMO systems, eigenvalue expansion or eigenvalue expansion can be performed on the characteristic matrix H of the channel to obtain Me of the "eigenmodes" of the MIMO channel. Data is transmitted on Me eigenmodes, which are orthogonal spatial channels.

The closed-loop speed control technologies described in this patent document can be used for time-division duplex systems (TDI-systems) as well as for frequency-division duplex systems (DDI-systems). For TOU systems, the downlink and uplink share the same frequency range and should likely experience similar fading and multipath effects. Thus, the frequency characteristic of the channel of each line can be estimated on the basis of the control signal received on either one or the other line. For an EOO system, the downlink and uplink use different frequency bands and should probably experience different fading and multipath effects. The frequency response for each line can be estimated based on the control signal of that line.

Closed-loop speed control technologies can be used for MIMO systems with both partial CI and full CI. These technologies can also be used for the downlink as well as for the uplink.

Closed-loop speed control technologies are further described in detail for an exemplary multi-channel communication system, which is a TOYOO system with MIMO-OBROM with full C5I. For simplicity, in the following description, the term "eigenmode" and "broadband eigenmode" are used to refer to the case where an attempt is made to orthogonalize the spatial channels, even though this may not be completely successful due to, for example, incomplete channel estimation.

I. LLP system with MIMO-OBM

Fig.5 shows an exemplary TOO-system 500 with MIMO-ORM with a number of access points 500 (AP) that support communication for a number of user terminal devices 520 (OT). For simplicity, only two access points, 510a and 51050, are shown in Fig.5. An access point may also be referred to as a base station, base transceiver system, node B, or some other terminology.

The user terminal may be fixed or mobile, and may also be referred to as an access terminal, mobile station, user equipment (UE), wireless device, or some other terminology. Each user terminal may communicate with one or possibly multiple access points on the downlink and/or uplink at any given time.

The system controller 530 connects to the access points 510 and provides coordination and control for these access points. Fig. 6 shows an exemplary frame structure 600 that may be used in a TOU system 500 with MIMO-OBM.

Data transfer takes place on elements of TOYUO-frames, each of which captures a specific duration of time (for example, 2ms). Each TOO frame is divided into a downlink phase and an uplink phase, and each phase is further divided into multiple segments for multiple transport channels. In the embodiment shown in Fig. 6, the downlink transport channels include a broadcast channel (BCH), a direct control channel (DSCH) and a direct channel (ESC), and the uplink transport channels include it has a return channel (VSN) and a random access channel (RAN).

In the downlink phase, the BCH segment 610 is used to transmit the protocol data (PO) BCH module 612, which includes a call control signal 614, an MMO control signal 616, and a BCH message 618. The call control signal is control signal transmitted from all antennas and used for time and frequency capture. A MIMO control signal is a control signal transmitted from all antennas, but with different orthogonal codes for each antenna, in order to enable user terminals to identify the antennas individually. Control signal

MIMO is used for channel estimation. A BSN message carries system parameters for user terminals. ESSN-segment 620 is used to transmit one RO BESN, which carries assignments for downlink and uplink resources (eg, selected transmission modes for downlink and uplink) and other signaling for user end devices. ESN segment 630 is used to transmit one or more ESN 632 downlinks. Different types of ESN Swarms can be defined. For example, the ROI ESN 632a includes a controlled reference signal 634a and a data packet 63ba, and the ROSH ESN 632606 includes only a data packet 6360. The controlled reference signal is a control signal that is transmitted in a special broadband eigenmode (as described below) and used to evaluate the channel.

In the uplink phase, the ASN segment 640 is used to transmit one or more ASN Swarms 642 on the uplink. Different types of SLE of ASD can also be defined. For example, the ASN ROI 642a includes only the data packet 646ba, and the BASN ROI 6425 includes the controlled reference signal 6445 and the data packet 6465. The BASN segment 650 is used by the user terminal to access the system and send short messages on the uplink connection A SWARM Swarm 652 may be sent in a Swarm segment 650 and includes a control signal (eg, controlled reference signal) 654 and a message 656 .

Fig. 6 shows an exemplary frame structure for a TOU system. Other frame structures may also be used and are within the scope of the invention. 1. Spatial processing

For a system with MIMO OBEOM, the frequency response of the channel between the access point and the user terminal can be characterized by a set of characteristic matrices of the channel H(K), for Kk is K, where K is the set of all subbands of interest (for example, K--1, . .., ME). For TOU-system with MIMO-

ORBROM with a shared frequency range, the channel frequency characteristics of the downlink and uplink can be allowed to be reversible with respect to each other. This means that if NIC) represents the characteristic matrix of the channel from antenna array A to antenna array B for subband K, then the reversible channel assumes that the connection from array B to array A is given by H"(K), where A" means transposition A.

However, the frequency characteristics of the transmission and reception links at the access point are typically different from the frequency characteristics of the transmission and reception links at the user terminal.

A calibration may be performed to obtain correction matrices used to account for differences in frequency response. With these correction matrices, the "calibrated" downlink channel characteristic, Nsap(K) observed by the user terminal is the transpose of the "calibrated" characteristics of the uplink channel, Neor(K), which the access point adheres to, i.e. Neap(K)-H"sur(K), for K is K. For simplicity, the further description assumes that the frequency characteristics of the downlink and uplink channels communication lines are calibrated and reversible in relation to each other.

In the downlink, the control MIMO signal can be transmitted by the access point (for example, in

VSN-segment 610) and used by the user terminal to obtain an estimate. pi Neapk) - calibrated frequency characteristic of the downlink channel, - ; for K is K. The UE may estimate the calibrated frequency response of the uplink channel as

Neorikyu) Neap(yu gy ; gy NI - - The user terminal device can perform expansion on special "Neorik) values of the matrix for each subrange k, as set out below: х х ху (КН

Neoria) - Ozr (YushchYUM (Kk), for is K n)

Odo(Yu - (Mao x M « Neorik) where ar(Yu) 7 (Mar x Mar) is the unitary matrix of the left eigenvectors of the TR matrix; ik «s Nooriyu) sh ) (Marh My) is the diagonal matrix of singular values of the MR matrix;

M dk! ! Neo-Cr(yu)

Let U. (Mah we) - the unitary matrix of the right eigenvectors of the TR matrix;

AN - conjugate transposition of A;

Mar - the number of antennas at the access point; and

We are the number of antennas on the user terminal. . x NeapiK)

In a similar way, the expansion by singular values of the matrix - can be expressed as: лк АЖ d Ж

Neapia - UYU r(K), for which there are K (2) lodges lodges k

I would have tarni; respectively left | | Noah in where - and - the unitary matrix, respectively, of the left and right eigenvectors of the matrix - and "is" means complex conjugation. Decomposition by singular values is described by Gilbert Strang (Sibepy

Zmapo) in the book entitled "I ipeag AIderga apa 5 Arriisayope", besopa Eayop, Asadetis Rgev5, 1980 ("Linear algebra and its applications", second edition, scientific publishing house, 1980).

As shown in equations (1) and (2), the matrix of left and right eigenvectors for one line is complex. . with. . . here is also the conjugation of the matrices, respectively, from the right and left eigenvectors for another line. The matrices Oar(K) Y can be used by the access point and the user terminal, respectively, for spatial processing and are indicated as such by their subscripts. The matrix Shyu) includes estimates of a special value, which represent the gain coefficients of the spatial channels (or eigenmodes) of the characteristic matrix of the channel H(K) for each subband of K.

Eigenvalue expansion can be performed independently for the characteristic matrix

Noshriyu) village that for each subband K in order to determine the Me eigenmodes of such a subband. Estimates of special about, . (yu ! b1 pl. bo be values for each diagonal matrix - can be ordered so that (7 (K)" (Kr... (kyu), where b shk . Ge; - . 1(k) is the largest estimate special value, and "5 (Кк) is the smallest estimate of the singular value for the subrange K. When the estimates of the singular value for each diagonal matrix are ordered, the eigenvalues . . . ' x MK) . . . vectors (or columns) of associatively connected matrices CC ) and (- are also ordered accordingly. "Broadband eigenmode" can be defined as the set of identically ordered eigenmodes of all subbands after ordering. Thus, the t-th broadband eigenmode includes the 5th eigenmodes of all subbands. "Main » wideband eigenmode is associatively associated with the largest eigenvalue score in the matrix , for each of the subbands. M5 parallel channels can be formed using M wideband eigenmodes.

The user terminal may transmit a controlled reference signal on the uplink (for example, in the VCH-segment 640 or the VCH-segment 650 of Fig.6). The controlled uplink reference signal for wideband eigenmode can be expressed as:

run away)

Choreot(k) 0 p(K), for Kk (3) where Khuregrt(K) is a vector of Mi symbols sent from Mi antennas of user terminal devices for subband K of broadband eigenmode t for the controlled reference signal;

In children). I have ' - the th column of the -h matrix for the subrange K, where

Ma (kyu) -I U (yu) Ushcho(K) Um also and r(k) - a control symbol sent over the K subband.

The controlled reference signal for all Me wideband eigenmodes can be transmitted in M" symbol OROM-periods or less than in Me symbol ORUOM-periods using subband multiplexing. The controlled reference signal for each wideband eigenmode may also be transmitted over multiple symbol BOTH periods.

The received uplink reference signal at the access point can be expressed as:

Netso (yuYu Udt(K) 4 will tear SHY t year) eyelid) 9

Oartok) is a gift tt (Yur(K)kpor(k), for which is K de Goret(K) is a vector with Mar symbols received on Mar antennas of access points for the subband k of the broadband eigenmode t for the controlled reference signal;

Oartew). but with tar, - the th column of the matrix Ozr(K) for the subrange K, where - yara(K) arc) 0 Oarm, (Ю

Ovr(yutary -arg What armr I; b. ho. e e - -p (Kk) - estimation of a special value for the subband K of the broadband eigenmode t, i.e. the tth ! . oyu. diagonal element of the matrix -;i

Poir(k) - additive Gaussian white noise (AM/OM) for subband K on the uplink.

As shown in equation (4), the received reference signal is controlled at the access point (in the absence of

Worthy) be sy. OartiK) of noise), is approximately equal to " --n (YUDK(K). The access point can thus receive estimates and " ; db o, . - o. and -t(k) for each subband K based on the received controlled reference signal for the subrange... b c, e i b

The estimate -7 (K) for the subband K of the broadband eigenmode t, -7 (K), can be expressed as:

E where I means the quadratic norm of a; lead) 5 orvgti),

Yishovsti is the element of the RT vector. 7.

M represents the set of broadband eigenmodes of interest, for example, M--1,..., M). sia Oarty(K) still . and the Party)

The estimate "for subband K of broadband eigenmode t, 72P; z" can be expressed as:

OartiK) g (K),6 6 -art - -irzot rt (yu, for Kk is Kk ( )

The double cover for ' and -tp(k) indicates that they are estimates of estimates, i.e., estimates received by the access point for estimates " and -tp(k) received by the user terminal. If the controlled reference signal for of each wideband eigenmode is transmitted over numerous BOTH periods of the symbol, then the access point can average the received controlled reference signal over each wideband eigenmode to obtain a more accurate estimate of i -t(k.

Table 1 summarizes the spatial processing at the access point and user terminal for transmitting and receiving data on multiple broadband eigenmodes.

Table 1

Downlink link! Uplink line of communication

Keredos Access Point: Reception Paradise | Oct

Custom | Reception: 1 Transmission:

I am a khintsevny device; laku and che A

UA NI and

In Table 1, 5(k) is the "data" vector from the modulated symbols (obtained from the symbol conversion in the transmitter), x(K) is the "transmitted vector" from the transmitted symbols (obtained after spatial processing), tsk) " the received vector" from the received symbols (obtained after OBYOM processing at the receiver), and (K) is the estimate of the vector 5(K) (obtained after spatial processing at the receiver), where all vectors are for the subrange of K. Subscripts " ap" and "pr" for these vectors mean the descending and ascending lines of communication --1. . p., XX (Kyu) . in accordance. In Table 1, - is a diagonal matrix defined as k-1 x (Y). xhi ) aiad(1/st(yu) 1/o2(K) ... 1/oma(K)).

The controlled reference signal may be transmitted for one broadband mode at a time by the user terminal or may be transmitted for multiple broadband eigenmodes simultaneously using an orthogonal basis (eg, Walsh codes). Controlled reference signal. . . Parti) for each wideband mode can be used by the access point to obtain "P;

OBOM-periods) for Me eigenmodes of each subband, then, due to noise and other sources of degradation in the soya oo Parti) o br(yu not wireless line, Me vectors 7eRt matrix ЗР for each subband K may not be no ! - arc) s . orthogonal to each other. In this case, the M5 vectors of the matrix 726 for each subrange of K can be reduced to orthogonal form using OH-factorization, polar decomposition, or some other method.

At the access point, the received 5MA estimate for subband K of the broadband eigenmode t, uar,t(K) can be expressed as:

Believe me) ---- (7

Uart(K)- b,ar ,dlyake Kk de Rurt(K) - the transmitted power, which is used by the user terminal device for the subband K of the broadband eigenmode t on the uplink; and

Mo,ar - the minimum noise level at the access point.

At the user terminal, the received 5MA estimate for subband K of the wideband eigenmode t, usht(K), can be expressed as:

Raltik)etK) pi 8) bi ,dlyakeK de Rapt(k) - the transmitted power, which is used by the access point for sub-band K of broadband eigenmode t on the downlink; and

Mo, is the minimum noise level at the user end device.

As shown in equations (7) and (8), the received MA for each subband of each wideband mode, ut(K), depends on the channel gain (which is Zt (K) or St (K) of the minimum noise level of the receiver Mo and the transmitted power, P(k).The received 5MA may be different for different subbands and eigenmodes.

Fig. 7 shows a block diagram of the sequence of 700 operations for the transmission of multiple data streams in multiple broadband eigenmodes on the downlink and uplink in the TOU-system with MIMO-OBM.

The sequence of 700 operations assumes that the calibration has already been performed and that the channel frequency pom-pom | . Vsivyu) To you, the characteristics of the downlink and uplink communication lines are transpositions of each other, i.e. R ad -sdp - For the sequence of operations 700, channel evaluation is performed at stage 710, transmission mode selection is performed at stage 730, and data transmission/reception is performed at stage 760.

To evaluate the channel, the access point transmits a control MMO signal on the downlink (for example, on the VSN) (step 712). The user terminal receives and processes the MIMO control signal, ! ! oh ped Neapk) to obtain an estimate of the calibrated frequency response of the downlink channel, sp", dlk ek (step 714). The user terminal then estimates the calibrated frequency response of the uplink channel d AT d as Nosco(u Noap(u and performs a singular value expansion (5MO) of Nsor(k) to obtain the matrices and , for K is K as shown in equation (1) (step 716). The user terminal then transmits the controlled uplink reference signal communication line (for example, by BASN or BSN) using the matrices Xa(u ; for K is K, as shown in equation (3) (step 718). The access point receives and . . . under UU Or processes the controlled uplink reference signal communication lines to obtain matrices and , for Kk is Kk as described above (step 720).

For downlink data transmission, the user terminal selects a transmission mode (with the highest supported data rate) for each wideband downlink eigenmode based on the diagonal matrix y) of the minimum Mosh noise level at the user terminal and information of the external loop of the downlink (for example,

ZMA-compensation and/or transmission mode settings for the downlink) (step 740). The transmission mode selection is described below. The user terminal then sends feedback information that includes M5 transmission modes selected by the user terminal for the downlink and may further include the minimum Mosh noise level at the user terminal (step 742). (The controlled reference signal transmitted in step 718 can also be considered as feedback information sent by the user terminal.)

For data transmission over the uplink, the access point selects Me transmission modes for Me on g. - X(K) p. . broadband eigenmodes on the uplink based on the diagonal matrix - 7 , the minimum Moire noise level at the access point and external closed-loop information (eg, 5MA compensation and/or uplink transmission mode settings) (step 750 ). The access point additionally selects M" transmission modes for Me broadband eigenmodes on the downlink based on feedback information received from the user terminal device (step 752). The access point then sends the selected transmission modes for both the downlink and the uplink (e.g., ESN) (step 754). The user terminal accepts the selected transmission modes for both communication lines (step 756).

For downlink data transmission, the access point (1) encodes and modulates data for each broadband eigenmode of the downlink according to the transmission mode selected for the same. . Bap(yu) Or(yu broadband eigenmode, (2) spatially processes the data vector with the matrix . as shown in Table 1 to obtain the transmitted vector khap(K), and (3) transmits the vector xKhap(k) down downlink (steps 1-62). The user terminal (1) receives the downlink transmission, (2) performs x-"t filtering by applying 5 y Xdyu coordinated filtering of the received vector by the matrix l as shown in of Table 1 to obtain the vector zap(Kk)) for K is K, and (3) demodulates and decodes the received symbols according to the transmission mode selected for each downlink eigenmode (step 764).

For uplink data transmission, the user terminal (1) encodes and modulates data for each broadband eigenmode of the uplink according to the transmission mode selected. . . I have for such a wideband eigenmode, (2) spatially processes the data vector zco(K) with the matrix , to obtain the transmitted vector khor(K) for K is K, and (3) transmits the vector khor(K) on the uplink zv connection (step 712). The access point (1) receives the transmission on the uplink, (2) performs filtering of the received vector i IN A ho (yuY barium BuriK) ! ! !

Ior(K) matrix ; to obtain the vector and (3) demodulates and decodes the recovered symbols according to the transmission mode selected for each wideband eigenmode of the uplink (step 774). For simplicity, the operation of the closed circuit and the setting of the transmission mode by the external circuit are not shown in Fig.7.

Fig. 7 shows a special variant of the implementation of the sequence of operations, which can be used for data transmission on the downlink and uplink communication lines in an exemplary TOU-system with MIMO-OBM. Also, other sequences of operations can be implemented, with the help of which the evaluation of the channel, the selection of the transmission mode and/or the transmission/reception of data in some other ways can be performed. 2. Selection of transmission mode

Fig. 8 shows a block diagram of the sequence of operations 800 for selecting Me transmission modes for M" broadband eigenmodes. A sequence of operations 800 may be used for steps 740 and 750

Fig. 7. In the initial position, the total transmission power, Rio, available at the transmitter for data transmission, is distributed among the M wideband eigenmodes based on the power distribution scheme (step 812). The transmitted power, Pt, allocated to each wideband eigenmode is then distributed among the Me subbands of that wideband eigenmode based on the same or a different power distribution scheme (step 814). Power distribution in parallel over M5 broadband eigenmodes and power distribution in parallel over Me subbands of each broadband eigenmode can be performed as described below.

Operating 5MA for each wideband eigenmode, wrt(K), calculated on the basis of (1) allocated transmitted powers, Pt(K) and channel gains st(K) for subbands of such wideband eigenmode, (2) minimum noise level Mo at the receiver, and (3) 5-MA compensation for each broadband eigenmode (step 816). Calculation of working 5MA is described below. The appropriate transmission mode Dt is then selected for each wideband eigenmode based on the operating 5MA for that wideband eigenmode and the matching table (step 818). The excess power for each broadband eigenmode is determined, and the total excess power for all broadband eigenmodes is redistributed across one or more broadband eigenmodes to improve efficiency (step 820). The transmission mode for each wideband eigenmode can be adjusted (eg, to the next lower data rate) if designated by the outer loop information (step 822). Each of the steps in Fig. 8 is described in detail below.

A. Distribution of power over wideband eigenmodes For step 812 of FIG. 8, the total transmitted power of the Horn can be distributed over Me wideband eigenmodes using various schemes.

Some of these power distribution schemes are described below.

In a uniform power distribution scheme, the total transmitted power Rose is evenly distributed over the Me wideband eigenmodes, so that they are all allocated equal power. Transmitted power

The ratio allocated to each broadband eigenmode t can be expressed as:

Va - r dlytem (9)

In a diluted power distribution scheme, the total Ryuzi transmitted power is distributed over the Me wideband eigenmodes based on a "dilution" or "filling" procedure. The dilution procedure distributes the total power transmitted by Rio to the M5 broadband eigenmodes so that the total spectral density is maximized. Dilution is described by Robert J. Gallagher in the book (Iptogtaiop Tneogu apa Veiijabie Sottipisaiop, dopp UMieu apa bopz, 1968 (Information Theory and Reliable Communication, 1968)). Dilution for M5 broadband eigenmodes can be done in a number of ways, some of which are described below.

In the first embodiment, the total power transmitted to Rosa, SPoChchatku is distributed among the MeMe subbands/eigenmodes using dilution and based on the accepted ratios 5MA, ut(K), for K is K, i.e. M. The accepted 5MA, ut(K) can be calculated as shown in Eq. (7) or (8), with the assumption that Ryugsa is uniformly distributed over the M5Me subbands/eigenmodes. The result of this power distribution is the initial transmitted power, P'(K), for each subband/eigenmode.

The transmitted power, P, allocated to each subband eigenmode is then obtained by summing the initial transmitted powers, P'n(K), allocated to the Me subbands of such subband eigenmode, as follows:

Me

P - UR'ya(K), for t is M (10) k-th

In a second embodiment, the total transmitted power Pa is distributed over M broadband eigenmodes based on the averaged 5MAs calculated for these broadband eigenmodes. First, the averaged ZM, uhot, calculated for each broadband eigenmode t based on the accepted 5MA for

M subbands of such a broadband eigenmode as set out below: 1 of them m tt(yu (179 - ME ka

Uahd,t- where uahdt oCalculated as described above for the first embodiment. Dilution is then performed to distribute the total transmitted power, Rosa, over the Me broadband eigenmodes based on their averaged 5MA, uahdt, FOR t E M. In a third embodiment, the total transmitted power, Rioia is distributed over the M5 broadband eigenmodes based on the averaged 5MAs for these broadband eigenmodes, after channel inversion is applied to each broadband mode. For this embodiment, the total power transmitted to Ryugzi is initially distributed uniformly over Mz wideband eigenmodes. Channel inversion is then performed (as described below) independently for each wideband eigenmode to determine the initial power assignment, P"sh(K), for each subband of such wideband eigenmode. After channel inversion, the received 5MA is the same as over all subbands of each wideband mode. The averaged 5MA for each wideband eigenmode is then equated to the received 5MA for any one of the subbands of such wideband eigenmode. The received 5MA, y"n(K), for one subband of each broadband eigenmode can be determined from the initial power assignment, P"n(K), as shown in equations (7) and (8). The total transmitted power, Ryuga, is then distributed over the M5 broadband eigenmodes using dilution and on the basis of their averaged ZM, u"t(K), for that M.

Other circuits may also be used to distribute the total transmitted power over the Me broadband eigenmodes, and this is within the scope of the invention.

B. Subband power distribution in each wideband eigenmode

For step 814 in Fig.8, the transmitted power allocated to each broadband eigenmode, P't, can be distributed over Me subbands of such broadband eigenmode using different schemes.

Some of these power distribution schemes are described below.

In the uniform power distribution scheme, the transmitted power for each wideband eigenmode, Pt, is distributed uniformly in parallel over the Me subbands, so that they are all allocated equal power. The transmitted power, Ru(K), allocated to each subband can be expressed as:

R ke (2)

Rt(k)- dlyakeeKitye M

For a uniform power distribution scheme, the adopted 5MA for the Me subbands of each broadband eigenmode should probably differ by subband.

In the channel-inverted scheme, the transmitted power for each wideband eigenmode, P, is distributed unevenly over the Me subbands so that they become similar to the received 5MA at the receiver. In the following description, st(K) means the estimated channel gain, which is equal to ot) for the downlink and bik) for the uplink. For the channel-inverted scheme, the Ot normalization is first calculated for each broadband eigenmode as follows: 1

Me

UP/st(u (5)

Yut-K-.dlateye M

The transmitted power, Pt(K), allocated to each subband of each broadband eigenmode can then be calculated as:

ЮР тю | 19 .dlyaYakKyeEKitye M

The specific transmission weight, M/t(k), can be calculated for each subband of each wideband mode as follows:

Uk) - I will kill "for the sake of Kite M (15)

Specific transmission weights are used to scale the modulation symbols at the transmitter. For the channel-inversion scheme, all Me subbands are used for each wideband eigenmode, and the received SMAs for the subbands are approximately equal.

In a selective channel inversion scheme, the transmitted power for each wideband mode is

Pt distributed unevenly over selected some of the Me subbands so that the selected subbands become similar to the 5MA received at the receiver. Selected subbands are subbands with channel gains equal to or greater than the threshold gain. For this scheme, the total power gain, dt, is first calculated for each broadband eigenmode as described below: 1 Me 2 bt hretyu (16)

KE Kk- ,.dlyateeM

The rt normalization is then calculated for each broadband eigenmode as follows: bi - --nya

In P/st(yu)) (17 st(K)» Type ,dlatee M where Wdt is the threshold value of the amplification factor and W is the scaling factor, which can be chosen to bring the full pass power to the maximum value or on the basis of some other criterion The transmitted power is allocated to each subband of each wideband eigenmode,

Ри(K), can be expressed as:

Because, if oh?) » Tue

Ra(K)-3 satc) (c)

In another case, for which Kite M

For a selective channel inversion scheme, Me or less subbands can be selected for use for each wideband eigenmode and the 5MAs received for the selected subbands are approximately equal.

Other schemes can also be used to distribute the transmitted power, Pt, over the Me subbands of each broadband eigenmode, and this falls within the scope of the invention.

C. Transmission mode selection for each broadband eigenmode

For step 816 in FIG. 8, the operating 5MA is calculated for each broadband eigenmode. Working 5MA shows the bandwidth of the wideband eigenmode channel. Different methods may be used for step 816, depending on whether similar or different 5MAs are received over the ranges of each broadband eigenmode. In the following description, the 5MA ratios are given in units of decibels (av).

If channel inversion or selective channel inversion is performed, then the 5MAs received for the subbands of each broadband eigenmode, ut(K), for K are K, are similar. The received 5MA for the subband K of the broadband eigenmode t, ut(K), can be calculated as: 2 ooo Tv BYU

Mo (19) ut(K)- ; for which Kite M

The operating 5MA for each broadband eigenmode, wort, is equal to the received 5MA for any one of the subbands of such broadband eigenmode, minus the 5MA compensation for such broadband eigenmode, as follows:

War,t-:Ut(K)-uUoz,t, FOR any (20)

KeK, t is M, (аВ) where ut(K), War,t | Uoz,t ALL are given in units of аВ in equations (19) and (20).

If the transmitted power, Pt, for each wideband eigenmode is uniformly distributed over the subbands, then the received 5MAs for the subbands of each wideband eigenmode are likely to be different. In this case, the operating 5MA for each broadband eigenmode, uor,t, can be calculated as:

War,t--Uamo,t"Uro,t- Uov,t" (ав) (21) where uaho,t is the average of 5МА, which are accepted, for Me under the ranges of broadband eigenmode n; and

Uso,t - the feedback coefficient that takes into account the 5MAs that are received, which can be a function of the change

ZMA that are accepted.

For step 818 of Fig.8, the appropriate transmission mode is selected for each wideband eigenmode based on the operating 5MA for such wideband eigenmode. The system can be designed to support multiple transmission modes. A transfer mode with an index of 0 is for zero data rate (ie, no data transfer). Each supported transmission mode is associatively associated with a specific minimum 5MA required to achieve the desired throughput level (e.g.

REA with a value of 195). Table 2 lists an exemplary set of 14 transmission modes supported by the system, which are identified by transmission mode indices from 0 to 13. Each transmission mode is associatively associated with a specific spectral density, a specific coding ratio, a specific modulation scheme, and the minimum 5MA required to achieve REAK value of 195 for a channel that does not freeze, with

AM/OM. Spectral density refers to the data rate (that is, the information transfer rate in bits) normalized by the bandwidth of the system, and is given in units of bits per second per Hertz (bits per sec/Hertz). The spectral density for each transmission mode is determined by the coding scheme and the modulation scheme for that transmission mode. The degree of coding and the modulation scheme for each transmission mode according to Table 2 are characteristic of the design solution of the exemplary system.

Table 2

017 Г17711111100171 11111111 -11- 7117141 И7771111117115777171177171717111341 177111 оРОК | 7777 684 7776... 25 2 YuBKMM | 58 2 sh-- | 160 АМС ЯИ лу 778 1 111111171535 2 ЩЦCB | le | б0АМ 17777 1вб2е7 798 11111117140111717711111231111711111бюАМ 11111740 712 | 77771717171171в60 7... 7. |. 534 | 25 in OAM

For each supported transmission mode with a non-zero data transfer rate, the required 5MA is obtained on the basis of a defined structural solution of the system (ie, a specific degree of coding, compression schemes, modulation schemes, etc., used by the system for such a transmission mode) and for the channel with AMM. The required 5MA can be obtained by machine simulations, empirical measurements, and so on, as is known in the art. A correspondence table can be used to store the set of supported transmission modes and their required 5MAs.

The working 5MA for each wideband eigenmode, uor,t, can be provided to a matching table, which then assigns the transmission mode Dt to that wideband eigenmode. This transmission mode Dt is supported by the transmission mode with the highest data rate and required 5ME, ugedo,t, which is less than or equal to the operating 5MA (ie, ugedutsuor,t). The matching table thus selects the highest possible data rate for each wideband eigenmode based on the operating 5MA for such wideband eigenmode.

O. Redistribution of transmitted power

For step 820 of Fig.8, the excess transmitted power for each wideband eigenmode is determined and redistributed to improve throughput. The following terms are used for further description: - Active broadband eigenmode - broadband eigenmode with a non-zero data rate (ie, a transmission mode indexed from 1 to 13 inclusive according to Table 2); - Saturated broadband eigenmode - broadband eigenmode with maximum data transfer rate (ie, transmission mode having an index of 13); and - Unsaturated wideband eigenmode is an active wideband eigenmode with a non-zero data rate less than the maximum data rate (ie, a transmission mode having an index of 1 to 12 inclusive).

The operating 5MA for the wideband eigenmode may be less than the minimum required 5MA in the compliance table (ie, Uworths-1.8V for the transmission modes shown in Table 2). In this case, the wideband eigenmode may be disabled (ie, not used) and the transmitted power for that wideband eigenmode may be redistributed to other wideband eigenmodes.

The selected transmission mode dt for each active broadband mode is associatively connected with the necessary 5MV, ugedo,t, яЯКe is equal to or less than the working 5МА, that is, ugedopesuUor,p. The minimum transmitted power required for each active broadband eigenmode R'ed,t can be calculated as:

Rpugedut schu (gg)

Rgedft- Cake "for you" M

The required transmitted power is zero (R'ea,t-0) for each wideband eigenmode that is disabled (ie, with the transmission mode index 0 in Table 2).

The excess power for each wideband eigenmode, Rexse,t, IS THE AMOUNT OF RESOLVED POWER that exceeds the minimum power required to achieve the desired 5MA (ie, Rexsevv,.teRt-R'ed,t).

The total excess power for all broadband eigenmodes, Rehsezh, can be calculated as:

Me

XX Rt -Redt) (23)

Rekhsevv-: K-

Total excess capacity, Rechseee can be redistributed in various ways. For example, the total excess power, Rex, can be redistributed over one or more wideband eigenmodes, so that a higher total bandwidth is achieved. In one embodiment, the total excess power, Rexess, is distributed one unsaturated wideband eigenmode at a time, starting with the best one having the highest data rate, to move the wideband eigenmode to the next higher data rate. In another embodiment, the total excess power is redistributed in a wideband eigenmode that can achieve the highest data rate increase with the least amount of transmitted power.

If all wideband eigenmodes are engaged at the highest data rate, or if the residual excess power cannot increase the data rate of any wideband eigenmode, then the residual excess power can be redistributed to one, multiple, or all active wideband eigenmodes to improve the allowable limits 5MA for these broadband eigenmodes.

E. Setting the transmission mode

For step 822 in Fig.8, the transmission mode for each wideband eigenmode can be adjusted based on information from the outer loop. The selected transmission modes for the broadband eigenmodes of the downlink and uplink can be configured using the technologies described above in Fig.2.

For example, if excessive packet errors are received in a given broadband eigenmode, the outer circuit may provide transmission mode tuning to such broadband eigenmode. As another example, the received moving average 5MA may be maintained in operation for each broadband eigenmode and used to calculate the marginal deviation of the 5MA for such broadband eigenmode. If the marginal deviation of 5MA for a given wideband eigenmode is negative, then the transmission mode for the wideband eigenmode can be set to the next lower data rate. If a packet is transmitted on multiple wideband eigenmodes, the transmission mode for the wideband eigenmode with the worse 5MA deviation may be adjusted to the next lower data rate whenever packet errors are detected. In any case, the transmission mode setting may dictate the selection of another transmission mode with a lower data rate than the one selected in step 818 .

II. System with MIMO-OBM

Fig. 9A shows a block diagram of an embodiment of an access point 510x and a user terminal device 520x in a TOYOO system with MIMO-OBM. The access point 510x is one of the access points 510 of Fig.5, and the user terminal device 520x is one of the user terminal devices 520. Fig.9A shows processing for downlink transmission. In this case, the access point 51Ox is the transmitter 110 of FIG. 1 and the user terminal 520x is the receiver 150.

For downlink transmission, at the access point 510x, the traffic data is provided from the data source 912 to the TX data processing device 920, which demultiplexes the traffic data into

Ms of data streams, where Me»1. The data of the communication stream may come from multiple data sources (eg, one data source for each high-level application), and demultiplexing may not be necessary. For simplicity, only one data source 912 is shown in FIG. 9A. TX data processing device 920 formats, encodes, compresses, modulates and scales each data stream according to the transmission mode selected for such data stream to provide a stream of corresponding scaled modulation symbols.

The data transfer rate, encoding and modulation for each data stream can be determined by the data transfer rate control, coding control and modulation control, respectively, provided by the controller 940. The TX data processing device 920 provides Ms streams of scaled modulation symbols to the TX spatial processing device 928.

The TX spatial processing unit 928 processes the Me streams of scaled modulation symbols based on the selected transmission scheme, multiplexes them into control symbols, and provides the Mar streams of transmitted symbols,

Mar transmission (TMTA) blocks from 930a to 930ar. The selected transmission scheme can be for transmission diversity, spatial multiplexing, or pattern control. Transmission diversity causes data to be transmitted redundantly from multiple antennas and/or across multiple subbands to achieve diversity and improve reliability. Space-time transmission diversity (5TTO) can be used for transmission diversity. Pattern control causes data to be transmitted over a single (best) spatial channel at full power using phase control information for the main eigenmode. Spatial multiplexing causes data to be transmitted over multiple spatial channels to achieve the highest spectral density. Spatial processing for spatial multiplexing is shown in Table 1. Each transmitter unit 930 performs OBEOM processing on its own transmitted symbol stream to provide a corresponding OEEOM symbol stream that further processed to produce a modulated signal. Mar modulated signals from transmission units from 93ba to 930bar are then transmitted using Mar antennas from 932a to 932ar, respectively.

At the user terminal 520x, the transmitted signals are received by each of the antennas 952a through 952c, and the received signal from each antenna is provided to the associatively linked receiving unit 954 (ASMNA). Each receiving unit 954 states and digitizes its received signal to provide a stream of counts, which is further processed to predict a corresponding stream of received symbols. Receiver units 954a through 954c provide Mi streams of received symbols to an I/O spatial processing device 962, which performs spatial processing based on the selected transmission scheme (eg, as shown in Table 1 for spatial multiplexing). AX-device 962 spatial processing provides

Me of recovered symbol streams, which are estimates of the Mc of modulation symbol streams transmitted by the access point 510x. AX data processing device 964 then demodulates, decompresses, and decodes each recovered symbol stream according to the selected transmission mode to provide corresponding decoded data streams that are estimates of data streams transmitted by access point 510x. Processing with AH-device 962 spatial processing and

Data processing by AX-device 964 is complementary to the spatial processing performed by TX-device 928 and data processing by TX-device 920 at the access point 510x, respectively.

Channel estimator 974 obtains estimates of one or more downlink channel characteristics and provides channel estimates to controller 970. Channel estimates may be for channel gains, minimum Mod noise, and so on. The input data processing device 964 can predict the status of each received data packet. Based on the various types of information received from the channel estimator 974 and the HF data processing device 964, the controller 970 determines the transmission mode for each of the multiple parallel downlink channels using techniques described below. Each parallel channel may correspond to a broadband eigenmode (as described above) or some other combination of subbands and eigenmodes. Controller 970 provides feedback information, which may include downlink transmission mode selections, channel estimates, end device noise floor, ASK and/or MAC messages for incoming data packets, and so on. , or any combination thereof. The feedback information is processed by TX-device 978 data processing and TX-device 980 spatial processing, multiplexed with a controlled reference signal, brought to a specified state by transmission units from 954a to 954tsi and transmitted using antennas from 952a to 952tsi to the access point 51oh.

At access point 510x, We signals transmitted from user terminal device 520x are received by antennas 932a through 932ar, reduced to a defined form by receiving units 930a through 93bar, and processed by AX spatial processing device 934 and AX data processing device 936 to recover the feedback information sent by the user terminal 520x. The feedback information is then provided to the controller 940 and used to control the processing of the Ms data streams sent to the user terminal 520x. For example, the data rate, encoding and modulation of each downlink data stream may be determined based on the transmission mode selected by the user terminal 520x. The received ASK/MAC may be used to initiate either full transmission or incremental transmission of each data packet received in error by the user terminal 520x. For step-by-step transmission, a small portion of the data packet received in error is transmitted to allow the user terminal 520x to recover the packet.

Channel estimator 944 obtains channel gain estimates based on the received controlled reference signal. Estimates of the channel gain are provided to the controller 940 and used (possibly together with an estimate of the minimum noise level Mod of the user terminal) to derive transmission weights for the downlink. Controller 940 provides data rate control for data source 912 and TX device 920 data processing. The controller 940 additionally provides regulation of coding and modulation, and transmission weighting factors to the TX device 920 of data processing. Channel evaluation and transmission mode for downlink transmission can be performed as described above.

Controllers 940 and 970 control access point 510x and user terminal 520x, respectively. Memory units 942 and 972 provide storage for program codes and data used by controllers 940 and 970, respectively.

Figure 98 shows an access point 510x and a user terminal 520x for uplink transmission. In this case, the user terminal device 520x is the transmitter 110 of Fig.1, and the access point 510x is the receiver 150. Channel estimation and transmission mode selection for uplink transmission can be performed as described above. Data processing at the access point 510x and user terminal 520x for uplink transmission may be performed in a manner similar to that described above for downlink transmission. Spatial processing at the access point 510x and at the user terminal 520x for the uplink may be performed as shown in Table 1.

A. Transmitting and receiving subsystems

For clarity, processing at the access point 510x and at the user terminal for downlink transmission is described in more detail below.

Fig. 10 shows a structural diagram of the subsystem 1000 of the transmitter, which is a variant of the implementation of the transmission part of the access point 510x. For this embodiment, the data processing TX device 920 includes a demultiplexer 1010 (Oetih), Me encoding devices 1012a to 10125, Mes compression devices 1014a to 10145 channel, Mes blocks 101ba to 10165 symbol conversion and Mes signal scaling blocks 1018a to 10185 (ie, one set of an encoder, a channel compression device, a symbol conversion block, and a signal scaling block for each of the Ms data streams). The demultiplexer 1010 demultiplexes the data stream (ie, bits of information) into Me data streams, where each data stream is provided at the data rate specified by the data rate control.

The demultiplexer 1010 may not be included if the exchange stream data is already provided as Me data streams.

Each encoder 1012 receives and encodes a corresponding data stream based on a selected encoding scheme (as indicated by the encoding regulation) to predict the code bits. Each data stream may carry one or more data packets, and each data packet is typically encoded separately to produce an encoded data packet. Encoding increases the reliability of data transmission. The selected encoding scheme may include any combination of CAC encoding, convolutional encoding, fast encoding, block encoding, and so on. The code bits from each encoding device 1012 are provided to a corresponding channel compression device 1014 which compresses the code bits based on a specific compression scheme. If the compression depends on the transmission mode, then the controller 940 provides control of the compression (as indicated by the dashed line) of the device 1014 channel compression. Compression provides time, frequency and/or spatial diversity for code bits.

The compressed bits from each channel compression device 1014 are provided to a corresponding symbol conversion unit 1016 which transforms the compressed bits based on the selected modulation scheme (as indicated by the modulation control) to provide modulation symbols. Block 1016 groups each set of B compressed bits in the form of a B-bit binary value, where B21, and further converts each B-bit value into a special modulation symbol based on a selected modulation scheme (eg, QQQ, M-P5K -phase M-manipulation, or M-OAM - quadrature M-modulation, in which M-29). Each modulation symbol is a complex value in the signal decomposition defined by the selected modulation scheme.

Manipulation symbols from each symbol conversion unit 1016 are then fed to a corresponding signal scaling unit 1018, which scales the modulation symbols by the transmission weights, MUC) for K is

K to successfully perform channel inversion and power distribution. Blocks 1018a to 10185 provide Ms streams of scaled symbols.

Each data stream is transmitted over a corresponding parallel channel, which may include any number and any combination of subbands, transmit antennas, and spatial channels. For example, a single data stream may be transmitted over all possible subbands of each broadband eigenmode as described above. TX-device 928 spatial processing performs the necessary spatial processing, if it takes place, on Me streams of scaled modulation symbols and predicts Mar streams of transmitted symbols. Spatial processing can be done as shown in Table 1.

For a transmission scheme in which a single data stream is transmitted over all subbands of each wideband mode (for a full C5I MIMO system as described above), M5 sets from encoder 1012, channel compression device 1014, symbol conversion unit 1016, and unit 1018 signal scaling can be used to process M" streams of data (where Meo-Me-MarsMy), to provide Mar streams of scaled modulation symbols. The TX spatial processing unit 928 then performs spatial processing on Mar streams of scaled modulation symbols as shown in Table 1 to provide Mar streams of transmitted symbols.

For each scheme in which a single data stream is transmitted over all subbands of each transmit antenna (for a system with MIMO with partial C5I), Mar sets from the encoder 1012, the channel compression device 1014, the symbol conversion unit 1016 and the signal scaling unit 1018 can be used to process Mar data streams (de Mo-Mar) to provide Mar streams of scaled modulation symbols. The TX spatial processing unit 928 then simply forwards each stream of scaled modulation symbols as a stream of transmitted symbols. When no spatial processing is performed for this transmission scheme, each symbol transmitted is a modulation symbol.

In general, the TX spatial processing device 928 performs appropriate demultiplexing and/or spatial processing of the scaled modulation symbols to obtain transmitted symbols for the parallel channel used for each data stream. The TX spatial processing device 928 further multiplexes the control symbols with the transmitted symbols, for example, using time-division multiplexing (TDM) or code-division multiplexing (CDM).

Control symbols may be sent on all or a subset of the subbands/eigenmodes used to carry data in the exchange stream. The TX spatial processing unit 928 provides the Mear streams of transmitted symbols Mear to the transmission units 930ba to 93bar.

Each transmission unit 930 performs ORAM processing on the corresponding stream of transmitted symbols and provides a corresponding modulated signal. OBRUOM processing typically involves (1) transforming each set of Me symbols transmitted into a time slot using Me - a discrete inverse Fourier transform to produce "transformed" symbols that contain Me counts, and (2) repeating a portion of each transformed symbol to obtain the BOTH symbol that contains

Me--Mer, counted. The repeated portion is indicated by the reference as a cyclic prefix, and Mer indicates the number of counts that are repeated. The BOTH symbols are further processed (eg, converted to one or more analog signals, amplified, filtered, and frequency modulated) by the transmission unit 930 to produce a modulated signal. Other design solutions for the transmitter subsystem 1000 can also be implemented and are within the scope of the invention.

The controller 940 can perform various functions related to closed-loop speed control for the downlink and uplink (for example, selecting the transmission mode for the uplink and calculating the transmission weights for the downlink). For uplink transmission, the controller 940 may perform the sequence of operations 800 of FIG. 8 and select a transmission mode for each of the multiple parallel uplink channels. Within the controller 940, the power allocation unit 1042 distributes the total transmitted power, Ryugashr, over multiple parallel channels (eg, based on estimates of the channel gain, tyu , and estimates of the minimum noise floor, Mo ar, for the access point). Channel inversion block 1044 performs channel inversion for each parallel channel.

The transmission mode selector (TM) 1046 selects the appropriate transmission mode for each parallel channel. Memory unit 942 may store a matching table 1048 for supported transmission modes and their required 5MA (eg, as shown in Table 2). For downlink transmission, controller 940 may also perform the sequence of operations 800 of FIG. 8 to determine the transmitted power for each subband of each wideband eigenmode and calculate transmission weights used to scale the modulation symbols before by downlink transmission.

Fig. 11 shows a structural diagram of the receiver subsystem 1100, which is an embodiment of the receiving part of the user terminal device 520x. Mar transmitted signals from the access point 510x are received by antennas 952a to 952, and the received signal from each antenna is provided to the corresponding receiving unit 954.

Each receiving unit 954 conditions and digitizes its received signal to obtain a stream of counts, and additionally performs BOTH processing on the counts. OBJOM processing at the receiver typically involves (1) removing the cyclic prefix in each received OBJOM symbol to yield the received transformed symbol, and (2) transforming each received transformed symbol into the frequency domain using a Fast Fourier Transform (FFT). , to obtain a set of Me received symbols for Me subbands. The received symbols are estimates of the transmitted symbols sent by the 510x access point. Blocks 954a to 954c provide We streams of received symbols to the input device 962 spatial processing.

The spatial processing AX device 962 performs spatial or spatio-temporal processing on Me streams of received symbols to provide Me streams of recovered symbols. The HF spatial processing device 962 can implement a linear zero-corrector (7E-corrector - a corrector that rotates insignificant spectral components of a frequency signal to zero) (which is also indicated by the reference as a corrector of matrix rotation of the channel correlation function (SSMI)), a minimum mean square corrector errors (MM5I), linear

MM5E corrector (MM5BE-IG E), corrector with decisive feedback (ORE) or other corrector.

AX-device 964 data processing accepts Me streams of recovered symbols from AX-device 962 spatial processing. Each stream of reconstructed symbols is provided to a corresponding inverse symbol transform block 1132, which demodulates the reconstructed symbols according to the modulation scheme used for such stream, as indicated by the demodulation setting provided by controller 970. The demodulated data stream from each inverse symbol transform block 1132 is associatively decompressed. connected device 1134 to decompress the channel in a manner complementary to that performed at the access point 510x for such data flow. If the compression depends on the transmission mode, the controller 970 provides a decompression setting to the channel decompression device 1134, as indicated by the dashed line. The decompressed data from each channel decompression device 1134 is decoded by an associatively linked decoding device 1136 in a manner complementary to that performed at the access point 510xX as indicated by the decoding setting provided by the controller 970. For example, a fast decoding device or an algorithm decoding device

Viterbi can be used for decoder 1136 if fast or convolutional coding, respectively, is performed at access point 510x. Decoding device 1136 may also provide a status of each received data packet (eg, indicating whether the packet was received correctly or in error).

The decoding device 1136 may additionally store demodulated data for packets decoded with an error so that this data may be combined with additional data from the next partial transmission and decoded.

In the embodiment shown in FIG. 11, the channel estimator 974 estimates the channel frequency response and noise floor at the user terminal 520x (eg, based on received control symbols) and provides channel estimates to the controller 970. The controller 970 performs various functions, relating to closed-loop speed control for both downlink and uplink (for example, selection of transmission mode for downlink and calculation of transmission weights for uplink). For downlink transmission, the controller 970 can perform a sequence of operations 800 in Fig.8. Within the controller 970, the power distribution unit 1172 distributes the total transmitted power, Ruiasp, over multiple parallel channels (eg, based on estimates of the transmission ratio and estimates of the minimum noise level Mosh for the user terminal).

Channel inversion block 1174 performs inversion for each of the multiple parallel channels. The transmission mode selection device 1176 selects the appropriate transmission mode for each parallel channel. The memory unit 972 may store a matching table 1178 for supported transmission modes and their required 5MA (eg, as shown in Table 2). The controller 970 provides Ms selected transmission modes for Ms parallel channels on the downlink, which may be part of the feedback information sent to the access point 510x. For uplink transmission, controller 970 may perform a sequence of operations 800 of FIG. 3 to determine the transmitted power for each subband of each wideband eigenmode and calculate transmission weights used to scale the modulation symbols prior to transmission on the uplink.

For clarity, the transmitter subsystem 1000 has been described for the access point 510x and the receiver subsystem 1100 has been described for the user terminal 520x. The transmitter subsystem 1000 may also be used for the transmitting portion of the user terminal device 520x, and the receiver subsystem 1100 may also be used for the receiving portion of the access point 510x.

B. Regulation of the speed of uplink and downlink communication lines

Fig. 12A shows a sequence of operations for closed-loop rate control for downlink based on the frame structure shown in Fig. 6. The ROY VSN is transmitted in the first segment of each TOU frame (see Fig) and includes a control MiIMO signal that can be used by the user terminal to evaluate and monitor the downlink. A controlled reference signal may also be sent in the initial part of the ESN ROI sent to the user terminal. The UE evaluates the downlink based on the control MIMO signal and/or the controlled reference signal, and selects the appropriate transmission mode (with the highest supported data rate) for each wideband eigenmode of the downlink (ie, each parallel channel). The user terminal then sends these modes as "proposed" transmission modes for the downlink in the ASN ROI sent to the access point.

The access point accepts the proposed transmission modes from the user terminal device and schedules the downlink data transmission in the next TOO frame(s). The access point selects transmission modes for the downlink, which may be accepted from the user terminal or some other transmission mode (with a lower data rate), depending on the system load and other factors. The access point sends task information to the user terminal (which includes the transmission modes selected by the access point for downlink transmission) over the UECH. The access point then transmits the data over the ESN to the user terminal using the selected transmission modes. The user terminal receives the task information and receives the transmission modes selected by the access point. The user terminal then processes the downlink transmission according to the selected transmission mode. For the embodiment shown in Fig. 12A, the delay between the evaluation of the channel, the selection of the transmission mode by the user terminal, and the use of those transmission modes for the downlink is typically the duration of one TOO frame, but may vary depending on applications, system configurations, and other factors.

Fig. 128 shows a sequence of operations for closed-loop speed control for an uplink based on the frame structure shown in Fig.b. The user terminal device transmits a controlled reference signal on the VASN during access to the system and on the VAS when the ESN/ASN resources are assigned (see Fig.b6). The access point evaluates the uplink based on the received controlled reference signal and selects the appropriate transmission mode for each broadband eigenmode of the uplink. The access point sends task information to the user terminal (which includes the transmission modes selected for uplink transmission) over the UECH. The user terminal transmits data over the VSN to the access point using the selected transmission modes. The access point processes the uplink transmission according to the selected transmission modes.

Closed-loop speed control technologies described in this patent document can be implemented in various ways. For example, these technologies may be implemented in hardware, software, or a combination thereof. For hardware implementation, the elements used to regulate the speed of a closed loop in the transmitter and receiver (for example, controllers 940 and 970) can be implemented within one or more specialized integrated circuits (ABIS), digital signal processors (O5R - TSP), devices digital signal processing (DSP), logic circuit devices (RIbB), programmable gate arrays, data processing devices, controllers, microcontrollers, other electronic components designed to perform the functions described in this patent document, or their combination.

For software implementation, parts of closed-loop speed control can be implemented as modules (eg, procedures, functions, and so on) that perform the functions described in this patent document. Software codes can be stored in a memory block (for example, the memory block 942 or 972 of Fig.9A and 98) and executed by a data processing device (for example, a controller 940 or 970). The memory unit may be implemented within the data processing device or be external to the data processing device, in which case it may be communicatively connected to the data processing device by various means known in the art. techniques

Headings are included in this patent document for reference and to assist in locating specific sections. These headings are not intended to limit the scope of the concepts described in this patent document, and these concepts may have applicability in other sections throughout the patent specification.

The foregoing description of the disclosed embodiments is intended to enable any person skilled in the art to make or use the present invention. Various modifications of these embodiments will be readily apparent to those skilled in the art, and the characterizing principles described herein may be applied to other embodiments without departing from the spirit or scope of the invention. Thus, the present invention is not intended to be limited to the embodiments shown in this patent document, but is intended to be provided in the broadest scope that does not conflict with the principles and novel features described in this patent document. pa ila ko Preima ila she leredanich Priimach ko 152

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