M440613 五、新型說明： 【新型所屬之技術領域】 本創作係有關一種調光電路，特別是指一種利用内建電池來維持 驅動控制器有足夠的工作電壓，據以穩定負載運作之調光電路。 【先前技術】 按’光於人們日常生活中扮演著不可或缺的照明作用，其使得人 眼能看清事物，從而給人們之生活和工作帶來了方便。為了能提供人 們於昏暗環境或是夜間的情況下，依然能有充足的光源，因此照明產 φ =已普及應用於日常生活中。再者，照明用電佔一個國家用電比例非 常的高，似乎無法脫離人類現有的生活方式，近年來能源與環保問題 爻到重視，在能源、經濟與環保三者之間必須兼顧的同時，以及隨著 士活品質的提升，燈光不在只侷限於單一亮度照明而已，為因應各種 亮度照明需求趨勢下，調光式照明裝置因應而生。 傳統的可調光照明裝置在設計上只適用連接真正的電阻負載，例 如白熾燈或鹵素燈，以白熾燈為例，係利用白熾燈及其串聯之調光器 進行調光，調光器主要是以矽控元件構成，如雙向交流觸發三極2 (TRIAC)，藉由改變施加在矽控元件上的觸發電壓值，矽控元件的導 鲁通角可獲得調整而改變施加在白熾燈上的交流電壓值，從而調整 燈之發光亮度。 為了降低功率消耗及節省能源，有越來越多的燈具係以LED或省 電燈泡做為照明元件以取代傳、統白熾燈具H這些照明元件的驅 動控制器大夕會使用1C(集成電路，Integrated Circuit)來控制照明元件 跟OFF，若1C要正常運作就必須要提供一穩定直流工作電壓 (Vcc，fuPPly Voltag#IC，當 Vcc 大於 1(：啟動電壓(如_ 時IC就會正常運作’反之，Vcc低於停止電壓(tum-off她剛時IC 就2止運作，通常這些IC的啟動電壓是介於8 lv至9 9v、停止電 壓疋介於7.2V至8.8V。驅動控制器的工作電壓通常會從整流器串接電 M440613 阻降壓或疋由功率控制器提供一輔助電源而來。若將現有的T扮調 光電路應胁LED或省電賊時’縣控㈣的直流卫作電壓準位會 隨TR^AC的導通角度不同會有所變化。若將TRUc導通角度調小時， ，使得ic的Vee直紅作霞介於啟動電麟停止電壓之間此時ic 就日進入個啟動、停止的一直重複狀態，進而產生照明元件的閃燦。 另外，每各鱗TRIAC的導通角度都不一樣，舉例來說，當a廠牌 TRIAC調整職泡不會閃料，將a麟換成B廠牌的TRIAc時， 也會因導通角度的問題可能會造成照明元件閃爍。因此，如何解決調 控燈，時能使亮度變化敎’不會出現_情況是亟待解決的問題。 路tit ’本創作遂針對上述先前技術之缺失，提出-種調光電 路，以有效克服上述之該等問題。 【新型内容】 供設—内部電池以提 功效。讓調光控制器處於低導通角狀時仍可維持亮度變化穩定的 置上本二!ϊ在提供一種調光電路，其可應用於任何照明裝 了&供南效率、使用壽命長且不閃爍的調光功效。 -整·^上=Γ ’本創作提供一種調光電路，包括一調光控制器、 一第控制15、—驅動控制器及—電池。調光控制器接收 1壓H 節訊號’並根據亮度調節訊號調整第一交 流器連接調光控制器，係將第二交 制巧，輸ϋ _爾接整流器與功率控M440613 V. New description: [New technical field] This creation is related to a dimming circuit, especially a dimming circuit that uses built-in batteries to maintain a sufficient operating voltage of the drive controller to stabilize the load. . [Prior Art] According to the light in the daily life of people plays an indispensable lighting role, which enables the human eye to see things, thus bringing convenience to people's lives and work. In order to provide people with sufficient light source in the dark environment or at night, the lighting production φ = has been widely used in daily life. Moreover, the proportion of electricity used for lighting in a country is very high, and it seems that it cannot be separated from the existing lifestyle of human beings. In recent years, energy and environmental protection issues have been paid attention to, and energy, economy and environmental protection must be taken into consideration. As the quality of the staff is improved, the lighting is not limited to a single brightness illumination. In response to the trend of various brightness lighting requirements, dimming lighting devices are born. Traditional dimmable lighting devices are designed to connect only to real resistive loads, such as incandescent or halogen lamps. For incandescent lamps, for example, incandescent lamps and their series dimmers are used for dimming. It is composed of a control element, such as bidirectional AC Trigger Triode 2 (TRIAC). By changing the value of the trigger voltage applied to the control element, the conduction angle of the control element can be adjusted and changed to be applied to the incandescent lamp. The AC voltage value is adjusted to adjust the brightness of the lamp. In order to reduce power consumption and save energy, more and more luminaires use LEDs or power-saving bulbs as lighting components to replace the transmission controllers of the illuminating components of the illuminating and illuminating lamps. 1C (Integrated, Integrated) Circuit) to control the lighting element and OFF, if 1C is to operate normally, it must provide a stable DC working voltage (Vcc, fuPPly Voltag#IC, when Vcc is greater than 1 (: starting voltage (such as _ IC will work normally) Vcc is lower than the stop voltage (tum-off, when I just got the IC, it only works. Usually, the starting voltage of these ICs is between 8 lv and 9 9v, and the stop voltage 疋 is between 7.2V and 8.8V. The operation of the drive controller The voltage will usually be connected from the rectifier to the M440613 to prevent step-down or 功率 from the power controller to provide an auxiliary power supply. If the existing T-dressing dimming circuit should be against the LED or power-saving thief, the county control (four) of the DC security The voltage level will change with the conduction angle of TR^AC. If the TRUc conduction angle is adjusted to be small, the Vee of the ic will be reddish between the starting voltage and the stop voltage. Start and stop all the time The state, which in turn produces the flashing of the lighting components. In addition, the conduction angle of each scale TRIAC is different. For example, when a brand TRIAC adjusts the bubble, it will not flash, and alan is replaced by the TRIAc of the B brand. At the same time, the lighting element may flicker due to the conduction angle problem. Therefore, how to solve the regulation lamp can change the brightness 敎 'will not appear _ situation is an urgent problem to be solved. The lack of technology, proposed a kind of dimming circuit to effectively overcome the above problems. [New content] Supply - internal battery to improve efficiency. Even when the dimming controller is in low conduction angle, it can maintain stable brightness. This is a dimming circuit that can be applied to any lighting installation & dimming effect for south efficiency, long life and no flickering. - 整·^上=Γ 'This creation provides A dimming circuit comprises a dimming controller, a first control 15, a driving controller and a battery. The dimming controller receives a 1 voltage H-segment signal and adjusts the first AC connection according to the brightness adjustment signal A controller-based system of the second cross-coincidence, the output rectifier connected ϋ _ Seoul power control
二找電壓提n電源予驅器=其H 電池過裤控繼骑龍；及魏連接㈣控制器， 電池於工作«小於轉歸，提供H源予驅動㈣器，使其 透過功率控制器調整驅動電壓。 底下藉由具體實施例詳加說明，當更容易瞭解本創作之目的技 術内谷、特點及其所達成之功效。 【實施方式】 如第1圖所示，為本創作之第一實施例架構圖。壓電驅動電路1〇 ^括:半橋驅動電路12、-壓電餅14及至少—分流電路.半橋 驅動電路12包含串聯之—上臂開關組18及—下臂開關組加，半橋驅 $電路12係、接收—輸人直流電壓（D，並根據上臂開_ 18及下 臂開關組20之切触轉換為紐之—交流電壓。壓電元件M係電性 連接半橋㈣f路16，並接受交流電壓，賴振後以驅動-負載22 。其中’負载22可為冷陰極燈管(CCFL)、熱陰極燈管(HCFL)、 二7C度放電燈(HID Lamp)、發光二極體(LED)、整流器電路、壓電致動 器和開關電料。分流電路16電性連接於半橋驅動電路12與壓電元 件14之間，分流電路16係與半橋驅動電路12進行諧振，使上臂開關 組18及下臂開關組2〇進行零電壓切換，容後介紹。 在此’先說明上述元件的細部電路，以便於瞭解後續電路上的操 作方式。上臂開關組18包含一第一寄生電容（Cki) 182及一第一寄生 二極體184。下臂開關組2〇包含一第二寄生電容（Ck2；) 202及一第二 寄生二極體204。壓電元件丨4係為壓電變壓器或壓電諧振器，在此以 壓電變壓器為例說明，其包含—輸入電容（Cp) 142。在此第一實施例 中，本創作使用一組分流電路16為例說明，其包含串聯之一分流電感 (Ls) 162、一雙向開關（Ks) 164及一分流電源（Vdc/2) 166。其中， 分流電源166係提供一驅動電壓予雙向開關164，且分流電源166之 直流電壓值為輸入直流電壓（VDC)的一半。 接續，請同時配合第2圖，為本創作之第一實施例波形圖。在此， 係說明歷電驅動電路10之操作過程中，如何達到零電壓切換之功效β 首先’操作在[t〇-ti]期間’上臂開關組（κ,) 18呈導通狀態’而下臂開 M440613 關組（K2) 2G呈截止狀態，此時分流電路16係關閉的因此，輸入 電流ip流至壓電元件14，而其輸入電容142上的_ Vp會等於輸入 直流電壓，赠壓為正I此操作期間於結束時分流電路16 之雙向開關164仍呈現關閉狀態。 接、.貝操作在M2]期間，上臂開關組w與下臂開關组同時呈 現截止狀態時，此觸即為傳統半橋電路龍區時間（dead·);此 時，分流電路16即導通，输入電容142、第二寄生電容2〇2、第一寄 生電谷182與分流電感162開始諧振，輸入電容142與第二寄生電容 202會經由分流電路16開始諧振放電，同時第一寄生電容182開始被 雜充電。值得注意的是，輸入電容142上的跨壓％係以正弦斜率遞 減至零電壓’而上臂開關組18上的跨壓會遞增至輸人直流電源（Vdc) 的電壓準位；如此-來，即可作為下臂開關組2G的零電壓切換之關鍵 條件。當然，若在[tH2]期間，諧振放電電流不夠大時，則輸入電容142 與第二寄生電容2〇2就不能完全放電到零，且下臂開關組2〇亦不能在 下一操作期間進行零電壓導通。其中，分流電感丨62與全部電容於h七] 諧振期間的計算如下列公式1。 ’2 ’1 - Ky[Ls(Cp +CKi+CK2).....⑴ 由於[trt2]之時間通常很小，在諧振期間，可直接在分流電路16上使用 小電感值（分流電感162)去配合壓電驅動電路1〇上的全部電容。為 了讓整體電路更薄型化’更可利用分流電路16中導線上的寄生電感Ί 或分流電路16的印刷電路板（PCB)上之線徑漏感所產生的微小電感 值’來搭配輸入電容142、第一寄生電容182與第二寄生電容202進 行諧振。當輸入電容142上的跨壓vP放電至零時，此操作期間即結束。 接續，操作在[trt3]期間，上臂開關組18、下臂開關組2〇及分流 電路16同時呈現截止狀態時。這期間，下臂開關組2〇之第二寄生二 極體204會導通’以提供電流im流過壓電元件14。當下臂開關組2〇 開始導通時，此操作期間即結束。 M440613 接續’操作在[t3-t4】期間，上臂開關組18呈截止狀態，而下臂開關 :呈導通狀態’此時分流電路16仍然為卿的。在上臂開關組18 f截止切制導通_，壓電元件14 _人電料Q，也就是輸入電 谷142上跨壓％為〇，直到切換後，％仍維持〇，故可達到零電麼切 換。當下臂卩組20 _域止狀態時，此操作編即結束。 接續，操作在m5]期間，上臂開關組18及下臂開關組2〇兩者呈 ，止狀態’此時分流電路16開始導通，如同操作在㈣期間輸入電 容142、第二寄生電容202、第一寄生電容182與分流電感162開始諧 X ’輸入電谷142與第二寄生電容2〇2會經由分流電路16開始譜振放 電’同時第-寄生電容182開始被諧振充電。其中，分流電感162盘 全部電容於[trt5]諧振期間的計算如下列公式2。 〜 ’5 ’4 - (^p + CKi + CK2) (2) 在請振期間’輸入電幻42上的跨壓Vp係以正弦斜率遞增至輸入 直流電源（VDC:)的電壓準位，且上臂開關組18上的跨壓係二正弦斜 率遞減至零種；如此—來’即可作為上制敝18的零電壓切換之 3鍵條件。當然’若在如5]期間，譜振放電電流不夠大時則輸入電 容142就不能完全放電到零，且上臂開關组18亦不能在下—操作期間 進行零電壓導通。當輸人電容142上的跨壓Vp充電至輸入直流電二、 (VDC)的電壓準位時，此操作期間即結束。 接續，操作在[Vto]期間，上臂開關組18、下臂開關組2〇及分流電 路16同時呈現戴止狀態時，此時，輸入電容M2上的跨壓％開始被 充電至輸入直流電源（vDC)的電壓準位。同時上臂開關組18的第— 寄生二極體184會導通，以提供電流im流過壓電元件14。當上臂開關 組18開始導通時，此操作期間即結束。由於上臂開關組18由戴止切 換為導通時刻，_電元件14的輸人電壓（VP)充電至輸入直流電源. (vDC)的電壓準位，直到切換後，Vp仍維持Vdc，故可達到^電壓: 20 =臂開關組20兩者為戴止，此為半橋驅動電;的组 知作在[Vt2J期間及ft4•咖間，輸入電 ㈣^時間。 一寄生電謂與分_ 162雜電& m生電容撕、第 來達到愛μ娜之㈣£ I错由分流電路16放電， ㈣之第娜嫩魏，為下臂開關 υ之第一寄生一極體204及上臂開關組^ « 、操作在[ί2·__•咖間，提 而負載22則接收壓電元件14上電流 件… 意的是，壓電元件14與分流電路16兩^里而作動。值得注 3件Μ疋文上臂開關組18及下臂開關組2()產 f 刀流電路關為零雙切換之用。 皮所駆動’而 ^中本創作使用分流電路16使半橋驅 換，仍需滿足下列兩個條件，如下公式⑴至⑷示零電壓切 間。⑽大的死區時間td㈣一也就是td等於_或_ td> ^ V ^ ^κ\ κι)…(3) 2.足夠大的充電及放電電荷Q。 ‘k’…"(4) 乃-πλΙ^^Ρ^κι +CKi)…..(5) q ts (6) ^Idc^Vv .2π ，sm——t 作[t/t、二3雙向開關164 ’ Ts為雙向開關164的導通時間’如操 [由2間或M5]_; is為分流電路16的.電流。 A式(3)-⑹可知’零電壓切換的兩個條件是足夠大的死區時間及 M440613 分流電路16的電流is，和其餘因子(如鮮和負載）關聯性不大。分流 電路16的電流is是被輸入直流電壓（Vdc)、分流電感162 (Ls)和輪 入電容142(CP)、第-寄生電容182(Cki)、第二寄生電容2〇2(c幻) 的電容值所決定’皆為S]有it件之值。因此，只要將死區時間固定， 即可把零電壓切換條件固定’且和操作頻率與負載無關，因此能達到 零電壓切換的大頻寬功效。時間td對應的頻率為1/td，所以分流電路 16的操作頻率上限值即為1/ί(1。 再如第3 ’為本_之第二實_架構i其與第一實施 例差異在於：第二實施例為實際雙向開關整合半橋驅動電路之設計， 籲也就是將分流電路設計為二組，詳言之，在壓電驅動電路1〇中，半橋 驅動電路12與壓電元件14之間係電性連接二分流電路，其為一第— 分流電路24及-第二分流電路26，第—分流電路％包含串聯之一第 -分流電感242 (L,)及-第-單向開關244 a)。第二分流電路％ 連接第-分流電路24，第二分流電路26包含串聯之—第二分流電感 262 (L2)及一第二單向開關264⑻。其中半橋驅動電路12盘壓 電，们4之組成元件與第一實施例相同，故在此不科述。值得注意 的是:第-分流電路24 接連接輸入直流電壓（v〇c)，作為驅動電壓 Φ Vl ’第一分流電路26直接連接接地（ον)，作為驅動電壓V2。如此， 即可省去外接電源，進而簡化整體的電路拓墣設計。 接續’請同時配合第4圖，為本創作之第二實施例波形目。在此， 係說明壓電驅動電路10之操作過程中，如何達到零電壓切換之功效。 首先，操作在[Vh]期間，上臂開關組（Κι) 18呈導通狀態，而下臂開 =組（K2) 2G呈截止狀態’此時第__分流電路24及第二分流電路26 白為關閉的’因此，輸入電流ip流至壓電元件14，而其輸入電容142 上=跨璧vP會等於輸入直流電壓（Vdc)，骑壓為正值。此操作期間 於、，、。束時’第-單向開關244及第二單向開關264仍呈現關閉狀態。 接續’操作在如2]期間，上臂開關組與下臂開關組2〇同時呈 現截止狀態時，第一分流電路24仍呈現戴止狀態，但是下臂開關組 M440613 20在t, ==¾期間時導通。所以輸入電容丨42、第二寄生電容202、第一 寄生電谷182與第二分流電感262開始諸振，輸入電容142與第二寄 生電谷202會經由第一分流電路26開始諧振放電，同時第一寄生電容 182開始被諧振充電。值得注意的是，輸入電容142上的跨壓Vp係以 正弦斜率遞減至零電壓，而上臂開關組18上的跨壓會遞増至輸入直流 電源（VDC)的電壓準位；如此一來，即可作為下臂開關組2〇的零電 壓切換之關鍵條件。當然，若在[t〆2]期間，諧振放電電流不夠大時， 則輸入電容142與第二寄生電容202就不能完全放電到零，且下臂開 關組20亦不能在下一操作期間進行零電壓導通。其中，第二分流電感 262與全部電容於匕七]諧振期間的計算如下列公式7。 ’5 - ’4 > ^s(Cp+C^+CK2)….⑺ =於Ms]之時間通常很小，在諧振期間，可直接在第—分流電路 24，第二分流電路26jl使削、電感去配合魏驅動電路⑺上的全部 電容。當輸入電容142上的跨壓Vp放電至零時，此操作期間即結束。 接續’操作在m3]期間，上臂開關組18、下臂開關組2〇及0 ^流電路24同時呈現截止狀態時。在η期間，第二分流電路^之 第-早向開關264仍為導通，但輸入電容142上的跨壓％ 。此 之第二寄生二極體204會導通，以提供電流流過 _ 同時，第一分流電感262上剩餘的電流（is2)被線性放 續§第==262完全放電後’第二分流電路26自動被關閉。 …、後第一早向開關264可以在這操作期 ί下呆是用比較低的切換速度關閉第二單向開關264。 田下’開L開料料，此麟綱即結束。 操作在_期間，上臂開關組18與下臂開關組20皆呈現 導通狀態，此時第—分流電 2G白呈現 因此壓電祕U祕= €兩者仍為關閉的； 電轉14的輸人麵朴也就是輸人電容142上跨壓V為〇, 10 田接:關ΐ20切換為截止狀態時，此操作期間即結束。 截止狀離，=在_期間’上臂開關組18及下臂開關組20兩者呈 在t==t門門= 二分流電路24仍為截止狀態’但第一單向開關244 ί雷導通。如同操作在㈣_，輸人電容⑷、第二寄 電容L㈣第—寄生電容182與第二分流電感264開始諧振，輸入 同時望二从一^生電谷202會經由第一分流電路24開始諧振充電’ 容142 μ 1汰電# 182開始被譜振放電。因此，在譜振期間，輸入電 準位，且上劈^ %係以正弦斜率遞增至輸入直流電源（Vdc)的電麼 來，a ”關組18上的跨祕以正弦斜率遞減至零電廢；如此一 期門^開關組18的零電麼切換之關鍵條件。當然，若在㈣ 時’職人電容142就不能完全放電到零， 149 18亦不能訂―操作_進行零電壓導通。當輸入電容 期間即結^ VP充電至輸人直流電源（VdG)的電壓準位時，此操作 八操作她★]期間，上臂開關經18、下臂開關組20及第一 技私同時壬現截止狀態時’且第一單向開關244仍為導通；此 ㈣2電谷142上的跨壓％開始被充電至輸入直流電源（VdC)的 H 同時上臂開關組18的第-寄生二極體184會導通，以提供 壓電元件14°同時，第一分流電感242上剩餘的電流⑴） pwm至〇 ’且第一分流電路26自動被關閉。當下臂開關組20 開始導通時，此操作期間即結束。 關述之第二實施例的操作期間可得知，上臂開關組18及下臂開 /7》丨轉作在[V ^綱及[叫綱會導通，其他操作期間， 上。開關、、且I8及下臂開關組2〇兩者為截止，此為半橋驅動電路U的 死區時間。操作在[trt2]期間及[Vt5]期間，輸入電容142、第二寄生電 ffi、第一寄生電容182與第一分流電感如、第二分流電感尬譜 振充電，或藉由第-分流電感242、第二分流電感262放電，來達到 零祕切換之功效。另一達到零電壓切換之功效，為下臂開關組2〇之 M440613 第二寄生二極體204及上臂開關組18之第一寄生二極體184分別對應 操作在[Vt3]期間及[trto]期間，第一分流電路24與第二分流電路26上 剩餘的電流（‘與。）會被放電。 再如第5圖所示’為本創作之第三實施例架構圖。其與第一實施例 差異在於：增設一第一電容（Q) 28、一第二電容（c2) 30及一分流 電容（Cs) 32。其中，上臂開關組18並聯第一電容28，壓電元件14 並聯弟一電容30，如圖中之等效電路所示，第一電容28與分流電路 16之間串聯分流電容32。其中，第二電容3〇可改變分流電路16中之 分流電流值is，以及第一電容28與分流電路16之諧振頻率（fs)。可 利用第一電容28與第二電容30來降低諧振頻率（fs)，可增大分流電 路I6中的電流^。分流電容32可增加諸振頻率⑹及減小分流電路 16中的電流ls。加入上述之電容，可使壓電駆動電路1〇的零電壓切換 條件具有更設計彈性。 ' 再如第6圖所示’為本創作之第四實施例架構圖。其與第三實抽 例差異在於：壓電元件係為壓電馳器34，使用—第三電容A) 3< 取代第二電容（c2)，而原壓電變壓器的機械譜振Lm_Cm_Rm由壓電舞 振，34之機械諧振LmrCmrRm2來取代，簡單來說，就是利賴制 =34取代，輕壓器轉遞能量。如此可省略雜電㈣器的輸出 和各^⑽）°羊。、之眉愿電逢壓器中的電流im會流進輸出電容(c〇ut， =^ 22 ’而在壓電諧振器34的例子中，電流&會直接流進負載a。 ^電流im(㈣速度)域·絲的物理 件下，壓電諧振器34在負载22 i ^ 電路能更加關化。、载2上戦大的輸出瓦數，且整體 制由於目_電變壓器驅動電路中，無法在變頻書 電切換動作，且可用頻率範圍太ΐ 的話病而限制了發展及應用。為此，本 半橋開_ 储f大_，鋪时流電路在 賴#振’使得在負載變動及操作頻率變動 M440613 I，仍可麟零縣場之功效。再者，_分流來取代一般電 感於主電流触所佔⑽積及所造成的損耗，賴能讓整體電路薄型 ^又可提高整體電路效能，有助於整體技術發展、助及產品之競 唯以上所述者，僅為本創作之較佳實施例而已 創作實施之範®。故即凡依本創作+請範騎述 ’限定本 均等變化或_，均應包括於本創作之申請專利範=及精神所為之 【圖式簡單說明】 内。Second, find the voltage to raise the n power supply to the drive = its H battery has been controlled by the trousers; and Wei connected (four) controller, the battery in the work «less than the outcome, provide H source to drive (four), make it through the power controller to adjust Drive voltage. The details of the technology, the characteristics, and the effects achieved by the purpose of this creation are more easily explained by the detailed description of the specific embodiments. [Embodiment] As shown in Fig. 1, it is an architectural diagram of a first embodiment of the present invention. The piezoelectric driving circuit 1 includes: a half bridge driving circuit 12, a piezoelectric cake 14 and at least a shunt circuit. The half bridge driving circuit 12 includes a series-upper arm switch group 18 and a lower arm switch group plus half bridge drive $1212, receiving-input DC voltage (D, and according to the upper arm opening _ 18 and the lower arm switch group 20 is switched into a button - AC voltage. Piezoelectric element M is electrically connected to the half bridge (four) f 16 And accept the AC voltage, after the vibration is driven to load 22. Among them 'load 22 can be cold cathode lamp (CCFL), hot cathode lamp (HCFL), two 7C discharge lamp (HID Lamp), light-emitting diode The body (LED), the rectifier circuit, the piezoelectric actuator and the switching material. The shunt circuit 16 is electrically connected between the half bridge driving circuit 12 and the piezoelectric element 14, and the shunt circuit 16 is resonant with the half bridge driving circuit 12. The upper arm switch group 18 and the lower arm switch group 2 are switched to zero voltage, which will be described later. Here, the detailed circuit of the above components will be described to facilitate understanding of the operation mode on the subsequent circuit. The upper arm switch group 18 includes a first a parasitic capacitance (Cki) 182 and a first parasitic diode 184. The lower arm The switch group 2A includes a second parasitic capacitance (Ck2;) 202 and a second parasitic diode 204. The piezoelectric element 丨4 is a piezoelectric transformer or a piezoelectric resonator, and a piezoelectric transformer is taken as an example here. The input capacitor (Cp) 142 is included. In the first embodiment, the present invention uses a component flow circuit 16 as an example, which includes a series shunt inductor (Ls) 162 and a bidirectional switch (Ks) 164. And a shunt power supply (Vdc/2) 166. The shunt power supply 166 provides a driving voltage to the bidirectional switch 164, and the DC voltage of the shunt power supply 166 is half of the input DC voltage (VDC). 2 is a waveform diagram of the first embodiment of the present invention. Here, it is explained how to achieve the effect of zero voltage switching during the operation of the electric drive circuit 10. First, 'Operation during the period [t〇-ti]' upper arm The switch group (κ,) 18 is in a conducting state 'the lower arm is open M440613 the off group (K2) 2G is in an off state, at which time the shunt circuit 16 is turned off, therefore, the input current ip flows to the piezoelectric element 14 and its input capacitance _ Vp on 142 will be equal to the input DC voltage The boost voltage is positive I. During the operation, the bidirectional switch 164 of the shunt circuit 16 is still in the off state at the end. During the M2, the upper arm switch group w and the lower arm switch group simultaneously exhibit the off state, the touch That is, the traditional half-bridge circuit time (dead·); at this time, the shunt circuit 16 is turned on, the input capacitor 142, the second parasitic capacitor 2〇2, the first parasitic valley 182 and the shunt inductor 162 start to resonate, the input capacitor The 142 and second parasitic capacitances 202 begin a resonant discharge via the shunt circuit 16 while the first parasitic capacitance 182 begins to be mischarged. It is worth noting that the voltage across the input capacitor 142 is decremented to zero voltage with a sinusoidal slope and the voltage across the upper arm switch group 18 is increased to the voltage level of the input DC power supply (Vdc); It can be used as a key condition for zero voltage switching of the lower arm switch group 2G. Of course, if the resonant discharge current is not large enough during [tH2], the input capacitor 142 and the second parasitic capacitor 2〇2 cannot be completely discharged to zero, and the lower arm switch group 2〇 cannot be zero during the next operation. The voltage is turned on. The calculation of the shunt inductor 丨62 and the total capacitance during the resonance period of h7] is as shown in the following formula 1. '2 '1 - Ky[Ls(Cp +CKi+CK2).....(1) Since the time of [trt2] is usually small, a small inductance value (shunt inductor 162) can be directly used on the shunt circuit 16 during resonance. ) to match all the capacitances on the piezoelectric drive circuit 1〇. In order to make the overall circuit thinner, the input capacitance 142 can be matched with the parasitic inductance on the wire in the shunt circuit 16 or the small inductance value generated by the line leakage inductance on the printed circuit board (PCB) of the shunt circuit 16. The first parasitic capacitance 182 resonates with the second parasitic capacitance 202. This operation period ends when the voltage across the input capacitor 142 is discharged to zero. In the subsequent operation, during the [trt3], the upper arm switch group 18, the lower arm switch group 2, and the shunt circuit 16 are simultaneously turned off. During this time, the second parasitic diode 204 of the lower arm switch group 2 turns "on" to supply current im to the piezoelectric element 14. This operation ends when the lower arm switch group 2〇 starts to conduct. M440613 Continuation' Operation During [t3-t4], the upper arm switch group 18 is in an off state, and the lower arm switch is in an on state. At this time, the shunt circuit 16 is still clear. In the upper arm switch group 18 f, the cut-off conduction _, the piezoelectric element 14 _ human electric material Q, that is, the input voltage valley 142, the cross-pressure % is 〇, until the switching, the % remains 〇, so can it reach zero electricity? Switch. This operation ends when the lower arm 卩 group 20 _ domain stop state. In the continuation, during the operation of m5], both the upper arm switch group 18 and the lower arm switch group 2 are in the stop state 'At this time, the shunt circuit 16 starts to conduct, as in the operation (4), the input capacitor 142, the second parasitic capacitor 202, A parasitic capacitance 182 begins to harmonize with the shunt inductor 162. The input power valley 142 and the second parasitic capacitance 2〇2 begin to undergo spectral discharge via the shunt circuit 16 while the first-parasitic capacitance 182 begins to be resonantly charged. Among them, the calculation of the total capacitance of the shunt inductor 162 in the [trt5] resonance period is as shown in the following formula 2. ~ '5 '4 - (^p + CKi + CK2) (2) During the oscillation period, the voltage across the input phantom 42 is incremented to the voltage level of the input DC power supply (VDC:) with a sinusoidal slope, and The two-sinusoidal slope of the cross-voltage system on the upper arm switch group 18 is decremented to zero; thus, it can be used as a 3-key condition for the zero voltage switching of the upper cymbal 18. Of course, if the spectral discharge current is not large enough during the period as in 5, the input capacitor 142 cannot be completely discharged to zero, and the upper arm switch group 18 cannot perform zero voltage conduction during the lower-operation period. This operation period ends when the voltage across the input capacitor 142 is charged to the voltage level of the input DC 2, (VDC). After the operation, during the [Vto] period, when the upper arm switch group 18, the lower arm switch group 2〇, and the shunt circuit 16 are simultaneously in the wearing state, at this time, the voltage across the input capacitor M2 starts to be charged to the input DC power source ( The voltage level of vDC). At the same time, the first parasitic diode 184 of the upper arm switch group 18 is turned on to provide current im flowing through the piezoelectric element 14. This operation ends when the upper arm switch group 18 begins to conduct. Since the upper arm switch group 18 is switched from the wear switch to the turn-on time, the input voltage (VP) of the electrical component 14 is charged to the voltage level of the input DC power supply (vDC), and Vp remains Vdc until after switching, so that ^ Voltage: 20 = Both arm switch groups 20 are worn, this is half-bridge drive; the group is known to be [Vt2J and ft4• coffee, input power (four) ^ time. A parasitic electrician and sub- _ 162 miscellaneous electric & m raw capacitor tearing, the first to reach the love of Na Na (four) £ I wrong by the shunt circuit 16 discharge, (four) the first Nai Wei, the first parasitic of the lower arm switch The pole body 204 and the upper arm switch group ^ « operate in the [ί2·__• coffee room, and the load 22 receives the current component on the piezoelectric element 14... meaning that the piezoelectric element 14 and the shunt circuit 16 are two And act. It is worthwhile to note that 3 pieces of upper arm switch group 18 and lower arm switch group 2 () produce f knife flow circuit for zero double switching. The skin is swayed by the 'there is a need to satisfy the following two conditions using the shunt circuit 16 to switch the half bridge. The following equations (1) to (4) show the zero voltage cut. (10) Large dead time td (four) One is that td is equal to _ or _td> ^ V ^ ^κ\ κι) (3) 2. A sufficiently large charge and discharge charge Q. 'k'..."(4) is -πλΙ^^Ρ^κι +CKi).....(5) q ts (6) ^Idc^Vv .2π , sm --t [t/t, 2 The bidirectional switch 164 'Ts is the on-time of the bidirectional switch 164' as operated [by 2 or M5]_; is the current of the shunt circuit 16. A equations (3)-(6) show that the two conditions of zero voltage switching are a sufficiently large dead time and the current is of the M440613 shunt circuit 16, and the correlation with other factors (such as fresh and load) is not significant. The current is of the shunt circuit 16 is input DC voltage (Vdc), shunt inductor 162 (Ls) and wheel capacitance 142 (CP), parasitic capacitance 182 (Cki), second parasitic capacitance 2 〇 2 (c magic) The capacitance value determines that 'all S' has the value of the it piece. Therefore, as long as the dead time is fixed, the zero voltage switching condition can be fixed' and the operating frequency is independent of the load, so that the large bandwidth effect of zero voltage switching can be achieved. The frequency corresponding to the time td is 1/td, so the upper limit of the operating frequency of the shunt circuit 16 is 1/ί(1. Another example is the difference between the third embodiment of the third 'the _' and the first embodiment. Therefore, the second embodiment is a design of an integrated bidirectional switch integrated half-bridge driving circuit, and the shunting circuit is designed as two groups. In detail, in the piezoelectric driving circuit 1〇, the half-bridge driving circuit 12 and the piezoelectric The components 14 are electrically connected to a two-shunt circuit, which is a first shunt circuit 24 and a second shunt circuit 26. The first shunt circuit % includes one of the series-divided inductors 242 (L,) and - - One way switch 244 a). The second shunt circuit % is connected to the first-shunt circuit 24, and the second shunt circuit 26 includes a second shunt inductor 262 (L2) and a second unidirectional switch 264 (8). The half-bridge driving circuit 12 is piezoelectrically pressed, and the components of the four components are the same as those of the first embodiment, and therefore will not be described here. It is to be noted that the first-shunt circuit 24 is connected to the input DC voltage (v〇c) as the driving voltage Φ V1 '. The first shunt circuit 26 is directly connected to the ground (ον) as the driving voltage V2. In this way, the external power supply can be omitted, thereby simplifying the overall circuit topology design. Continuation ‘Please also cooperate with Figure 4, which is the waveform of the second embodiment of the creation. Here, it is explained how to achieve the effect of zero voltage switching during the operation of the piezoelectric driving circuit 10. First, during [Vh] operation, the upper arm switch group (Κι) 18 is in an on state, and the lower arm is on = group (K2) 2G is in an off state. At this time, the __ shunt circuit 24 and the second shunt circuit 26 are white. Closed 'Therefore, the input current ip flows to the piezoelectric element 14, and its input capacitance 142 = 璧vP will be equal to the input DC voltage (Vdc), and the riding pressure is positive. During this operation, at , , , . The beam-head-one-way switch 244 and the second one-way switch 264 are still in a closed state. During the subsequent operation, as in the case of 2, when the upper arm switch group and the lower arm switch group 2 are simultaneously in an off state, the first shunt circuit 24 still assumes a wear state, but the lower arm switch group M440613 20 is during t, ==3⁄4 Turn on. Therefore, the input capacitor 丨42, the second parasitic capacitor 202, the first parasitic valley 182 and the second shunt inductor 262 start to oscillate, and the input capacitor 142 and the second parasitic valley 202 start resonant discharge through the first shunt circuit 26, and simultaneously The first parasitic capacitance 182 begins to be resonantly charged. It is worth noting that the voltage across the input capacitor 142 is reduced to zero voltage with a sinusoidal slope, and the voltage across the upper arm switch group 18 is transferred to the voltage level of the input DC power supply (VDC); It can be used as a key condition for zero voltage switching of the lower arm switch group 2〇. Of course, if the resonant discharge current is not large enough during [t〆2], the input capacitor 142 and the second parasitic capacitor 202 cannot be completely discharged to zero, and the lower arm switch group 20 cannot perform zero voltage during the next operation. Turn on. The calculation of the second shunt inductor 262 and the total capacitance during the resonance period is as follows. '5 - '4 > ^s(Cp+C^+CK2)....(7) = at Ms] The time is usually very small. During the resonance, it can be directly cut in the first-shunt circuit 24, and the second shunt circuit 26jl The inductor is matched with all the capacitors on the Wei drive circuit (7). This operation period ends when the voltage across the input capacitor 142 is discharged to zero. During the operation of m3, the upper arm switch group 18, the lower arm switch group 2〇, and the 0^current circuit 24 are simultaneously turned off. During η, the first-to-earth switch 264 of the second shunt circuit is still turned on, but the voltage across the input capacitor 142 is %. The second parasitic diode 204 is turned on to provide current flow _ while the remaining current (is2) on the first shunt inductor 262 is linearly delayed. § ==262 is fully discharged after the second shunt circuit 26 Automatically turned off. ..., the first early morning switch 264 can be turned off during this operation period to turn off the second one-way switch 264 with a relatively low switching speed. Tianxia's open L material, and this Lin class ends. During operation _, both the upper arm switch group 18 and the lower arm switch group 20 are in a conducting state, and at this time, the first-divided power 2G is white, so the piezoelectric secret is still closed; the input face of the electric motor 14 Park is the input voltage 142 across the voltage V is 〇, 10 field connection: When the switch 20 is switched to the off state, this operation period ends. In the _ period, both the upper arm switch group 18 and the lower arm switch group 20 are in the t==t gate = the two-shunt circuit 24 is still in the off state' but the first unidirectional switch 244 ί is turned on. As in operation (4) _, the input capacitor (4), the second capacitor L (four), the parasitic capacitor 182 and the second shunt inductor 264 begin to resonate, and the input simultaneously from the first power grid 202 will start resonant charging via the first shunt circuit 24. ' 容 142 μ 1 汰 电 # 182 began to be spectrally discharged. Therefore, during the spectral period, the input level is entered, and the upper 劈^% is incremented to the input DC power (Vdc) with a sinusoidal slope. The crossover on the a group of the sinusoids is decremented to zero with a sinusoidal slope. Waste; the key condition of the zero-switching of the door switch group 18. Of course, if the employee capacitance 142 cannot be completely discharged to zero at (4), 149 18 can not be ordered - operation _ for zero voltage conduction. During the input capacitor, when the VP is charged to the voltage level of the input DC power supply (VdG), during the operation of the operation, the upper arm switch is terminated by the 18, the lower arm switch group 20 and the first technology. In the state of 'and the first one-way switch 244 is still conducting; the cross-voltage % on the (four) 2 electric valley 142 is initially charged to the input DC power supply (VdC) H while the first-parasitic diode 184 of the upper arm switch group 18 is Turning on to provide the piezoelectric element 14° while the current (1) remaining on the first shunt inductor 242 is pwm to 〇' and the first shunt circuit 26 is automatically turned off. When the lower arm switch group 20 starts to conduct, the operation period ends. During the operation of the second embodiment It can be seen that the upper arm switch group 18 and the lower arm open/7" turn into both [V^ and [the call will be turned on, during other operations, on. switch, and I8 and lower arm switch group 2" For the cutoff, this is the dead time of the half bridge drive circuit U. During the [trt2] period and [Vt5], the input capacitor 142, the second parasitic electric ffi, the first parasitic capacitance 182 and the first shunt inductor, etc. The two-shunt inductor 尬 spectral charge is charged, or the first shunt inductor 242 and the second shunt inductor 262 are discharged to achieve the function of zero-cut switching. Another function of achieving zero voltage switching is the lower arm switch group 2〇 M440613 The second parasitic diode 204 and the first parasitic diode 184 of the upper arm switch group 18 respectively operate corresponding to the current remaining in the first shunt circuit 24 and the second shunt circuit 26 during [Vt3] and [trto] ( 'And.' will be discharged. Another example is the architecture diagram of the third embodiment of the present invention as shown in Fig. 5. The difference from the first embodiment is that a first capacitor (Q) 28 and a second capacitor are added. (c2) 30 and a shunt capacitor (Cs) 32. wherein the upper arm switch group 18 is connected in parallel with the first capacitor 28, The piezoelectric element 14 is connected in parallel with a capacitor 30. As shown by the equivalent circuit in the figure, a shunt capacitor 32 is connected in series between the first capacitor 28 and the shunt circuit 16. The second capacitor 3〇 can change the shunt in the shunt circuit 16. The current value is, and the resonant frequency (fs) of the first capacitor 28 and the shunt circuit 16. The first capacitor 28 and the second capacitor 30 can be utilized to lower the resonant frequency (fs), and the current in the shunt circuit I6 can be increased. The shunt capacitor 32 can increase the vibration frequency (6) and reduce the current ls in the shunt circuit 16. By adding the above capacitor, the zero voltage switching condition of the piezoelectric chopper circuit 1 can be more flexibly designed. 'As shown in Fig. 6,' is the architectural diagram of the fourth embodiment of the present invention. The difference from the third actual example is that the piezoelectric element is a piezoelectric actuator 34, and the third capacitor A) 3 is used instead of the second capacitor (c2), and the mechanical spectrum Lm_Cm_Rm of the original piezoelectric transformer is pressed. Electric dance vibration, 34 mechanical resonance LmrCmrRm2 to replace, in simple terms, is the Lilai system = 34 replacement, light pressure device transfer energy. This can omit the output of the (4) device and each ^(10))° sheep. The current im in the eyebrow will flow into the output capacitor (c〇ut, =^ 22 '. In the example of the piezoelectric resonator 34, the current & will flow directly into the load a. ^ Current im ((4) Speed) Under the physical part of the wire, the piezoelectric resonator 34 can be more closely turned on in the load 22 i ^ circuit, and the output wattage of the load 2 is large, and the overall system is in the drive circuit of the electric transformer. It is impossible to switch the operation of the inverter book, and the available frequency range is too sloppy, which limits the development and application. For this reason, the half bridge opens _ storage f big _, and the shop time flow circuit is in the load And the operating frequency change M440613 I, still can be the effect of Lin County. In addition, _ shunt to replace the general inductance in the main current contact (10) product and the resulting loss, can make the overall circuit thin ^ can improve the overall Circuit performance, which contributes to the overall technical development and assists in the competition of the products mentioned above, is only created and implemented by the preferred embodiment of this creation. This equal change or _ should be included in the patent application for this creation = and spirit For the [simplified description of the diagram] inside.
第1圖為本創作之第一實施例示意圖。 第2圖為本創作之調光波形圖。 第3圖為本創作之第二實施例示意圖。 【主要元件符號說明】 1〇調光控制器 12整流器 14功率控制器 16驅動控制器 18電池 φ 20交流電源 22負載 13Figure 1 is a schematic view of a first embodiment of the present invention. The second picture is the dimming waveform of the creation. Figure 3 is a schematic view of a second embodiment of the creation. [Main component symbol description] 1〇 dimming controller 12 rectifier 14 power controller 16 drive controller 18 battery φ 20 AC power supply 22 load 13