M410164 五、新型說明： 【新型所屬之技術領域】 本創作有關於一種照明裝置，且特別是有關於一種發 光二極體的照明裝置。 【先前技術】 在發光二極體(LED)的驅動技術中，一般常採用交流電 AC驅動發光二極體的方式。此種方式為將交流電AC輸入 至2電路BR ’交流電AC經全波整流後，再經由限流電 阻R1以驅動發光二極體燈陣列LA，如圖！所示。然而， 此種驅動方式可能會因為不穩定的交流電Ac而產生以下 缺點。 一、輸出功率不穩定。換言之，流過發光二極體燈陣 列LA的平均電流會隨交流電ac的峰值電壓而變動，導致 發光二極體燈陣列LA的輸出功率不穩定與亮度變動大的 問題，而易造成發光二極體燈陣列LA損壞或光衰。 一、發光效率低。發光二極體燈陣列la的導通電壓通 常會设計為接近交流電AC的峰值電壓，此設計會導致每一 電壓周期的燈管電流其導通時間短的情況。在電流導通時 間短的情況下’必目對增加燈管電流的峰值，才能夠維 持固定的平均電流流過發光二極體燈陣列LA…般來說， $光-極體的發光強度與燈管電流成非線性關係，如在特 疋電/瓜1A %，發光強度為！，當增加電流時，發光強 度僅為1.6而非2。因此，將發光二極體燈陣列LA的導通 電[。又。十為接近父流電AC的峰值電壓，係會造成發光二極 租燈陣列LA發光效率變低，進而間接影響整體系統效率， 即正粗系統效率=發光二極體驅動轉換效率X發光二極體發 3/26 M410164 光效率。 【新型内容】 本創作實施例提供一種照明裝置及其控制方法，其中 照明裝置依據交流電源整流後的輸入電源，對應改變照 明裝置中二個以上的發光模組與整流單元之間連結的 關係’以達到兩的發光效率及長的使用壽命。 依據一實施例，本創作之照明裝置接收一交流電， 包括一第一發光模組、一第二發光模組、一整流單元及 一控制模組。整流單元將交流電轉成一輸入電源。控制 模組搞接於整流單元、第一發光模組及第二發光模組， 其係接收輪入電源，並且在輸入電源小於一參考值時， 控制第一發光模組、第二發光模組及整流單元形成第一 連結狀態，或在輸入電源大於參考值時，控制第一發光 模組、第二發光模組及整流單元形成第二連結狀態。 依據另一實施例，本創作之照明裝置的控制方法，適 用於-控制模組對-第—發光模組與—第二發光模组的控 制’其步驟包括有：首先’取得__輸人電源，該輸入電源 為交流電經整流後的電源；織，在輸人電源小於一參考 =時，控制第-發光模組與第二發光模組及輸入電源形成 一—連結狀態丨接著，在輸入電源大於參考值時，控制第 。發光模組與第二發光模組及輸人電源形成第二連結狀態 依據再一實施例，本創作之照明裝置的控制方法， 二用控制模組對多個發光模組的控制，其步驟包括 控 德㈣先’取得—輸人電源，該輸人電源為交流電經整流 後的電源；然後，在輸入電源小於一第一參考值時广 4/26 制多個發光模組與輪 在輸入電源大於該第成第—連結狀態；接著’ ，控制多個發光模㈣輪且小於—第二參考值時 後，在輸入電源大於第ft源形成第二連結狀態；然 與輸入電源形成第三連結;^值時，控制多個發光模組 涼本創作貫施例所提供的照明裝置係依據交 ::…“的！入電源，對應改變照明裝置中二個或 ^ =上的發光核組與整流單元之間連結的關係，並且 、乂仔-固定平均電流下，可以降低每電壓周期流過發 光核組的電流峰值’進而達到高發光效率及使用壽命長 的效果。 為使此更進一步瞭解本創作之特徵及技術内容’請參 閱以下有關本創作之詳細說明與附圖，但是此等說明與所 附圖式僅係用來說明本創作，而非對本創作的權利範圍作 任何的限制。 【實施方式】 本創作實施例所提供的照明裝置，其驅動方式係利用 交流電整流後的輸入電源直接驅動二個或兩個以上發光 模組的技術。本創作實施例中較佳的發光模組可以是發 光一極體(LED)或發光二極體陣列(LED Array)，發光二 極體陣列包括多個彼此連接的發光二極體(LED)。前述 中’該些發光二極體(LED)包括彼此串聯、並聯或串並 聯等連接關係。然，發光二極體或發光二極體陣列並不 為本創作唯一限制，凡可以被交流電整流後的輸入電源直 接驅動的發光模組皆為本創作的範圍。 參閱圖2。圖2為本創作實施例的功能架構示意圖。照 5/26 M410164 明裝置1包括-控制模經1Q、—整流單元i^、一第一 發光模組12及一第二發光模組14，其中控制模組1〇耦 接於整流單兀11、第一發光模組12及第二發光模組14 。整流單元11將一交流電AC轉成一輸入電源vbr，該 輸入電源Vbr的電壓波形係為正弦波(sine wave)的交流電 AC經過整流後的波形，因此，輸入電源vbr的電壓大小隨 著交流電AC而變化。 復參考圖2。控制模組1〇接收輸入電源Vbr，並且 偵測輸入電源Vbr的電壓大小。同時，控制模組設 有一參考值’其中當輸入電源Vbr的電壓小於參考值時 ’控制模組10係控制第一發光模組12與第二發光模組 14及整流單元11形成第一連結狀態。另外，當輸入電 源Vbr的電壓大於參考值時，控制模組1〇則控制第一 發光模組10與第二發光模組14及整流單元11形成第 二連結狀態。 如此，照明裝置1係能夠依據交流電AC整流後的 輸入電源Vbr，對應改變第一發光模組1〇、第二發光模 組14與整流單元Π之間的連結關係，在求得一固定平 均電流下，可以降低每電壓周期流過第一發光模組10 與第二發光模組14的電流峰值，進而達到高發光效率 及使用壽命長的效果。 參考圖3。圖3為本創作第一實施例的電路示意圖。 整流單元11為一全波整流器，其係用來將交流電AC整 流成輸入電源Vbr，其中整流單元η可以是一顆整流晶 片或是由4個二極體BR1〜BR4連接組成’此為一般熟 知技術，在此不再贅述。 6/26 M410164 控制模組10包括一開關單元102與一控制單元104 。開關單元102耦接於第一發光模組12與第二發光模 組14。控制單元104耦接於整流單元11與開關單元102 ，係依據輸入電源Vbr的電壓是否大於一參考值，而加 以控制開關單元102的動作。開關單元102的動作係可 以改變第一發光模組12、第二發光模組14與整流單元 11之間的連接關係，三者之間的連接關係係隨著輸入電 源Vbr的電壓是否大於參考值而處在第一連結狀態或第 二連結狀態。 復參考圖3。開關單元102包括一二極體D1、一第 一電晶體Q1及一第二電晶體Q2,前述各元件之間的連 接關係及動作說明如下。二極體D1的陽極端連接第一 發光模組12的輸出端T12，二極體D1的陰極端則連接 第二發光模組14的輸入端T21。第一電晶體Q1的輸出 /入端C1經由限流電阻R3連接二極體D1的陰極端，第 一電晶體Q1的輸出/入端E1連接第一發光模組12的輸 入端T11，且第一電晶體Q1的受控端B1連接控制單元 104。同時，第二電晶體的Q2的輸出/入端C2經由限流 電阻R2連接第二發光模組14的輸出端T22，第二發光 模組14的輸出端T22經由限流電阻R1連接接地端Gnd 及整流單元11，第二電晶體的Q2的輸出/入端E2連接 二極體D1之陽極端，第二電晶體的Q2的受控端B2連 接控制單元104。 本實施例之限流電路係由限流電阻Rl、R2、R3串 並聯接組成，然此種方式並不是唯一的限流電路，凡是 可以依據輸入電源Vbr而控制流過發光模組的電流的電 7/26 M410164 路都為本創作主張權利的範圍。 復參考圖3。控制單元104包括一分壓電路1042與 一驅動電路1044。分壓電路1042連接於整流單元11， 其係依據輸入電源Vbr而建立一輸入電壓比例值VR， 該輸入電壓比例值VR的電壓大小與輸入電源Vbr成比 例。本實施例之分壓電路1042係由電阻R12、R13串接 組成，然此種方式並不是唯一的分壓電路，凡是可以依 據輸入電源Vbr而建立輸入電壓比例值VR的分壓電路 都為本創作主張權利的範圍。 驅動電路1044耦接於分壓電路1042，其係接收分 壓電路1042所建立的輸入電壓比例值VR，其中驅動電 路1044具有設定值Vth。驅動電路1044在輸入電壓比 例值VR小於設定值Vth時，控制第一電晶體Q1與第 二電晶體Q2導通(turn on)，以令第一發光模組12、第 二發光模組14及整流單元11形成第一連結狀態。另外 ，驅動電路1044在輸入電壓比例值VR大於設定值Vth 時，控制第一電晶體Q1與第二電晶體Q2截止(turn off) ，以令第一發光模組12、第二發光模組14及整流單元 11形成第二連結狀態。 本實施例之驅動電路1044包括二個電晶體Q3、Q4 ，然此種電路並不是唯一的驅動電路，凡是可以依據輸 入電壓比例值VR與設定值Vth之間的比較結果，加以 驅動第一電晶體Q1與第二電晶體Q2的電路都為本創作 主張權利的範圍。 參考圖3與圖4。圖4為圖3的電路波形示意圖。 控制單元104從整流單元11接收輸入電源Vbr，並在分 8/26 M410164 壓電路1042的電阻R13上建立輸入電壓比例值VR。當 輸入電源Vbr在期間T1時，建立在電阻R13上的輸入 電壓比例值VR尚且小於電晶體Q4的設定值Vth(意即 輸入電源Vbr小於參考值Vref)。在此期間T1，建立在 分壓電路1042上的電阻電壓VR12會令電晶體Q3導通 ，以控制第一電晶體Q1與第二電晶體Q2進入導通(turn on)狀態，進而讓第一發光模組12與第二發光模組14 並聯電性連結於整流單元11以形成第一連結狀態。此 時，分別流過第一發光模組12與第二發光模組14的電 流11如圖4所示。 另外，在期間T2，建立在電阻R13上的輸入電壓 比例值VR隨著輸入電源Vbr電壓的增加而大於電晶體 Q4的設定值Vth(意即輸入電源Vbr大於參考值Vref)。 在此期間T2，電晶體Q4進入導通，以令電晶體Q3進 入截止。截止的電晶體Q3係控制第一電晶體Q1與第二 電晶體Q2進入截止(turn off)狀態，進而讓第一發光模 組12與第二發光模組14串聯電性連結於整流單元11 以形成第二連結狀態。此時，流過第一發光模組12與 第二發光模組14的電流12如圖4所示。 換言之，控制單元104在較低的輸入電源Vbr下控 制開關單元102,以令第一發光模組12與第二發光模組 14並聯連接，進而讓較低的輸入電源Vbr供電給並聯的 第一發光模組12與第二發光模組14。由於並聯的第一 發光模組12與第二發光模組14具有較低的導通電壓， 因此，較低的輸入電源Vbr即可以讓並聯的第一發光模 組12與第二發光模組14動作以產生電流II。另外，控 9/26 M410164 制單元104在較高的輸入電源Vbr下控制開關單元102 ，以令第一發光模組12與第二發光模組14串聯連接， 進而讓較高的輸入電源Vbr供電給串聯的第一發光模組 12與第二發光模組14。由於串聯的第一發光模組12與 第二發光模組14具有較高的導通電壓，因此，較高的 輸入電源Vbr即可以讓串聯的第一發光模組12與第二 發光模組14動作以產生電流12。 如此，利用較低的輸入電源Vbr供電給並聯的第一 發光模組12與第二發光模組14，以及較高的輸入電源 Vbr供電給串聯的第一發光模組12與第二發光模組14 的方式，在求得一固定平均電流下，即可以降低每電壓 周期流過第一發光模組12與第二發光模組14的電流峰 值，進而達到高發光效率及使用壽命長的效果。 復參考圖3與圖4。輸入電源Vbr(或輸入電壓比例 值VR)為正弦波的交流電AC整流後的電源，其電壓波 形係以90度為對稱增減，因此，控制單元104在期間 T3、T4對電晶體Q3、Q4的動作控制係對應且相同於期 間T2、T1，如圖4所示。 綜上所述，控制單元104會追隨輸入電源Vbr的電 壓大小，在一電壓週期内，讓第一發光模組12、第二發 光模組14與整流單元11之間的連結關係依序循環動作 在第一連結狀態、第二連結狀態、第一連結狀態之間。 如此，在固定平均電流的驅動方式下，控制單元104的 控制方式，將可以降低每電壓周期流過第一發光模組12 、第二發光模組14的電流峰值（如同電流12)，進而提高 照明裝置1整體的發光效率及使用壽命。 10/26 參考圖5。圖5為本創作第二實施例的電路示意圖。 本實施例的照明裝置2與圖3的照明裝置1之間主要的差 別在於控制模組20。照明裝置2的控制模組20包括一開 關單元202與一控制單元204。開關單元202為一電晶 體Q3,其中電晶體Q3的輸出/入端C3經由限流電阻R2 連接第一發光模組12的輸出端T12與第二發光模組14 的輸入端T21。電晶體Q3的輸出/入端E3連接於接地端 Gnd，第二發光模組14的輸出端T22經由限流電阻R1 連接於接地端Gnd，電晶體Q3的受控端B3連接控制單 元 204。 復參考圖5。控制單元204包括一分壓電路2042與 一驅動電路2044，其中分壓電路2042與圖3的分壓電 路1042相同，在此不再贅述。另外，本實施例之驅動 電路2044包括一個電晶體Q4，其係依據輸入電壓比例 值VR與設定值Vth之間的比較結果，以驅動電晶體Q3 ，進而令第一發光模組12、第二發光模組14及整流單 元11形成第一連結狀態或第二連結狀態。 如此，控制單元204從整流單元11接收輸入電源 Vbr，並在分壓電路2042的電阻R13上建立輸入電壓比 例值VR。在輸入電壓比例值VR尚且小於電晶體Q4的 設定值Vth期間，建立在分壓電路2042上的電阻電壓 VR12會先令電晶體Q3導通，進而讓第一發光模組12 單獨的電性連結於整流單元11以及第二發光模組14切 離整流單元11以形成第一連結狀態。 另外，在輸入電壓比例值VR隨著輸入電源Vbr電 壓的增加而大於電晶體Q4的設定值Vth期間。電晶體 11/26 M410164 Q4進入導通，以令電晶體Q3截止，進而讓第一發光模 組12與第二發光模組14串聯電性連結於整流單元11 以形成第二連結狀態。 換言之’控制單元204在較低的輸入電源Vbr下控 制開關單元202,以令第一發光模組12單獨的串聯電性 連結於整流單元11，進而讓較低的輸入電源Vbr供電給 第一發光模組12。由於單獨的第一發光模組π具有較 低的導通電壓’因此，較低的輸入電源Vbr即可以讓單 獨的第一發光模組12先行動作。另外，控制單元204 在較高的輸入電源Vbr下控制開關單元202，以令第一 發光模組12與第二發光模組14串聯連接，進而讓較高 的輸入電源Vbr供電給串聯的第一發光模組12與第二 發光模組14。由於串聯的第一發光模組12與第二發光 模組14具有較高的導通電壓，因此’較高的輸入電源M410164 V. New description: [New technical field] This creation relates to a lighting device, and in particular to a lighting device for a light-emitting diode. [Prior Art] In the driving technology of a light-emitting diode (LED), an alternating current AC driving a light-emitting diode is generally used. In this way, the AC power is input to the 2 circuit BR' AC AC after full-wave rectification, and then the current-limiting resistor R1 is used to drive the LED array LA, as shown in the figure! Shown. However, this type of driving may cause the following disadvantages due to the unstable AC. First, the output power is unstable. In other words, the average current flowing through the LED array LA varies with the peak voltage of the AC ac, resulting in an unstable output power of the LED array LA and a large variation in luminance, which is liable to cause a light-emitting diode. The body light array LA is damaged or light fading. First, the luminous efficiency is low. The turn-on voltage of the LED array l is typically designed to be close to the peak voltage of the AC AC. This design results in a short on-time of the lamp current for each voltage cycle. In the case of a short current conduction time, it is necessary to increase the peak value of the lamp current to maintain a constant average current flowing through the LED array LA. In general, the luminous intensity of the light-polar body and the lamp The tube current is in a non-linear relationship, such as in the special electricity / melon 1A%, the luminous intensity is! When the current is increased, the luminous intensity is only 1.6 instead of 2. Therefore, the conduction of the LED array LA is performed. also. Ten is close to the peak voltage of the parent current AC, which will cause the luminous efficiency of the LED array to be low, which indirectly affects the overall system efficiency, ie, the efficiency of the thick system = the efficiency of the LED driving conversion X-emitting diode Body hair 3/26 M410164 light efficiency. [New Content] The present embodiment provides a lighting device and a control method thereof, wherein the lighting device changes the relationship between two or more lighting modules and the rectifying unit in the lighting device according to the input power source after the rectification of the AC power source. In order to achieve two luminous efficiency and long service life. According to an embodiment, the lighting device of the present invention receives an alternating current, and includes a first lighting module, a second lighting module, a rectifying unit and a control module. The rectifying unit converts the alternating current into an input power source. The control module is connected to the rectifying unit, the first lighting module and the second lighting module, and is configured to receive the wheeled power supply, and control the first lighting module and the second lighting module when the input power source is less than a reference value And the rectifying unit forms a first connected state, or controls the first lighting module, the second lighting module and the rectifying unit to form a second connecting state when the input power is greater than the reference value. According to another embodiment, the control method of the lighting device of the present invention is applicable to the control of the control module pair-the first lighting module and the second lighting module. The steps include: firstly obtaining __input The power source is the rectified power source of the alternating current power; the weaving, when the input power source is less than a reference=, controls the first lighting module to form a connection state with the second lighting module and the input power source, and then input When the power supply is greater than the reference value, control is performed. The light-emitting module and the second light-emitting module and the input power source form a second connection state. According to still another embodiment, the control method of the illumination device of the present invention, the control module controls the plurality of light-emitting modules, and the steps thereof include Controlled (four) first 'acquired-input power supply, the input power is the rectified power supply of the alternating current; then, when the input power is less than a first reference value, the 4/26 multi-light module and the wheel are input power When the plurality of illuminating mode (four) wheels are controlled and less than the second reference value, the second connection state is formed when the input power source is greater than the ft source; however, the third connection is formed with the input power source. When the value is ^, the illumination device provided by the control of the plurality of light-emitting modules is based on the intersection of::..." into the power supply, corresponding to changing the illuminating core group of the two or ^= in the lighting device The relationship between the rectifying units and the current at the fixed average current of the clams can reduce the peak current flowing through the illuminating core group per voltage cycle, thereby achieving high luminous efficiency and long service life. Further understanding of the features and technical contents of the present application 'Please refer to the following detailed description and drawings of the present invention, but the description and the drawings are only used to illustrate the present invention, and not to the scope of the present invention. [Embodiment] The illumination device provided in the present embodiment is driven by an AC power rectified input power source to directly drive two or more light-emitting modules. The module may be a light emitting diode (LED) or a light emitting diode array (LED Array), and the light emitting diode array includes a plurality of light emitting diodes (LEDs) connected to each other. The aforementioned 'light emitting diodes' (LED) includes the connection relationship of series, parallel or series-parallel connection with each other. However, the LED or LED array is not the only limitation of this creation, and the illumination module can be directly driven by the AC power rectified input power. The scope of this creation is as follows. Refer to Figure 2. Figure 2 is a schematic diagram of the functional architecture of the present embodiment. Photo 5/26 M410164 The device 1 includes a control mode via 1Q, a rectification unit. The first lighting module 12 and the second lighting module 14 are coupled to the rectifying unit 11, the first lighting module 12 and the second lighting module 14. The rectifying unit 11 An alternating current AC is converted into an input power source vbr. The voltage waveform of the input power source Vbr is a rectified waveform of a sine wave AC current. Therefore, the magnitude of the voltage of the input power source vbr varies with the alternating current AC. Referring to Figure 2, the control module 1 receives the input power Vbr and detects the voltage of the input power source Vbr. At the same time, the control module is provided with a reference value 'When the voltage of the input power source Vbr is less than the reference value', the control module The 10 series controls the first light emitting module 12, the second light emitting module 14 and the rectifying unit 11 to form a first connected state. In addition, when the voltage of the input power source Vbr is greater than the reference value, the control module 1〇 controls the first light-emitting module 10 to form a second connection state with the second light-emitting module 14 and the rectifying unit 11. In this manner, the illuminating device 1 can determine a fixed average current according to the connection relationship between the first illuminating module 1 〇, the second illuminating module 14 and the rectifying unit 依据 according to the AC power rectified input power source Vbr. In the following, the current peaks flowing through the first light-emitting module 10 and the second light-emitting module 14 per voltage cycle can be reduced, thereby achieving high luminous efficiency and long service life. Refer to Figure 3. FIG. 3 is a schematic circuit diagram of the first embodiment of the present invention. The rectifying unit 11 is a full-wave rectifier for rectifying the alternating current AC into an input power source Vbr, wherein the rectifying unit n can be a rectifying chip or composed of four diodes BR1 BRBR4 connected. Technology will not be described here. The 6/26 M410164 control module 10 includes a switch unit 102 and a control unit 104. The switch unit 102 is coupled to the first light emitting module 12 and the second light emitting module 14. The control unit 104 is coupled to the rectifying unit 11 and the switching unit 102, and controls the action of the switching unit 102 according to whether the voltage of the input power source Vbr is greater than a reference value. The operation of the switch unit 102 can change the connection relationship between the first lighting module 12, the second lighting module 14 and the rectifying unit 11, and the connection relationship between the three is related to whether the voltage of the input power source Vbr is greater than a reference value. It is in the first link state or the second link state. Refer to Figure 3 for details. The switching unit 102 includes a diode D1, a first transistor Q1, and a second transistor Q2. The connection relationship and operation between the components are as follows. The anode end of the diode D1 is connected to the output end T12 of the first light-emitting module 12, and the cathode end of the diode D1 is connected to the input end T21 of the second light-emitting module 14. The output/input terminal C1 of the first transistor Q1 is connected to the cathode end of the diode D1 via the current limiting resistor R3, and the output/input terminal E1 of the first transistor Q1 is connected to the input terminal T11 of the first light emitting module 12, and A controlled end B1 of a transistor Q1 is coupled to the control unit 104. At the same time, the output/input terminal C2 of the second transistor Q2 is connected to the output terminal T22 of the second light-emitting module 14 via the current limiting resistor R2, and the output terminal T22 of the second light-emitting module 14 is connected to the ground terminal Gnd via the current limiting resistor R1. And the rectifying unit 11, the output/input terminal E2 of the second transistor Q2 is connected to the anode terminal of the diode D1, and the controlled terminal B2 of the second transistor Q2 is connected to the control unit 104. The current limiting circuit of the embodiment is composed of a series of current limiting resistors R1, R2, and R3. However, this method is not the only current limiting circuit. Any current flowing through the light emitting module can be controlled according to the input power source Vbr. Electricity 7/26 M410164 Road is the scope of the author's claim. Refer to Figure 3 for details. The control unit 104 includes a voltage dividing circuit 1042 and a driving circuit 1044. The voltage dividing circuit 1042 is connected to the rectifying unit 11, and establishes an input voltage proportional value VR according to the input power source Vbr. The voltage level of the input voltage proportional value VR is proportional to the input power source Vbr. The voltage dividing circuit 1042 of the embodiment is composed of resistors R12 and R13 connected in series, but this method is not the only voltage dividing circuit, and the voltage dividing circuit capable of establishing the input voltage proportional value VR according to the input power source Vbr Both are the scope of claiming rights for this creation. The driving circuit 1044 is coupled to the voltage dividing circuit 1042, which receives the input voltage proportional value VR established by the voltage dividing circuit 1042, wherein the driving circuit 1044 has a set value Vth. The driving circuit 1044 controls the first transistor Q1 and the second transistor Q2 to turn on when the input voltage ratio value VR is less than the set value Vth, so that the first light emitting module 12, the second light emitting module 14 and the rectification are performed. Unit 11 forms a first connected state. In addition, the driving circuit 1044 controls the first transistor Q1 and the second transistor Q2 to turn off when the input voltage ratio value VR is greater than the set value Vth, so that the first light emitting module 12 and the second light emitting module 14 are turned off. And the rectifying unit 11 forms a second connected state. The driving circuit 1044 of this embodiment includes two transistors Q3 and Q4. However, such a circuit is not the only driving circuit. The first circuit can be driven according to the comparison result between the input voltage proportional value VR and the set value Vth. The circuits of the crystal Q1 and the second transistor Q2 are within the scope of the claimed claims. Refer to Figures 3 and 4. 4 is a schematic diagram of a circuit waveform of FIG. 3. The control unit 104 receives the input power source Vbr from the rectifying unit 11, and establishes an input voltage proportional value VR on the resistor R13 of the divided 8/26 M410164 voltage circuit 1042. When the input power source Vbr is in the period T1, the input voltage proportional value VR established on the resistor R13 is still smaller than the set value Vth of the transistor Q4 (i.e., the input power source Vbr is smaller than the reference value Vref). During this period T1, the resistor voltage VR12 established on the voltage dividing circuit 1042 turns on the transistor Q3 to control the first transistor Q1 and the second transistor Q2 to enter a turn-on state, thereby allowing the first light to be emitted. The module 12 and the second light-emitting module 14 are electrically connected in parallel to the rectifying unit 11 to form a first connected state. At this time, the current 11 flowing through the first light-emitting module 12 and the second light-emitting module 14 respectively is as shown in FIG. Further, in the period T2, the input voltage proportional value VR established on the resistor R13 is larger than the set value Vth of the transistor Q4 as the input power source Vbr voltage is increased (that is, the input power source Vbr is larger than the reference value Vref). During this period T2, the transistor Q4 enters conduction to turn on the transistor Q3. The cut-off transistor Q3 controls the first transistor Q1 and the second transistor Q2 to enter a turn-off state, and the first light-emitting module 12 and the second light-emitting module 14 are electrically connected to the rectifying unit 11 in series. A second connected state is formed. At this time, the current 12 flowing through the first light-emitting module 12 and the second light-emitting module 14 is as shown in FIG. In other words, the control unit 104 controls the switch unit 102 under the lower input power source Vbr to connect the first lighting module 12 and the second lighting module 14 in parallel, thereby allowing the lower input power source Vbr to be powered to the first in parallel. The light emitting module 12 and the second light emitting module 14 are provided. Since the first light-emitting module 12 and the second light-emitting module 14 in parallel have a lower turn-on voltage, the lower input power source Vbr can operate the first light-emitting module 12 and the second light-emitting module 14 in parallel. To generate current II. In addition, the control 9/26 M410164 unit 104 controls the switch unit 102 under a higher input power source Vbr to connect the first lighting module 12 and the second lighting module 14 in series, thereby allowing a higher input power source Vbr to be powered. The first light emitting module 12 and the second light emitting module 14 are connected in series. Since the first light-emitting module 12 and the second light-emitting module 14 in series have a high turn-on voltage, the higher input power source Vbr can operate the first light-emitting module 12 and the second light-emitting module 14 in series. To generate a current of 12. In this way, the lower input power source Vbr is used to supply the first light-emitting module 12 and the second light-emitting module 14 in parallel, and the higher input power source Vbr is supplied to the first light-emitting module 12 and the second light-emitting module in series. In the method of 14 , when a fixed average current is obtained, the current peak flowing through the first light-emitting module 12 and the second light-emitting module 14 per voltage cycle can be reduced, thereby achieving high luminous efficiency and long service life. Refer to Figure 3 and Figure 4 for details. The input power source Vbr (or the input voltage ratio value VR) is a sinusoidal alternating current AC rectified power supply, and the voltage waveform thereof is symmetrically increased or decreased by 90 degrees. Therefore, the control unit 104 pairs the transistors Q3 and Q4 during the period T3 and T4. The motion control system corresponds to and is the same as the period T2, T1, as shown in FIG. In summary, the control unit 104 follows the voltage of the input power source Vbr, and sequentially cycles the connection relationship between the first lighting module 12, the second lighting module 14, and the rectifying unit 11 in a voltage cycle. The first connection state, the second connection state, and the first connection state. In this way, in the driving mode of the fixed average current, the control mode of the control unit 104 can reduce the current peak value (like the current 12) flowing through the first lighting module 12 and the second lighting module 14 per voltage cycle, thereby improving The luminous efficiency and the service life of the illumination device 1 as a whole. 10/26 Refer to Figure 5. Fig. 5 is a circuit diagram showing the second embodiment of the creation. The main difference between the illumination device 2 of the present embodiment and the illumination device 1 of Fig. 3 is the control module 20. The control module 20 of the lighting device 2 includes a switching unit 202 and a control unit 204. The switch unit 202 is an electric crystal Q3. The output terminal C3 of the transistor Q3 is connected to the output terminal T12 of the first lighting module 12 and the input terminal T21 of the second lighting module 14 via the current limiting resistor R2. The output/input terminal E3 of the transistor Q3 is connected to the ground terminal Gnd, the output terminal T22 of the second lighting module 14 is connected to the ground terminal Gnd via the current limiting resistor R1, and the controlled terminal B3 of the transistor Q3 is connected to the control unit 204. Refer to Figure 5 for details. The control unit 204 includes a voltage dividing circuit 2042 and a driving circuit 2044. The voltage dividing circuit 2042 is the same as the voltage dividing circuit 1042 of FIG. 3 and will not be described herein. In addition, the driving circuit 2044 of the embodiment includes a transistor Q4, which is driven according to the comparison result between the input voltage proportional value VR and the set value Vth to drive the transistor Q3, thereby causing the first light emitting module 12 and the second The light-emitting module 14 and the rectifying unit 11 form a first connected state or a second connected state. Thus, the control unit 204 receives the input power source Vbr from the rectifying unit 11, and establishes the input voltage ratio value VR on the resistor R13 of the voltage dividing circuit 2042. During the input voltage proportional value VR is still less than the set value Vth of the transistor Q4, the resistor voltage VR12 established on the voltage dividing circuit 2042 will first turn on the transistor Q3, thereby allowing the first lighting module 12 to be electrically connected separately. The rectifying unit 11 and the second lighting module 14 are cut away from the rectifying unit 11 to form a first connected state. Further, the input voltage proportional value VR is larger than the set value Vth of the transistor Q4 as the input power source Vbr voltage increases. The transistor 11/26 M410164 Q4 is turned on to turn off the transistor Q3, and the first illuminating module 12 and the second illuminating module 14 are electrically connected in series to the rectifying unit 11 to form a second connecting state. In other words, the control unit 204 controls the switch unit 202 under the lower input power source Vbr to electrically connect the first light-emitting module 12 to the rectifying unit 11 in series, thereby allowing the lower input power source Vbr to supply the first light. Module 12. Since the single first lighting module π has a lower on-voltage, the lower input power source Vbr allows the individual first lighting module 12 to operate first. In addition, the control unit 204 controls the switch unit 202 under the higher input power source Vbr to connect the first light-emitting module 12 and the second light-emitting module 14 in series, thereby allowing the higher input power source Vbr to be powered to the first in series. The light emitting module 12 and the second light emitting module 14 are provided. Since the first light-emitting module 12 and the second light-emitting module 14 connected in series have a high turn-on voltage, the higher input power is
Vbr即可以讓事聯的第一發光模組12與第二發光模組 14動作。 如此’利用較低的輸入電源Vbr供電給單獨的第一 發光模組12，以及較高的輸入電源vbr供電給串聯的第 一發光模組12與第二發光模組14的方式，即可以降低 每電壓周期流過第—發光模組12與第二發光模組14的 電/;IL峰值’進而達到高發光效率及使用壽命長的效果。 '上所述，控制單元204會追隨輸入電源vbr的電 壓大小，在一電壓遇期内，讓第一發光模組12、第二 組14與整流單元Π之間的連結關係依序循環動作 在第一連結狀態1二連結狀態、第-連結狀態之間。 如此’在固定平均電流的驅動方式下，控制單元2〇4的 12/26 M410164 控制方式，將可以降低每電壓周期流過第一發光模組12 、第二發光模組14的電流峰值，進而提高照明裝置2 整體的發光效率及使用壽命。 配合圖3，請參考圖6。圖6為本創作第三實施例的 電路示意圖。本實施例的照明裝置3與圖3的照明裝置1 之間主要的差別在於，本實施例的照明裝置3更包括一功 率補償模組16。功率補償模組16耦接於整流單元11、 控制模組10、第一發光模組12及第二發光模組14，其 係根據輸入電源Vbr的電壓大小，對應調整流過第一發 光模組12與第二發光模組14的總電流ILED。換句話 說，功率補償模組16係隨著輸入電源Vbr的電壓大小 ，以對流過第一發光模組12與第二發光模組14的總電 流ILED作補償，以令在額定交流電AC範圍下，讓輸 入功率維持在一額定範圍内。 前述中，照明裝置3藉由功率補償模組16對電流 的補償作用，將可以有效的抑制流過第一發光模組12 與第二發光模組14的電流峰值。相較於圖4，如圖7所 示，在期間T1流過第一發光模組12與第二發光模組14 的電流II峰值較為平整。另外，在期間T2，流過第一 發光模組12與第二發光模組14的電流12峰值也較為平 整。 值得一提的是，功率補償模組16不需搭配控制模 組10，也可以單獨的與整流單元11、第一發光模組12 及第二發光模組14耦接構成一種照明裝置（未標示），以 作為該種照明裝置的電流補償，令該種照明裝置的輸入 功率可以維持在一額定範圍内。 13/26 M410164 功率補償模組16包括一電壓控制電流源162與一 定電流源164。電壓控制電流源162耦接於整流單元11 ’係根據輸入電源Vbr的電壓大小，對應輸出一補償電 流1br。舉例來說’輸入電源Vbr的電壓越大，對應輸 出的補償電流Ibr也相對變大’反之，輸入電源Vbr的 電壓越小’對應輸出的補償電流Ibr也相對變小。前述 十’電壓控制電流源162包括電阻R1、R2、及稽納二 極體ZD1 ’其係利用前端取樣方式取得輸入電源vbr的 電壓大小’再根據輸入電源Vbr的電壓大小，對應輸出 補償電流Ibr，以作為總電流ILED的補償。 另外，定電流源164耦接電壓控制電流源丨62、控 制模組10、第一發光模組12及第二發光模組14，其係 從電壓控制電流源162接收補償電流Ibr，並且根據補償 電流Ibr的大小，加以調整流過第一發光模組12與第二 發光模組14的總電流ILED。舉例來說，補償電流Ibr 越大，則流過第一發光模組12與第二發光模組14的總 電流ILED相對變小，反之，補償電流Ibr越小，則流過 第一發光模組12與第二發光模組14的總電流ILED相 對變大。 综上所述，功率補償模組16取得輸入電源Vbr的 電壓，並且追隨輸入電源Vbr的電壓大小，以對應補償 流過第一發光模組Π與第二發光模組14的總電流ILED ，進而讓總電流ILED能夠維持在額定範圍之内。 如此’本實施例的照明裝置3係可以利用功率補償模 組16作為總電流ILED的補償，讓總電流不至於 受到不穩定的輸入電源Vbr影響，進而讓輸入功率能夠 14/26 M410164 維持在額定範圍内，得以解決第一發光模組12與第二 發光模組14受到不穩定的交流電Ac之影響所造成損壞 與光衰的問題。The Vbr can operate the first lighting module 12 and the second lighting module 14 of the event. Thus, the method of using the lower input power source Vbr to supply the separate first lighting module 12 and the higher input power source vbr to the first lighting module 12 and the second lighting module 14 in series can be reduced. The voltage / the IL peak of the first light-emitting module 12 and the second light-emitting module 14 flows through the voltage cycle to achieve high luminous efficiency and long service life. As described above, the control unit 204 follows the magnitude of the voltage of the input power source vbr. During a voltage period, the connection relationship between the first lighting module 12, the second group 14 and the rectifying unit 依 is sequentially circulated. The first connection state is between the two connection states and the first connection state. Thus, in the driving mode of the fixed average current, the 12/26 M410164 control mode of the control unit 2〇4 can reduce the current peak flowing through the first lighting module 12 and the second lighting module 14 every voltage cycle, and further Improve the overall luminous efficiency and service life of the lighting device 2. Referring to Figure 3, please refer to Figure 6. Fig. 6 is a circuit diagram showing the third embodiment of the creation. The main difference between the illuminating device 3 of the present embodiment and the illuminating device 1 of Fig. 3 is that the illuminating device 3 of the present embodiment further includes a power compensation module 16. The power compensation module 16 is coupled to the rectifying unit 11, the control module 10, the first lighting module 12, and the second lighting module 14, and is correspondingly adjusted to flow through the first lighting module according to the voltage of the input power source Vbr. 12 and the total current ILED of the second lighting module 14. In other words, the power compensation module 16 compensates for the total current ILED flowing through the first lighting module 12 and the second lighting module 14 according to the voltage of the input power source Vbr, so as to be in the rated AC power range. , to keep the input power within a nominal range. In the foregoing, the illuminating device 3 can effectively suppress the current peaks flowing through the first lighting module 12 and the second lighting module 14 by the power compensation function of the power compensation module 16. Compared with FIG. 4, as shown in FIG. 7, the current II peak flowing through the first light-emitting module 12 and the second light-emitting module 14 during the period T1 is relatively flat. In addition, during the period T2, the peak value of the current 12 flowing through the first light-emitting module 12 and the second light-emitting module 14 is also relatively flat. It is worth mentioning that the power compensation module 16 does not need to be combined with the control module 10, and can be separately coupled with the rectifying unit 11, the first lighting module 12 and the second lighting module 14 to form a lighting device (not labeled) In order to compensate the current of the lighting device, the input power of the lighting device can be maintained within a rated range. The 13/26 M410164 power compensation module 16 includes a voltage controlled current source 162 and a predetermined current source 164. The voltage control current source 162 is coupled to the rectifying unit 11 ′ according to the magnitude of the voltage of the input power source Vbr, and correspondingly outputs a compensation current 1br. For example, the larger the voltage of the input power source Vbr, the larger the compensation current Ibr corresponding to the output. On the contrary, the smaller the voltage of the input power source Vbr, the smaller the compensation current Ibr corresponding to the output. The tenth voltage control current source 162 includes resistors R1, R2, and an arrester diode ZD1 'which uses the front-end sampling method to obtain the voltage magnitude of the input power source vbr', and then according to the magnitude of the voltage of the input power source Vbr, corresponding to the output compensation current Ibr To compensate for the total current ILED. In addition, the constant current source 164 is coupled to the voltage control current source 62, the control module 10, the first illumination module 12, and the second illumination module 14, which receives the compensation current Ibr from the voltage control current source 162, and is compensated according to the compensation. The current Ibr is adjusted to the total current ILED flowing through the first lighting module 12 and the second lighting module 14. For example, the larger the compensation current Ibr is, the smaller the total current ILED flowing through the first illumination module 12 and the second illumination module 14 is. On the contrary, the smaller the compensation current Ibr is, the third illumination module flows. 12 is relatively larger than the total current ILED of the second lighting module 14. In summary, the power compensation module 16 obtains the voltage of the input power source Vbr and follows the voltage of the input power source Vbr to compensate for the total current ILED flowing through the first and second light-emitting modules 14 and 14 Allow the total current ILED to remain within the rated range. Thus, the lighting device 3 of the present embodiment can utilize the power compensation module 16 as a compensation for the total current ILED, so that the total current is not affected by the unstable input power source Vbr, thereby allowing the input power to be maintained at 14/26 M410164. In the range, the problem that the first light-emitting module 12 and the second light-emitting module 14 are damaged by the unstable alternating current Ac and the light decay is solved.
復參考圖6。定電流源164包括電晶體Q5、Q6、電 阻R4、R5、R6。電阻R4耦接至輸入電源Vbr，係提供 笔曰日肽Q5偏壓電流及電晶體Q6的驅動電流，電晶體 Q6的党控端B6受控於電晶體q5。此時流過電阻R6的 電流ID約為總電流ILED，電流ID在電阻R6上建立的 電壓VR6，以讓電晶體q5工作在作用區（&比〜regi〇n) 。如此，連接於電晶體（^6之受控端36的電晶體Q5即 可以用來調整流過電晶體Q6的總電流ILED，使其維持 在一固定的電流值。 另外’電壓控制電流源162所輪出的補償電流此 經由定電流源i64的電阻R5流至電阻R6，當電阻R5 遠大於電阻R6時，電壓VR6會形士仏 乂成ibrxRS的偏移電壓Refer to Figure 6 for details. Constant current source 164 includes transistors Q5, Q6, resistors R4, R5, R6. The resistor R4 is coupled to the input power source Vbr to provide a bias current of the pentatom peptide Q5 and a driving current of the transistor Q6. The party terminal B6 of the transistor Q6 is controlled by the transistor q5. At this time, the current ID flowing through the resistor R6 is about the total current ILED, and the current ID is the voltage VR6 established on the resistor R6 to allow the transistor q5 to operate in the active region (&~regi〇n). Thus, the transistor Q5 connected to the controlled terminal 36 of the transistor (6) can be used to adjust the total current ILED flowing through the transistor Q6 to maintain it at a fixed current value. In addition, the 'voltage controlled current source 162 The compensation current that is turned out flows to the resistor R6 via the resistor R5 of the constant current source i64. When the resistor R5 is much larger than the resistor R6, the voltage VR6 is shaped like an offset voltage of the ibrxRS.
V〜e)，依據戴維靈定理可求得腺6=鳩_此 im，電壓控制電流源162輪出的補償電流此 =作為總電流謂的補償’使總電流 入功率能_持在駭範_，b ’料躲 與第二發光模組Η受到不穩定的交；^一發光模级12 成損壞與光衰的問題。 AC之影響所造 復參考圖6。電壓控制電流源 -發光模組12的輸出端Τ12與第二絡也可以輕接於第 二發光模組14之間的一電壓差， 端丁22,進而根據輸入電源Vbr*第一光模組14的輸出 ^ . 办拓/、 發光模組12及第 以對應輸出補償電 15/26 M410164 流Ibr。前述的電壓控制電流源162包括電阻R3與稽納 二極體ZD2，其係利用後端取樣方式取得電壓差△ V， 再根據電壓差Δν對應輸出補償電流Ibr，以作為總電流 ILED的補償。 舉例來說，在第一發光模組12與第二發光模組14 形成並聯連結狀態下，電壓差Δν大約等於輸入電源 Vbr減去第一發光模組12的導通順向偏壓（forward biased)Vl或減去第二發光模組14的導通順向偏壓 (forward biased) V2，即 Δν=νΐ)Γ-νΐ 或 Δν=Vbr-V2。在 第一發光模組12與第二發光模組14形成串聯連結狀態 下，電壓差Δν大約等於輸入電源Vbr減去第一發光模 組12與第二發光模組14的導通順向偏壓（forward biased)，即△ V=Vbr-(Vl+V2)。 復參考圖6。前述的電壓控制電流源162亦可以包 括電阻R1〜R3、稽納二極體ZD1〜ZD2，其係同時結合 前端與後端取樣方式，對應輸出補償電流Ibr，以作為總 電流ILED的補償。 配合圖5，請參考圖8。圖8為本創作第四實施例的 電路示意圖。本實施例的照明裝置4與圖5的照明裝置2 之間主要的差別在於，本實施例的照明裝置4更包括一功 率補償模組46。功率補償模組46耦接於整流單元11、 控制模組20、第一發光模組12及第二發光模組14，其 係根據輸入電源Vbr的電壓大小，對應調整流過第一發 光模組12與第二發光模組14的總電流ILED。前述中 ，功率補償模組46的實施與圖6所示的功率補償模組 16相同，在此不再贅述。 16/26 〃參考圖9。圖9為本創作第五實施例的電路示意圖 …、月裝置5包括一控制模組5〇與多個發光模組52， 夕個I光模組52包括四個發光模組52八、52β、52匸、 52D，然不以此為限。控制模組5〇耦接整流單元μ與 多個發光模組52,其中控制模组5〇從整流單元51接收 輸入電源Vbr。 ^控制模組50中的控制單元501依據交流電AC整流 後的輸入電源Vbr，對應控制開關（s—H1〜S_H3、 S_L1〜S__L3、S_M1〜S—M3)，以改變多個發光模組52與 整流單元51之間連結的關係，進而降低每電壓周期流 過發光模組52的電流峰值，達到照明裝置5具有高發 光效率及使用壽命長的效果。 參考圖9與圖10。圖10為圖9的電路波形示意圖 。在輸入電源Vbr小於一苐一設定值Vrefl的期間Τι， 控制模組50内部的開關S_H1〜S—H3、S L1〜S L3受控 導通’開關S_M1〜S_M3受控截止’進而讓發光模組52a 、52B、52C、52D共同並聯電性連結於整流單元5}以 形成第一連結狀態。此時’分別流過發光模組52A、52B 、52C、52D的電流111如圖1〇所示。V~e), according to Daviding's theorem can be obtained gland 6 = 鸠 _ this im, voltage control current source 162 round of compensation current this = as the total current said compensation 'to make the total current into the power _ _ _ , b 'Material hiding and the second lighting module Η are subject to unstable intersection; ^ A luminosity level 12 becomes a problem of damage and light decay. Refer to Figure 6 for the effects of AC. The output voltage 电流12 and the second network of the voltage control current source-light-emitting module 12 can also be lightly connected to a voltage difference between the second light-emitting module 14, the terminal 22, and then according to the input power source Vbr* the first light module The output of 14 ^. The extension /, the illumination module 12 and the corresponding output compensation power 15 / 26 M410164 flow Ibr. The aforementioned voltage control current source 162 includes a resistor R3 and a synchronizing diode ZD2, which uses a back-end sampling method to obtain a voltage difference ΔV, and then outputs a compensation current Ibr according to a voltage difference Δν to compensate for the total current ILED. For example, in a state in which the first light emitting module 12 and the second light emitting module 14 are connected in parallel, the voltage difference Δν is approximately equal to the input power source Vbr minus the forward biased bias of the first light emitting module 12. Vl is subtracted from the forward biased V2 of the second light-emitting module 14, that is, Δν=νΐ)Γ-νΐ or Δν=Vbr-V2. In a state in which the first light emitting module 12 and the second light emitting module 14 are connected in series, the voltage difference Δν is approximately equal to the input power source Vbr minus the conduction forward bias of the first light emitting module 12 and the second light emitting module 14 ( Forward biased), ie Δ V = Vbr - (Vl + V2). Refer to Figure 6 for details. The aforementioned voltage control current source 162 may also include resistors R1 R R3 and sina diodes ZD1 ZZD2, which combine the front end and back end sampling modes, and output the compensation current Ibr as compensation for the total current ILED. Referring to Figure 5, please refer to Figure 8. Fig. 8 is a circuit diagram showing the fourth embodiment of the creation. The main difference between the illuminating device 4 of the present embodiment and the illuminating device 2 of Fig. 5 is that the illuminating device 4 of the present embodiment further includes a power compensation module 46. The power compensation module 46 is coupled to the rectifying unit 11, the control module 20, the first lighting module 12, and the second lighting module 14, and is correspondingly adjusted to flow through the first lighting module according to the voltage of the input power source Vbr. 12 and the total current ILED of the second lighting module 14. In the foregoing, the implementation of the power compensation module 46 is the same as that of the power compensation module 16 shown in FIG. 6, and details are not described herein again. 16/26 〃 Refer to Figure 9. FIG. 9 is a schematic diagram of a circuit according to a fifth embodiment of the present invention. The monthly device 5 includes a control module 5 and a plurality of illumination modules 52. The illumination module 52 includes four illumination modules 52, 52β, 52匸, 52D, but not limited to this. The control module 5 is coupled to the rectifying unit μ and the plurality of lighting modules 52. The control module 5 receives the input power Vbr from the rectifying unit 51. The control unit 501 in the control module 50 is configured to change the plurality of light-emitting modules 52 according to the AC power-rectified input power source Vbr corresponding to the control switches (s_H1 to S_H3, S_L1 to S__L3, S_M1 to S-M3). The relationship between the rectifying units 51 is further reduced, and the current peak flowing through the light-emitting module 52 per voltage cycle is reduced, so that the lighting device 5 has a high luminous efficiency and a long service life. Reference is made to Figures 9 and 10. Figure 10 is a schematic diagram of the circuit waveform of Figure 9. During the period when the input power source Vbr is less than a set value Vref1, the switches S_H1 to S-H3 and S L1 to S L3 inside the control module 50 are controlled to be turned on, and the switches S_M1 to S_M3 are controlled to be turned off to allow the light-emitting module to be turned on. 52a, 52B, 52C, and 52D are electrically connected in parallel to the rectifying unit 5} to form a first connected state. At this time, the current 111 flowing through the light-emitting modules 52A, 52B, 52C, and 52D, respectively, is as shown in FIG.
接著’在輸入電源Vbr大於第一設定值yrefi且小 於一第二設定值Vref2的期間T2，控制模組50内部的 開關 S_H1、S_H3、S—L1、S一L3、S-M2 受控截止，開 關S_H2、S—L2、S—M1、S_M3受控導通，進而讓發光 模組52A、52B串聯電性連結於整流單元51以及發光模 組52C、52D串聯電性連結於整流單元51以形成第二連 結狀態。此時，分別流過發光模組52A、52與52C、52D 17/26 M410164 的電流112如圖10所示。 然後，在輸入電源Vbr大於第二設定值Vref2的期 間T3，控制模組50内部的開關S_H1、S_H3、S_L1、 S__L3、S_H2、S_L2受控截止，開關S_M1〜S_M3受控 導通，進而讓發光模組52A、52B、52C、52D彼此串聯 電性連結於整流單元51以形成第三連結狀態。此時， 流過發光模組52A、52B、52C、52D的電流113如圖10 所示。 復參考圖10與圖9。輸入電源Vbr為正弦波的交流 電AC整流後的電源，其電壓波形係以90度為對稱增減 ，因此，控制模組50在期間T4、T5、T6對内部開關 S_H1〜S_H3、S_L1〜S_L3 、S_M1〜S_M3的動作控制係 對應且相同於期間T3、T2、T1，如圖10所示。 綜上所述，控制模組50會追隨輸入電源Vbr的電 壓大小’讓發光模組52A、52B、52C、52D與整流單元 51之間的連結關係依序循環動作在第一連結狀態、第二 連結狀態、第三連結狀態、第二連結狀態、第一連結狀 態之間。如此’在固定平均電流的驅動方式下，控制模 組50的控制方式，將可以降低每電壓周期流過發光模 組52A、52B、52C、52D的電流峰值，進而提高照明裝 置5整體的發光效率及使用壽命。 復參考圖9。照明裝置5更包括一功率補償模組56 。功率補償模組56耦接於整流單元51、控制模組5〇及 多個發光模組52，其係根據輸入電源vbr的電壓大小， 對應調整流過多個發光模組52的總電流ILED。前述中 ，功率補償模組56的實施與圖6所示的功率補償模組 18/26 M410164 16相同，在此不再贅述。 本創作第五實施例的控制模組50係依據圖10所揭 露的開關控制時序，使用對稱方式控制發光模組52A、 52B、52C、52D與整流單元51之間的連結關係，此種 方式並不是唯一的時序控制方式，凡是可以依據輸入電 源Vbr而控制發光模組之間的連結關係的電路都為本創 作主張權利的範圍。 以上所述僅為本創作之實施例，其並非用以侷限本 創作之專利範圍。 【圖式簡單說明】 圖1為傳統的發光二極體(LED)驅動電路； 圖2為本創作實施例的功能架構示意圖； 圖3為本創作第一實施例的電路示意圖； 圖4為圖3的電路波形示意圖； 圖5為本創作第二實施例的電路示意圖； 圖6為本創作第三實施例的電路示意圖； 圖7為圖6的電路波形示意圖； 圖8為本創作第四實施例的電路示意圖； 圖9為本創作第五實施例的電路示意圖；及 圖10為圖9的電路波形示意圖。 【主要元件符號說明】 習知： 父流電AC 整流電路BR 發光二極體燈陣列LA 限流電阻R1 19/26 M410164 本創作： 照明裝置1、2、3、4、5 控制模組10、20、50 整流單元11、51 第一發光模組12 第二發光模組14 交流電AC 接地端Gnd 輸入電源Vbr 開關單元102 控制單元104、501 二極體D1 第一電晶體Q1 第二電晶體Q2 分壓電路1042 驅動電路1044 電阻 R12、R13 限流電阻Rl、R2、R3 電晶體 Q3、Q4、Q5、Q6 輸入電壓比例值VR 設定值Vth 參考值Vref 第一參考值Vrefl 第二參考值Vref2 開關單元202 控制單元204 20/26 M410164 分壓電路2042 驅動電路2044 功率補償模組】6、46、56 電壓控制電流源162、462 定電流源164、464 補償電流Ibr 總電流ILED 流過電阻R6的電流ID 電壓 VR6、VR12Then, during a period T2 when the input power source Vbr is greater than the first set value yrefi and less than a second set value Vref2, the switches S_H1, S_H3, S_L1, S-L3, and S-M2 inside the control module 50 are controlled to be turned off. The switches S_H2, S_L2, S_M1, and S_M3 are controlled to be turned on, and the light-emitting modules 52A and 52B are electrically connected in series to the rectifying unit 51 and the light-emitting modules 52C and 52D are electrically connected in series to the rectifying unit 51 to form a first Two link status. At this time, the current 112 flowing through the light-emitting modules 52A, 52 and 52C, 52D 17/26 M410164, respectively, is as shown in FIG. Then, during a period T3 when the input power source Vbr is greater than the second set value Vref2, the switches S_H1, S_H3, S_L1, S__L3, S_H2, and S_L2 inside the control module 50 are controlled to be turned off, and the switches S_M1 to S_M3 are controlled to be turned on, thereby allowing the light emitting mode to be turned on. The groups 52A, 52B, 52C, and 52D are electrically connected in series to the rectifying unit 51 in series to form a third connected state. At this time, the current 113 flowing through the light-emitting modules 52A, 52B, 52C, and 52D is as shown in FIG. Referring to Figures 10 and 9, The input power source Vbr is a sinusoidal AC AC rectified power supply, and its voltage waveform is symmetrically increased or decreased by 90 degrees. Therefore, the control module 50 pairs the internal switches S_H1 to S_H3, S_L1 to S_L3 during the period T4, T5, and T6. The operation control of S_M1 to S_M3 corresponds to and is the same as the periods T3, T2, and T1, as shown in FIG. In summary, the control module 50 follows the voltage magnitude of the input power source Vbr. The switching relationship between the light-emitting modules 52A, 52B, 52C, and 52D and the rectifying unit 51 is sequentially cycled in the first connected state and the second. Between the connected state, the third connected state, the second connected state, and the first connected state. Thus, in the driving mode of the fixed average current, the control mode of the control module 50 can reduce the current peaks flowing through the light-emitting modules 52A, 52B, 52C, and 52D per voltage cycle, thereby improving the overall luminous efficiency of the illumination device 5. And service life. Refer to Figure 9 for details. The lighting device 5 further includes a power compensation module 56. The power compensation module 56 is coupled to the rectifying unit 51, the control module 5, and the plurality of lighting modules 52. The total current ILED flowing through the plurality of lighting modules 52 is adjusted according to the voltage of the input power source vbr. In the foregoing, the implementation of the power compensation module 56 is the same as that of the power compensation module 18/26 M410164 16 shown in FIG. 6, and details are not described herein again. The control module 50 of the fifth embodiment of the present invention controls the connection relationship between the light-emitting modules 52A, 52B, 52C, and 52D and the rectifying unit 51 in a symmetric manner according to the switch control timing disclosed in FIG. It is not the only timing control method. Any circuit that can control the connection relationship between the light-emitting modules according to the input power source Vbr is the scope of the claimed claim. The above description is only an embodiment of the present invention, and is not intended to limit the scope of the patent of the present invention. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a schematic diagram of a functional structure of a conventional light-emitting diode (LED); FIG. 2 is a schematic diagram of a functional architecture of a first embodiment of the present invention; FIG. 3 is a circuit diagram of a second embodiment of the present invention; FIG. 6 is a schematic circuit diagram of a third embodiment of the present invention; FIG. 7 is a schematic diagram of a circuit diagram of FIG. FIG. 9 is a schematic circuit diagram of a fifth embodiment of the present invention; and FIG. 10 is a schematic diagram of a circuit waveform of FIG. [Main component symbol description] Convention: Parent current AC rectification circuit BR LED array lamp LA current limiting resistor R1 19/26 M410164 This creation: Lighting device 1, 2, 3, 4, 5 control module 10, 20, 50 rectification unit 11, 51 first illumination module 12 second illumination module 14 AC AC ground Gnd input power Vbr switch unit 102 control unit 104, 501 diode D1 first transistor Q1 second transistor Q2 Voltage dividing circuit 1042 Driving circuit 1044 Resistor R12, R13 Current limiting resistor Rl, R2, R3 Transistor Q3, Q4, Q5, Q6 Input voltage proportional value VR Set value Vth Reference value Vref First reference value Vrefl Second reference value Vref2 Switch unit 202 control unit 204 20/26 M410164 voltage dividing circuit 2042 driving circuit 2044 power compensation module] 6, 46, 56 voltage control current source 162, 462 constant current source 164, 464 compensation current Ibr total current ILED flowing through the resistor R6 current ID voltage VR6, VR12
發光模組 52、52A、52B、52C、52D 21/26Lighting module 52, 52A, 52B, 52C, 52D 21/26