M376921 . 五、新型說明： ^ 【新型所屬之技術領域】 本創作是有關於一種偶極天線，特別是有關於一種可 抑制雜訊之串聯偶極天線。 【先前技術】 現今各式電子產品已普遍設置可收發無線訊號之天線 來提昇電子產品的無線接收資訊及行動通訊能力，天線為 φ 搭配日益小型化、薄形化的電子設備發揮無線通訊的傳輸 特性，因此業者無不研發更具小型化的天線來滿足電子設 備的需求，而在習知的天線設計上，為了要增加通訊頻段 和頻寬，一般是以增加天線的數目或以其他形式的寬頻天 線來涵蓋操作頻段，如此會產生不必要的頻段雜訊，並影 響天線收發訊號的品質，為解決這個問題，習用寬頻天線 的作法是加入濾波器來抑制高頻雜訊，此作法會增加成本 且無法使天線達到小型化及輕量化的結構需求。 【新型内容】 有鑑於上述先前技術所產生的問題，本創作之主要目 的為提供一種串聯偶極天線，其具有可抑制不必要的頻段 雜訊，進而構成訊號傳輸用之高增益串聯偶極天線者。 根據本創作之目的，提出一種串聯偶極天線，此天線 的簡要如下： 該天線包含：一訊號線、一接地導體、第一輻射導體 、一繞線、第二輻射導體。該繞線介於第一、二輻射導體 M376921 之間，該第一輻射導體介於接地導體與繞線之間，以使第 - 一輻射導體分別連接訊號線之導體與繞線，第二輻射導體 '一端連接繞線，寄生導體位於第一輻射導體與接地導體之 間，以使寄生導體之一端與接地導體連接，藉由改變寄生 導體的位置或改變寄生導體的長度、寬度可抑制不必要的 頻段雜訊，進而構成訊號傳輸用之高增益串聯偶極天線者 〇 為讓本創作之上述目的、特徵和優點能更明顯易僅， ^ 下文特舉一較佳實施例，並配合所附圖式，作詳細說明如 下： 【實施方式】 請配合參閱第1 、2圖所示，其繪示依照本創作一較 佳實施例所提供的一種串聯偶極天線示意圖。該天線1包 含：訊號線11、接地導體12、第一輻射導體13、繞線14、 第二輻射導體15。該繞線14介於第一、二輻射導體13、15 • 之間，該第一輻射導體13介於接地導體12與繞線14之間， 以使第一輻射導體13二端分別連接訊號線11之導體111與 繞線14，’第二輻射導體15 —端連接繞線14，該訊號線11為 一同軸傳輸線，包含有導體111 、絕緣體112 、外導體1 13，接地導體12内部具有貫穿二端之穿孔121 ，訊號線11 由接地導體12 —端穿入至穿孔121内部，以使訊號線11之 外導體113與接地導體12另一端電性連接，另於第一輻射 導體13與接地導體12之間設置寄生導體16，其内部為中空 以及二端為通孔，以使寄生導體16之一端與接地導體12連 4 M376921 . 接，第一輻射導體13連接訊號線11之導體111可 - 導體16之中空内部，又該訊號線11之外導體113 ' 體12電性連接處至第一輻射導體13之整體長度以 導體12的長度皆近似於第一共振頻率的四分之一 實施例的第一共振頻率為2.4〜2.5GHz )，第二 15的長度近似於第一共振頻率的二分之一波長， 16的長度近似於第三共振頻率的四分之一波長（ 的第三共振頻率為4. 9〜5. 8GHz )，進而構成訊 φ 之高增益串聯偶極天線者。 請配合參閒第3 、4圖所示，其繪示依照本 較佳實施例所提供的一種串聯偶極天線示意圖。 包含：基板10，以及分別設置於基板10第一表面 號線1〗、接地導體12、第一輻射導體13、繞線14 射導體15。該繞線14介於第一、二輻射導體13、 該第一輻射導體13介於接地導體12與繞線14之間 一輻射導體13二端分別連接訊號線11之導體111 • 之第一接點141 ，第二輻射導體15 —端連接繞線 接點142 ，該訊號線11為一同軸傳輸線，包含有 、絕緣體112 '外導體113 ，訊號線11之外導體 地導體12電性連接，另於第一輻射導體13二側各 生導體曱161及寄生導體乙162 ，以使寄生導體 寄生導體乙162之一端與接地導體12連接，訊號 導體113與接地導體12電性連接處至第一輻射導 體長度以及該接地面12的長.度皆近似於第一共振 分之一波長（本實施例的第一共振頻率為2. 4〜 位於寄生 與接地導 及該接地 波長（本 輻射導體 寄生導體 本實施例 號傳輸用 創作第二 該天線1 101之訊 、第二輻 15之間， ，以使第 與繞線14 14之第二 導體111 113與接 設置一寄 甲161及 線11之外 體13之整 頻率的四 2.5GHz ) M376921 ，第二輻射導體15的長度近似於第一共振頻率的二 - 波長，寄生導體曱161和寄生導體乙162的長度分 ' 似於第三共振頻率的四分之一波長（本實施例的第 頻率為4. 9〜5. 8GHz )，進而構成訊號傳輸用之高 聯偶極天線者。 請參閱第5圖所示，本創作第三較佳實施例所 一種串聯偶極天線示意圖，其中該基板10 之第二 02設有寄生導體丙163 ，其二端分別與寄生導體曱 φ 寄生導體乙162之一端相對。 功效說明： 本創作功效增進之事實如下： 本創作天線藉由繞線造成電流相位延遲，使流 輻射導體及接地導體之電流與第二輻射導體上之電 位，以形成串聯陣列天線，增加天線的增益。寄生 寄生導體曱和寄生導體乙的長度分別都近似於第三 • 率的四分之一波長，藉由移動寄生導體、寄生導體 生導體乙連接於接地導體的位置或改變寄生導體、 體甲、乙的長度、寬度，可抑制不必要的頻段雜訊 :本實施例可抑制第三共振頻率為4. 9〜5. 8GHz的 較佳實施方式之一）。實際使用網路分析儀量測反 結果如第6圖所示，整體具有良好的收發訊號之電 ，以符合小型化及輕量化的天線結構需求者。 本創作天線藉由基板之第二表面設有寄生導體 寄生導體丙，可抑制不必要的頻段雜訊。實際使用 分之一 別都近 三共振 增益串 提供的 表面 1 161及 經第一 流同相 導體、 共振頻 曱和寄 寄生導 (例如 言皆振為 射損耗 氣特性 丙，該 網路分 6 M376921 析儀量測反射損耗結果如第6圖所示，整體具有良好的收 發訊號之電氣特性，以符合小型化及輕量化的天線結構需 求者。 上述實施例所揭示者係藉以具體說明本創作，且文中 雖透過特定的術語進行說明，當不能以此限定本新型創作 之專利範圍；熟悉此項技術領域之人士當可在瞭解本創作 之精神與原則後對其進行變更與修改而達到等效目的，而 此等變更與修改，皆應涵蓋於如后所述申請專利範圍所界 定之範疇中。 M376921 【圖式簡單說明】 第1圖：係本創作一較佳實施例所提供的串聯偶極天線之 立體示意圖。 第2圖：係本創作一較佳實施例所提供的串聯偶極天線之 剖面示意圖。 第3圖：係本創作第二較佳實施例所提供的串聯偶極天線 之立體示意圖。 第4圖：係本創作第二較佳實施例所提供的串聯偶極天線 之平面示意圖。 第5圖：係本創作第三較佳實施例所.提供的串聯偶極天線 之平面示意圖。 第6圖：係本創作天線實際使用網路分析儀量測反射損耗 示意圖。 【主要元件符號說明】 天線 1 基板 10 第二表面 102 導體 111 外導體 113 第一輻射導體 13 第一接點 141 第二輻射導體 15 寄生導體甲 161 寄生導體丙 163 第一表面 訊號線 絕緣體 接地導體 繞線 弟二接點 寄生導體 寄生導體乙 0 244 2 8M376921 . V. New description: ^ [New technical field] This creation is about a dipole antenna, especially for a series dipole antenna that can suppress noise. [Prior Art] Nowadays, various types of electronic products have been widely equipped with antennas for transmitting and receiving wireless signals to enhance the wireless receiving information and mobile communication capabilities of electronic products. The antenna is used for φ to transmit wireless communication with increasingly smaller and thinner electronic devices. Characteristics, so the industry has developed more compact antennas to meet the needs of electronic devices. In the conventional antenna design, in order to increase the communication frequency band and bandwidth, it is generally to increase the number of antennas or other forms. Broadband antennas cover the operating frequency band, which will generate unnecessary frequency band noise and affect the quality of the antenna transmit and receive signals. To solve this problem, the practice of using a wideband antenna is to add a filter to suppress high frequency noise. This method will increase. The cost does not make the antenna demand for miniaturization and lightweight construction. [New content] In view of the problems caused by the above prior art, the main purpose of the present invention is to provide a series dipole antenna having a high gain series dipole antenna for suppressing unnecessary frequency band noise and for signal transmission. By. According to the purpose of the present invention, a series dipole antenna is proposed. The antenna is as follows: The antenna comprises: a signal line, a ground conductor, a first radiation conductor, a winding, and a second radiation conductor. The winding is between the first and second radiation conductors M376921, and the first radiation conductor is interposed between the ground conductor and the winding, so that the first radiation conductor is respectively connected to the conductor and the winding of the signal line, and the second radiation One end of the conductor is connected to the winding, and the parasitic conductor is located between the first radiation conductor and the ground conductor, so that one end of the parasitic conductor is connected to the ground conductor, and the position of the parasitic conductor can be changed or the length and width of the parasitic conductor can be changed to suppress unnecessary The frequency band noise, which in turn constitutes the high gain series dipole antenna for signal transmission, makes the above objects, features and advantages of the present invention more obvious, and the following is a preferred embodiment and is accompanied by the accompanying The drawings are described in detail as follows: [Embodiment] Referring to Figures 1 and 2, a schematic diagram of a series dipole antenna according to a preferred embodiment of the present invention is shown. The antenna 1 includes a signal line 11, a ground conductor 12, a first radiation conductor 13, a winding 14, and a second radiation conductor 15. The winding 14 is interposed between the first and second radiation conductors 13, 15 . The first radiation conductor 13 is interposed between the ground conductor 12 and the winding 14 so that the two ends of the first radiation conductor 13 are respectively connected to the signal line. The conductor 111 of the 11 is connected to the winding 14 and the second radiating conductor 15 is connected to the winding 14. The signal line 11 is a coaxial transmission line, and includes a conductor 111, an insulator 112, and an outer conductor 13. The grounding conductor 12 has a through-opening inside. The two ends of the through hole 121, the signal line 11 is penetrated into the inner side of the through hole 121 by the grounding conductor 12, so that the outer conductor 113 of the signal line 11 is electrically connected to the other end of the grounding conductor 12, and the first radiation conductor 13 and the grounding. A parasitic conductor 16 is disposed between the conductors 12, and the inside thereof is hollow and the two ends are through holes, so that one end of the parasitic conductor 16 is connected to the ground conductor 12 by 4 M376921. The first radiation conductor 13 is connected to the conductor 111 of the signal line 11 - the hollow interior of the conductor 16, and the outer length of the conductor 113' body 12 electrically connected to the first radiation conductor 13 is such that the length of the conductor 12 is approximately one quarter of the first resonance frequency The first resonant frequency of the example is 2.4 〜5GHz。 The length of the second resonant frequency is approximately one-half of the first resonant frequency, and the third resonant frequency is 4. 9~5 8 GHz ), which in turn constitutes a high gain series dipole antenna of φ φ. Please refer to FIG. 3 and FIG. 4 for a schematic diagram of a series dipole antenna according to the preferred embodiment. The substrate 10 is disposed on the first surface line 1 of the substrate 10, the ground conductor 12, the first radiation conductor 13, and the wire 14 conductor 15. The winding 14 is interposed between the first and second radiating conductors 13, the first radiating conductor 13 is between the grounding conductor 12 and the winding 14, and the first end of the radiating conductor 13 is connected to the conductor 111 of the signal line 11 respectively. Point 141, the second radiation conductor 15 is connected to the winding contact 142. The signal line 11 is a coaxial transmission line, and comprises an insulator 112' outer conductor 113, and the conductor 12 of the signal line 11 is electrically connected to the conductor. The conductors 161 and the parasitic conductors 162 are formed on both sides of the first radiation conductor 13 such that one end of the parasitic conductor parasitic conductor B 162 is connected to the ground conductor 12, and the signal conductor 113 and the ground conductor 12 are electrically connected to the first radiation. The length of the conductor and the length of the ground plane 12 are both approximately one wavelength of the first resonance (the first resonance frequency of the embodiment is 2. 4~ located at the parasitic and ground lead and the ground wavelength (the parasitic conductor of the radiation conductor) In the embodiment, the second antenna 15 101 and the second spoke 15 are created for transmission, so that the second conductor 111 113 of the first winding 14 14 is connected to a mail 161 and the line 11. The whole frequency of the body 13 is four. 5 GHz ) M376921 , the length of the second radiation conductor 15 is approximately two-wavelength of the first resonance frequency, and the lengths of the parasitic conductor 曱 161 and the parasitic conductor B 162 are similar to a quarter wavelength of the third resonance frequency (this embodiment The frequency of the example is 4. 9~5. 8GHz), which constitutes a high-connected dipole antenna for signal transmission. Referring to FIG. 5, a schematic diagram of a series dipole antenna according to the third preferred embodiment of the present invention is shown. The second 02 of the substrate 10 is provided with a parasitic conductor C163, and its two ends are respectively opposite to one end of the parasitic conductor 曱φ parasitic conductor B 162. Efficacy description: The fact that the creation effect is improved is as follows: The line causes a phase delay of the current, so that the current flowing through the radiation conductor and the ground conductor and the potential on the second radiation conductor form a series array antenna, increasing the gain of the antenna. The lengths of the parasitic parasitic conductor 寄生 and the parasitic conductor B are respectively similar to A quarter wavelength of the rate, by moving the parasitic conductor, the parasitic conductor, the conductor B is connected to the ground conductor or changing the length of the parasitic conductor, body armor, and B. , Width, frequency of unnecessary noise can be suppressed: the present embodiment can suppress a resonance frequency of one of the third preferred embodiment of the embodiment 4. 9~5 8GHz). The actual use of the network analyzer measurement results as shown in Figure 6, the overall good signal transmission and reception, in order to meet the needs of miniaturized and lightweight antenna structure. The antenna of the present invention is provided with a parasitic conductor parasitic conductor C on the second surface of the substrate to suppress unnecessary band noise. The actual use is divided into the surface 1 161 provided by the near three resonant gain strings and the first-phase in-phase conductor, the resonant frequency and the parasitic conduction (for example, the oscillating loss is the characteristic of the gas loss, and the network is divided into 6 M376921. The measured reflectance loss results are shown in Fig. 6. The overall electrical characteristics of the transmitted and received signals are good to meet the requirements of miniaturized and lightweight antenna structures. The above embodiments disclose the present invention. Although the text is explained by specific terms, it is not possible to limit the scope of patents of this new creation; those who are familiar with the technical field can change and modify the spirit and principles of this creation to achieve the equivalent purpose. And such changes and modifications shall be included in the scope defined by the scope of the patent application as described later. M376921 [Simplified description of the drawings] Figure 1: Series dipole provided by a preferred embodiment of the present invention A perspective view of an antenna. Fig. 2 is a schematic cross-sectional view of a series dipole antenna provided by a preferred embodiment of the present invention. A perspective view of a series dipole antenna provided by the second preferred embodiment. Fig. 4 is a plan view showing a series dipole antenna provided by the second preferred embodiment of the present invention. The schematic diagram of the series dipole antenna provided by the third preferred embodiment. Fig. 6 is a schematic diagram of the actual use of the network analyzer to measure the reflection loss. [Main component symbol description] Antenna 1 Substrate 10 Second surface 102 conductor 111 outer conductor 113 first radiation conductor 13 first contact 141 second radiation conductor 15 parasitic conductor a 161 parasitic conductor C 163 first surface signal line insulator ground conductor winding two contact parasitic conductor parasitic conductor B 0 244 2 8