TWM312119U - Exchange-type power supply with feedback-control on the primary side - Google Patents
Exchange-type power supply with feedback-control on the primary side Download PDFInfo
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- TWM312119U TWM312119U TW95219460U TW95219460U TWM312119U TW M312119 U TWM312119 U TW M312119U TW 95219460 U TW95219460 U TW 95219460U TW 95219460 U TW95219460 U TW 95219460U TW M312119 U TWM312119 U TW M312119U
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M312119 八、新型說明: 【新型所屬之技術領域】 二:作係關於-種-次側回授控制 ,尤指輸出達到電流限制時,輪出 可控制維料變,錢顺出 =出電〜仍 【先前技術】 交換式電源供應器在市;l a 穩壓電源供應器’岐換式遍被❹並已取代線性 度調整控制器控制功率電:曰==為:必須仰賴-脈波寬 波寬度調整控制器依據 生的回授訊號調變脈波寬度調整二二或輸:電流產 以產生適當的導通時間與;: 應器利用,回授方式無法達到丄 變率要求’所以大部份交換式電源授^^ =接由二:欠側取得,需經由光耦合器傳遞 號至一次侧端以控制脈波 彳丨口杈讯 號。因此,光耦合器、回授二二;二的輸出脈波訊 器等回授、限流元件的使:二:的^電阻與運算放大 電為:::ΓΓ授控制的交換式電源供應器 源-供應電首先電路致動由直流輪入電 兒/瓜/,丨L、、工啟動電阻R2對 電⑽到達脈波寬度調整器υ 充電 度調整㈣開始輸出脈波控制功率電晶體二 M312119 、晶體Q1導通時,電流由直流輸入電源VIN供應電流流經 變壓器T1之-次側主線圈、電晶體Q1相到輸入電壓 VIN的負端,二次側因為二極體D3與輸出繞組極性相反所 以無法從-次侧傳遞能量到輸出端,此時能量暫時儲存於 變壓裔T1中,當一次侧電流偵測電阻R6的電壓達到參考 電壓值時,功率電晶體QU成截止,此時二次侧因為二 極體D3與輸出繞組極性變為正向,所以將變壓器丁1的儲 φ 存此1傳遞到輸出端V0,輸出電容C4經過多次週期的充 電崎輸出穩壓點。另外一方面,一次側輔助繞組產生之 電壓經電阻R1和二極體D丨供應電流到電源電壓V c C,提 供脈波寬度調整㈣ϋ m❺電源,辅助繞㈣—路徑則 ”阻R1和二極體D2與電容C6整流後成一直流電壓, 再經電阻R3、R4分壓接至脈波寬度調整器、U1的電壓回授 輸入接腳VFB,電容C6的電壓將會反映輸出端v〇的變 $。由於輸出整流二極體D3壓降隨負載高低變化並且電 • 一 C6的1壓亦隨導通週期大小不同影響,以致從—次側電 奋^6的電屋偵測方式無法完成反映出二次側輸出電壓V〇 =變化,所以輸出電壓調整率較高,無法提供較穩定的電 ^輸而且輸出端通常需接一假負載電阻R8,使輕載時 =出兒壓不致漂移過高準位,因為需接-假負載電阻R8 , ,所以無法達到GREEN MODE之無載要求下輸入功 、^低於G.3W規定,同時此方式並無提供輸纽流電路, 出電流會隨輪出電壓下降而上昇。而電路保護需依 J偵測電阻R6回授訊號限制輸出功率,待脈波 7 M312119 寬度調整器m的電源電應vcc低於最低卫作電麼 脈波寬度調整控制器m’等糊再 - 重新啟動電壓準位時方再次輸出,整缝 == 率於此時方能有效降低。 u輸入功 電路=為回授控制的交換式電_ / ’❼考弟二圖’輸出端vo、缓電阻R8、R9 ^壓後輸人到回授穩壓器U3的輸人端,回_· u3輪 “控制光耦合器U2二次侧的發光二極體電流,再轉換 為一次側電流訊號控制脈波寬度調整器的♦壓回俨_ 入接腳WB的電壓。在狀的輸出負載下脈^度調= 制盗U1的電壓回授輸入接腳VFB的電壓將固定不變 出負載變動時錢回授輸人接腳VFB的電壓將隨之調整: 維持穩定的電壓輸出。-次側辅助繞組也因為電壓超ς泰 源電壓取開始向電容C2充電並供應脈波寬度調整^ 器m電源所需的電壓。此外,第二圖中二二欠側利用^阻 以、R6、R7、電容C4與電晶體Q12組成輪出限流電路, 當電阻R6的電壓超過電晶體q12之基極_射極接面電壓時 限流開始動作。電晶體Q12集極控制光搞合器二次側二: 光二極體電流,使得一次側脈波寬度調整控制器υ〗的^ 波波寬受到限制,此輸出限流電路因基極_射極接面電壓易 隨溫度變化,所以限颇作的精確衫高為其缺點私較適 用於低價之充電器電路。 第三圖為習知的二次側回授控制的交換式電源供應哭 另-電路方塊圖,請參考第三圖,其精確歧高適用^ M312119 大功率及較大輸出電流的交換電源供絲,係湘運算放 大器U4 A、U4B與回授穩壓器U3、光轉合器仍作為電壓 回授及輸出限流電路。其中,回授穩壓器U3在此為-參 考電麈,生裝置,其提供穩” 2 5V參考電壓給電壓回授 控制運算放MIKA與輸$限流㈣運算放大器㈣,電 ㈣算放大H U4A與輸出限流控觸算放大器 側的2出端各接一二極體D3、D4後接光輕合器U2二次 出脈波宽度達到穩壓及限流的:皮:=U1的輸 採用但零件多、成本高為其缺點。、緣路精確度高常被 廊哭口 ^如何創作出—種—:欠側回授控制交換式電評 應-輸出達到電流限制 、式逼斜、 將 流仍可控制維持不變,而達到輪出降但輸出電 是本創作所欲積極探討之處。 呆4目的者, 【新型内容】 有趫於上述習知之缺憾,創 逐竭其心智悉心研究克服,以 ^:未療於完肩 錢’运而研發出一種一次 二=期利用取樣與保留控制電路取;二換式電源伤 非連續镇式工作時的諧波電壓之轉二:側輔助繞麵 制’產生料漏雙重功t '线作為回拍 與輸出負栽範圍内具有穩定的電二出,的輪入電 輪出電壓下降但輸出電流仍可控制維持=到电 ^312119 達到輸出過電流保護的目的。 之:f"目的在提供-種-次側回授控制交換式 电源仏應裔,/、精著取樣與保留控制電路取得一次側辅助 繞組在非連續模式工作時的諧波電屋之轉角電壓值作為回 授控制,在輸出達到電流限制時,輪出電壓下降但輸出電 流仍可控制維持不變,而達到輪出過電流保護的目的。 时=作之目的係提供—次側回授控制交換式電源供應 祕式變壓器,其具有—初極繞組、-輔助 :组5=繞=_極繞組連接-電源;-功率電晶 ㈣二^ = ϋ ’ 一―次侧回授控制脈波寬度調整 取樣及保留控制電路,其連接該辅助繞 广决差放大盗’其連接該取樣及保留控制電路;一分 ^器二其連接該取樣及保留控制電路;—乘法器,其連接 ,;弟—比較器,其連接該誤差放大器及該功率 „-弟二比較器’其連接該第一比較器及該乘法器; 2率限制補償電路,其連接該乘法器;一控制開關’其 =接該電源及該功率_補償電路;-輸出驅動器,其連 ,功f電晶體;—正反器,其連接該輸出驅動器,·-振 /產,器,其連接該正反器;—前緣消除電路,其連接該 ^ 〇R閘,其連接該第一比較器、該第二比較器 。^緣4除電路;其中,當該電游的電塵達到該一次側 :授控制脈波寬度調整控制器的啟動電壓時,一低壓鎖止 二路UVL0控制該控制開關導通,該功率限制補償電路產生 率F f]補仏電壓,該功率限制補償電壓傳至該乘法器 M312119 輸入端;該振盪產生器彥生一導通訊號傳至該正反器之s 輸入端,使該正反器之Q輸出端由低準位電壓轉為高準位 電壓,該輸出驅動器導通該功率電晶體;該辅助繞組之電 壓回授於該取樣與保留控制電路而產生一電壓值,該電壓 值與一第一參考電壓經該誤差放大器輸出一誤差放大值電 壓,該誤差放大值電壓經複數電阻分壓產生一控制電屬, 該控制電壓傳至該第一比較器之反向輪入端;該電壓值另 一路徑經該分壓器降壓後,利用乘法器與功率限制補償電 壓產生相乘之值再加上一第二參考電壓產生一限流參考電 壓,該限流參考電壓傳至該第一比較器之另一反向輸入 端;該功率電晶體之一源極電壓傳至該第一比較器之非反 向輸入端及該第二比較器之非反向輸人端;當該源極電壓 大於該限流參考電壓或該控制電壓時產生一截止訊號,該 截止訊號㈣QR _至該n肖除電路後產生—重置訊M312119 VIII. New description: [New technical field] Second: The system is related to the -sub-secondary feedback control, especially when the output reaches the current limit, the wheel can control the material change, and the money goes out = power out ~ Still [Prior Art] Switching power supply in the market; la regulated power supply '岐 式 遍 ❹ ❹ has replaced the linearity adjustment controller to control power: 曰 == is: must rely on - pulse wide The width adjustment controller adjusts the pulse width according to the raw feedback signal to adjust the two or two: current production to generate the appropriate conduction time and;; the device uses, the feedback method can not reach the enthalpy rate requirement 'so most The switching power supply is ^^ = connected to the second side: the underside is obtained, and the number is transmitted to the primary side via the optical coupler to control the pulse wave. Therefore, the optocoupler, the feedback two or two; the output pulse detector of the second, the feedback device, and the current-limiting component: the second: the resistance and the operational amplification are::: the exchange-controlled power supply of the control Source-supply power first circuit actuation by DC wheel input / melon /, 丨 L,, work start resistance R2 power (10) to pulse width adjuster 充电 charge degree adjustment (four) start output pulse control power transistor two M312119, When the crystal Q1 is turned on, the current is supplied from the DC input power supply VIN through the secondary side of the transformer T1, the secondary side of the transistor Q1 to the negative end of the input voltage VIN, and the secondary side because the polarity of the diode D3 and the output winding are opposite. The energy cannot be transferred from the secondary side to the output end. At this time, the energy is temporarily stored in the transformer T1. When the voltage of the primary current detecting resistor R6 reaches the reference voltage value, the power transistor QU is turned off. Because the polarity of the diode D3 and the output winding becomes positive, the storage φ of the transformer D1 is transferred to the output terminal V0, and the output capacitor C4 passes through the charging and output regulation point of the cycle. On the other hand, the voltage generated by the primary side auxiliary winding supplies current to the power supply voltage V c C via the resistor R1 and the diode D , to provide pulse width adjustment (4) ϋ m ❺ power supply, auxiliary winding (four) - path then "resistance R1 and diode The body D2 and the capacitor C6 are rectified into a DC voltage, and then connected to the pulse width adjuster and the voltage feedback input pin VFB of the U1 via the resistors R3 and R4. The voltage of the capacitor C6 will reflect the change of the output terminal v〇. Since the voltage drop of the output rectifying diode D3 varies with the load level and the electric power, the voltage of one C6 also affects the size of the conduction period, so that the detection method of the electric house from the secondary side can not be completed. The secondary side output voltage V〇=change, so the output voltage regulation rate is high, and it is unable to provide a stable power supply. The output terminal usually needs to be connected with a dummy load resistor R8, so that the light load does not cause excessive drift when the load is light. Level, because the connection-false load resistance R8 is required, the input power of the GREEN MODE is not met, and the power is lower than the G.3W specification. At the same time, the input current circuit is not provided, and the current will follow the wheel. The output voltage rises and rises. The circuit protection needs to limit the output power according to the J detection resistor R6 feedback signal. The power supply of the pulse wave 7 M312119 width adjuster m should be lower than the minimum power supply wave pulse width adjustment controller m', etc. When the voltage level is started, the output is again output, and the whole seam == rate can be effectively reduced at this time. u Input power circuit = exchange type for feedback control _ / '❼考弟二图' Output terminal vo, slow resistance R8, R9 ^ after the pressure is input to the input terminal of the feedback regulator U3, back to the _· u3 wheel "controls the light-emitting diode current of the secondary side of the optical coupler U2, and then converts to the primary side current signal control pulse The voltage width adjuster ♦ presses back 俨 _ the voltage of the input pin WB. Under the output load of the pulse, the voltage of the voltage feedback input pin VFB will be fixed. When the load changes, the voltage of the input pin VFB will be adjusted accordingly: Maintain stable Voltage output. - The secondary side auxiliary winding also starts to charge capacitor C2 and supply the voltage required for the pulse width adjustment m power supply because the voltage exceeds the source voltage. In addition, in the second figure, the second and second undersides use the resistor, R6, R7, capacitor C4 and transistor Q12 to form a turn-off current limiting circuit. When the voltage of the resistor R6 exceeds the base-emitter junction voltage of the transistor q12. The time limit flow starts to move. Transistor Q12 collector control light combiner secondary side two: light diode current, so that the primary side pulse width adjustment controller υ 〗 〖 wave width is limited, this output current limiting circuit due to the base _ emitter The junction voltage is easy to change with temperature, so the accuracy of the accurate shirt height is more suitable for low-cost charger circuits. The third figure is the conventional secondary side feedback control switching power supply crying-circuit block diagram, please refer to the third figure, its accurate high height is applicable ^ M312119 high power and large output current exchange power supply wire , Xiangxiang operational amplifier U4 A, U4B and feedback regulator U3, optical converter is still used as voltage feedback and output current limiting circuit. Among them, the feedback regulator U3 is here - reference power, the device, which provides a stable "25V reference voltage to the voltage feedback control operation amplifier MIKA and the input current limit (four) operational amplifier (four), electricity (four) calculation amplification H U4A and the output current limit control amplifier side of the 2 terminals are connected to a diode D3, D4 and then connected to the light and light combiner U2 secondary pulse width to achieve voltage regulation and current limit: skin: = U1 loss The use of many parts, high cost is its shortcoming. The accuracy of the edge is often riddled by the porch ^ how to create a kind -: under-back feedback control exchange-type electrical evaluation - output reaches current limit, type of oblique The flow can still be controlled to remain unchanged, but to achieve the round-trip and drop-off, but the output power is the place where the author wants to actively explore. For the purpose of staying in the 4th, [new content] It is contrary to the shortcomings of the above-mentioned practices, creating a heart and mind The study overcomes the problem of ^: untreated in the shoulder money' to develop a second two-stage sampling and retention control circuit; two-type power supply injury in the non-continuous town operation when the harmonic voltage turns two: side Auxiliary winding system to produce the material leakage double function t' line as a back shot and output negative load There is a stable electric two-out, the wheel-in electric wheel output voltage drops but the output current can still be controlled to maintain = to the electric ^312119 to achieve the purpose of output over-current protection. The: f " purpose is to provide - type - secondary side feedback control The switching power supply 仏, /, the fine sampling and retention control circuit obtains the corner voltage value of the harmonic electric house when the primary auxiliary winding is operated in the discontinuous mode as the feedback control, and when the output reaches the current limit, the wheel is turned off. The voltage drops but the output current can still be controlled to maintain the same, and the purpose of the overcurrent protection is achieved. The purpose of the current supply is to provide a sub-back feedback control switching power supply secret transformer, which has a primary winding, - Auxiliary: group 5 = winding = _ pole winding connection - power supply; - power electric crystal (four) two ^ = ϋ '1 - secondary side feedback control pulse width adjustment sampling and retention control circuit, which is connected to the auxiliary winding Amplifying the thief's connection to the sampling and retention control circuit; a branching device 2 connected to the sampling and retention control circuit; a multiplier, a connection thereof; a comparator-connector connecting the error amplifier and the power „−弟二 comparator“ is connected to the first comparator and the multiplier; a rate limiting compensation circuit connected to the multiplier; a control switch 'which is connected to the power source and the power_compensation circuit;-output driver a continuous transistor, a flip-flop connected to the output driver, a vibration/production device connected to the flip-flop; a leading edge cancellation circuit connected to the ^R gate The first comparator and the second comparator are connected. The edge 4 divides the circuit; wherein, when the electric dust of the electric wave reaches the primary side: when the control pulse width adjustment controller starts voltage, a low voltage lock two-way UVL0 controls the control switch to be turned on, the power limit compensation The circuit generation rate F f] is a complementary voltage, and the power limitation compensation voltage is transmitted to the input end of the multiplier M312119; the oscillation generator transmits a communication number to the input end of the flip-flop to make the flip-flop The Q output is converted from a low level voltage to a high level voltage, and the output driver turns on the power transistor; the voltage of the auxiliary winding is fed back to the sampling and retention control circuit to generate a voltage value, and the voltage value is a reference voltage is outputted by the error amplifier to an error amplification value voltage, and the error amplification value voltage is divided by a plurality of resistors to generate a control electric quantity, and the control voltage is transmitted to a reverse wheel end of the first comparator; the voltage value is After the other path is stepped down by the voltage divider, a multiplicative value is multiplied by the power limiting compensation voltage and a second reference voltage is generated to generate a current limiting reference voltage. The current limiting reference voltage is transmitted. To another inverting input of the first comparator; a source voltage of the power transistor is transmitted to a non-inverting input of the first comparator and a non-inverting input of the second comparator; When the source voltage is greater than the current limiting reference voltage or the control voltage, a cutoff signal is generated, and the cutoff signal (4) QR _ is generated after the circuit is removed - a reset signal
號至該正反器之&輸入端,該重置訊號使該正反鈐 出端由高準位電壓轉為低準位電壓 2 率電晶體不導通。 竭出使該功 出電壓下降但輸出 I流保護的目的。 藉此,在輪出達到電流限制時,輪 電流仍可控制維持不變’而達到輸出過 L貫施方式】 ,使責審查委員充分瞭解本創 ;作:藉::ϊ具體之實施例, 卞文评細呪明,說明如後: M312119 ::圖為本創作之較佳具體實施例之一次側回授控制 父祆’電:供應器電路系統方塊圖、第五圖為示於第四圖 中之m度輕控㈣㈣電路方塊圖歧第六圖為本 創作,較佳具體實施例之控制訊號圖,請同時參考第四 圖、第五圖及第六圖,本創作之較佳具體實施例之一次側 回授控制交換式電源供應器包含-返馳式變壓器T卜其具 有-初m -漏繞組及—次極繞組,初極繞組連接 私源,功率包日日體Q1,其連接該初級繞組;一次側回授 控制脈波寬度調整控制H m,其具有—取樣及保留控制電 路2,其連接辅助繞組;一誤差放大器AMpl,其連接取樣 及保留控制電路2 ; —分壓器DIVIDER,其連接取樣及保 留控制電路2 ; —乘法器MULT,其連接該分壓器To the & input of the flip-flop, the reset signal causes the positive and negative output terminals to change from a high-level voltage to a low-level voltage. The purpose of reducing the power output voltage but protecting the output I current is exhausted. Therefore, when the rotation reaches the current limit, the wheel current can still be controlled to maintain the same 'to achieve the output of the L-application method】, so that the responsible review committee fully understands the original; by: by: ϊ specific examples,卞 评 , , , M M 312 M M M M 312 312 312 312 312 312 312 312 312 312 312 312 312 312 312 312 312 312 312 312 312 312 M 312 M M M M 312 312 M M 312 M 312 M M M The second embodiment of the present invention is a control signal diagram of the preferred embodiment. Please refer to the fourth, fifth and sixth figures at the same time. The primary side feedback control switching power supply includes a flyback transformer T having an initial m-drain winding and a secondary winding, the primary winding is connected to a private source, and the power pack is connected to the Japanese body Q1. Primary winding; primary side feedback control pulse width adjustment control H m having a sampling and retention control circuit 2 connected to the auxiliary winding; an error amplifier AMpl connected to the sampling and retention control circuit 2; - voltage divider DIVIDER , its connection sampling and insurance Leave control circuit 2; - multiplier MULT connected to the voltage divider
DIVIDER; —第一比較器c〇Ml,其連接誤差放大器AMP1 及功率電晶體Q1 ; —第二比較器COM2,其連接第一比較 器C0M1及乘法器MULT ; —功率限制補償電路1,其連 接乘法器MULT; —控制開關sw,其連接電源及功率限制 補償電路1 ; 一輸出驅動器DRIVER,其連接功率電晶體 Q1 ; —正反器FF1,其連接輸出驅動器DRIVER ; —振盪 產生器OSC,其連接正反器FF1 ; —前緣消除電路LEB, 其連接正反器FF1 ; — 〇R閘,其連接第一比較器C0M1、 第二比較器COM2及前緣消除電路LEB;當電源電壓VCC 由電阻R2、二極體D4充電到達脈波寬度調整控制器U1 的啟動電壓時,脈波寬度調整控制器U1開始動作,低壓 鎖止電路UVLO輸出一 UVO訊號使内部穩壓電路BAND 12 M312119 ,gap輸出一參考電壓並且讓一補償控制開關sw導通,+ -阻R2乃切換至與乘法器MULT連接的功率限制補償電ς 1 ’其與内部分壓電阻分屡產生因輸入電壓VIN之變動產 生不同之功率限制補償電壓WL使得高低壓輸入時的功率 限制點趨於一致。脈波寬度調整控制器之振盪產生哭 OSC輸出一導通訊號到正反器FF1之s輪入端,使正反哭 FF1輸出端Q由低準位電壓轉為高準位電壓,第一輸出ς 動器DRIVER因此輸出高準位電壓使功率電晶體Q1轉為 參考電壓VCL_處於低準位電壓使得脈波寬度調整控制 器υι之導通週期被限流參考電壓VCL限制由最低導^週 ;期隨輸出電壓與輔助繞組電壓變高漸漸展開,而提供― -S〇FT STAR丁的啟動效果。另-方面辅助繞組因為變壓哭 開始動作而開始產生電壓經二極體D2、電阻幻供應電源 電壓VCC,輔助繞組電壓在非連續工作模式時的諧波電壓 ❿之轉角電壓值經電阻R3,分麼,電屋回授輸入接聊VFB $過脈波寬度調整控制器m之取樣與保留控制電路2取 件为壓電壓值作為内部穩壓控制與限流控制的電壓值 v卜5亥私壓值VI與第-參考電壓VREF1經誤差放大器 AMP1輸出兩者誤差之放大值,此_誤差放大器ΑΜρι輸 ,電壓端COMP接一補償元件(例如:電容C5或是利用電 谷及至少-電阻構成)防止誤差放大器ΑΜρι減情形發 - 生。此一誤差放大值電壓經過電阻R7、R8分壓產生一控 制電壓VCTL,控制電壓VCTL接至第一比較器c〇M 1之 M312119 一反向輸入端,此第一比較器C0M1之非反向輸入端則另 接到電流偵侧電阻R6偵侧一次侧電流偵測電壓VCS,非 反向輸入端之一次侧電流偵測電壓VCS與反向輸入端之控 制電壓VCTL比較,當一次侧電流偵測電壓VCS大於控制 電壓VCTL時產生一截止訊號經〇R閘到前緣消除電路 LEB(LEADING EDGE BLANKING)消除一次侧電流偵測電 壓VCS之前緣雜訊電壓後輸出一重置訊號到正反器FF1之 R輸入端,使正反器FF1輸出端Q由高準位電壓轉為低準 位電壓,第一輸出驅動器DRIVER因此輸出低準位電壓使眷 功率電晶體Q1轉為不導通狀態。脈波寬度調整控制器U1 之振盈產生器OSC再次輸出導通脈衝訊號到正反器FF1之 S輸入端’使正反器FF1再次將輸出端Q由低準位電壓轉 “ 為高準位電壓’第一輸出驅動器DRIVER再次輸出高準位 ·— 電壓,使功率電晶體Q1再次轉為導通狀態,再次比較控 · 制電壓VCTL與一次侧電流偵測電壓vcs,產生截止訊號 經0R閘到前緣消除電路LEB (LEADING EDGE | BLANKING)消除一次側電流偵測電壓yes之前緣雜訊電 壓後輸出重置訊號到正反器FF1之尺輸入端,使正反器FF1 輸出端Q由高準位電壓轉為低準位電壓,第一輸出驅動器 DRIVER控制功率電晶體Q1轉為不導通狀態,重覆上述動 作產生一穩定的輸出控制。本創作的一次侧回授控制的脈 波寬度调整控制器Ul之功率限制補償電壓VPL係由電源 之電壓經一電阻分壓後傳至減法器3之反向輸入端與一第 三參考電壓VERF3比較後產生,而限流參考電壓VCL由 14 M312119 取樣與保留控制電路2的輸出電壓 =二1二之比率降壓後與功率限制補償= 相乘後加上第二參考電壓v 通吊麥考電壓卿2設定為一微小的電屋 嶋段由小變大防止輪出電流超過限制Π 茶考—VCL隨輸出端V〇電壓的高低而變化,因此可 以控制輸出電流於限制範圍内。DIVIDER; - first comparator c 〇 Ml connected to error amplifier AMP1 and power transistor Q1; - second comparator COM2 connected to first comparator C0M1 and multiplier MULT; - power limit compensation circuit 1, connected Multiplier MULT; - Control switch sw, which is connected to the power supply and power limit compensation circuit 1; an output driver DRIVER connected to the power transistor Q1; - a flip-flop FF1 connected to the output driver DRIVER; - an oscillation generator OSC, Connect the flip-flop FF1; - leading edge cancel circuit LEB, which is connected to the flip-flop FF1; - 〇R gate, which is connected to the first comparator C0M1, the second comparator COM2 and the leading edge cancel circuit LEB; when the power supply voltage VCC is When the resistor R2 and the diode D4 are charged to reach the starting voltage of the pulse width adjusting controller U1, the pulse width adjusting controller U1 starts to operate, and the low voltage locking circuit UVLO outputs a UVO signal to make the internal voltage stabilizing circuit BAND 12 M312119 , gap A reference voltage is output and a compensation control switch sw is turned on, and the +-resistance R2 is switched to a power limit compensation circuit 1 connected to the multiplier MULT. The variation of the voltage VIN produces different power limit compensation voltages WL such that the power limit points at high and low voltage inputs tend to be uniform. The oscillation of the pulse width adjustment controller generates a crying OSC output a communication number to the s wheel of the flip-flop FF1, so that the positive and negative crying FF1 output terminal Q is converted from the low level voltage to the high level voltage, the first output ς The DRIVER thus outputs a high-level voltage to turn the power transistor Q1 into the reference voltage VCL_ at a low level voltage so that the on-period of the pulse width adjustment controller 被 is limited by the current-limit reference voltage VCL by the lowest period; As the output voltage and the auxiliary winding voltage become higher, the "-S〇FT STAR" start effect is provided. On the other hand, the auxiliary winding starts to generate voltage through the diode D2, the resistor supply power supply voltage VCC, and the corner voltage value of the auxiliary winding voltage in the discontinuous operation mode is passed through the resistor R3. Divided into, electric house feedback input chat VFB $ pulse width adjustment controller m sampling and retention control circuit 2 take the piece of voltage as the internal voltage control and current limit control voltage value v The voltage value VI and the first reference voltage VREF1 are outputted by the error amplifier AMP1, and the error value is amplified by the error amplifier ,ρι, and the voltage terminal COMP is connected to a compensation component (for example, the capacitor C5 or the electric valley and the at least resistor). ) Prevent the error amplifier from 减ρι reducing the situation. The voltage of the error amplification value is divided by the resistors R7 and R8 to generate a control voltage VCTL, and the control voltage VCTL is connected to an inverting input terminal of the M312119 of the first comparator c〇M1, and the non-inverting of the first comparator C0M1 The input terminal is further connected to the current detecting side resistor R6 to detect the primary side current detecting voltage VCS, and the primary side current detecting voltage VCS of the non-inverting input terminal is compared with the control voltage VCTL of the inverting input terminal, when the primary side current detecting When the measured voltage VCS is greater than the control voltage VCTL, a cutoff signal is generated. The LEA gate is removed to the leading edge canceling circuit LEB (LEADING EDGE BLANKING) to eliminate the primary side current detecting voltage VCS leading edge noise voltage and output a reset signal to the flip-flop The R input terminal of FF1 turns the output terminal Q of the flip-flop FF1 from the high-level voltage to the low-level voltage, and the first output driver DRIVER thus outputs a low-level voltage to turn the 眷 power transistor Q1 into a non-conducting state. The oscillation generator OSC of the pulse width adjustment controller U1 outputs the conduction pulse signal to the S input terminal of the flip-flop FF1 again, so that the flip-flop FF1 turns the output terminal Q from the low-level voltage to the high-level voltage again. 'The first output driver DRIVER again outputs the high level ·- voltage, so that the power transistor Q1 is turned into the on state again, and the control voltage VCTL and the primary side current detection voltage vcs are compared again, and the cutoff signal is generated through the 0R gate. The edge elimination circuit LEB (LEADING EDGE | BLANKING) eliminates the primary side current detection voltage yes before the edge noise voltage and outputs a reset signal to the input terminal of the flip-flop FF1, so that the output terminal Q of the flip-flop FF1 is high-level. When the voltage is turned to the low level voltage, the first output driver DRIVER controls the power transistor Q1 to turn into a non-conducting state, and repeats the above action to generate a stable output control. The pulse width adjustment controller of the primary side feedback control of the present invention is created. The power limit compensation voltage VPL of Ul is generated by dividing the voltage of the power source by a resistor and then transmitting it to the inverting input terminal of the subtractor 3 to be compared with a third reference voltage VERF3, and the current limiting reference voltage V is generated. The CL is sampled by 14 M312119 and the output voltage of the hold control circuit 2 = the ratio of two to two. After the step-down and the power limit compensation = multiplied by the second reference voltage v, the switch is set to a small amount of electricity. The eaves section is changed from small to large to prevent the current from exceeding the limit. Π Tea test—VCL varies with the V〇 voltage at the output, so the output current can be controlled within the limits.
如上所述,其中電麼回授輸入接腳WB接一二極體 D3負責將電壓回授輸人接腳WB之負壓鉗位在負 〇·7ν)電壓的準位,電壓回授輸人接腳vfb經過取樣鱼保 留控制電路2取得魏轉角電壓值儲存於電容。轉角電 壓值一方面經第一誤差放大器AMP1及電阻R7、R8產生 控制電壓VCTL,另-方面經—緩衝器BUFFER、分壓器 divider、乘法器MULT再加第二參考電壓VREF2產: 限流參考電壓VCL,限流參考電壓VCL等於分壓器 DIVIDER的輸出電壓與功率限制補償電壓vpL乘積再加 第二參考電壓VREF2之值。輸入電壓VIN經一補償控制 開關SW再與電阻R5產生分壓輸入減法器3之反向輪入 端,其與第三參考電壓VREF3比較輸出功率限制補償電壓 VPL。一次側電流偵測電壓vcs將分別與限流參考電壓 VCL·及控制電壓vcTL比較,當一次侧電流偵測電壓Vcs 大於其中一組電壓時將輸出截止訊號,截止訊號經間 再經前緣消除電路LEB(LEADING EDGE BLANKING)消除 一次側電流偵測電壓VCS之前緣雜訊電壓後,輸出一重置 15 M312119 減到正反為FF1之R輸入端,使正反器則輸出端Q由. 同準位私壓轉為低準位電壓,第一輸出驅動器driver因 此輸出低準位電壓,使功率電晶體Q1 #為不導通狀態。 移相WPHASE SHIFT產生一空白訊號肌八狐輸入取樣 與保奋控制電路2,讓電路取樣時序在空白訊號BLANK之 後,以避開取樣在電壓回授輸入接腳VFB電壓振鈴 (RINGING)區域。 第七圖為本創作之理想輸出限流之曲線圖,輸出最大 包抓被限制在限制電流值,當輸出電壓下降至一設定值時# 輸出電流折回。 ^第八圖為本創作之較佳具體實施例之一次側回授控制 父換式電源供應益内之取樣與保留控制電路之内部電路方 塊圖,係利用電壓回授輸入接腳VFB的電壓在空白訊號 -BLANK之後較平坦的電壓準位予以儲存並追隨電壓變 - 化,§私壓回授輸入接腳VFB電壓到達諧波開始處時轉折 進入另一陡峭的斜率變化時,從取樣及保留控制電路取得 ⑩ 之電壓V1立刻停止追隨電壓回授輸入接腳VFB的電壓變 化並記憶儲存轉角處電壓值,以作為内部穩壓控制與限流 L制的控制電壓,如第八圖所示,空白訊號BLANK將控 :私日日體Q4導通將電壓VI放電歸零,待空白訊號BLANK 結束後仔止放電,運算放大器AMp2與電晶體Q2在較平 ~的斜率^壓時構成一電壓隨耦器使電壓回授輸入接腳 , VFB的電壓傳送儲存於電容ο上,電容c2之電壓即為控、 制電壓VI,偏壓BIAS控制電晶體Q5導通形成一放電電 16 M312119 流Idschg,此放電電流Idschg設定為遠小於電壓隨耦器控 制的充電mhg’目的是產生與電壓賴輸人接腳vfb 的電壓相_應之電壓變化,電壓回授輸人接腳VFB的電壓 與空白訊f虎BLANK #反相訊號經及M AND輸入正反器 FF3控制電晶體Q5導通與關閉,用以獲取電壓v卜正反 器FF2為防止於第一諧波之後有誤觸發動作發生,由此, 取樣與保留控制電路即可取得非連續模缸作時的譜波電 壓之轉角電壓值作為回授控制。 _如上所述’本創作係藉著取樣與保留控制電路取得一 次側輔助繞組在非連續模式1㈣㈣波電壓之轉角電壓 值作為回授控制’在輸出達到電流限制時,輸出電壓下降 ,出電流仍可控制維持不變,而達到輸出過電流保護的 ^的;i產業上的可利用性而言,利用本創作所衍生的產 σα,當可充分滿足目前市場的需求。As described above, in which the feedback input pin WB is connected to a diode D3, the voltage is applied to the negative voltage of the input pin WB to be clamped at the level of the negative 〇7ν) voltage, and the voltage feedback is input. The pin vfb is obtained by the sample fish retention control circuit 2 to obtain a value of the Wei corner voltage stored in the capacitor. The corner voltage value is generated on the one hand by the first error amplifier AMP1 and the resistors R7, R8 to generate the control voltage VCTL, and the other side is generated by the buffer BUFFER, the voltage divider divider, the multiplier MULT plus the second reference voltage VREF2: current limiting reference The voltage VCL, the current-limit reference voltage VCL is equal to the value of the output voltage of the voltage divider DIVIDER and the power limit compensation voltage vpL plus the second reference voltage VREF2. The input voltage VIN is controlled by a compensation switch SW and a resistor R5 to generate a voltage division input subtractor 3 of the reverse wheel input terminal, which compares the output power limit compensation voltage VPL with the third reference voltage VREF3. The primary current detection voltage vcs will be compared with the current limiting reference voltage VCL and the control voltage vcTL respectively. When the primary side current detection voltage Vcs is greater than one of the voltages, the cutoff signal will be output, and the cutoff signal will be eliminated by the leading edge. The circuit LEB (LEADING EDGE BLANKING) eliminates the primary side current detection voltage VCS leading edge noise voltage, and outputs a reset 15 M312119 to the R input of the positive and negative FF1, so that the positive and negative ends of the output terminal Q. The standard private voltage is converted to a low level voltage, and the first output driver driver thus outputs a low level voltage, so that the power transistor Q1# is in a non-conducting state. The phase shift WPHASE SHIFT generates a blank signal muscle eight fox input sampling and the control circuit 2, so that the circuit sampling timing is after the blank signal BLANK to avoid sampling in the voltage feedback input pin VFB voltage ringing (RINGING) area. The seventh picture is the graph of the ideal output current limit of the creation. The maximum output of the output is limited to the limit current value. When the output voltage drops to a set value, the output current is folded back. The eighth figure is a block diagram of the internal circuit of the sampling and retention control circuit of the primary side feedback control of the parental switching power supply in the preferred embodiment of the present invention, which uses the voltage feedback voltage of the input pin VFB. The blank signal - the flat voltage level after BLANK is stored and follows the voltage change. § The private voltage feedback input pin VFB voltage reaches the harmonic start when turning to another steep slope change, from sampling and retention. The control circuit obtains the voltage V1 of 10 and immediately stops the voltage change following the voltage feedback input pin VFB and memorizes the voltage value at the storage corner as the control voltage of the internal voltage regulation control and the current limit L system, as shown in the eighth figure. The blank signal BLANK will control: the private day and body Q4 is turned on and the voltage VI is discharged to zero. After the blank signal BLANK is finished, the discharge is stopped. The operational amplifier AMp2 and the transistor Q2 form a voltage with a flat slope. The voltage is fed back to the input pin, and the voltage transfer of VFB is stored on the capacitor ο. The voltage of the capacitor c2 is the voltage of the control and the voltage VI, and the bias voltage BIAS controls the transistor Q5 to be turned on to form a discharge battery 16 M3. 12119 flow Idschg, the discharge current Idschg is set to be much smaller than the voltage follower controlled charging mhg' purpose is to generate a voltage change with the voltage of the input pin vfb, the voltage feedback to the input pin VFB Voltage and blank signal f Tiger BLANK #反信号信号 and M AND input flip-flop FF3 control transistor Q5 turn-on and turn-off, to obtain voltage v Bu-flip FF2 to prevent false trigger action after the first harmonic Occurs, whereby the sampling and retention control circuit can obtain the corner voltage value of the spectral voltage when the discontinuous cavity is in operation as the feedback control. _ As mentioned above, this creation uses the sampling and retention control circuit to obtain the value of the corner voltage of the primary auxiliary winding in the discontinuous mode 1 (four) (four) wave voltage as the feedback control. When the output reaches the current limit, the output voltage drops, and the output current remains. The control can be maintained unchanged, and the output overcurrent protection can be achieved; in terms of the availability of the industry, the production of σα derived from the creation can fully satisfy the current market demand.
,本創作在上文巾佳實關揭露,㈣習本項技 ^應理解的是,該實_伽於微本創作,而不岸解 7限制賴作之_。^主意的是,舉凡與該實施例等 變化與置換,均應設為涵蓋於本創作之射内。因此, 本剑作之保護範圍當以下文之中請專利範圍所界定者為準 【圖式簡單說明】 第一圖為習知的一 電路方塊圖。 次側回授控制的交換式 電源供應This creation is disclosed in the above article. (4) The skill of the book is understood to be that the _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ The idea is that any changes and permutations, such as the embodiment, should be made to cover the creation of this creation. Therefore, the scope of protection of this sword is subject to the definition of patent scope in the following text. [Simple description of the diagram] The first diagram is a circuit diagram of a conventional circuit. Secondary side feedback controlled switching power supply
M312119 第二圖為習知的二次侧回授控制的交換式電源供應器 電路方塊圖。 第三圖為習知的二次侧回授控制的交換式電源供應器 另一電路方塊圖。 第四圖為本創作之較佳具體實施例之一次侧回授控制 交換式電源供應器電路糸統方塊圖。 第五圖為示於第四圖中之脈波寬度調整控制器内部電 路方塊圖。 第六圖為本創作之較佳具體實施例之控制訊號圖。 第七圖為本創作之理想輸出限流之曲線圖。 第八圖為本創作之較佳具體實施例之一次侧回授控制 交換式電源供應器内之取樣與保留控制電路之内部電路方 塊圖。 【主要元件符號說明】 ui脈波寬度調整控制器 U2光耦合器 U3回授穩壓器 U4A、U4B運算放大器 UVLO低壓鎖止電路 UVO訊號 BAND GAP内部穩壓電路 SW補償控制開關 M312119M312119 The second figure is a block diagram of a conventional switched-mode power supply circuit for secondary side feedback control. The third figure is another circuit block diagram of a conventional secondary power supply controlled switching power supply. The fourth figure is a block diagram of the primary side feedback control switching power supply circuit of the preferred embodiment of the present invention. The fifth figure is a block diagram of the internal circuit of the pulse width adjustment controller shown in the fourth figure. Figure 6 is a control signal diagram of a preferred embodiment of the present invention. The seventh picture is a graph of the ideal output current limit of the creation. Figure 8 is a block diagram showing the internal circuit of the sample and hold control circuit in the primary side feedback control switching power supply of the preferred embodiment of the present invention. [Main component symbol description] ui pulse width adjustment controller U2 optocoupler U3 feedback regulator U4A, U4B operational amplifier UVLO low voltage lockout circuit UVO signal BAND GAP internal voltage regulator circuit SW compensation control switch M312119
Cn電容 1功率限制補償電路 2取樣與保留控制電路 3減法器 MULT乘法器 VIN輸入電壓 VCC電源電壓 V0輸出端 VCL限流參考電壓 VPL功率補償電壓 VCTL控制電壓 OSC振盪產生器 FF1、FF2、FF3 正反器 DRIVER第一輸出驅動器 Q1功率電晶體 Q2、Q3、Q4、Q5、Q12 電晶體 Dn二極體 VFB電壓回授輸入接腳 T1變壓器 AMP1誤差放大器 AMP2運算放大器 COMP輸出電壓端 C0M1第一比較器 COM2第二比較器 19 M312119 LEB前緣消除電路 DIVIDER分壓器 BUFFER緩衝器 VERF1第一參考電壓 VERF2第二參考電壓 VERF3第三參考電壓 VCS —次侧電流偵測電壓 ldschg放電電流 lchg充電電流 BALNK空白訊號 BIAS偏壓 VI電壓Cn Capacitor 1 Power Limit Compensation Circuit 2 Sample and Retention Control Circuit 3 Subtractor MULT Multiplier VIN Input Voltage VCC Supply Voltage V0 Output Terminal VCL Current Limit Reference Voltage VPL Power Compensation Voltage VCTL Control Voltage OSC Oscillator Generator FF1, FF2, FF3 Positive Counter DRIVER first output driver Q1 power transistor Q2, Q3, Q4, Q5, Q12 transistor Dn diode VFB voltage feedback input pin T1 transformer AMP1 error amplifier AMP2 operational amplifier COMP output voltage terminal C0M1 first comparator COM2 second comparator 19 M312119 LEB leading edge elimination circuit DIVIDER voltage divider BUFFER buffer VERF1 first reference voltage VERF2 second reference voltage VERF3 third reference voltage VCS - secondary side current detection voltage ldschg discharge current lchg charging current BALNK blank Signal BIAS bias VI voltage
2020
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TW95219460U TWM312119U (en) | 2006-11-03 | 2006-11-03 | Exchange-type power supply with feedback-control on the primary side |
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Cited By (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
TWI404308B (en) * | 2010-04-28 | 2013-08-01 | System General Corp | Control apparatus and methods for primary-side-regulation power converters |
TWI416854B (en) * | 2011-01-27 | 2013-11-21 | Mean Well Entpr Co Ltd | Switch power supply apparatus and transient peak current compensation method thereof |
TWI481167B (en) * | 2012-10-19 | 2015-04-11 | Lite On Technology Corp | A switching power supply |
CN108450047A (en) * | 2015-10-23 | 2018-08-24 | 戴洛格半导体公司 | Primary side with calibrated output voltage adjusts flyback converter |
US11088622B2 (en) | 2019-12-24 | 2021-08-10 | Chicony Power Technology Co., Ltd. | Voltage converting apparatus |
-
2006
- 2006-11-03 TW TW95219460U patent/TWM312119U/en unknown
Cited By (6)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
TWI404308B (en) * | 2010-04-28 | 2013-08-01 | System General Corp | Control apparatus and methods for primary-side-regulation power converters |
TWI416854B (en) * | 2011-01-27 | 2013-11-21 | Mean Well Entpr Co Ltd | Switch power supply apparatus and transient peak current compensation method thereof |
TWI481167B (en) * | 2012-10-19 | 2015-04-11 | Lite On Technology Corp | A switching power supply |
CN108450047A (en) * | 2015-10-23 | 2018-08-24 | 戴洛格半导体公司 | Primary side with calibrated output voltage adjusts flyback converter |
CN108450047B (en) * | 2015-10-23 | 2019-10-25 | 戴洛格半导体公司 | Primary side with calibrated output voltage adjusts flyback converter |
US11088622B2 (en) | 2019-12-24 | 2021-08-10 | Chicony Power Technology Co., Ltd. | Voltage converting apparatus |
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