TWI765772B - Method for equalizing input signal to generate equalizer output signal and parametric equalizer - Google Patents
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Abstract
Description
本發明係有關於等化器設計,尤指一種動態地調整權重值(weighting value)來等化一輸入訊號以產生一等化器輸出訊號的方法以及相關參數等化器。The present invention relates to the design of an equalizer, and more particularly, to a method for dynamically adjusting a weighting value to equalize an input signal to generate an output signal of an equalizer, and a related parameter equalizer.
參數等化器係一種可以配置參數(諸如中心頻率(center frequency)及品質因數(quality factor, Q))以對輸入訊號進行輸出頻率響應調變的等化器。藉由利用參數等化器,當輸入至參數等化器的訊號之位準(level)太大時,可避免發生訊號的削波(clipping),然而,當輸入至參數等化器的訊號之位準太小時,藉由利用參數等化器無法達到良好的聽覺效果,此外,當輸入至參數等化器的訊號之位準太大時,可能會損失增益補償(gain compensation),因此,為了解決上述問題,極需一種針對輸入訊號的位準來補償輸出頻率響應的方法以及相關參數等化器。A parametric equalizer is an equalizer that can configure parameters such as center frequency and quality factor (Q) to modulate the output frequency response of an input signal. By using the parametric equalizer, when the level of the signal input to the parametric equalizer is too large, clipping of the signal can be avoided. However, when the signal input to the parametric equalizer is If the level is too small, a good hearing effect cannot be achieved by using the parametric equalizer. In addition, when the level of the signal input to the parametric equalizer is too large, gain compensation may be lost. Therefore, in order to To solve the above problems, a method for compensating the output frequency response according to the level of the input signal and a related parameter equalizer are extremely needed.
因此,本發明的目的之一在於提供一種動態地調整權重值來等化一輸入訊號以產生一等化器輸出訊號的方法以及相關參數等化器,以解決上述問題。Therefore, one of the objectives of the present invention is to provide a method for dynamically adjusting a weight value to equalize an input signal to generate an output signal of an equalizer and a related parameter equalizer to solve the above problems.
根據本發明之一實施例,揭露了一種參數等化器。本發明的參數等化器根據等化器輸出訊號來動態地調整權重值,而不是調整參數等化器的增益值。該參數等化器包含有一第一參數等化器電路、一第二參數等化器電路、一第一乘法電路、一第二乘法電路、一加法電路以及一權重控制電路。第一參數等化器電路具有有著正增益之一第一轉移函數,並且用以根據該第一轉移函數來處理一輸入訊號以及藉由處理該輸入訊號來輸出一第一輸出訊號,第二參數等化器電路具有有著負增益之一第二轉移函數,並且用以根據該第二轉移函數來處理該輸入訊號以及藉由處理該輸入訊號來輸出一第二輸出訊號,第一乘法電路耦接於第一參數等化器電路,並且用以將該第一輸出訊號以及一第一權重值相乘以產生一第一調整輸出訊號,第二乘法電路耦接於第二參數等化器電路,並且用以將該第二輸出訊號以及一第二權重值相乘以產生一第二調整輸出訊號,加法電路耦接於第一乘法電路以及第二乘法電路,並且用以將該第一調整訊號以及該第二調整訊號結合以產生一等化器輸出訊號,權重控制電路耦接於第一乘法電路、第二乘法電路以及加法電路,並且用以根據該等化器輸出訊號來動態地調整該第一權重值以及該第二權重值。According to an embodiment of the present invention, a parameter equalizer is disclosed. The parametric equalizer of the present invention dynamically adjusts the weight value according to the equalizer output signal, instead of adjusting the gain value of the parametric equalizer. The parameter equalizer includes a first parameter equalizer circuit, a second parameter equalizer circuit, a first multiplication circuit, a second multiplication circuit, an addition circuit and a weight control circuit. The first parameter equalizer circuit has a first transfer function with a positive gain, and is used for processing an input signal according to the first transfer function and outputting a first output signal by processing the input signal. The second parameter The equalizer circuit has a second transfer function with negative gain, and is used for processing the input signal according to the second transfer function and outputting a second output signal by processing the input signal, the first multiplying circuit is coupled to in the first parameter equalizer circuit and used for multiplying the first output signal and a first weight value to generate a first adjusted output signal, the second multiplication circuit is coupled to the second parameter equalizer circuit, and used for multiplying the second output signal and a second weight value to generate a second adjustment output signal, the adding circuit is coupled to the first multiplication circuit and the second multiplication circuit, and is used for the first adjustment signal and the second adjustment signal is combined to generate an equalizer output signal, the weight control circuit is coupled to the first multiplying circuit, the second multiplying circuit and the adding circuit, and is used for dynamically adjusting the equalizer output signal according to the equalizer output signal the first weight value and the second weight value.
根據本發明之一實施例,揭露了一種動態地調整權重值來等化一輸入訊號以產生一等化器輸出訊號的方法。該方法包含有:藉由具有有著正增益之一第一轉移函數的一第一參數等化器電路來處理該輸入訊號,以產生並且輸出一第一輸出訊號;藉由具有有著負增益之一第二轉移函數的一第二參數等化器電路來處理該輸入訊號,以產生並且輸出一第二輸出訊號;將該第一輸出訊號以及一第一權重值相乘,以產生一第一調整輸出訊號;將該第二輸出訊號以及一第二權重值相乘,以產生一第二調整輸出訊號;將該第一調整輸出訊號以及該第二調整輸出訊號結合,以產生該等化器輸出訊號;以及根據該等化器輸出訊號來動態地調整該第一權重值以及該第二權重值。According to an embodiment of the present invention, a method for dynamically adjusting a weight value to equalize an input signal to generate an equalizer output signal is disclosed. The method includes: processing the input signal by a first parametric equalizer circuit having a first transfer function with a positive gain to generate and output a first output signal; by having a first transfer function with a negative gain A second parameter equalizer circuit of the second transfer function processes the input signal to generate and outputs a second output signal; multiply the first output signal and a first weight value to generate a first adjustment output signal; multiply the second output signal and a second weight value to generate a second adjusted output signal; combine the first adjusted output signal and the second adjusted output signal to generate the equalizer output signal; and dynamically adjusting the first weight value and the second weight value according to the output signal of the equalizer.
第1圖為依據本發明一實施例之參數等化器10的示意圖,參數等化器10根據等化器輸出訊號來動態地調整權重值,而不是調整增益值,舉例來說,權重值包含有一第一權重值以及一第二權重值,並且第一權重值以及第二權重值的總和係等於一,為了簡潔起見,第一權重值以及一第二權重值分別標示為 “ β ” 以及 “ 1-β ” 。FIG. 1 is a schematic diagram of a
參數等化器10接收一輸入訊號A_IN諸如一音頻訊號(audio signal),並且等化輸入訊號A_IN以產生一等化器輸出訊號EQ_OUT。如第1圖所示,參數等化器10包含有參數等化器電路12、參數等化器電路14、乘法電路16、乘法電路18、加法電路20以及權重控制電路22,參數等化器電路12具有一個有著正增益G
1(G
1>0)的轉移函數H
1,並且用以根據轉移函數H
1來處理輸入訊號A_IN以及藉由處理輸入訊號A_IN來輸出一第一輸出訊號A_OUT_1,參數等化器電路14具有一個有著負增益G
2(G
2<0)的轉移函數H
2,並且用以根據轉移函數H
2來處理輸入訊號A_IN以及藉由處理輸入訊號A_IN來輸出一第二輸出訊號A_OUT_2,其中參數等化器電路12的中心頻率(center frequency)與參數等化器電路14的中心頻率相同。
The
乘法電路16耦接於參數等化器電路12,並且用以將第一輸出訊號A_OUT_1與第一權重值β相乘,以產生一第一調整輸出訊號AD_OUT_1(亦即AD_OUT_1 = A_OUT_1 * β)。乘法電路18耦接於參數等化器電路14,並且用以將第二輸出訊號A_OUT_2與第二權重值1-β相乘,以產生一第二調整輸出訊號AD_OUT_2 (亦即AD_OUT_2 = A_OUT_2 * (1-β))。加法電路20耦接於乘法電路16以及乘法電路18,並且用以將第一調整輸出訊號AD_OUT_1與第二調整輸出訊號AD_OUT_2結合,以產生等化器輸出訊號EQ_OUT(亦即EQ_OUT = AD_OUT_1 + AD_OUT_2)。權重控制電路22耦接於乘法電路16、乘法電路18以及加法電路20,並且用以根據等化器輸出訊號EQ_OUT來動態地調整第一權重值β以及第二權重值1-β。The multiplying
此外,參數等化器電路12可以為由一二階濾波器(biquad filter)所實現的一尖峰濾波器(peaking filter),而參數等化器電路14則可以為由一二階濾波器所實現的一陷波濾波器(notch filter),但是本發明不限於此。舉例來說,當參數等化器電路12或參數等化器電路14由一二階濾波器所實現時,參數等化器電路12或參數等化器電路14的轉移函數可由以下方程式來表示:
In addition, the
其中係數b 0、b 1、b 2、a 1、a 2可由以下matlab程式碼來決定: K = tan( (pi * fc) / fs); The coefficients b 0 , b 1 , b 2 , a 1 , and a 2 can be determined by the following matlab code: K = tan( (pi * fc) / fs);
V0 = 10^(G / 20);V0 = 10^(G / 20);
if ( V0 < 1 ) % invert gain if a cutif ( V0 < 1 ) % invert gain if a cut
V0= 1 / V0;V0 = 1 / V0;
endend
if (G > 0)if (G > 0)
b0 = ( 1 + ( V0 / Q ) * K ) + K^2 ) / ( 1 + ( ( 1 / Q ) * K ) + K^2 );b0 = ( 1 + ( V0 / Q ) * K ) + K^2 ) / ( 1 + ( ( 1 / Q ) * K ) + K^2 );
b1 = ( 2 * ( K^2 – 1 ) ) / ( 1 + ( (1 / Q) * K ) + K^2 );b1 = ( 2 * ( K^2 - 1 ) ) / ( 1 + ( (1 / Q) * K ) + K^2 );
b2 = ( 1 - ( V0 / Q ) * K ) + K^2 ) / ( 1 + ( ( 1 / Q ) * K ) + K^2 );b2 = ( 1 - ( V0 / Q ) * K ) + K^2 ) / ( 1 + ( ( 1 / Q ) * K ) + K^2 );
a1 = b1;a1 = b1;
a2 = ( 1 - ( 1 / Q ) * K ) + K^2 ) / (1 + ( ( 1 / Q ) * K ) + K^2 );a2 = ( 1 - ( 1 / Q ) * K ) + K^2 ) / (1 + ( ( 1 / Q ) * K ) + K^2 );
elseelse
b0 = ( 1 + ( 1 / Q ) * K ) + K^2 ) / ( 1 + ( ( V0 / Q ) * K ) + K^2 );b0 = ( 1 + ( 1 / Q ) * K ) + K^2 ) / ( 1 + ( ( V0 / Q ) * K ) + K^2 );
b1 = ( 2 * ( K^2 – 1 ) ) / ( 1 + ( ( V0 / Q ) * K ) + K^2 );b1 = ( 2 * ( K^2 - 1 ) ) / ( 1 + ( ( V0 / Q ) * K ) + K^2 );
b2 = ( 1 - ( 1 / Q ) * K ) + K^2 ) / ( 1 + ( ( V0 / Q ) * K ) + K^2 );b2 = ( 1 - ( 1 / Q ) * K ) + K^2 ) / ( 1 + ( ( V0 / Q ) * K ) + K^2 );
a1 = b1;a1 = b1;
a2 = ( 1 - ( V0 / Q ) * K ) + K^2 ) / ( 1 + ( ( V0 / Q ) * K ) + K^2 );a2 = ( 1 - ( V0 / Q ) * K ) + K^2 ) / ( 1 + ( ( V0 / Q ) * K ) + K^2 );
endend
在上述matlab程式碼中,fc係為中心頻率,fs係為取樣率(sampling rate),G係為以分貝(decibel, dB)為單位的對數增益(logarithmic gain),以及Q係為品質因數。In the above matlab code, fc is the center frequency, fs is the sampling rate, G is the logarithmic gain in decibels (dB), and Q is the quality factor.
舉例來說,參數等化器電路12係為由一二階濾波器所實現的具有+12分貝增益(亦即G
1= +12dB)以及品質因數Q
P的一尖峰濾波器,而參數等化器電路14係為由一二階濾波器所實現的具有-6分貝增益(亦即G
2= -6dB)以及品質因數Q
N的一陷波濾波器,但是本發明不限於此。藉由上述方程式以及matlab程式碼,可以決定出轉移函數H
1以及轉移函數H
2,再者,轉移函數H
1以及轉移函數H
2的權重值組合可用來達到不同增益值,其表示如下:
=
For example, the
為了將上述兩個分數化簡為一個公分母(common denominator),其假設 ,藉此取得以下分數: = In order to reduce the above two fractions to a common denominator, it is assumed that , to obtain the following scores: =
其中
係為一新的線性增益,當β係等於1時,參數等化器10可視為一尖峰濾波器,其由參數等化器電路12所實現,而當β係等於0時,參數等化器10可視為一陷波濾波器,其由參數等化器電路14所實現。此外,權重值組合所需要的品質因數Q
P以及品質因數Q
N之間的關係(例如
)可藉由將該兩個分數化簡為一個公分母的計算過程中來決定,因此,參數等化器10可藉由轉移函數H
1以及轉移函數H
2的權重值組合來達到+12分貝以及-6分貝之間的不同增益值,其中品質因數Q
N與品質因數Q
P之比值係為一預定常數(例如
)。由於參數等化器10僅應用參數等化器電路12、參數等化器電路14以及權重值(亦即第一權重值β以及第二權重值1-β)組合,因此本發明的硬體成本不高而且本發明相當容易配置,此外,參數等化器電路12以及參數等化器電路14可由可程式化(programmable)的二階濾波器來實現,因此,當參數等化器電路12以及參數等化器電路14沒在使用時,參數等化器電路12以及參數等化器電路14可以被重複使用(reuse)於其它用途。
in is a new linear gain, when β is equal to 1, the
第2圖為依據本發明一實施例之權重控制電路200的示意圖。第1圖所示之參數等化器10中的權重控制電路22可以利用第2圖所示之權重控制電路200來實現,如第2圖所示,權重控制電路200包含有一能量偵測電路24以及一權重值產生器26,能量偵測電路24用以測量等化器輸出訊號EQ_OUT的一能量位準EL,權重值產生器26耦接於能量偵測電路24,並且用以根據等化器輸出訊號EQ_OUT的能量位準EL來動態地調整第一權重值β以及第二權重值1-β。在本實施例中,能量偵測電路24包含有一絕對值電路28以及一阿爾發濾波器(alpha filter)30,絕對值電路28用以藉由對等化器輸出訊號EQ_OUT進行絕對值計算來產生等化器輸出訊號EQ_OUT的一絕對值AV,阿爾發濾波器30耦接於絕對值電路28以及權重值產生器26,並且用以根據絕對值計算結果(亦即絕對值AV)來產生能量位準EL,以及將能量位準EL傳送至權重值產生器26,舉例來說,阿爾發濾波器30可以為二階阿爾發濾波器,並且二階阿爾發濾波器的係數為2的次方(亦即
、
、
、…等等),但是本發明不限於此。
FIG. 2 is a schematic diagram of a weight control circuit 200 according to an embodiment of the present invention. The
對於藉由斜率調整來直接地控制權重值(例如第一權重值β以及第二權重值1-β之中的其中一個;為了更好地理解,所控制的是第一權重值β)以根據等化器輸出訊號EQ_OUT的能量位準EL來動態地調整第一權重值β以及第二權重值1-β,在權重值產生器26中採用了一攻擊(attack)控制以及一釋放(release)控制,其中當能量位準EL小於一門檻值(threshold value)TH時,釋放控制用以釋放等化器輸出訊號EQ_OUT,而當能量位準EL不小於門檻值TH時,攻擊控制用以壓抑(suppress)等化器輸出訊號EQ_OUT。因此,權重值產生器26另用以接收一參考門檻值RTH、一攻擊率設置AR以及一釋放率設置RR,其中權重值產生器26內部使用的門檻值TH係藉由將參考門檻值RTH以及一預定係數相乘來取得(例如TH = RTH * 0.635,其中0.635係為預定係數),並且攻擊率設置AR可大於釋放率設置RR。For directly controlling the weight value (eg, one of the first weight value β and the second weight value 1-β; for better understanding, the first weight value β is controlled) to be controlled according to the slope adjustment The energy level EL of the equalizer output signal EQ_OUT dynamically adjusts the first weight value β and the second weight value 1-β. An attack control and a release are used in the
在從阿爾發濾波器30接收能量位準EL之後,權重值產生器26將能量位準EL與門檻值TH進行比較,如果能量位準EL小於門檻值TH(亦即在釋放控制範圍內),則權重值產生器26根據釋放率設置RR所指定的斜率調整來控制第一權重值β;以及如果能量位準EL不小於門檻值TH(亦即在攻擊控制範圍內),則權重值產生器26根據攻擊率設置AR所指定的斜率調整來控制第一權重值β。參數等化器10藉由斜率調整來直接地控制第一權重值β以動態地調整第一權重值β以及第二權重值1-β,而不是藉由線性至對數轉換(linear to logarithm transfer)來動態地調整增益值,應注意的是,動態地調整第一權重值β以及第二權重值1-β的過程中無需線性至對數轉換,如此一來,參數等化器10有著較低的硬體成本。After receiving the energy level EL from the
在釋放控制中(亦即能量位準EL小於門檻值TH),3個從最大到最小的係數C 1、C 2、C 3(例如C 1= 0.666、C 2= 0.43、C 3= 0.26)用以對第一權重值β進行分類,以及4個從最大到最小的分數S 1、S 2、S 3、S 4(例如S 1= 、S 2= 、S 3= 、S 4= )用以設定釋放率設置RR以供斜率調整之用,但是本發明不限於此。如果第一權重值β大於或等於C 1(例如0.666),則藉由將分數S 1(例如 )與第一權重值β相加(亦即β = β + S 1)來調整/更新第一權重值β;如果第一權重值β大於或等於C 2(例如0.43)並且小於C 1(例如0.666),則藉由將分數S 2(例如 )與第一權重值β相加(亦即β = β + S 2)來調整/更新第一權重值β;如果第一權重值β大於或等於C 3(例如0.26)並且小於C 2(例如0.43),則藉由將分數S 3(例如 )與第一權重值β相加(亦即β = β + S 3)來調整/更新第一權重值β;以及如果第一權重值β小於C 3(例如0.26),則藉由將分數S 4(例如 )與第一權重值β相加(亦即β = β + S 4)來調整/更新第一權重值β。 In the release control (ie the energy level EL is less than the threshold value TH), 3 coefficients C 1 , C 2 , C 3 from the largest to the smallest (eg C 1 = 0.666, C 2 = 0.43, C 3 = 0.26) used to classify the first weight value β, and 4 scores S 1 , S 2 , S 3 , S 4 from largest to smallest (eg S 1 = , S 2 = , S 3 = , S 4 = ) is used to set the release rate setting RR for slope adjustment, but the present invention is not limited thereto. If the first weight value β is greater than or equal to C 1 (eg 0.666), then by dividing the fraction S 1 (eg 0.666) ) and the first weight value β (ie β = β + S 1 ) to adjust/update the first weight value β; if the first weight value β is greater than or equal to C 2 (eg 0.43) and less than C 1 (eg 0.666), then by dividing the fraction S 2 (eg ) and the first weight value β (ie, β = β + S 2 ) to adjust/update the first weight value β; if the first weight value β is greater than or equal to C 3 (eg 0.26) and less than C 2 (eg 0.43), by dividing the fraction S 3 (eg ) and the first weight value β (ie, β = β + S 3 ) to adjust/update the first weight value β; and if the first weight value β is less than C 3 (eg, 0.26), by adding the fraction S 4 (e.g. ) and the first weight value β (ie, β = β + S 4 ) to adjust/update the first weight value β.
在攻擊控制中(亦即能量位準EL不小於門檻值TH),3個從最大到最小的係數C 1、C 2、C 3(例如C 1= 0.666、C 2= 0.43、C 3= 0.26)用以對第一權重值β進行分類,以及4個從最大到最小的分數B 1、B 2、B 3、B 4(例如B 1= 、B 2= 、B 3= 、B 4= )用以設定攻擊率設置AR以供斜率調整之用,但是本發明不限於此。如果第一權重值β大於或等於C 1(例如0.666),則藉由從第一權重值β減去分數B 1(例如 ),亦即β = β - B 1,來調整/更新第一權重值β;如果第一權重值β大於或等於C 2(例如0.43)並且小於C 1(例如0.666),則藉由從第一權重值β減去分數B 2(例如 ),亦即β = β - B 2,來調整/更新第一權重值β;如果第一權重值β大於或等於C 3(例如0.26)並且小於C 2(例如0.43),則藉由從第一權重值β減去分數B 3(例如 ),亦即β = β – B 3,來調整/更新第一權重值β;以及如果第一權重值β小於C 3(例如0.26),則藉由從第一權重值β減去分數B 4(例如 ),亦即β = β – B 4,來調整/更新第一權重值β。 In attack control (that is, the energy level EL is not less than the threshold value TH), three coefficients C 1 , C 2 , and C 3 from the largest to the smallest (for example, C 1 = 0.666, C 2 = 0.43, C 3 = 0.26 ) to classify the first weight value β, and 4 scores B 1 , B 2 , B 3 , B 4 from largest to smallest (eg B 1 = , B 2 = , B 3 = , B 4 = ) is used to set the attack rate setting AR for slope adjustment, but the present invention is not limited to this. If the first weight value β is greater than or equal to C 1 (eg 0.666), then by subtracting the fraction B 1 (eg 0.666) from the first weight value β ), that is, β = β - B 1 , to adjust/update the first weight value β; if the first weight value β is greater than or equal to C 2 (eg 0.43) and less than C 1 (eg 0.666), then by A weight value β minus the fraction B 2 (eg ), that is, β = β - B 2 , to adjust/update the first weight value β; if the first weight value β is greater than or equal to C 3 (eg 0.26) and less than C 2 (eg 0.43), then by A weight value β minus the fraction B 3 (eg ), ie β = β - B 3 , to adjust/update the first weight value β; and if the first weight value β is less than C 3 (eg, 0.26), by subtracting the fraction B 4 from the first weight value β (E.g ), that is, β = β – B 4 , to adjust/update the first weight value β.
在攻擊控制或釋放控制中,分數的分子係從最大到最小而不是全部相同(例如分數的分子均為1)之目的在於以使第一權重值β的整個控制範圍具有相對線性速率控制,此外,可以使第一權重值β的控制速度均勻。舉例來說,釋放率設置RR包含有S 1、S 2、S 3、S 4,可以被設置為 、 、 、 而不是 、 、 、 ;以及攻擊率設置AR包含有B 1、B 2、B 3、B 4,可以被設置為 、 、 、 而不是 、 、 、 。應注意的是,在本實施例中,攻擊率設置AR通常大於釋放率設置RR。 In attack control or release control, the numerators of the fractions are run from largest to smallest rather than all the same (eg, the numerators of the fractions are all 1) in order to have a relatively linear rate control over the entire control range of the first weight value β, and in addition , the control speed of the first weight value β can be made uniform. For example, the release rate setting RR includes S 1 , S 2 , S 3 , S 4 , and can be set as , , , instead of , , , ; and the attack rate setting AR contains B 1 , B 2 , B 3 , B 4 , and can be set as , , , instead of , , , . It should be noted that, in this embodiment, the attack rate setting AR is generally greater than the release rate setting RR.
在釋放控制中,4個分數S 1、S 2、S 3、S 4(例如S 1= 、S 2= 、S 3= 、S 4= )的分母,尤指分母的次方項(例如2的次方項諸如17),用以控制釋放率,分母的次方項越大,則釋放率愈大,舉例來說,當分母的次方項係為18時的控制率大於當分母的次方項係為16時的控制率。相似地,在攻擊控制中,4個分數B 1、B 2、B 3、B 4(例如B 1= 、B 2= 、B 3= 、B 4= )的分母的次方項也用以控制攻擊率。 In release control, 4 fractions S 1 , S 2 , S 3 , S 4 (eg S 1 = , S 2 = , S 3 = , S 4 = ), especially the power term of the denominator (for example, the power term of 2 such as 17) is used to control the release rate. The larger the power term of the denominator, the greater the release rate. The control rate when the square term is 18 is greater than that when the power term of the denominator is 16. Similarly, in attack control, the 4 fractions B 1 , B 2 , B 3 , B 4 (eg B 1 = , B 2 = , B 3 = , B 4 = ) to the power of the denominator is also used to control the attack rate.
應注意的是,權重控制電路200僅作為在參數等化器10中之權重控制電路22的範例說明之用,實際上,任何能夠根據等化器輸出訊號EQ_OUT來動態地調整第一權重值β以及第二權重值1-β的電路架構均可被權重控制電路22所採用,而這些替代設計均落入本發明的涵蓋範圍。It should be noted that the weight control circuit 200 is only used as an example to illustrate the
第3圖為依據本發明一實施例之第1圖所示之參數等化器10之不同增益值設置在不同權重值組合下的示意圖。參數等化器電路12以及參數等化器電路14分別被配置為具有有著+12分貝正增益之轉移函數H
1以及品質因數Q
P的一尖峰濾波器以及具有有著-6分貝負增益之轉移函數H
2以及品質因數Q
N的一陷波濾波器,並且參數等化器電路12的中心頻率
赫茲(hertz, Hz)與參數等化器電路14的中心頻率
赫茲相同。藉由上述轉移函數H
1以及轉移函數H
2的權重值組合,參數等化器10可以達到任何介於+12分貝至-6分貝的增益值,其中品質因數Q
N與品質因數Q
P之比值係為一預定常數(例如
)。
FIG. 3 is a schematic diagram illustrating that different gain values of the
如第3圖所示,藉由斜率調整來直接地控制權重值(例如第一權重值β以及第二權重值1-β之中的其中一個;為了更好地理解,所控制的是第一權重值β)以取得64條頻率響應曲線,頻率響應曲線的數量可以根據精準度來決定,因此,64條頻率響應曲線僅作為範例說明之用,本發明並不以此為限。當β等於1時,參數等化器10可視為具有有著+12分貝正增益之轉移函數H
1的尖峰濾波器(亦即第3圖中最上面的頻率響應曲線);以及當β等於0時,參數等化器10可視為具有有著-6分貝負增益之轉移函數H
2的陷波濾波器(亦即第3圖中最下面的頻率響應曲線),此外,第3圖中的響應曲線均為平滑曲線,其導致當使用參數等化器10時有著較少的訊號變化以及較少的功率變化。
As shown in Fig. 3, the weight value (for example, one of the first weight value β and the second weight value 1-β is directly controlled by the slope adjustment; for better understanding, the first weight value is controlled The weight value β) is used to obtain 64 frequency response curves. The number of frequency response curves can be determined according to the accuracy. Therefore, the 64 frequency response curves are only used for illustration purposes, and the present invention is not limited thereto. When β is equal to 1, the
第4圖為依據本發明一實施例之第1圖所示之參數等化器10所達到的增益值以及第1圖所示之參數等化器10所使用的權重值之間的關係示意圖。假設參數等化器電路12以及參數等化器電路14分別被配置為具有有著+12分貝正增益之轉移函數H
1以及品質因數Q
P的一尖峰濾波器以及具有有著-6分貝負增益之轉移函數H
2以及品質因數Q
N的一陷波濾波器,並且參數等化器電路12的中心頻率
赫茲與參數等化器電路14的中心頻率
赫茲相同。藉由上述轉移函數H
1以及轉移函數H
2的權重值組合,參數等化器10可以達到任何介於+12分貝至-6分貝的增益值,其中品質因數Q
N與品質因數Q
P之比值係為一預定常數(例如
)。
FIG. 4 is a schematic diagram illustrating the relationship between the gain value achieved by the
在上述釋放控制(或攻擊控制)中,4個分數
、
、
、
(或
、
、
、
)用以在第4圖中為斜率調整來設置釋放率設置RR(或攻擊率設置AR),此外,3個係數0.666、0.43以及0.26用以分類權重值(例如第一權重值β以及第二權重值1-β之中的其中一個;為了更好地理解,在此為第一權重值β)。在本實施例中,在4個區間中(亦即0≦β<0.26、0.26≦β<0.43、0.43≦β<0.666以及0.666≦β<1)大約取得4個斜率值,再者,該些分數的分子由這4個斜率值來決定,如第4圖所示,藉由將釋放率設置RR以及攻擊率設置AR的分數之分子設置為4到1而不是全部相同(例如分數之分子均為1),代表第1圖所示之參數等化器10所達到的自+12分貝至-6分貝的增益值以及權重值(例如第一權重值β)之間的關係之曲線可以為一平滑曲線,因此,權重值(例如第一權重值β)的整體控制範圍有著相對線性速度控制,此外,可以使權重值(例如第一權重值β)的控制速度均勻。
In the above release control (or attack control), 4 points , , , (or , , , ) is used to set the release rate setting RR (or attack rate setting AR) for slope adjustment in Figure 4, in addition, 3 coefficients 0.666, 0.43 and 0.26 are used to classify weight values (eg the first weight value β and the second weight value β and the second One of the weight values 1-β; for better understanding, here is the first weight value β). In this embodiment, approximately four slope values are obtained in four intervals (ie, 0≦β<0.26, 0.26≦β<0.43, 0.43≦β<0.666, and 0.666≦β<1). The numerator of the fraction is determined by these 4 slope values, as shown in Figure 4, by setting the numerator of the fraction for the release rate setting RR and the attack rate setting AR to be 4 to 1 instead of all being the same (e.g. is 1), the curve representing the relationship between the gain value from +12 dB to -6 dB and the weight value (for example, the first weight value β) achieved by the
第5圖為依據本發明另一實施例之第1圖所示之參數等化器10之不同增益值設置在不同權重值組合下的示意圖。假設參數等化器電路12以及參數等化器電路14分別被配置為具有有著+12分貝正增益之轉移函數H
1以及品質因數Q
P的一尖峰濾波器以及具有有著-12分貝負增益之轉移函數H
2以及品質因數Q
N的一陷波濾波器,並且參數等化器電路12的中心頻率
赫茲與參數等化器電路14的中心頻率
赫茲相同。藉由上述轉移函數H
1以及轉移函數H
2的權重值組合,參數等化器10可以達到任何介於+12分貝至-12分貝的增益值,其中品質因數Q
N與品質因數Q
P之比值係為一預定常數(例如
)。為了簡潔起見,在此不再重複詳細描述本實施例。
FIG. 5 is a schematic diagram illustrating that different gain values of the
如第5圖所示,藉由斜率調整來直接地控制權重值(例如第一權重值β以及第二權重值1-β之中的其中一個;為了更好地理解,所控制的是第一權重值β)以取得64條頻率響應曲線,頻率響應曲線的數量可以根據精準度來決定,因此,64條頻率響應曲線僅作為範例說明之用,本發明並不以此為限。當β等於1時,參數等化器10可視為具有有著+12分貝正增益之轉移函數H
1的尖峰濾波器(亦即第5圖中最上面的頻率響應曲線);以及當β等於0時,參數等化器10可視為具有有著-12分貝負增益之轉移函數H
2的陷波濾波器(亦即第3圖中最下面的頻率響應曲線),此外,第5圖中的響應曲線均為平滑曲線,其導致當使用參數等化器10時有著較少的訊號變化以及較少的功率變化。
As shown in Fig. 5, the weight value (for example, one of the first weight value β and the second weight value 1-β is directly controlled by the slope adjustment; for better understanding, the first weight value is controlled The weight value β) is used to obtain 64 frequency response curves. The number of frequency response curves can be determined according to the accuracy. Therefore, the 64 frequency response curves are only used for illustration purposes, and the present invention is not limited thereto. When β is equal to 1, the
第6圖為依據本發明另一實施例之第1圖所示之參數等化器10所達到的增益值以及第1圖所示之參數等化器10所使用的權重值之間的關係示意圖。假設參數等化器電路12以及參數等化器電路14分別被配置為具有有著+12分貝正增益之轉移函數H
1以及品質因數Q
P的一尖峰濾波器以及具有有著-12分貝負增益之轉移函數H
2以及品質因數Q
N的一陷波濾波器,並且參數等化器電路12的中心頻率
赫茲與參數等化器電路14的中心頻率
赫茲相同。藉由上述轉移函數H
1以及轉移函數H
2的權重值組合,參數等化器10可以達到任何介於+12分貝至-12分貝的增益值,其中品質因數Q
N與品質因數Q
P之比值係為一預定常數(例如
)。
FIG. 6 is a schematic diagram showing the relationship between the gain value achieved by the
在上述釋放控制(或攻擊控制)中,4個分數
、
、
、
(或
、
、
、
)用以在第6圖中為斜率調整來設置釋放率設置RR(或攻擊率設置AR),此外,3個係數0.666、0.43以及0.26用以分類權重值(例如第一權重值β以及第二權重值1-β之中的其中一個;為了更好地理解,在此為第一權重值β)。在本實施例中,在4個區間中(亦即0≦β<0.26、0.26≦β<0.43、0.43≦β<0.666以及0.666≦β<1)大約取得4個斜率值,再者,該些分數的分子由這4個斜率值來決定,如第6圖所示,藉由將釋放率設置RR以及攻擊率設置AR的分數之分子設置為4到1而不是全部相同(例如分數之分子均為1),代表第1圖所示之參數等化器10所達到的自+12分貝至-12分貝的增益值以及權重值(例如第一權重值β)之間的關係之曲線可以為一平滑曲線,因此,權重值(例如第一權重值β)的整體控制範圍有著相對線性速度控制,此外,可以使權重值(例如第一權重值β)的控制速度均勻。
In the above release control (or attack control), 4 points , , , (or , , , ) is used to set the release rate setting RR (or the attack rate setting AR) for the slope adjustment in Figure 6, in addition, 3 coefficients 0.666, 0.43 and 0.26 are used to classify the weight values (such as the first weight value β and the second weight value β and the second One of the weight values 1-β; for better understanding, here is the first weight value β). In this embodiment, approximately four slope values are obtained in four intervals (ie, 0≦β<0.26, 0.26≦β<0.43, 0.43≦β<0.666, and 0.666≦β<1). The numerator of the fraction is determined by these 4 slope values, as shown in Figure 6, by setting the numerator of the fraction for the release rate setting RR and the attack rate setting AR to be 4 to 1 instead of all being the same (e.g. is 1), the curve representing the relationship between the gain value from +12 dB to -12 dB and the weight value (for example, the first weight value β) achieved by the
第7圖為依據本發明一實施例之在輸入訊號A_IN係為第1圖所示之參數等化器10之帶內訊號(in-band signal)的情況下,輸入訊號A_IN、等化器輸出訊號EQ_OUT、等化器輸出訊號EQ_OUT的能量位準EL以及第一權重值β的示意圖。在本實施例中,輸入訊號A_IN的頻率係為200赫茲,並且參數等化器10的中心頻率也係為200赫茲,因此,輸入訊號A_IN位於參數等化器10之頻帶內,如第7圖所示,參數等化器10可以藉由斜率調整來控制權重值(例如第一權重值β以及第二權重值1-β之中的其中一個;為了更好地理解,第一權重值β)以產生等化器輸出訊號EQ_OUT,當等化器輸出訊號EQ_OUT的能量位準EL小於門檻值TH時,等化器輸出訊號EQ_OUT可以藉由釋放控制來被釋放,或當等化器輸出訊號EQ_OUT的能量位準EL不小於門檻值TH時,等化器輸出訊號EQ_OUT可以藉由攻擊控制來被壓抑。FIG. 7 shows the input signal A_IN and the output of the equalizer when the input signal A_IN is the in-band signal of the
第8圖為依據本發明另一實施例之在輸入訊號A_IN係為第1圖所示之參數等化器之帶外訊號(out-of-band signal)的情況下,輸入訊號A_IN、等化器輸出訊號EQ_OUT、等化器輸出訊號EQ_OUT的能量位準EL以及第一權重值β的示意圖。在本實施例中,輸入訊號A_IN的頻率係為5000赫茲,並且參數等化器10的中心頻率係為200赫茲,因此,輸入訊號A_IN係為參數等化器10之帶外訊號,如第8圖所示,雖然參數等化器10可以藉由斜率調整來控制權重值(例如第一權重值β以及第二權重值1-β之中的其中一個;為了更好地理解,在此為第一權重值β)以產生等化器輸出訊號EQ_OUT,但是等化器輸出訊號EQ_OUT與輸入訊號A_IN相同,因此,當輸入訊號A_IN係為參數等化器10之帶外訊號時,參數等化器10對輸入訊號A_IN不起作用。FIG. 8 shows the input signal A_IN, the equalization signal under the condition that the input signal A_IN is the out-of-band signal of the parameter equalizer shown in FIG. 1, according to another embodiment of the present invention. A schematic diagram of the output signal EQ_OUT of the equalizer, the energy level EL of the output signal EQ_OUT of the equalizer, and the first weight value β. In this embodiment, the frequency of the input signal A_IN is 5000 Hz, and the center frequency of the
第9圖為依據本發明一實施例之操作在掃頻(sweep frequency)上之第1圖所示之參數等化器10的示意圖。頻率從20千赫茲(kHz)掃描至20赫茲,並且參數等化器10之中心頻率係為2千赫茲,如第9圖所示,參數等化器10僅作用在2千赫茲上。FIG. 9 is a schematic diagram of the
第10圖為依據本發明另一實施例之操作在掃頻上之第1圖所示之參數等化器10的示意圖。頻率從20千赫茲掃描至20赫茲,並且參數等化器10之中心頻率係為5千赫茲,如第10圖所示,參數等化器10僅作用在5千赫茲上。FIG. 10 is a schematic diagram of the
回到第3圖,本發明所揭露的用來動態地調整權重值以等化輸入訊號A_IN之方法可達到兩個效果:類型I調整以及類型II調整。第11圖為利用本發明方法之後的輸入訊號之類型I調整的輸出頻率響應的示意圖。第12圖為利用本發明方法之後的輸入訊號之類型II調整的輸出頻率響應的示意圖。Returning to FIG. 3 , the method for dynamically adjusting the weight value to equalize the input signal A_IN disclosed in the present invention can achieve two effects: type I adjustment and type II adjustment. FIG. 11 is a schematic diagram of the output frequency response of the Type I adjustment of the input signal after using the method of the present invention. FIG. 12 is a schematic diagram of the output frequency response of the Type II adjustment of the input signal after using the method of the present invention.
請參照第11圖,類型I調整的實施例可參考第2圖以及第3圖,在類型I調整中,當能量位準EL大於門檻值TH時,第一權重值β被設置為不小於0.1432,此外,當第一權重值β等於0.1432時,輸出增益等於0分貝,因此,在類型I調整中,當輸入位準大於一預定門檻值(於第11圖中標示為“門檻”)時,在一特定頻率(例如本發明之參數等化器的中心頻率)下輸出增益保持不變。Please refer to FIG. 11, and the embodiment of Type I adjustment can refer to FIG. 2 and FIG. 3. In Type I adjustment, when the energy level EL is greater than the threshold value TH, the first weight value β is set to not less than 0.1432 , in addition, when the first weight value β is equal to 0.1432, the output gain is equal to 0 dB. Therefore, in Type I adjustment, when the input level is greater than a predetermined threshold value (marked as "threshold" in Figure 11), The output gain remains constant at a specific frequency (eg, the center frequency of the parametric equalizer of the present invention).
請參照第12圖,類型II調整的實施例可參考第2圖以及第3圖,在類型II調整中,當能量位準EL大於門檻值TH時,第一權重值β被設置為0,因此,在類型II調整中,當輸入位準大於一預定門檻值(於第12圖中標示為“門檻”)時,在一特定頻率(例如本發明之參數等化器的中心頻率)下輸出增益可以被衰減,以更進一步地避免訊號削波。Please refer to FIG. 12, and the embodiment of the type II adjustment can refer to FIG. 2 and FIG. 3. In the type II adjustment, when the energy level EL is greater than the threshold value TH, the first weight value β is set to 0, so , in type II adjustment, when the input level is greater than a predetermined threshold value (marked as "threshold" in Figure 12), the output gain is at a specific frequency (such as the center frequency of the parametric equalizer of the present invention) can be attenuated to further avoid signal clipping.
第13圖為利用先前技術之參數等化器時之輸出頻率響應的示意圖。如第13圖所示,不論輸入/輸出訊號的大小,先前技術之參數等化器(標示為“PEQ”)具有固定的增益衰減,與先前技術之參數等化器相比,本發明之參數等化器具有許多變化,其可在一特定頻率(例如本發明之參數等化器的中心頻率)下改變輸出響應。FIG. 13 is a schematic diagram of the output frequency response when using the prior art parametric equalizer. As shown in Figure 13, the prior art parametric equalizer (marked as "PEQ") has a fixed gain attenuation regardless of the size of the input/output signal. Compared with the prior art parametric equalizer, the parametric equalizer of the present invention Equalizers have many variations that alter the output response at a particular frequency (eg, the center frequency of the parametric equalizer of the present invention).
第14圖為依據本發明一實施例之動態地調整權重值以等化輸入訊號A_IN之方法流程圖。假若可以得到相同的結果,則步驟不一定要完全遵照第14圖所示的流程來依序執行,舉例來說,第14圖所示之方法可由第1圖所示之參數等化器10來加以實現。FIG. 14 is a flowchart of a method for dynamically adjusting the weight value to equalize the input signal A_IN according to an embodiment of the present invention. If the same result can be obtained, the steps do not have to be executed in sequence according to the flow shown in Fig. 14. For example, the method shown in Fig. 14 can be performed by the
在步驟S60中,輸入訊號A_IN被參數等化器接收。In step S60, the input signal A_IN is received by the parameter equalizer.
在步驟S62中,輸入訊號A_IN被第一參數等化器電路處理以產生並且輸出第一輸出訊號A_OUT_1。In step S62, the input signal A_IN is processed by the first parameter equalizer circuit to generate and output the first output signal A_OUT_1.
在步驟S64中,輸入訊號A_IN被第二參數等化器電路處理以產生並且輸出第二輸出訊號A_OUT_2。In step S64, the input signal A_IN is processed by the second parameter equalizer circuit to generate and output the second output signal A_OUT_2.
在步驟S66中,將第一輸出訊號A_OUT_1與第一權重值β相乘以產生第一調整訊號AD_OUT_1。In step S66, the first output signal A_OUT_1 is multiplied by the first weight value β to generate the first adjustment signal AD_OUT_1.
在步驟S68中,將第二輸出訊號A_OUT_2與第二權重值1-β相乘以產生第二調整訊號AD_OUT_2。In step S68, the second output signal A_OUT_2 is multiplied by the second weight value 1-β to generate a second adjustment signal AD_OUT_2.
在步驟S70中,將第一調整訊號AD_OUT_1與第二調整訊號AD_OUT_2結合以產生等化器輸出訊號EQ_OUT。In step S70, the first adjustment signal AD_OUT_1 and the second adjustment signal AD_OUT_2 are combined to generate the equalizer output signal EQ_OUT.
在步驟S72中,根據等化器輸出訊號EQ_OUT來動態地調整第一權重值β以及第二權重值1-β。In step S72, the first weight value β and the second weight value 1-β are dynamically adjusted according to the equalizer output signal EQ_OUT.
由於熟習技藝者可透過有關第1圖所示之參數等化器10的說明書內容而輕易瞭解第14圖所示各步驟的操作,為了簡明起見,於本實施例中類似的內容在此不重複贅述。
以上所述僅為本發明之較佳實施例,凡依本發明申請專利範圍所做之均等變化與修飾,皆應屬本發明之涵蓋範圍。
Since those skilled in the art can easily understand the operation of each step shown in FIG. 14 through the description of the
10,PEQ:參數等化器
12,14:參數等化器電路
16,18:乘法電路
20:加法電路
22:權重控制電路
A_IN:輸入訊號
A_OUT_1:第一輸出訊號
A_OUT_2:第二輸出訊號
AD_OUT_1:第一調整輸出訊號
AD_OUT_2:第二調整輸出訊號
β第一權重值
1-β:第二權重值
EQ_OUT:等化器輸出訊號
200:權重控制電路
24:能量偵測電路
26:權重值產生器
28:絕對值電路
30:阿爾發濾波器
AV:絕對值
EL:能量位準
TH:門檻值
RTH:參考門檻值
AR:攻擊率設置
RR:釋放率設置
S60~S72:步驟10, PEQ:
第1圖為依據本發明一實施例之參數等化器的示意圖。 第2圖為依據本發明一實施例之權重控制電路的示意圖。 第3圖為依據本發明一實施例之第1圖所示之參數等化器之不同增益值設置在不同權重值組合下的示意圖。 第4圖為依據本發明一實施例之第1圖所示之參數等化器所達到的增益以及第1圖所示之參數等化器所使用的權重值之間的關係示意圖。 第5圖為依據本發明另一實施例之第1圖所示之參數等化器之不同增益值設置在不同權重值組合下的示意圖。 第6圖為依據本發明另一實施例之第1圖所示之參數等化器所達到的增益值以及第1圖所示之參數等化器所使用的權重值之間的關係示意圖。 第7圖為依據本發明一實施例之在輸入訊號係為第1圖所示之參數等化器之帶內訊號的情況下,輸入訊號、等化器輸出訊號、等化器輸出訊號的能量位準以及權重值的示意圖。 第8圖為依據本發明另一實施例之在輸入訊號係為第1圖所示之參數等化器之帶外訊號的情況下,輸入訊號、等化器輸出訊號、等化器輸出訊號的能量位準以及權重值的示意圖。 第9圖為依據本發明一實施例之操作在掃頻上之第1圖所示之參數等化器的示意圖。 第10圖為依據本發明另一實施例之操作在掃頻上之第1圖所示之參數等化器的示意圖。 第11圖為利用本發明方法之後的輸入訊號之類型I調整的輸出頻率響應的示意圖。 第12圖為利用本發明方法之後的輸入訊號之類型II調整的輸出頻率響應的示意圖。 第13圖為利用先前技術之參數等化器時之輸出頻率響應的示意圖。 第14圖為依據本發明一實施例之動態地調整權重值以等化輸入訊號之方法流程圖。 FIG. 1 is a schematic diagram of a parameter equalizer according to an embodiment of the present invention. FIG. 2 is a schematic diagram of a weight control circuit according to an embodiment of the present invention. FIG. 3 is a schematic diagram illustrating that different gain values of the parameter equalizer shown in FIG. 1 are set under different weight value combinations according to an embodiment of the present invention. FIG. 4 is a schematic diagram illustrating the relationship between the gain achieved by the parameter equalizer shown in FIG. 1 and the weight value used by the parameter equalizer shown in FIG. 1 according to an embodiment of the present invention. FIG. 5 is a schematic diagram illustrating that different gain values of the parameter equalizer shown in FIG. 1 are set under different weight value combinations according to another embodiment of the present invention. FIG. 6 is a schematic diagram illustrating the relationship between the gain value achieved by the parameter equalizer shown in FIG. 1 and the weight value used by the parameter equalizer shown in FIG. 1 according to another embodiment of the present invention. FIG. 7 shows the energy of the input signal, the output signal of the equalizer, and the output signal of the equalizer when the input signal is the in-band signal of the parametric equalizer shown in FIG. 1 according to an embodiment of the present invention. Schematic diagram of level and weight value. FIG. 8 shows the input signal, the output signal of the equalizer, and the output signal of the equalizer when the input signal is an out-of-band signal of the parametric equalizer shown in FIG. 1 according to another embodiment of the present invention. Schematic diagram of energy levels and weight values. FIG. 9 is a schematic diagram of the parameter equalizer shown in FIG. 1 operating on a frequency sweep according to an embodiment of the present invention. FIG. 10 is a schematic diagram of the parameter equalizer shown in FIG. 1 operating on a frequency sweep according to another embodiment of the present invention. FIG. 11 is a schematic diagram of the output frequency response of the Type I adjustment of the input signal after using the method of the present invention. FIG. 12 is a schematic diagram of the output frequency response of the Type II adjustment of the input signal after using the method of the present invention. FIG. 13 is a schematic diagram of the output frequency response when using the prior art parametric equalizer. FIG. 14 is a flowchart of a method for dynamically adjusting weight values to equalize input signals according to an embodiment of the present invention.
10:參數等化器 10: Parameter equalizer
12,14:參數等化器電路 12,14: Parametric Equalizer Circuit
16,18:乘法電路 16,18: Multiplication circuit
20:加法電路 20: Addition circuit
22:權重控制電路 22: Weight control circuit
A_IN:輸入訊號 A_IN: input signal
A_OUT_1:第一輸出訊號 A_OUT_1: The first output signal
A_OUT_2:第二輸出訊號 A_OUT_2: The second output signal
AD_OUT_1:第一調整輸出訊號 AD_OUT_1: The first adjustment output signal
AD_OUT_2:第二調整輸出訊號 AD_OUT_2: The second adjustment output signal
β:第一權重值 β: the first weight value
1-β:第二權重值 1-β: The second weight value
EQ_OUT:等化器輸出訊號 EQ_OUT: Equalizer output signal
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TWI524706B (en) * | 2013-10-31 | 2016-03-01 | 晨星半導體股份有限公司 | Wireless communication receiver with i/q imbalance estimation and correction techniques |
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