TWI764551B - Resonant switching power converter - Google Patents

Abstract

The present invention provides a resonant switching power converter including: a first power stage circuit; a second power stage circuit; a controller; and a current sensing circuit configured to sense a first charging or discharging resonant current which flows through a first charging or discharging inductor of the first power stage circuit and sense a second charging or discharging resonant current which flows through a second charging or discharging inductor of the second power stage circuit, so as to generate corresponding first and second current sensing signals respectively, wherein the controller adjusts at least one of the following according to the first and second current sensing signals to render an output current of the first power stage circuit and an output current of the second power stage circuit in a specific ratio: a first delay time of a first charging process, a second delay time of a first discharging process, a third delay time of a second charging process, a fourth delay time of a second discharging process and two inputted voltages.

Description

Resonant Switching Power Converters

The present invention relates to a resonant switching power converter, in particular, to a resonant switching power converter capable of achieving current balance control.

FIG. 1 shows a conventional power converter. During the charging operation, the switches Q1, Q2, Q3, and Q4 are turned on, and the switches Q5, Q6, Q7, Q8, Q9, and Q10 are turned off, so that the capacitors C1, C2, and C3 are connected in series with each other between the input voltage Vin and the output voltage Vout. between. During the discharge operation, the switches Q5, Q6, Q7, Q8, Q9, and Q10 are turned on, and the switches Q1, Q2, Q3, and Q4 are turned off, so that the capacitors C1, C2, and C3 are connected in parallel between the ground potential and the output voltage Vout. . The capacitors and switches of this conventional power converter have very large inrush currents. Therefore, in other conventional power converters, inductors and capacitors are arranged at appropriate positions to form a resonant switching power converter, which can reduce inrush current. When the devices are operated in parallel, since the operation combination of the current has infinite solutions, if it is not properly controlled, the current will be unbalanced.

In view of this, the present invention addresses the above-mentioned shortcomings of the prior art, and proposes a resonant switching power converter capable of ensuring current balance when a plurality of converters are connected in parallel.

In one aspect, the present invention provides a resonant switching power converter for converting one or two input voltages into an output voltage, the resonant switching power converter comprising: a first power stage circuit comprising: a plurality of a first capacitor; at least one first charging inductor; at least one first discharging inductor; and a plurality of first switches for switching the corresponding plurality of first capacitors, the at least one first charging inductor and the at least one first discharging inductor The electrical connection relationship of the inductors; a second power stage circuit, comprising: a plurality of second capacitors; at least one second charging inductor; at least one second discharging inductor; and a plurality of second switches for switching the corresponding plurality of second capacitors the electrical connection relationship between the capacitor, the at least one second charging inductance and the at least one second discharging inductance; and a controller for periodically corresponding to a first charging process, a second charging process, at least a first charging process In a discharge procedure and at least one second discharge procedure, the corresponding plurality of first switches and the corresponding plurality of second switches are respectively operated; wherein, in the first charging procedure, the switching of the plurality of first switches is controlled to make The plurality of first capacitors and the at least one first charging inductor are connected in series between the one or two input voltages and the output voltage to form a first charging path; wherein, in the at least one first discharging process, control The switching of the plurality of first switches enables each of the first capacitors and the corresponding first discharge inductance to be connected in series between the output voltage and a ground potential, and simultaneously form or alternately form a plurality of first discharge paths; wherein, in the In the second charging procedure, the switching of the plurality of second switches is controlled, so that the plurality of second capacitors and the at least one second charging inductor are connected in series between the one or two input voltages and the output voltage to form a second A charging path; wherein, in the at least one second discharge procedure, the switching of the plurality of second switches is controlled, so that each of the second capacitors and the corresponding second discharge inductor are connected in series between the output voltage and a ground potential, A plurality of second discharge paths are formed simultaneously or alternately; wherein the controller is further configured to adjust at least one of the following according to a first current sensing signal and a second current sensing signal, so that the first power stage circuit The output current is proportional to the output current of the second power stage circuit: a first delay time, a second delay time, a third delay time and a fourth delay time, or the two input voltages; wherein the The first delay time is used to delay the starting time of the first charging process, the second delay time is used to delay the starting time of the at least one first discharging process, and the third delay time is used to delay the second charging process The fourth delay time is used to delay the start time of the at least one second discharge process; wherein the first current sensing signal is related to the at least one first charging inductor and/or the at least one first A first inductor current of the discharge inductor, wherein the second current sensing signal is related to the at least one second charging inductor and/or a second inductor current of the at least one second discharging inductor.

In one embodiment, the at least one first charging inductor is a first single charging inductor, the at least one first discharging inductor is a first single discharging inductor, and the at least one second charging inductor is a second single charging inductor , the at least one second discharge inductance is a second single discharge inductance.

In one embodiment, the at least one first charging inductance and the at least one first discharging inductance are a first single identical inductance, and the at least one second charging inductance and the at least one second discharging inductance are a second single identical inductance inductance.

In one embodiment, the controller includes at least one current sensing circuit, and the at least one current sensing circuit includes: at least one voltage sensing circuit for sensing the at least one first charging inductor and/or the at least one The voltage difference between the two ends of the first discharge inductor generates a first voltage sensing signal correspondingly, and is used to sense the voltage difference between the two ends of the at least one second charging inductor and/or the at least one second discharging inductor, and A second voltage sensing signal is correspondingly generated, wherein the first voltage sensing signal is related to the cross-voltage of a parasitic resistance of the at least one first charging inductor and/or the at least one first discharging inductor, and the second voltage sensing signal is The sensing signal is related to the cross-voltage of a parasitic resistance of the at least one second charging inductor and/or the at least one second discharging inductor; and at least one converting circuit is used for sensing the signal and the second voltage according to the first voltage The sensing signals respectively generate the first current sensing signal and the second current sensing signal.

In one embodiment, the controller further includes: an averaging circuit for averaging the first current sensing signal and the second current sensing signal to generate a current averaging signal; and at least one adjusting circuit , used to compare the current average signal with the first current sensing signal, and/or compare the current average signal with the second current sensing signal, and generate an adjustment signal, and adjust at least one of the following so that the The output current of the first power stage circuit is proportional to the output current of the second power stage circuit: the first delay time, the second delay time, the third delay time and the fourth delay time, or the two an input voltage.

In one embodiment, the fixed ratio is 1:1.

In one embodiment, the controller further includes: at least one delay circuit for generating the first delay time, the second delay time, the third delay time and/or the fourth delay time according to the adjustment signal , so that the output current of the first power stage circuit and the output current of the second power stage circuit have the fixed ratio.

In one embodiment, the controller adjusts at least one of the following to make the output current of the first power stage circuit and the output current of the second power stage circuit be the fixed ratio: when the first current sensing signal is greater than When the current average signal is used, the first delay time and/or the second delay time are extended; when the first current sensing signal is smaller than the current average signal, the first delay time and/or the second delay time are shortened ; when the second current sensing signal is greater than the current average signal, extend the third delay time and/or the fourth delay time; and/or when the second current sensing signal is less than the current average signal, shorten The third delay time and/or the fourth delay time.

In one embodiment, the two input voltages include a first input voltage and a second input voltage, respectively corresponding to the first power stage circuit and the second power stage circuit, wherein the controller adjusts at least one of the following , so that the output current of the first power stage circuit and the output current of the second power stage circuit have the fixed ratio: when the first current sensing signal is greater than the current average signal, reduce the first input voltage; When the first current sensing signal is less than the current average signal, increase the first input voltage; when the second current sensing signal is greater than the current average signal, decrease the second input voltage; and/or when the current average signal When the second current sensing signal is smaller than the current average signal, the second input voltage is increased.

In one embodiment, the first power stage circuit and the second power stage circuit alternately perform corresponding charging and discharging procedures.

In one embodiment, the resonant switching power converter is a bidirectional resonant switching power converter.

In one embodiment, the voltage conversion ratio of the one or two input voltages to the output voltage of the resonant switching power converter is 4:1, 3:1 or 2:1.

In yet another aspect, the present invention provides a resonant switching power converter for converting one or two input voltages into an output voltage, the resonant switching power converter comprising: a first power stage circuit, comprising: At least one first resonant cavity, the first resonant cavity has a first resonant capacitor and a first resonant inductor connected in series with each other; at least one first non-resonant capacitor; and a plurality of first switches, coupled to the at least one first The resonant cavity and the at least one first non-resonant capacitor are used to switch the electrical connection relationship between the corresponding first resonant cavity and the at least one first non-resonant capacitor, wherein in a first resonant process, the corresponding The first resonant cavity is resonantly charged, and in a second resonant process, the corresponding first resonant cavity is resonantly discharged, wherein the cross-voltage of the first non-resonant capacitor is maintained with the one or two input voltages a fixed ratio; a second power stage circuit, comprising: at least one second resonant cavity, the second resonant cavity has a second resonant capacitor and a second resonant inductance in series with each other; at least one second non-resonant capacitor; complex The second switch is coupled to the at least one second resonant cavity and the at least one second non-resonant capacitor, and is used for switching the electrical connection relationship between the corresponding second resonant cavity and the at least one second non-resonant capacitor, wherein In a third resonant process, the corresponding second resonant cavity is resonantly charged, and in a fourth resonant process, resonant discharge is performed on the corresponding second resonant cavity, wherein the second non-resonant capacitor The cross voltage is maintained at a fixed ratio with the one or two input voltages; and a controller is used for periodically corresponding to the first resonant process, the second resonant process, the third resonant process and the fourth resonant process. In the resonant procedure, the corresponding plurality of first switches and the corresponding plurality of second switches are respectively operated to perform corresponding resonant charging and resonant discharging; wherein the controller is further configured to sense a first current signal and a first Two current sensing signals to adjust at least one of the following, so that the output current of the first power stage circuit is proportional to the output current of the second power stage circuit: a first delay time, a second delay time, a The third delay time and a fourth delay time, or the two input voltages; wherein the first delay time is used to delay the start point of the first resonance process, and the second delay time is used to delay the second resonance process , the third delay time is used to delay the start time of the third resonance process, the fourth delay time is used to delay the start time of the fourth resonance process; wherein the first current sensing signal is related to A first inductor current of the first resonant inductor, wherein the second current sensing signal is related to a second inductor current of the second resonant inductor.

In one embodiment, the controller includes at least one current sensing circuit, and the at least one current sensing circuit includes: at least one voltage sensing circuit for sensing the voltage difference between the two ends of the first resonant inductor, and corresponding to A first voltage sensing signal is generated for sensing the voltage difference between the two ends of the second resonant inductor, and a second voltage sensing signal is correspondingly generated, wherein the first voltage sensing signal is related to the at least one first voltage sensing signal. a voltage across a parasitic resistance of a resonant inductor, the second voltage sensing signal is related to a voltage across a parasitic resistance of the at least one second resonant inductor; and at least one conversion circuit for sensing according to the first voltage The signal and the second voltage sensing signal respectively generate the first current sensing signal and the second current sensing signal.

One advantage of the present invention is that the present invention enables a resonant switching power converter with multiple power stage circuits to achieve current balance control without requiring an additional front-end voltage regulator for current balance control.

Another advantage of the present invention is that the present invention eliminates the need for additional current sensing resistors and reduces inrush current.

Yet another advantage of the present invention is that the present invention has higher efficiency compared to conventional power converters.

The following describes in detail with specific embodiments, when it is easier to understand the purpose, technical content, characteristics and effects of the present invention.

The drawings in the present invention are schematic, mainly intended to represent the coupling relationship between the circuits and the relationship between the signal waveforms, and the circuits, signal waveforms and frequencies are not drawn to scale.

FIG. 2 is a schematic circuit diagram showing a resonant switching power converter according to an embodiment of the present invention. As shown in FIG. 2 , the resonant switching power converter 20 of the present invention includes a first power stage circuit 201 and a second power stage circuit 202 . The first power stage circuit 201 and the second power stage circuit 202 are connected in parallel between the input voltage Vin and the output voltage Vout. The first power stage circuit 201 includes first capacitors C1, C2, C3, first switches Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8, Q9, Q10 and a first inductor L1. The first switches Q1-Q3 are respectively connected in series with the corresponding first capacitors C1-C3, and the first switch Q4 is connected in series with the first inductor L1. The first switches Q1-Q3 are respectively connected in series with the corresponding first capacitors C1-C3, and the first switch Q4 is connected in series with the first inductor L1.

The second power stage circuit 202 includes second capacitors C11 , C12 , C13 , second switches Q11 , Q12 , Q13 , Q14 , Q15 , Q16 , Q17 , Q18 , Q19 , Q20 , and a second inductor L11 . The second switches Q11-Q13 are respectively connected in series with the corresponding second capacitors C11-C13, and the second switch Q14 is connected in series with the second inductor L11. It should be noted that the number of capacitors in the resonant switching power converter of the present invention is not limited to three in this embodiment, but can also be two or more than four. The number of components shown in this embodiment is only for illustration. The present invention is not intended to limit the present invention. In one embodiment, the first inductor L1 and the second inductor L11 can be variable inductors.

As shown in FIG. 2 , one end of the first switch Q5 is coupled to the node between the first switch Q1 and the first capacitor C1, and one end of the first switch Q6 is coupled to the node between the first switch Q2 and the first capacitor C2 node, and one end of the first switch Q7 is coupled to the node between the first switch Q3 and the first capacitor C3. One end of the first switch Q8 is coupled to the node between the first capacitor C1 and the first switch Q2, one end of the first switch Q9 is coupled to the node between the first capacitor C2 and the first switch Q3, and the first switch One end of Q10 is coupled to the node between the first capacitor C3 and the first switch Q4. As shown in FIG. 2, after the other ends of the first switches Q5-Q7 are electrically connected to a node in common, they are coupled to the node between the first switch Q4 and the first inductor L1, and the other ends of the first switches Q8-Q10 are connected to the node between the first switch Q4 and the first inductor L1. Commonly coupled to ground potential. The other end of the first inductor L1 is coupled to the output voltage Vout, and the other end of the first switch Q1 is coupled to the input voltage Vin.

Referring to FIG. 2 again, one end of the second switch Q15 is coupled to the node between the second switch Q11 and the second capacitor C11, and one end of the second switch Q16 is coupled to the node between the second switch Q12 and the second capacitor C12. node, and one end of the second switch Q17 is coupled to the node between the second switch Q13 and the second capacitor C13. One end of the second switch Q18 is coupled to the node between the second capacitor C11 and the second switch Q12, one end of the second switch Q19 is coupled to the node between the second capacitor C12 and the second switch Q13, and the second switch One end of Q20 is coupled to the node between the second capacitor C13 and the second switch Q14. As shown in FIG. 2, after the other ends of the second switches Q15-Q17 are electrically connected to a node in common, they are coupled to the node between the second switch Q14 and the second inductor L11, and the other ends of the second switches Q18-Q20 are connected to the node between the second switch Q14 and the second inductor L11. Commonly coupled to ground potential. The other end of the second inductor L11 is coupled to the output voltage Vout, and the other end of the second switch Q11 is coupled to the input voltage Vin.

The controller 203 is used for generating a first charging operation signal G1A, a second charging operation signal G2A, at least one first discharging operation signal G1B and at least one second discharging operation signal G2B, respectively corresponding to a first charging procedure, A second charging process, at least one first discharging process and at least one second discharging process respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first switches Q1-Q10 respectively. The electrical connection relationship between a capacitor C1-C3 and the corresponding second capacitor C11-C13. FIG. 3 is a circuit schematic diagram showing a controller and a current sensing circuit in a resonant switching power converter according to an embodiment of the present invention, which shows an embodiment of the controller 203 and the current sensing circuit 204 of FIG. 2 . In one embodiment, the controller 203 further includes delay circuits 2033a and 2033b for delaying the starting time of the first charging process by a first delay time and/or the starting time of the at least one first discharging process by a first delay time. Two delay times are used to delay the start point of the second charging process a third delay time and/or the start point of the at least one second discharge process a fourth delay time.

Referring to FIG. 2 again, at least one current sensing circuit 204 is coupled to the first inductance L1 and coupled to the second inductance L11 for sensing a first inductance flowing through the first inductance L1 during the first charging process. A charging resonant current and/or a first discharging resonant current flowing through the first inductor L1 is sensed during the first discharging process, and a first current sensing signal I1 is correspondingly generated and used in the second charging process When sensing a second charging resonant current flowing through the second inductor L11 and/or sensing a second discharging resonant current flowing through the second inductor L11 during the second discharging process, a second current sensing Test signal I2. The controller 203 is coupled to the current sensing circuit 204 for adjusting at least one of the following according to the first current sensing signal I1 and the second current sensing signal I2, so that the output current of the first power stage circuit 201 is the same as the first current sensing signal I2. The output currents of the two power stage circuits 202 are in a fixed ratio: the first delay time, the second delay time, the third delay time and the fourth delay time.

The switch driver 205 is coupled between the controller 203 and the plurality of first switches Q1-Q10, and is coupled between the controller 203 and the plurality of second switches Q11-Q20, and is used for according to the first charging operation signal G1A or the second A discharge operation signal G1B controls the plurality of first switches Q1-Q10, and is used for controlling the plurality of second switches Q11-Q20 according to the second charge operation signal G2A or the second discharge operation signal G2B. Specifically, as shown in the figure, the plurality of switch drivers 205 respectively generate corresponding driving signals G1A according to the first charging operation signal G1A, the first discharging operation signal G1B, the second charging operation signal G2A and the second discharging operation signal G2B, respectively. ', G1B', G2A' and G2B' are used to drive the corresponding plurality of first switches Q1-Q10 and the plurality of second switches Q11-Q20. In one embodiment, the driving signals G1A', G1B', G2A' and G2B' and the corresponding first charging operation signal G1A, first discharging operation signal G1B, second charging operation signal G2A and second discharging operation signal G2B are respectively Corresponding to the same phase.

Referring to FIG. 2 again, the first switches Q1-Q10 can switch the power of the corresponding first capacitors C1-C3 and the first inductor L1 according to the first charging operation signal G1A and the first discharging operation signal G1B generated by the controller 203 . connection relationship. The second switches Q11-Q20 can switch the electrical connection relationship between the corresponding second capacitors C11-C13 and the second inductor L11 according to the second charging operation signal G2A and the second discharging operation signal G2B generated by the controller 203. In a first charging procedure, according to the first charging operation signal G1A and the first discharging operation signal G1B, the first switches Q1-Q4 are controlled to be turned on, and the first switches Q5-Q10 are controlled to be turned off, so that the first capacitor C1 -C3 are connected in series with each other and connected in series with the first inductor L1 between the input voltage Vin and the output voltage Vout to form a first charging path. In a first discharging procedure, according to the first charging operation signal G1A and the first discharging operation signal G1B, the first switches Q5-Q10 are controlled to be turned on, and the first switches Q1-Q4 are turned off, so that the first capacitor C1, the first A capacitor C2 and a first capacitor C3 are connected in parallel with each other and then connected in series with the first inductor L1 to form a plurality of first discharge paths.

Similarly, in a second charging procedure, according to the second charging operation signal G2A and the second discharging operation signal G2B, the second switches Q11-Q14 are controlled to be turned on, and the second switches Q15-Q20 are controlled to be turned off, so that the first The two capacitors C11-C13 are connected in series with each other and are connected in series with the second inductor L11 between the input voltage Vin and the output voltage Vout to form a second charging path. In a second discharge procedure, according to the second charging operation signal G2A and the second discharging operation signal G2B, the second switches Q15-Q20 are controlled to be turned on, and the second switches Q11-Q14 are turned off, so that the second capacitor C11, the second The two capacitors C12 and the second capacitor C13 are connected in parallel with each other and then the second inductor L11 is connected in series to form a plurality of second discharge paths.

It should be noted that the above-mentioned first charging procedure and the above-mentioned first discharging procedure are repeatedly performed in different time periods, but not simultaneously, and the above-mentioned second charging procedure and the above-mentioned second discharging procedure are repeated in different time periods. staggered, not simultaneously. Wherein, each of the first charging process and the first discharging process is repeatedly staggered and sequenced, and each of the second charging process and the second discharging process is repeatedly staggered and sequenced, so that the energy provided by the input voltage Vin, The capacitor and the inductor are charged in the charging process in the resonance mode, and the energy in the capacitor and the inductance is discharged in the discharging process in the resonance mode, and converted into the output voltage Vout. In this embodiment, the DC bias voltage of each of the first capacitors C1, C2, C3 and the second capacitors C11, C12, and C13 is Vo, so the first capacitors C1, C2, C3 and the second Capacitors C11, C12, and C13 need to withstand a lower rated voltage, so smaller capacitors can be used.

In one embodiment, the resonant switching power converter 20 can be a bidirectional resonant switching power converter. The so-called bidirectional resonant switching power converter means that the roles of the input terminal (providing the input voltage Vin) and the output terminal (providing the output voltage Vout) are reversed, which means that in the embodiment shown in FIG. 2, the resonant switching power conversion The converter 20 can convert the output voltage Vout to the input voltage Vin. In one embodiment, the voltage conversion ratio of the input voltage Vin to the output voltage Vout of the resonant switching power converter 20 may be 4:1, 3:1 or 2:1.

In one embodiment, the voltage conversion ratio of the resonant switching power converter 20 can be adjusted flexibly. When the first switches Q10 and Q4 are kept off, the voltage conversion ratio of the first power stage circuit 201 can be adjusted to 3:1. Similarly, for example, the first switch Q6 can be selected to be kept on, and the first switches Q9, Q3, Q7, Q10 and Q4 can be selected to be kept off, then the voltage conversion ratio of the first power stage circuit 201 can be adjusted to 2: 1. Similarly, for example, in the second charging process and the second discharging process, by selecting to keep the second switch Q7 on, and selecting to keep the second switches Q10 and Q4 off, the second power stage circuit 202 can be switched on. The voltage conversion ratio is adjusted to 3:1. Similarly, for example, the second switch Q6 can be selected to be kept on, and the second switches Q9, Q3, Q7, Q10, and Q4 can be selected to be kept off, so that the voltage conversion ratio of the second power stage circuit 202 can be adjusted to 2: 1.

Referring to FIG. 3 again, in one embodiment, the current sensing circuit 204 includes at least one voltage sensing circuit 2041a and 2041b. The voltage sensing circuit 2041a is used for sensing the voltage difference (L1A-L1B) between the two ends of the first inductor L1, and correspondingly generating a first voltage sensing signal. The voltage sensing circuit 2041b is used for sensing the voltage difference (L2A-L2B) between the two ends of the second inductor L11, and correspondingly generating a second voltage sensing signal. In one embodiment, the voltage sensing circuits 2041a and 2041b respectively include a resistor Rcs1 and a resistor Rcs2, which are respectively coupled to one side of the first inductor L1 and one side of the second inductor L11. The voltage sensing circuits 2041a and 2041b further include a capacitor Cs1 and a capacitor Cs2, which are respectively coupled to the other side of the first inductor L1 and the other side of the second inductor L11. As known to those skilled in the art, in one embodiment, the resistor Rcs1 , the resistor Rcs2 , the capacitor Cs1 , and the capacitor Cs2 of the voltage sensing circuits 2041 a and 2041 b can adopt the DCR current detection structure, so the related principles are omitted here. narration.

The current sensing circuit 204 further includes at least one converting circuit 2042a and 2042b, which are respectively coupled to the output ends of the at least one voltage sensing circuit 2041a and 2041b, and are used for sensing the first voltage and the second voltage sensing signal according to the The first current sensing signal I1 and the second current sensing signal I2 are correspondingly generated respectively. In one embodiment, at least one conversion circuit 2042a and 2042b can be a transconductance amplifier, respectively, to convert the first voltage sensing signal and the second voltage sensing signal into the first current according to the transduction value gm, respectively The sensing signal I1 and the second current sensing signal I2. The first current sensing signal I1 and the second current sensing signal I2 are proportional to the first inductor current IL1 and the second inductor current IL11 respectively.

It should be noted that the above-mentioned current sensing circuit 204 uses the DCR current detection structure as an embodiment, but this is not intended to limit the scope of the present invention. In other embodiments, other current detection methods can also be used to sense For the current of the first power stage circuit and the second power stage circuit, for example, a current sensing resistor can also be connected in series on the current path to sense the current, or to sense the voltage across the switch (such as Q4, Q7, Q14 and Q17, etc. ) to sense the current to obtain the corresponding current sensing signal, and the current balance can still be controlled by the aforementioned averaging and comparison, the same below.

In one embodiment, the aforementioned fixed ratio may be 1:1 to achieve current balance. In this embodiment, as shown in FIG. 3 , the controller 203 further includes an averaging circuit 2031 coupled to the at least one current sensing circuit 204 for the first current sensing signal I1 and the second current sensing signal I1 The measurement signal I2 is averaged to generate a current average signal Iavg. In this embodiment, the controller 203 may further include at least one adjustment circuit 2032a and 2032b, coupled to the averaging circuit 2031 and at least one current sensing circuit 204, for comparing the current average signal Iavg with the first current sensing signal I1 or The second current sensing signal I2 generates a delay time adjustment signal Ta1 and Ta2 to the delay circuits 2033a and 2033b, respectively. The delay circuits 2033a and 2033b modify the aforementioned first delay time and second delay time, or the third delay time and fourth delay time according to the delay time adjustment signals Ta1 and Ta2, respectively, to generate the first charging operation signal G1A and the first discharging operation signal G1A respectively. The operation signal G1B, the second charge operation signal G2A and the second discharge operation signal G2B are used to make the output current of the first power stage circuit 201 and the output current of the second power stage circuit 202 have the fixed ratio.

In one embodiment, when the first current sensing signal I1 is greater than the current average signal Iavg, the first delay time and/or the second delay time can be extended, and when the first current sensing signal I1 is less than the current average signal Iavg , the first delay time and/or the second delay time can be shortened. When the second current sensing signal I2 is greater than the current average signal Iavg, the third delay time and/or the fourth delay time can be extended, and when the second current sensing signal I2 is less than the current average signal Iavg, the third delay time can be shortened the delay time and/or the fourth delay time.

FIG. 4 is a schematic diagram showing signal waveforms of related signals of the first power stage circuit 201 of a resonant switching power converter 20 according to an embodiment of the present invention. The inductor current, the inductor voltage, the first charging operation signal G1A and the first discharging operation signal G1B are shown in FIG. 4 . It can be seen from FIG. 4 that td1 is the first delay time, and td2 is the second delay time. In this embodiment, prolonging the first delay time td1 and/or the second delay time td2 can reduce the first inductor current IL1, and conversely, shortening the first delay time td1 and/or the second delay time td2 can increase the first inductor current IL1 , so that the first inductor current IL1 and the second inductor current IL11 have the fixed ratio, and then the output current of the first power stage circuit 201 and the output current of the second power stage circuit 202 can have the fixed ratio. The operation principle of the second power stage circuit 202 is the same as that of the first power stage circuit 201, so it is omitted.

In one embodiment, the delay time in the first power stage circuit 201 and the second power stage circuit 202 can be adjusted at the same time, so that the output current of the first power stage circuit 201 and the output current of the second power stage circuit 202 are equal to each other. For the fixed ratio, in another embodiment, only the delay time of one of the first power stage circuit 201 and the second power stage circuit 202 can be adjusted, and the output current of the first power stage circuit 201 can also be adjusted to The output current of the second power stage circuit 202 is the fixed ratio.

FIG. 5 is a schematic circuit diagram showing a resonant switching power converter according to another embodiment of the present invention. The difference between this embodiment and the embodiment of FIG. 2 is that the power stage circuit of this embodiment is configured with a charging inductance and a discharging inductance on the charging path and the discharging path respectively. Specifically, the first power stage circuit 501 adopts a first power stage circuit 501. A charging inductor L3 and a first discharging inductor L2. The second power stage circuit 502 of this embodiment adopts a second charging inductor L13 and a second discharging inductor L12. The first power stage circuit 501 and the second power stage circuit 502 are connected in parallel between the input voltage Vin and the output voltage Vout.

As shown in FIG. 5, the first power stage circuit 501 of the resonant switching power converter 50 of the present invention includes first capacitors C1, C2, C3, first switches Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8, Q9, Q10, a first charging inductor L3 and a first discharging inductor L2, and the second power stage circuit 502 includes second capacitors C11, C12, C13, second switches Q11, Q12, Q13, Q14, Q15, Q16, Q17, Q18, Q19, Q20, a second charging inductor L13 and a second discharging inductor L12. The first switches Q1-Q3 are respectively connected in series with the corresponding first capacitors C1-C3, the first switch Q4 is connected in series with the first charging inductor L3, the second switches Q11-Q13 are respectively connected in series with the corresponding second capacitors C11-C13, and The second switch Q14 is connected in series with the second charging inductor L13. It should be noted that the number of capacitors in the resonant switching power converter of the present invention is not limited to three in this embodiment, but can also be two or more than four. The number of components shown in this embodiment is only for illustration. The present invention is not intended to limit the present invention. In one embodiment, the inductance value of the first charging inductor L3 can be equal to the inductance value of the first discharging inductor L2, and the inductance value of the second charging inductor L13 can be equal to the inductance value of the second discharging inductor L12. In another embodiment, the inductance value of the first charging inductance L3 and the inductance value of the first discharging inductance L2 can be configured in an appropriate ratio, so that the resonant frequencies of the charging process and the discharging process are equal. The operation principle of the second power stage circuit 202 is the same as that of the first power stage circuit 201, so it is omitted.

As shown in FIG. 5 , one end of the first switch Q5 is coupled to the node between the first switch Q1 and the first capacitor C1, and one end of the first switch Q6 is coupled to the node between the first switch Q2 and the first capacitor C2 node, and one end of the first switch Q7 is coupled to the node between the first switch Q3 and the first capacitor C3. One end of the first switch Q8 is coupled to the node between the first capacitor C1 and the first switch Q2, one end of the first switch Q9 is coupled to the node between the first capacitor C2 and the first switch Q3, and the first switch One end of Q10 is coupled to the node between the first capacitor C3 and the first switch Q4. As shown in FIG. 5 , after the other ends of the first switches Q5 - Q7 are electrically connected to a node in common, they are connected in series to the first discharge inductor L2 . The other ends of the first switches Q8-Q10 are commonly coupled to the ground potential. The other ends of the first charging inductor L3 and the first discharging inductor L2 are commonly coupled to the output voltage Vout, and the other end of the first switch Q1 is coupled to the input voltage Vin.

Similarly, as shown in FIG. 5, one end of the second switch Q15 is coupled to the node between the second switch Q11 and the second capacitor C11, and one end of the second switch Q16 is coupled to the second switch Q12 and the second capacitor C12 A node between the second switch Q17 and one end of the second switch Q17 is coupled to the node between the second switch Q13 and the second capacitor C13. One end of the second switch Q18 is coupled to the node between the second capacitor C11 and the second switch Q12, one end of the second switch Q19 is coupled to the node between the second capacitor C12 and the second switch Q13, and the second switch One end of Q20 is coupled to the node between the second capacitor C13 and the second switch Q14. As shown in FIG. 5 , after the other ends of the second switches Q15-Q17 are electrically connected to a node in common, they are connected in series to the second discharge inductor L12. The other ends of the second switches Q18-Q20 are commonly coupled to the ground potential. The other ends of the second charging inductor L13 and the second discharging inductor L12 are commonly coupled to the output voltage Vout, and the other end of the second switch Q11 is coupled to the input voltage Vin.

The controller 503 is used for generating a first charging operation signal G1A, a second charging operation signal G2A, at least one first discharging operation signal G1B and at least one second discharging operation signal G2B, respectively corresponding to a first charging procedure, A second charging process, at least one first discharging process and at least one second discharging process respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first switches Q1-Q10 respectively. The electrical connection relationship between a capacitor C1-C3 and the corresponding second capacitor C11-C13. In one embodiment, the controller 503 can also adopt the structure shown in FIG. 3 , for example, further comprising a delay circuit for delaying the start point of the first charging process by a first delay time and/or the at least one first delay time. The starting time of the discharging process is a second delay time, and is used to delay the starting time of the second charging process by a third delay time and/or the starting time of the at least one second discharging process by a fourth delay time.

Referring to FIG. 5 again, at least one current sensing circuit 504 is coupled to the first discharge inductance L2 and coupled to the second discharge inductance L12 for sensing the flow through the first discharge inductance L2 during the first discharge process a first discharge resonant current, and correspondingly generate a first current sensing signal I1, which is used for sensing a second discharge resonant current flowing through the second discharge inductor L12 during the second discharge process, and correspondingly generates a The second current sensing signal I2. It should be appreciated that, in another embodiment, at least one current sensing circuit 504 may also be coupled to the first charging inductor L3 and the second charging inductor L13 for sensing the flow through the first charging process during the first charging process. A first charging resonant current of a charging inductor L3 is used to sense a second charging resonant current flowing through the second charging inductor L13 during the second charging process, and correspondingly generate the first current sensing signal I1 and The second current sensing signal I2.

The controller 503 is coupled to the current sensing circuit 504, and is used for adjusting at least one of the following according to the first current sensing signal I1 and the second current sensing signal I2, so that the output current of the first power stage circuit 501 is the same as the first current sensing signal I2. The output currents of the two power stage circuits 502 are in a fixed ratio: the first delay time, the second delay time, the third delay time and the fourth delay time. The switch driver 505 is coupled between the controller 503 and the plurality of first switches Q1-Q10, and is coupled between the controller 503 and the plurality of second switches Q11-Q20, and is used for according to the first charging operation signal G1A or the second A discharge operation signal G1B controls the plurality of first switches Q1-Q10, and is used for controlling the plurality of second switches Q11-Q20 according to the second charge operation signal G2A or the second discharge operation signal G2B. In one implementation, the current sensing circuit 504 can also adopt the structure shown in FIG. 3 .

The first switches Q1-Q10 can switch the corresponding first capacitors C1-C3 and the first charging inductor L3 and the first discharging inductor L2 according to the first charging operation signal G1A and the first discharging operation signal G1B generated by the controller 503 the electrical connection. In a first charging procedure, according to the first charging operation signal G1A and the first discharging operation signal G1B, the first switches Q1-Q4 are controlled to be turned on, and the first switches Q5-Q10 are controlled to be turned off, so that the first capacitor C1 -C3 are connected in series with each other and connected in series with the first charging inductor L3 between the input voltage Vin and the output voltage Vout to form a first charging path. In a first discharging procedure, according to the first charging operation signal G1A and the first discharging operation signal G1B, the first switches Q5-Q10 are controlled to be turned on, and the first switches Q1-Q4 are turned off, so that the first capacitor C1, the first A capacitor C2 and a first capacitor C3 are connected in parallel with each other and then connected in series with the first discharge inductor L2 to form a plurality of first discharge paths.

Similarly, the second switches Q11-Q20 can switch the corresponding second capacitors C11-C13, the second charging inductor L13 and the second charging operation signal G2A and the second discharging operation signal G2B according to the second charging operation signal G2A and the second discharging operation signal G2B generated by the controller 503. The electrical connection relationship of the discharge inductor L12. In a second charging process, according to the second charging operation signal G2A and the second discharging operation signal G2B, the second switches Q11-Q14 are controlled to be turned on, and the second switches Q15-Q20 are controlled to be non-conductive, so that the second capacitor C11 -C13 are connected in series with each other and connected in series with the second charging inductor L13 between the input voltage Vin and the output voltage Vout to form a second charging path. In a second discharge procedure, according to the second charging operation signal G2A and the second discharging operation signal G2B, the second switches Q15-Q20 are controlled to be turned on, and the second switches Q11-Q14 are turned off, so that the second capacitor C11, the second The two capacitors C12 and the second capacitor C13 are connected in parallel with each other, and then the second discharge inductor L12 is connected in series to form a plurality of second discharge paths.

FIG. 6 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention. As shown in FIG. 6 , the resonant switching power converter 60 of the present invention includes a first power stage circuit 601 and a second power stage circuit 602 . The first power stage circuit 601 and the second power stage circuit 602 are connected in parallel between the input voltage Vin and the output voltage Vout. The first power stage circuit 601 includes first capacitors C1, C2, C3, first switches Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8, Q9, Q10 and first inductors L1, L2, L3. The second power stage circuit 602 includes second capacitors C11, C12, C13, second switches Q11, Q12, Q13, Q14, Q15, Q16, Q17, Q18, Q19, Q20, and second inductors L11, L12, L13. The first switches Q1-Q3 are respectively connected in series with the corresponding first capacitors C1-C3, and the first capacitors C1-C3 are respectively connected in series with the corresponding first inductors L1-L3. The second switches Q11-Q13 are respectively connected in series with the corresponding second capacitors C11-C13, and the second capacitors C11-C13 are respectively connected in series with the corresponding second inductors L11-L13. It should be noted that the number of capacitors in the resonant switching power converter of the present invention is not limited to three in this embodiment, but may also be two or more, and the number of inductors is not limited to three in this embodiment. , or more than two or four, the number of elements shown in this embodiment is only used to illustrate the present invention, but not to limit the present invention.

As shown in FIG. 6 , one end of the first switch Q5 is coupled to the node between the first switch Q1 and the first capacitor C1, and one end of the first switch Q6 is coupled to the node between the first switch Q2 and the first capacitor C2 node, and one end of the first switch Q7 is coupled to the node between the first switch Q3 and the first capacitor C3. One end of the first switch Q8 is coupled to the node between the first inductor L1 and the first switch Q2, one end of the first switch Q9 is coupled to the node between the first inductor L2 and the first switch Q3, and the first switch One end of Q10 is coupled to the node between the first inductor L3 and the first switch Q4. As shown in FIG. 6 , the other ends of the first switches Q5 - Q7 are commonly coupled to the output voltage Vout. The other ends of the first switches Q8-Q10 are commonly coupled to the ground potential. The first switch Q4 is coupled between the first inductor L3 and the output voltage Vout, and one end of the first switch Q1 is coupled to the input voltage Vin.

Similarly, one end of the second switch Q15 is coupled to the node between the second switch Q11 and the second capacitor C11, one end of the second switch Q16 is coupled to the node between the second switch Q12 and the second capacitor C12, and One end of the second switch Q17 is coupled to the node between the second switch Q13 and the second capacitor C13. One end of the second switch Q18 is coupled to the node between the second inductor L11 and the second switch Q12, one end of the second switch Q19 is coupled to the node between the second inductor L12 and the second switch Q13, and the second switch One end of Q20 is coupled to the node between the second inductor L13 and the second switch Q14. As shown in FIG. 6 , the other ends of the second switches Q15-Q17 are commonly coupled to the output voltage Vout. The other ends of the second switches Q18-Q20 are commonly coupled to the ground potential. The second switch Q14 is coupled between the second inductor L13 and the output voltage Vout, and one end of the second switch Q11 is coupled to the input voltage Vin.

The controller 603 is used for generating a first charging operation signal G1A, a second charging operation signal G2A, at least one first discharging operation signal G1B and at least one second discharging operation signal G2B, respectively corresponding to a first charging procedure, A second charging process, at least one first discharging process and at least one second discharging process respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first switches Q1-Q10 respectively. The electrical connection relationship between a capacitor C1-C3 and the corresponding second capacitor C11-C13. In one embodiment, the controller 603 can also adopt the structure shown in FIG. 3 , for example, further comprising a delay circuit for delaying the start point of the first charging process by a first delay time and/or the at least one first delay time. The starting time of the discharging process is a second delay time, and is used to delay the starting time of the second charging process by a third delay time and/or the starting time of the at least one second discharging process by a fourth delay time.

Referring to FIG. 6 again, at least one current sensing circuit 604 is coupled to the first inductor L3 and coupled to the second inductor L13 for sensing a first inductor flowing through the first inductor L3 during the first charging process. A charging resonant current and/or a first discharging resonant current flowing through the first inductor L3 is sensed during the first discharging process, and a first current sensing signal I1 is correspondingly generated, which is used in the second charging process When sensing a second charging resonant current flowing through the second inductor L13 and/or sensing a second discharging resonant current flowing through the second inductor L13 during the second discharging process, and correspondingly generating a second current sensing Test signal I2. It should be appreciated that, in another embodiment, at least one current sensing circuit 604 can also be coupled to the first inductor L2 and the second inductor L12 for sensing the flow through the first inductor during the first charging process A first charging resonant current of L2 and/or a first discharging resonant current flowing through the first inductor L2 is sensed during the first discharging process, and a first current sensing signal I1 is correspondingly generated, and used for During the second charging process, a second charging resonant current flowing through the second inductor L12 is sensed and/or a second discharging resonant current flowing through the second inductor L12 is sensed during the second discharging process, and correspondingly generate a The second current sensing signal I2.

In yet another embodiment, at least one current sensing circuit 604 can also be coupled to the first inductor L1 and the second inductor L11 for sensing a first charge flowing through the first inductor L1 during the first charging process. The resonant current and/or a first discharge resonant current flowing through the first inductor L1 is sensed during the first discharge process, and a first current sensing signal I1 is correspondingly generated, which is used for sensing during the second charge process Sensing a second charging resonant current flowing through the second inductor L11 and/or sensing a second discharging resonant current flowing through the second inductor L11 during the second discharging process, and correspondingly generating a second current sensing signal i2. The controller 603 is coupled to the current sensing circuit 604 for adjusting at least one of the following according to the first current sensing signal I1 and the second current sensing signal I2, so that the output current of the first power stage circuit 601 is the same as the first current sensing signal I2. The output currents of the two power stage circuits 602 are in a fixed ratio: the first delay time, the second delay time, the third delay time and the fourth delay time. The switch driver 605 is coupled between the controller 603 and the plurality of first switches Q1-Q10, and is coupled between the controller 603 and the plurality of second switches Q11-Q20, and is used for according to the first charging operation signal G1A or the second A discharge operation signal G1B controls the plurality of first switches Q1-Q10, and is used for controlling the plurality of second switches Q11-Q20 according to the second charge operation signal G2A or the second discharge operation signal G2B. In one implementation, the current sensing circuit 604 can also adopt the structure shown in FIG. 3 .

The first switches Q1-Q10 can switch the electrical connection relationship between the corresponding first capacitors C1-C3 and the first inductors L1-L3 according to the first charging operation signal G1A and the first discharging operation signal G1B generated by the controller 603 . In a first charging procedure, according to the first charging operation signal G1A and the first discharging operation signal G1B, the first switches Q1-Q4 are controlled to be turned on, and the first switches Q5-Q10 are controlled to be turned off, so that the first capacitor C1 -C3 and the first inductors L1-L3 are connected in series between the input voltage Vin and the output voltage Vout to form a first charging path. In a first discharging procedure, according to the first charging operation signal G1A and the first discharging operation signal G1B, the first switches Q5-Q10 are controlled to be turned on, and the first switches Q1-Q4 are not turned on, so that the first capacitor C1 and the corresponding The first inductor L1 is connected in series between the output voltage Vout and the ground potential, the first capacitor C2 and the corresponding first inductor L2 are connected in series between the output voltage Vout and the ground potential, and the first capacitor C3 and the corresponding first inductor L3 are connected in series with the output A plurality of first discharge paths are formed between the voltage Vout and the ground potential.

The second switches Q11-Q20 can switch the electrical connection relationship between the corresponding second capacitors C11-C13 and the second inductors L11-L13 according to the second charging operation signal G2A and the second discharging operation signal G2B generated by the controller 603 . In a second charging process, according to the second charging operation signal G2A and the second discharging operation signal G2B, the second switches Q11-Q14 are controlled to be turned on, and the second switches Q15-Q20 are controlled to be non-conductive, so that the second capacitor C11 -C13 and the second inductors L11-L13 are connected in series between the input voltage Vin and the output voltage Vout to form a second charging path. In a second discharging process, according to the second charging operation signal G2A and the second discharging operation signal G2B, the second switches Q15-Q20 are controlled to be turned on, and the second switches Q11-Q14 are not turned on, so that the second capacitor C11 and the corresponding The second inductor L11 is connected in series between the output voltage Vout and the ground potential, the second capacitor C12 and the corresponding second inductor L12 are connected in series between the output voltage Vout and the ground potential, and the second capacitor C13 and the corresponding second inductor L13 are connected in series with the output A plurality of second discharge paths are formed between the voltage Vout and the ground potential.

FIG. 7 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention. As shown in FIG. 7 , the resonant switching power converter 70 includes a first power stage circuit 701 and a second power stage circuit 702 . The first power stage circuit 701 and the second power stage circuit 702 are connected in parallel between the input voltage Vin and the output voltage Vout. The first power stage circuit 701 includes first resonant capacitors C1, C3, at least one first non-resonant capacitor C2, first switches Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8, Q9, Q10 and a first resonant Inductors L1, L2. The second power stage circuit 702 includes second resonant capacitors C11 , C13 , at least one second non-resonant capacitor C12 , second switches Q11 , Q12 , Q13 , Q14 , Q15 , Q16 , Q17 , Q18 , Q19 , Q20 and a second resonant Inductors L11, L12.

As shown in FIG. 7 , the controller 703 is used for generating a first resonance operation signal G1, a second resonance operation signal G2, a third resonance operation signal G3, and a fourth resonance operation signal G4, respectively corresponding to a first resonance procedure, A second resonant process, a third resonant process and a fourth resonant process operate the corresponding plural first switches Q1-Q10 and the corresponding plural second switches Q11-Q20 to switch the corresponding first resonant capacitor C1 , C3 and the electrical connection relationship of the first non-resonant capacitor C2 and the corresponding electrical connection relationship of the second resonant capacitors C11, C13 and the second non-resonant capacitor C12.

The resonant switching power converter 70 includes at least one first resonant cavity, such as first resonant cavities 706 and 707, the first resonant cavity 706 has a first resonant capacitor C1 and a first resonant inductor L1 connected in series with each other, and the first The resonant cavity 707 has a first resonant capacitor C3 and a first resonant inductor L2 connected in series with each other. The resonant switching power converter 70 further includes at least one second resonant cavity, such as second resonant cavities 708 and 709 , the second resonant cavity 708 has a second resonant capacitor C11 and a second resonant inductor L11 connected in series with each other, and the second resonant cavity 708 The two resonant cavities 709 have a second resonant capacitor C13 and a second resonant inductor L12 connected in series with each other. In one embodiment, the controller 703 can also adopt the structure shown in FIG. 3 , for example, further includes a delay circuit for delaying the start point of the first resonance process a first delay time and/or the second resonance process The start time point of the , a second delay time is used to delay the start time point of the third resonance process a third delay time and/or the start time point of the fourth resonance process a fourth delay time.

Referring to FIG. 7 again, at least one current sensing circuit 704 is coupled to the first resonant inductor L2 and coupled to the second resonant inductor L12 for sensing the flow through the first resonant inductor L2 during the first resonant process A first resonant current and/or a second resonant current flowing through the first resonant inductor L2 is sensed during the second resonant process, and a first current sensing signal I1 is correspondingly generated and used for the third A third resonant current flowing through the second resonant inductor L12 is sensed during the resonant process and/or a fourth resonant current flowing through the second resonant inductor L12 is sensed during the fourth resonant process, and a second resonant current is correspondingly generated. Current sensing signal I2. It should be appreciated that, in another embodiment, at least one current sensing circuit 704 may also be coupled to the first resonant inductor L1 and the second resonant inductor L11 for sensing the flow through the first resonant process during the first resonant process. A first resonant current of a resonant inductor L1 and/or a second resonant current flowing through the first resonant inductor L1 is sensed during the second resonant process, and a first current sensing signal I1 is correspondingly generated, and the In order to sense a third resonant current flowing through the second resonant inductor L11 during the third resonant process and/or sense a fourth resonant current flowing through the second resonant inductor L11 during the fourth resonant process, respectively corresponding to A second current sensing signal I2 is generated.

The controller 703 is coupled to the current sensing circuit 704 for adjusting at least one of the following according to the first current sensing signal I1 and the second current sensing signal I2, so that the output current of the first power stage circuit 701 is the same as the first current sensing signal I2. The output currents of the two power stage circuits 702 are in a fixed ratio: the first delay time, the second delay time, the third delay time and the fourth delay time. The switch driver 705 is coupled between the controller 703 and the plurality of first switches Q1-Q10, and is coupled between the controller 703 and the plurality of second switches Q11-Q20, and is used for operating according to the first resonance signal G1 or the second The two resonant operation signals G2 control the plurality of first switches Q1-Q10, and are used to control the plurality of second switches Q11-Q20 according to the third resonant operation signal G3 or the fourth resonant operation signal G4.

Specifically, the complex switch driver 705 as shown in the figure respectively generates the corresponding driving signal G1 according to the first resonance operation signal G1, the second resonance operation signal G2, the third resonance operation signal G3 and the fourth resonance operation signal G4 respectively ', G2', G3' and G4' are used to drive the corresponding plurality of first switches Q1-Q10 and the plurality of second switches Q11-Q20. In one embodiment, the driving signals G1', G2', G3' and G4' and the corresponding first resonance operation signal G1, second resonance operation signal G2, third resonance operation signal G3 and fourth resonance operation signal G4 are respectively Corresponding to the same phase.

In one implementation, the current sensing circuit 704 can also adopt the structure shown in FIG. 3 . The first resonant operation signal G1, the second resonant operation signal G2, the third resonant operation signal G3 and the fourth resonant operation signal G4 correspond to the first charging operation signal G1A, the first discharging operation signal G1B, the The two charging operation signals G2A and the second discharging operation signal G2B, and the driving signals G1', G2', G3' and G4' respectively correspond to the driving signals G1A', G1B', G2A' and G2B'.

The first switches Q1-Q10 are correspondingly coupled to at least one first resonant cavity 706, 707, and respectively switch the corresponding first resonant cavity according to a corresponding first resonant operation signal G1 and a second resonant operation signal G2 The electrical connection relationship between 706 and 707 corresponds to a first resonance process and a second resonance process. The second switches Q11-Q20 are coupled to at least one second resonant cavity 708, 709 correspondingly, and switch the corresponding second resonant cavity according to a corresponding third resonant operation signal G3 and a fourth resonant operation signal G4 respectively The electrical connection relationship between 708 and 709 corresponds to a third resonance process and a fourth resonance process. In the first resonance process, the corresponding resonant cavities 706 and 707 are resonantly charged, and in the second resonance process, the corresponding resonant cavities 706 and 707 are resonantly discharged. In the third resonance process, the corresponding resonant cavities 708 and 709 are resonantly charged, and in the fourth resonance process, the corresponding resonant cavities 708 and 709 are resonantly discharged.

At least one first non-resonant capacitor C2 is coupled to at least one first resonant cavity 706, 707, and the first resonant operation signal G1 and the second resonant operation signal G2 switch the first non-resonant capacitor C2 and the at least one first resonant The electrical connection relationship between the cavities 706 and 707 . At least one second non-resonant capacitor C12 is coupled to at least one second resonant cavity 708, 709, and the third resonance operation signal G3 and the fourth resonance operation signal G4 switch the second non-resonant capacitor C12 and the at least one second resonance The electrical connection relationship between the cavities 708 and 709 . The voltage across the first non-resonant capacitor C2 and the second non-resonant capacitor C12 is maintained at a constant ratio to the input voltage Vin, for example, half the input voltage Vin in this embodiment.

The first resonance process and the second resonance process are repeatedly interleaved with each other, and the third resonance process and the fourth resonance process are repeatedly interleaved with each other to convert the input voltage Vin into the output voltage Vout. The first resonant operation signal G1 and the second resonant operation signal G2 are respectively switched to a conduction level for a period of conduction, the third resonance operation signal G3 and the fourth resonance operation signal G4 are respectively switched to a conduction level for a period of conduction, And the plurality of on-time periods of the first resonant operation signal G1 and the second resonant operation signal G2 do not overlap each other, so that the first resonant process and the second resonant process do not overlap each other, the third resonant operation signal G3 and the fourth resonant operation signal G3 and the fourth The plurality of on-time periods of the resonant operation signal G4 do not overlap each other, so that the third resonant process and the fourth resonant process do not overlap each other.

In the first resonance process, according to the first resonance operation signal G1, the first switches Q1, Q3, Q5, Q8, and Q9 are turned on, and the first switches Q2, Q4, Q6, Q7, and Q10 are turned off, so that the first resonance is made. The first resonant capacitor C1 and the first resonant inductor L1 of the cavity 706 are connected in series between the input voltage Vin and the output voltage Vout, and make the first non-resonant capacitor C2 and the first resonant capacitor C3 and the first resonant capacitor of the first resonant cavity 707 resonate The inductor L2 is connected in series between the ground potential and the output voltage Vout to charge the first resonant capacitors C1 and C3 and discharge the first non-resonant capacitor C2. In the second resonance process, according to the second resonance operation signal G2, the first switches Q2, Q4, Q6, Q7, and Q10 are turned on, and the first switches Q1, Q3, Q5, Q8, and Q9 are turned off, so that the first non-conducting The resonant capacitor C2 and the first resonant capacitor C1 and the first resonant inductor L1 of the first resonant cavity 706 are connected in series between the ground potential and the output voltage Vout, and the first resonant capacitor C3 of the first resonant cavity 707 and the first resonant inductor L2 is connected in series between the ground potential and the output voltage Vout, and discharges the first resonant capacitors C1 and C3 and charges the first non-resonant capacitor C2.

In the third resonance process, according to the third resonance operation signal G3, the second switches Q11, Q13, Q15, Q18, and Q19 are turned on, and the second switches Q12, Q14, Q16, Q17, and Q20 are turned off, so that the second resonance is made. The second resonant capacitor C11 and the second resonant inductor L11 of the cavity 708 are connected in series between the input voltage Vin and the output voltage Vout, so that the second non-resonant capacitor C12 and the second resonant capacitor C13 and the second resonant capacitor of the second resonant cavity 709 resonate The inductor L12 is connected in series between the ground potential and the output voltage Vout to charge the second resonant capacitors C11 and C13 and discharge the second non-resonant capacitor C12. In the fourth resonance process, according to the fourth resonance operation signal G4, the second switches Q12, Q14, Q16, Q17, and Q20 are turned on, and the second switches Q11, Q13, Q15, Q18, and Q19 are turned off, so that the second non-conducting The resonant capacitor C12, the second resonant capacitor C11 and the second resonant inductor L11 of the second resonant cavity 708 are connected in series between the ground potential and the output voltage Vout, and the second resonant capacitor C13 of the second resonant cavity 709 and the second resonant inductor L12 is connected in series between the ground potential and the output voltage Vout, and discharges the second resonant capacitors C11 and C13, and charges the second non-resonant capacitor C12.

The operation of the resonant switching power converter 70 having the resonant cavities 706 , 707 , 708 and 709 shown in FIG. 7 is well known to those skilled in the art, and will not be repeated here.

FIG. 8 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention. The difference between this embodiment and FIG. 2 is that this embodiment uses two input voltages. For example, the first power stage circuit and the second power stage circuit respectively convert the input voltages Vin1 and Vin2 to generate the output voltage Vout. Embodiments employ one input voltage Vin. In one embodiment, the resonant switching power converter is configured as an interleaved power converter. That is, when the first power stage circuit 801 of the resonant switching power converter 80 is in the first charging process, the second power stage circuit 802 performs the second discharging process. Similarly, when the first power stage circuit 801 of the resonant switching power converter 80 is in the first discharging process, the second power stage circuit 802 performs the second charging process. In other words, when the first switches Q1 - Q4 receive the enabling of the first charging operation signal G1A from the controller 803 , the second switches Q15 - Q20 receive the enabling of the second discharging operation signal G2B from the controller 803 . When the first switches Q5 - Q10 receive the enabling of the first discharging operation signal G1B from the controller 803 , the second switches Q11 - Q14 receive the enabling of the second charging operation signal G2A from the controller 803 .

The first switches Q1-Q10, the first capacitors C1-C3, the first inductor L1, the second switches Q11-20, the second capacitors C11-C13, the second inductor L11, the current sensing circuit 804, the switch driver in this embodiment 805 and the first switches Q1-Q10 of FIG. 2, the first capacitors C1-C3, the first inductor L1, the second switches Q11-20, the second capacitors C11-C13, the second inductor L11, the current sensing circuit 204, the switches The driver 205 is similar and will not be described in detail. The controller 803 is used for generating a first charging operation signal G1A, a second charging operation signal G2A, at least one first discharging operation signal G1B and at least one second discharging operation signal G2B, respectively corresponding to a first charging procedure, A second charging process, at least one first discharging process and at least one second discharging process respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first switches Q1-Q10 respectively. The electrical connection relationship between a capacitor C1-C3 and the corresponding second capacitor C11-C13. The controller 803 can further generate an input voltage adjustment signal Va1 and an input voltage adjustment signal Va2 to adjust the input voltages Vin1 and Vin2 respectively. The controller 803 is coupled to the current sensing circuit 804 for adjusting at least one of the input voltage Vin1 and the input voltage Vin2 according to the first current sensing signal I1 and the second current sensing signal I2, so that the first power stage The output current of the circuit 801 is proportional to the output current of the second power stage circuit 802 .

FIG. 9 is a circuit schematic diagram showing a controller and a current sensing circuit in a resonant switching power converter according to an embodiment of the present invention, which shows an embodiment of the controller 803 and the current sensing circuit 804 of FIG. 8 . The averaging circuit 8031, the voltage sensing circuits 8041a and 8041b, the resistors Rcs1 and Rcs2, the capacitors Cs1 and Cs2, the conversion circuits 8042a and 8042b in this embodiment are the same as the averaging circuit 2031, the voltage sensing circuits 2041a and 2041b in the embodiment of FIG. 3 . , the resistors Rcs1 and Rcs2 , the capacitors Cs1 and Cs2 , and the conversion circuits 2042 a and 2042 b are similar, so they are not described in detail. The difference between this embodiment and the embodiment of FIG. 3 is that the adjustment circuits 8032a and 8032b in the controller 803 of this embodiment are coupled to the averaging circuit 8031 and at least one current sensing circuit 804 for comparing the current average signal Iavg with the first A current sensing signal I1 or a second current sensing signal I2 respectively generates an input voltage adjustment signal Va1 and Va2 to the input voltages Vin1 and Vin2.

The input voltages Vin1 and Vin2 are increased or decreased according to the input voltage adjustment signals Va1 and Va2 respectively, so that the output current of the first power stage circuit 801 and the output current of the second power stage circuit 802 have a constant ratio. Since increasing the input voltage can increase the output power, the output current of the corresponding power stage circuit can be increased. Specifically, in one embodiment, at least one of the following adjustment methods can be performed, so that the output of the first power stage circuit 801 can be increased. The current is proportional to the output current of the second power stage circuit 802: when the first current sensing signal I1 is greater than the current average signal Iavg, the input voltage Vin1 is reduced, and when the first current sensing signal I1 is less than the current average signal Iavg , increase the input voltage Vin1. When the second current sensing signal I2 is greater than the current average signal Iavg, the input voltage Vin2 is decreased, and when the second current sensing signal I2 is less than the current average signal Iavg, the input voltage Vin2 is increased.

FIG. 10 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention. The difference between this embodiment and the embodiment of FIG. 5 is that this embodiment uses two input voltages. For example, the first power stage circuit and the second power stage circuit respectively convert the input voltages Vin1 and Vin2 to generate the output voltage Vout, and The embodiment of FIG. 5 uses an input voltage Vin. In one embodiment, the resonant switching power converter is configured as an interleaved power converter. That is, when the first power stage circuit 1001 of the resonant switching power converter 100 is in the first charging process, the second power stage circuit 1002 performs the second discharging process. Similarly, when the first power stage circuit 1001 of the resonant switching power converter 100 is in the first discharging process, the second power stage circuit 1002 performs the second charging process. In other words, when the first switches Q1 - Q4 receive the enabling of the first charging operation signal G1A from the controller 1003 , the second switches Q15 - Q20 receive the enabling of the second discharging operation signal G2B from the controller 1003 . When the first switches Q5 - Q10 receive the enabling of the first discharging operation signal G1B from the controller 1003 , the second switches Q11 - Q14 receive the enabling of the second charging operation signal G2A from the controller 1003 .

In this embodiment, the first switches Q1-Q10, the first capacitors C1-C3, the first charging inductor L3, the first discharging inductor L2, the second switch Q11-20, the second capacitors C11-C13, the second charging inductor L13, The second discharge inductor L12, the current sensing circuit 1004, the switch driver 1005, the first switches Q1-Q10, the first capacitors C1-C3, the first charging inductor L3, the first discharging inductor L2, the second switch Q11- 20. The second capacitors C11-C13, the second charging inductance L13, the second discharging inductance L12, the current sensing circuit 504, and the switch driver 505 are similar, so they will not be repeated. The controller 1003 is used for generating a first charging operation signal G1A, a second charging operation signal G2A, at least one first discharging operation signal G1B and at least one second discharging operation signal G2B, respectively corresponding to a first charging procedure, A second charging process, at least one first discharging process and at least one second discharging process respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first switches Q1-Q10 respectively. The electrical connection relationship between a capacitor C1-C3 and the corresponding second capacitor C11-C13. The controller 1003 can further be used to generate an input voltage adjustment signal Va1 and an input voltage adjustment signal Va2 to adjust the input voltages Vin1 and Vin2 respectively. The controller 1003 is coupled to the current sensing circuit 1004 for adjusting at least one of the input voltage Vin1 and the input voltage Vin2 according to the first current sensing signal I1 and the second current sensing signal I2, so that the first power stage The output current of the circuit 1001 is proportional to the output current of the second power stage circuit 1002 . In one embodiment, the controller 1003 and the current sensing circuit 1004 can also adopt the structure shown in FIG. 9 .

FIG. 11 is a schematic circuit diagram showing a resonant switching power converter according to still another embodiment of the present invention. The difference between this embodiment and the embodiment of FIG. 6 is that this embodiment uses two input voltages. For example, the first power stage circuit and the second power stage circuit respectively convert the input voltages Vin1 and Vin2 to generate the output voltage Vout, and The embodiment of FIG. 6 uses an input voltage Vin. In one embodiment, the resonant switching power converter is configured as an interleaved power converter. That is, when the first power stage circuit 1101 of the resonant switching power converter 110 is in the first charging process, the second power stage circuit 1102 performs the second discharging process. Similarly, when the first power stage circuit 1101 of the resonant switching power converter 110 is in the first discharging process, the second power stage circuit 1102 performs the second charging process. In other words, when the first switches Q1 - Q4 receive the enabling of the first charging operation signal G1A from the controller 1103 , the second switches Q15 - Q20 receive the enabling of the second discharging operation signal G2B from the controller 1103 . When the first switches Q5 - Q10 receive the enable of the first discharge operation signal G1B from the controller 1103 , the second switches Q11 - Q14 receive the enable of the second charge operation signal G2A from the controller 1103 .

The first switches Q1-Q10, the first capacitors C1-C3, the first inductors L1-L3, the second switches Q11-20, the second capacitors C11-C13, the second inductors L11-L13, the current sensing circuit in this embodiment 1104, the switch driver 1105 and the first switches Q1-Q10, first capacitors C1-C3, first inductors L1-L3, second switches Q11-20, second capacitors C11-C13, and second inductors L11-L13 of FIG. 6 , the current sensing circuit 604, and the switch driver 605 are similar, so they will not be described in detail. The controller 1103 is used for generating a first charging operation signal G1A, a second charging operation signal G2A, at least one first discharging operation signal G1B and at least one second discharging operation signal G2B, respectively corresponding to a first charging procedure, A second charging process, at least one first discharging process and at least one second discharging process respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first switches Q1-Q10 respectively. The electrical connection relationship between a capacitor C1-C3 and the corresponding second capacitor C11-C13. The controller 1103 can further be used to generate an input voltage adjustment signal Va1 and an input voltage adjustment signal Va2 to adjust the input voltages Vin1 and Vin2 respectively. The controller 1103 is coupled to the current sensing circuit 1104 for adjusting at least one of the input voltage Vin1 and the input voltage Vin2 according to the first current sensing signal I1 and the second current sensing signal I2, so that the first power stage The output current of the circuit 1101 is proportional to the output current of the second power stage circuit 1102 . In one embodiment, the controller 1103 and the current sensing circuit 1104 can also adopt the structure shown in FIG. 9 .

FIG. 12 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention. The difference between this embodiment and the embodiment of FIG. 7 is that this embodiment uses two input voltages. For example, the first power stage circuit and the second power stage circuit respectively convert the input voltages Vin1 and Vin2 to generate the output voltage Vout, and The embodiment of FIG. 7 uses an input voltage Vin. In one embodiment, the resonant switching power converter is configured as an interleaved power converter. That is, when the first power stage circuit 1201 of the resonant switching power converter 120 is in the first resonance process, the second power stage circuit 1202 performs the fourth resonance process. Similarly, when the first power stage circuit 1201 of the resonant switching power converter 120 is in the second resonance process, the second power stage circuit 1202 executes the third resonance process. In other words, when the first switches Q1 - Q5 receive the enabling of the first resonant operation signal G1 from the controller 1203 , the second switches Q16 - Q20 receive the enabling of the fourth resonant operation signal G4 from the controller 1203 . When the first switches Q6 - Q10 receive the enabling of the second resonant operation signal G2 from the controller 1203 , the second switches Q11 - Q15 receive the enabling of the third resonant operating signal G3 from the controller 1203 .

The first switches Q1-Q10, the first capacitors C1-C3, the first inductors L1-L2, the second switches Q11-20, the second capacitors C11-C13, the second inductors L11-L12, and the current sensing circuit in this embodiment 1204, the switch driver 1205 and the first switches Q1-Q10, the first capacitors C1-C3, the first inductors L1-L2, the second switches Q11-20, the second capacitors C11-C13, and the second inductors L11-L12 of FIG. 7 , the current sensing circuit 704 and the switch driver 705 are similar, so they are not described in detail. The controller 1203 is used for generating a first resonance operation signal G1, a second resonance operation signal G2, a third resonance operation signal G3 and a fourth resonance operation signal G4, respectively corresponding to a first resonance process, a first resonance operation Two resonance procedures, a third resonance procedure and a fourth resonance procedure respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first capacitors C1- The electrical connection relationship between C3 and the corresponding second capacitors C11-C13. The controller 1203 can further be used to generate an input voltage adjustment signal Va1 and an input voltage adjustment signal Va2 to adjust the input voltages Vin1 and Vin2 respectively. The controller 1203 is coupled to the current sensing circuit 1204 for adjusting at least one of the input voltage Vin1 and the input voltage Vin2 according to the first current sensing signal I1 and the second current sensing signal I2, so that the first power stage The output current of the circuit 1201 is proportional to the output current of the second power stage circuit 1202 . In one embodiment, the controller 1203 and the current sensing circuit 1204 can also adopt the structure shown in FIG. 9 .

13 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention. The difference between this embodiment and FIG. 2 is that this embodiment uses two input voltages. For example, the first power stage circuit and the second power stage circuit respectively convert the input voltages Vin1 and Vin2 to generate the output voltage Vout. Embodiments employ an input voltage Vin. The first switches Q1-Q10, the first capacitors C1-C3, the first inductor L1, the second switches Q11-20, the second capacitors C11-C13, the second inductor L11, the current sensing circuit 1304, the switch driver in this embodiment 1305 and the first switches Q1-Q10 of FIG. 2, the first capacitors C1-C3, the first inductor L1, the second switches Q11-20, the second capacitors C11-C13, the second inductor L11, the current sensing circuit 204, the switches The driver 205 is similar and will not be described in detail. The controller 1303 is used for generating a first charging operation signal G1A, a second charging operation signal G2A, at least one first discharging operation signal G1B and at least one second discharging operation signal G2B, respectively corresponding to a first charging procedure, A second charging process, at least one first discharging process and at least one second discharging process respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first switches Q1-Q10 respectively. The electrical connection relationship between a capacitor C1-C3 and the corresponding second capacitor C11-C13. The controller 1303 can further generate an input voltage adjustment signal Va1 and an input voltage adjustment signal Va2 to adjust the input voltages Vin1 and Vin2 respectively. The controller 1303 is coupled to the current sensing circuit 1304, and is used for adjusting at least one of the following according to the first current sensing signal I1 and the second current sensing signal I2, so that the output current of the first power stage circuit 1301 is equal to the first current sensing signal I2. The output currents of the two power stage circuits 1302 are in a fixed ratio: the first delay time, the second delay time, the third delay time, the fourth delay time, the input voltage Vin1 and the input voltage Vin2. In one embodiment, the first power stage circuit 1301 and the second power stage circuit 1302 may be configured as an interleaved power converter as described in the aforementioned embodiment of FIG. 8 , that is, the first power stage circuit 1301 and the The operating phases of the second power stage circuits 1302 may be interleaved with each other.

It should be noted that the controller 1303 can determine the start time and time length of the charging process and the discharging process according to various methods. In one embodiment, for example, the loop control signal can be generated according to the output voltage Vout or the output current to In another embodiment, the starting time point and time length of the charging process and the discharging process can be determined, for example, according to the time point when the inductor current crosses the zero current. The aforementioned current balance control can further control the aforementioned delay time or input voltage to make the output current of each power stage circuit have a fixed proportional relationship or achieve current balance.

14 is a circuit schematic diagram showing a controller and a current sensing circuit in a resonant switching power converter according to an embodiment of the present invention, which shows an embodiment of the controller 1303 and the current sensing circuit 1304 of FIG. 13 . The averaging circuit 13031, the voltage sensing circuits 13041a and 13041b, the resistors Rcs1 and Rcs2, the capacitors Cs1 and Cs2, the conversion circuits 13042a and 13042b in this embodiment are the same as the averaging circuit 2031, the voltage sensing circuits 2041a and 2041b in the embodiment of FIG. 3 . , the resistors Rcs1 and Rcs2 , the capacitors Cs1 and Cs2 , and the conversion circuits 2042 a and 2042 b are similar, so they are not described in detail. The difference between this embodiment and the embodiment of FIG. 3 is that the adjustment circuits 13032a and 13032b in the controller 1303 of this embodiment are coupled to the averaging circuit 13031 and at least one current sensing circuit 1304 for comparing the current average signal Iavg with the first A current sensing signal I1 or a second current sensing signal I2 respectively generates an input voltage adjustment signal Va1 and Va2 to the input voltages Vin1 and Vin2 and/or respectively generates a delay time adjustment signal Ta1 and Ta2 to the delay circuit 13033a and 13033b. In other words, the present embodiment can adjust the delay time and/or the corresponding input voltage according to the current sensing signal to achieve current balance. In one embodiment, the input voltages Vin1 and Vin2 are increased or decreased according to the input voltage adjustment signals Va1 and Va2 respectively, so that the output current of the first power stage circuit 1301 and the output current of the second power stage circuit 1302 are equal to one Fixed scale. In one embodiment, the delay circuits 13033a and 13033b modify the first delay time and the second delay time, or the third delay time and the fourth delay time according to the delay time adjustment signals Ta1 and Ta2, respectively, to generate the first charging operation signal G1A, respectively and the first discharge operation signal G1B, the second charge operation signal G2A and the second discharge operation signal G2B, so that the output current of the first power stage circuit 1301 and the output current of the second power stage circuit 1302 have the fixed ratio.

In one embodiment, when the first current sensing signal I1 is greater than the current average signal Iavg, the input voltage Vin1 is decreased, and when the first current sensing signal I1 is less than the current average signal Iavg, the input voltage Vin1 is increased. When the second current sensing signal I2 is greater than the current average signal Iavg, the input voltage Vin2 is decreased, and when the second current sensing signal I2 is less than the current average signal Iavg, the input voltage Vin2 is increased. In one embodiment, when the first current sensing signal I1 is greater than the current average signal Iavg, the first delay time and/or the second delay time are extended, and when the first current sensing signal I1 is less than the current average signal Iavg, Shorten the first delay time and/or the second delay time. When the second current sensing signal I2 is greater than the current average signal Iavg, the third delay time and/or the fourth delay time are extended, and when the second current sensing signal I2 is less than the current average signal Iavg, the third delay time is shortened and/or the fourth delay time.

15 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention. The difference between this embodiment and the embodiment of FIG. 5 is that this embodiment uses two input voltages. For example, the first power stage circuit and the second power stage circuit respectively convert the input voltages Vin1 and Vin2 to generate the output voltage Vout, and The embodiment of FIG. 5 uses an input voltage Vin. In this embodiment, the first switches Q1-Q10, the first capacitors C1-C3, the first charging inductor L3, the first discharging inductor L2, the second switch Q11-20, the second capacitors C11-C13, the second charging inductor L13, The second discharge inductor L12, the current sensing circuit 1504, the switch driver 1505, the first switches Q1-Q10, the first capacitors C1-C3, the first charging inductor L3, the first discharging inductor L2, the second switch Q11- 20. The second capacitors C11-C13, the second charging inductance L13, the second discharging inductance L12, the current sensing circuit 504, and the switch driver 505 are similar, so they will not be repeated.

The controller 1503 is used for generating a first charging operation signal G1A, a second charging operation signal G2A, at least one first discharging operation signal G1B and at least one second discharging operation signal G2B, respectively corresponding to a first charging procedure, A second charging process, at least one first discharging process and at least one second discharging process respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first switches Q1-Q10 respectively. The electrical connection relationship between a capacitor C1-C3 and the corresponding second capacitor C11-C13. The controller 1503 can further generate an input voltage adjustment signal Va1 and an input voltage adjustment signal Va2 to adjust the input voltages Vin1 and Vin2 respectively. The controller 1503 is coupled to the current sensing circuit 1504, and is used for adjusting at least one of the following according to the first current sensing signal I1 and the second current sensing signal I2, so that the output current of the first power stage circuit 1501 is equal to the first current sensing signal I2. The output currents of the two power stage circuits 1502 are in a fixed ratio: the first delay time, the second delay time, the third delay time, the fourth delay time, the input voltage Vin1 and the input voltage Vin2. In one embodiment, the controller 1503 and the current sensing circuit 1504 can also adopt the structure shown in FIG. 14 . In one embodiment, the first power stage circuit 1501 and the second power stage circuit 1502 may be configured as an interleaved power converter as described in the aforementioned embodiment of FIG. 10 , that is, the first power stage circuit 1501 and the The operating phases of the second power stage circuits 1502 may be interleaved with each other.

FIG. 16 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention. The difference between this embodiment and the embodiment of FIG. 6 is that this embodiment uses two input voltages. For example, the first power stage circuit and the second power stage circuit respectively convert the input voltages Vin1 and Vin2 to generate the output voltage Vout, and The embodiment of FIG. 6 uses an input voltage Vin. The first switches Q1-Q10, the first capacitors C1-C3, the first inductors L1-L3, the second switches Q11-20, the second capacitors C11-C13, the second inductors L11-L13, the current sensing circuit in this embodiment 1604, the switch driver 1605 and the first switches Q1-Q10, first capacitors C1-C3, first inductors L1-L3, second switches Q11-20, second capacitors C11-C13, and second inductors L11-L13 of FIG. 6 , the current sensing circuit 604, and the switch driver 605 are similar, so they will not be described in detail.

The controller 1603 is used for generating a first charging operation signal G1A, a second charging operation signal G2A, at least one first discharging operation signal G1B and at least one second discharging operation signal G2B, respectively corresponding to a first charging procedure, A second charging process, at least one first discharging process and at least one second discharging process respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first switches Q1-Q10 respectively. The electrical connection relationship between a capacitor C1-C3 and the corresponding second capacitor C11-C13. The controller 1603 can further be used to generate an input voltage adjustment signal Va1 and an input voltage adjustment signal Va2 to adjust the input voltages Vin1 and Vin2 respectively. The controller 1603 is coupled to the current sensing circuit 1604 for adjusting at least one of the following according to the first current sensing signal I1 and the second current sensing signal I2, so that the output current of the first power stage circuit 1601 is the same as the first current sensing signal I2. The output currents of the two power stage circuits 1602 are in a fixed ratio: the first delay time, the second delay time, the third delay time, the fourth delay time, the input voltage Vin1 and the input voltage Vin2. In one embodiment, the controller 1603 and the current sensing circuit 1604 can also adopt the structure shown in FIG. 14 . In one embodiment, the first power stage circuit 1601 and the second power stage circuit 1602 may be configured as an interleaved power converter as described in the aforementioned embodiment of FIG. 11 , that is, the first power stage circuit 1601 and the The operating phases of the second power stage circuits 1602 may be interleaved with each other.

17 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention. The difference between this embodiment and the embodiment of FIG. 7 is that this embodiment adopts two input voltages. For example, the first power stage circuit and the second power stage circuit respectively convert the input voltages Vin1 and Vin2 to generate the output voltage Vout, and The embodiment of FIG. 7 uses an input voltage Vin. The first switches Q1-Q10, the first capacitors C1-C3, the first inductors L1-L2, the second switches Q11-20, the second capacitors C11-C13, the second inductors L11-L12, and the current sensing circuit in this embodiment 1704, the switch driver 1705 and the first switches Q1-Q10, first capacitors C1-C3, first inductors L1-L2, second switches Q11-20, second capacitors C11-C13, and second inductors L11-L12 of FIG. 7 , the current sensing circuit 704 and the switch driver 705 are similar, so they are not described in detail.

The controller 1703 is used for generating a first resonance operation signal G1, a second resonance operation signal G2, a third resonance operation signal G3 and a fourth resonance operation signal G4, respectively corresponding to a first resonance process, a first resonance operation Two resonance procedures, a third resonance procedure and a fourth resonance procedure respectively operate the corresponding first switches Q1-Q10 and the corresponding second switches Q11-Q20 to switch the corresponding first capacitors C1- The electrical connection relationship between C3 and the corresponding second capacitors C11-C13. The controller 1703 can further be used to generate an input voltage adjustment signal Va1 and an input voltage adjustment signal Va2 to adjust the input voltages Vin1 and Vin2 respectively. The controller 1703 is coupled to the current sensing circuit 1704, and is used for adjusting at least one of the following according to the first current sensing signal I1 and the second current sensing signal I2, so that the output current of the first power stage circuit 1701 is equal to the first current sensing signal I2. The output currents of the two power stage circuits 1702 are in a fixed ratio: the first delay time, the second delay time, the third delay time, the fourth delay time, the input voltage Vin1 and the input voltage Vin2. In one embodiment, the controller 1703 and the current sensing circuit 1704 can also adopt the structure shown in FIG. 14 . In one embodiment, the first power stage circuit 1701 and the second power stage circuit 1702 may be configured as an interleaved power converter as described in the aforementioned embodiment of FIG. 12 , that is, the first power stage circuit 1701 and the The operating phases of the second power stage circuits 1702 may be interleaved with each other.

FIG. 18 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention. This embodiment is similar to the embodiment of FIG. 2 , the difference is that, in this embodiment, the first power stage circuit 1801 and the first power stage 1802 , in the corresponding discharge procedure, the first capacitors C1 , C2 , and C3 are alternately To discharge, the second capacitors C11, C12, and C13 are discharged alternately. In this embodiment, the first discharge operation signal G1B includes a corresponding plurality of sub-discharge operation signals, and the corresponding switch driver 1805 generates corresponding sub-drive signals G1x', G1y' and G1z' according to the corresponding plurality of sub-discharge operation signals, It is used to control the first switches Q5 and Q8, Q6 and Q9, and Q7 and Q10 respectively, so as to control the first capacitors C1, C2, and C3 to discharge in turn. The second discharge operation signal G2B includes a corresponding plurality of sub-discharge operation signals, and the corresponding switch driver 1805 generates corresponding sub-drive signals G2x', G2y' and G2z' according to the corresponding plurality of sub-discharge operation signals to control the first The two switches Q15 and Q18 , Q16 and Q19 , and Q17 and Q20 control the second capacitors C11 , C12 and C13 to discharge alternately.

In this embodiment, the second delay time may correspond to at least one of the respective starting time points when the first capacitors C1, C2, and C3 discharge alternately, and the fourth delay time may correspond to the alternate discharge of the second capacitors C11, C12, and C13. at least one of the respective starting time points.

The present invention provides a resonant switching power converter as described above, which is controlled by sensing and comparing the currents of a plurality of power stage circuits, so that the resonant switching power converter with a plurality of power stage circuits can reach the current Balanced control, no need for additional current sense resistors, reduced inrush current and higher efficiency compared to traditional power converters.

The present invention has been described above with respect to the preferred embodiments, but the above descriptions are only intended to make the content of the present invention easy for those skilled in the art to understand, and are not intended to limit the broadest scope of rights of the present invention. The described embodiments are not limited to be applied individually, but can also be applied in combination. For example, two or more embodiments can be applied in combination, and some components of one embodiment can also be used to replace those in another embodiment. corresponding components. In addition, under the same spirit of the present invention, those skilled in the art can think of various equivalent changes and various combinations. According to the signal itself, when necessary, the signal is subjected to voltage-to-current conversion, current-to-voltage conversion, and/or ratio conversion, etc., and then processed or calculated according to the converted signal to generate an output result. It can be seen from this that under the same spirit of the present invention, those skilled in the art can think of various equivalent changes and various combinations, and there are many combinations, which are not listed and described here. Accordingly, the scope of the present invention should cover the above and all other equivalent changes.

20, 50, 60, 70, 80, 100, 110, 120, 130, 150, 160, 170, 180: Resonant switching power converters 201, 501, 601, 701, 801, 1001, 1101, 1201, 1301, 1501, 1601, 1701, 1801: First Power Stage Circuits 202, 502, 602, 702, 802, 1002, 1102, 1202, 1302, 1502, 1602, 1702, 1802: Second Power Stage Circuit 203, 503, 603, 703, 803, 1003, 1103, 1203, 1303, 1503, 1603, 1703: Controller 2031, 8031, 13031: Average circuit 2032a, 2032b, 8032a, 8032b, 13032a, 13032b: Adjustment circuit 2033a, 2033b, 13033a, 13033b: Delay Circuits 204, 504, 604, 704, 804, 1004, 1104, 1204, 1304, 1504, 1604, 1704: Current Sensing Circuits 2041a, 2041b, 8041a, 8041b, 13041, 13041b: Voltage Sensing Circuits 2042a, 2042b, 8042a, 8042b, 13042a, 13042b: Conversion circuit 205, 505, 605, 705, 805, 1005, 1105, 1205, 1305, 1505, 1605, 1705, 1805: Switch Drivers 706~709: Resonant cavity C1~C3: (first) capacitor C11~C13: The second capacitor Co: output capacitance Cs1, Cs2: Capacitance DCR1, DCR2: Resistor G1: The first resonance operation signal G1A: The first charging operation signal G1B: The first discharge operation signal G2: The second resonance operation signal G2A: The second charging operation signal G2B: The second discharge operation signal G3: The third resonance operation signal G4: Fourth resonance operation signal G1A', G1B', G2A', G2B': drive signal G1x’, G1y’, G1z’, G2x’, G2y’ , G2z’: drive signal G1', G2', G3', G4': drive signal gm: transduction value I1: The first current sensing signal I2: The second current sensing signal Iavg: Current average signal IL1: first inductor current IL11: Second inductor current L1: first (resonant) inductance L11: Second (resonant) inductor L12: Second (discharge/resonant) inductor L13: Second (charging) inductor L2: First (discharge/resonant) inductance L3: First (charging) inductor Q1~Q10: (first) switch Q11~Q20: The second switch Rcs1, Rcs2: Resistance RL: load resistance Ta1, Ta2: Delay time adjustment signal td1: first delay time td2: second delay time Va1, Va2: Input voltage adjustment signal Vin, Vin1, Vin2: Input voltage Vout: output voltage

FIG. 1 is a schematic diagram of a conventional power converter.

FIG. 2 is a schematic circuit diagram showing a resonant switching power converter according to an embodiment of the present invention.

3 is a schematic circuit diagram showing a controller and a current sensing circuit in a resonant switching power converter according to an embodiment of the present invention.

4 is a schematic diagram showing signal waveforms of related signals of the first power stage circuit of a resonant switching power converter according to an embodiment of the present invention.

FIG. 5 is a schematic circuit diagram showing a resonant switching power converter according to another embodiment of the present invention.

FIG. 6 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.

FIG. 7 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.

FIG. 8 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.

9 is a schematic circuit diagram showing a controller and a current sensing circuit in a resonant switching power converter according to an embodiment of the present invention.

FIG. 10 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.

FIG. 11 is a schematic circuit diagram showing a resonant switching power converter according to still another embodiment of the present invention.

FIG. 12 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.

13 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.

14 is a circuit schematic diagram showing a controller and a current sensing circuit in a resonant switching power converter according to an embodiment of the present invention.

15 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.

FIG. 16 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.

17 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.

FIG. 18 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.

130: Resonant Switching Power Converters

1301: First Power Stage Circuit

1302: Second Power Stage Circuit

1303: Controller

1304: Current Sensing Circuit

1305: Switch Driver

C1~C3: The first capacitor

C11~C13: The second capacitor

Co: output capacitance

G1A: The first charging operation signal

G1B: The first discharge operation signal

G2A: The second charging operation signal

G2B: The second discharge operation signal

G1A', G1B', G2A', G2B': drive signal

I1: The first current sensing signal

I2: The second current sensing signal

IL1: first inductor current

IL11: Second inductor current

L1: The first inductor

L11: Second inductor

Q1~Q10: The first switch

Q11~Q20: The second switch

RL: load resistance

Va1, Va2: Input voltage adjustment signal

Vin1, Vin2: Input voltage

Vout: output voltage

Claims (20)

A resonant switching power converter for converting one or two input voltages into an output voltage, the resonant switching power converter comprising: A first power stage circuit, comprising: a plurality of first capacitors; at least one first charging inductor; at least one first discharge inductor; and a plurality of first switches for switching the corresponding electrical connection relationship between the plurality of first capacitors, the at least one first charging inductor and the at least one first discharging inductor; A second power stage circuit comprising: a plurality of second capacitors; at least one second charging inductor; at least one second discharge inductor; and a plurality of second switches for switching the corresponding electrical connection relationships of the plurality of second capacitors, the at least one second charging inductor and the at least one second discharging inductor; as well as a controller for periodically operating the corresponding first switches and the corresponding first switches in a corresponding first charging procedure, a second charging procedure, at least a first discharging procedure and at least a second discharging procedure the plurality of second switches; Wherein, in the first charging procedure, the switching of the plurality of first switches is controlled, so that the plurality of first capacitors and the at least one first charging inductor are connected in series between the one or two input voltages and the output voltage, so as to forming a first charging path; Wherein, in the at least one first discharge procedure, the switching of the plurality of first switches is controlled, so that each of the first capacitors and the corresponding first discharge inductance are connected in series between the output voltage and a ground potential, and simultaneously form Or take turns to form a plurality of first discharge paths; Wherein, in the second charging procedure, the switching of the plurality of second switches is controlled, so that the plurality of second capacitors and the at least one second charging inductor are connected in series between the one or two input voltages and the output voltage, so as to forming a second charging path; Wherein, in the at least one second discharge procedure, the switching of the plurality of second switches is controlled, so that each of the second capacitors and the corresponding second discharge inductance are connected in series between the output voltage and a ground potential, and simultaneously form Or alternately form a plurality of second discharge paths; The controller is further configured to adjust at least one of the following according to a first current sensing signal and a second current sensing signal, so as to make the output current of the first power stage circuit and the output of the second power stage circuit The current is in a fixed ratio: a first delay time, a second delay time, a third delay time and a fourth delay time, or the two input voltages; The first delay time is used to delay the start time of the first charging process, the second delay time is used to delay the start time of the at least one first discharge process, and the third delay time is used to delay the second delay time a start time point of the charging process, and the fourth delay time is used to delay the start time point of the at least one second discharge process; Wherein the first current sensing signal is related to the at least one first charging inductor and/or a first inductor current of the at least one first discharging inductor, wherein the second current sensing signal is related to the at least one second charging The inductor and/or a second inductor current of the at least one second discharge inductor. The resonant switching power converter of claim 1, wherein the at least one first charging inductor is a first single charging inductor, the at least one first discharging inductor is a first single discharging inductor, and the at least one second charging inductor is a first single discharging inductor. The charging inductor is a second single charging inductor, and the at least one second discharging inductor is a second single discharging inductor. The resonant switching power converter of claim 1, wherein the at least one first charging inductor and the at least one first discharging inductor are a first single identical inductor, and the at least one second charging inductor and the at least one first discharging inductor are the same. The two discharge inductances are the second single identical inductance. The resonant switching power converter of claim 1, wherein the controller includes at least one current sensing circuit, and the at least one current sensing circuit includes: At least one voltage sensing circuit for sensing the voltage difference between the two ends of the at least one first charging inductor and/or the at least one first discharging inductor, and correspondingly generating a first voltage sensing signal for sensing The voltage difference across the at least one second charging inductor and/or the at least one second discharging inductor generates a second voltage sensing signal, wherein the first voltage sensing signal is related to the at least one first charging The voltage across the inductance and/or a parasitic resistance of the at least one first discharge inductance, the second voltage sensing signal is related to the at least one second charging inductance and/or the parasitic resistance of the at least one second discharge inductance cross pressure; and At least one conversion circuit is used for respectively generating the first current sensing signal and the second current sensing signal according to the first voltage sensing signal and the second voltage sensing signal. The resonant switching power converter of claim 1, wherein the controller further comprises: an averaging circuit for averaging the first current sensing signal and the second current sensing signal to generate a current averaging signal; and at least one adjustment circuit for comparing the current average signal with the first current sensing signal and/or comparing the current average signal with the second current sensing signal to generate an adjustment signal for adjusting at least one of the following , so that the output current of the first power stage circuit is proportional to the output current of the second power stage circuit: the first delay time, the second delay time, the third delay time and the fourth delay time , or the two input voltages. The resonant switching power converter of claim 5, wherein the fixed ratio is 1:1. The resonant switching power converter of claim 5, wherein the controller further comprises: at least one delay circuit for generating the first delay time, the second delay time, the third delay time and/or the fourth delay time according to the adjustment signal, so as to make the output current of the first power stage circuit is proportional to the output current of the second power stage circuit. The resonant switching power converter of claim 5, wherein the controller adjusts at least one of the following so that the output current of the first power stage circuit and the output current of the second power stage circuit are the fixed ratio: when the first current sensing signal is greater than the current average signal, extending the first delay time and/or the second delay time; When the first current sensing signal is smaller than the current average signal, shortening the first delay time and/or the second delay time; when the second current sensing signal is greater than the current average signal, extending the third delay time and/or the fourth delay time; and/or When the second current sensing signal is smaller than the current average signal, the third delay time and/or the fourth delay time are shortened. The resonant switching power converter of claim 5, wherein the two input voltages comprise a first input voltage and a second input voltage, corresponding to the first power stage circuit and the second power stage circuit, respectively, wherein the controller adjusts at least one of the following to make the output current of the first power stage circuit and the output current of the second power stage circuit be the fixed ratio: When the first current sensing signal is greater than the current average signal, reducing the first input voltage; When the first current sensing signal is smaller than the current average signal, increasing the first input voltage; When the second current sensing signal is greater than the current average signal, reducing the second input voltage; and/or When the second current sensing signal is smaller than the current average signal, the second input voltage is increased. The resonant switching power converter as claimed in claim 9, wherein the first power stage circuit and the second power stage circuit alternately perform corresponding charging and discharging procedures. The resonant switching power converter of claim 1, wherein the resonant switching power converter is a bidirectional resonant switching power converter. The resonant switching power converter of claim 1, wherein the voltage conversion ratio of the one or two input voltages to the output voltage of the resonant switching power converter is 4:1, 3:1 or 2:1 . A resonant switching power converter for converting one or two input voltages into an output voltage, the resonant switching power converter comprising: A first power stage circuit, comprising: at least one first resonant cavity, the first resonant cavity has a first resonant capacitor and a first resonant inductance connected in series with each other; at least one first non-resonant capacitor; and A plurality of first switches are coupled to the at least one first resonant cavity and the at least one first non-resonant capacitor for switching the electrical connection relationship between the corresponding first resonant cavity and the at least one first non-resonant capacitor, In a first resonant process, the corresponding first resonant cavity is resonantly charged, and in a second resonant process, resonant discharge is performed on the corresponding first resonant cavity, wherein the first non-resonant The voltage across the capacitor is maintained at a fixed ratio with the one or two input voltages; A second power stage circuit, comprising: at least one second resonant cavity, the second resonant cavity has a second resonant capacitor and a second resonant inductance connected in series with each other; at least one second non-resonant capacitor; A plurality of second switches are coupled to the at least one second resonant cavity and the at least one second non-resonant capacitor for switching the electrical connection relationship between the corresponding second resonant cavity and the at least one second non-resonant capacitor, In a third resonant process, the corresponding second resonant cavity is resonantly charged, and in a fourth resonant process, resonant discharge is performed on the corresponding second resonant cavity, wherein the second non-resonant The voltage across the capacitor is maintained at a constant ratio to the one or both input voltages; and a controller for periodically operating the corresponding first switches and the corresponding first switches in the corresponding first resonance procedure, the second resonance procedure, the third resonance procedure and the fourth resonance procedure a plurality of second switches to perform corresponding resonant charging and resonant discharging; The controller is further configured to adjust at least one of the following according to a first current sensing signal and a second current sensing signal, so as to make the output current of the first power stage circuit and the output of the second power stage circuit The current is in a fixed ratio: a first delay time, a second delay time, a third delay time and a fourth delay time, or the two input voltages; The first delay time is used to delay the start time of the first resonance process, the second delay time is used to delay the start time of the second resonance process, and the third delay time is used to delay the third resonance process The starting time point of , the fourth delay time is used to delay the starting time point of the fourth resonance procedure; The first current sensing signal is related to a first inductor current of the first resonant inductor, and the second current sensing signal is related to a second inductor current of the second resonant inductor. The resonant switching power converter of claim 13, wherein the controller comprises at least one current sensing circuit, the at least one current sensing circuit comprising: at least one voltage sensing circuit for sensing the voltage difference across the first resonant inductor, and correspondingly generating a first voltage sensing signal for sensing the voltage difference across the second resonant inductor, and A second voltage sensing signal is correspondingly generated, wherein the first voltage sensing signal is related to the cross-voltage of a parasitic resistance of the at least one first resonant inductor, and the second voltage sensing signal is related to the at least one second resonance the voltage across a parasitic resistance of the inductor; and At least one conversion circuit is used for respectively generating the first current sensing signal and the second current sensing signal according to the first voltage sensing signal and the second voltage sensing signal. The resonant switching power converter of claim 13, wherein the controller further comprises: an averaging circuit for averaging the first current sensing signal and the second current sensing signal to generate a current averaging signal; and at least one adjustment circuit for comparing the current average signal with the first current sensing signal and/or comparing the current average signal with the second current sensing signal to generate an adjustment signal for adjusting at least one of the following , so that the output current of the first power stage circuit is proportional to the output current of the second power stage circuit: the first delay time, the second delay time, the third delay time and the fourth delay time , or the two input voltages. The resonant switching power converter of claim 15, wherein the fixed ratio of the output current of the first power stage circuit to the output current of the second power stage circuit is 1:1. The resonant switching power converter of claim 15, wherein the controller further comprises: at least one delay circuit for generating the first delay time, the second delay time, the third delay time and/or the fourth delay time according to the adjustment signal, so as to make the output current of the first power stage circuit is proportional to the output current of the second power stage circuit. The resonant switching power converter of claim 15, wherein the controller adjusts at least one of the following so that the output current of the first power stage circuit and the output current of the second power stage circuit are the fixed ratio: when the first current sensing signal is greater than the current average signal, extending the first delay time and/or the second delay time; When the first current sensing signal is smaller than the current average signal, shortening the first delay time and/or the second delay time; when the second current sensing signal is greater than the current average signal, extending the third delay time and/or the fourth delay time; and/or When the second current sensing signal is smaller than the current average signal, the third delay time and/or the fourth delay time are shortened. The resonant switching power converter of claim 15, wherein the two input voltages comprise a first input voltage and a second input voltage, corresponding to the first power stage circuit and the second power stage circuit, respectively, wherein the controller adjusts at least one of the following to make the output current of the first power stage circuit and the output current of the second power stage circuit be the fixed ratio: When the first current sensing signal is greater than the current average signal, reducing the first input voltage; When the first current sensing signal is smaller than the current average signal, increasing the first input voltage; When the second current sensing signal is greater than the current average signal, reducing the second input voltage; and/or When the second current sensing signal is smaller than the current average signal, the second input voltage is increased. The resonant switching power converter of claim 19, wherein the first power stage circuit and the second power stage circuit alternately perform corresponding resonant charging and resonant discharging procedures.

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