TWI675538B - Power source controll circuit - Google Patents

Abstract

The invention discloses a power supply control circuit, which is a current-controlled hysteresis control circuit, including a DC input power supply, an input capacitor, a first switching element, a second switching element, an inductor, a current detector, and a two A pole body, a third switching element, a hysteresis current controller, and a load. The first terminal of the inductor is coupled to the second terminal of the first switching element and the first terminal of the second switching element. The second terminal of the inductor is coupled to the first terminal of the third switching element. An output current in the form of pulse width modulated PWM is output, and the output current flows into the load to drive the load to operate. The invention can improve the existing lack of constant-voltage hysteresis control, effectively achieve the purpose of providing high-precision, fast response, high-power and high-voltage power supply control, and is suitable for the application of program current.

Description

Power control circuit

The invention relates to a power supply control circuit, in particular to a power supply control circuit of current-type hysteresis control that outputs current in a PWM form.

In the prior art, especially for a control circuit of a laser diode driver, a conventional feedback control or a voltage hysteresis control is generally used. However, these existing technologies will be accompanied by the following shortcomings: Traditional hysteresis control ICs are mostly based on a constant voltage control method, and if they are to be modified to a constant current, they are mostly shunt resistors. As a detection, but when driving with a large current load application, the power loss using the Shunt Resistor will be very large. In addition, to reduce the power loss of the Shunt Resistor, the resistor itself must be kept very small. In this way, the accuracy is easily limited by the hardware specifications, and the cost of upgrading the hardware specifications will increase significantly. In addition, in the current application of constant voltage technology, it is necessary to consider the use of parallel connection. The shunt resistor must be placed on the high-side. However, the general current sense IC has a limit of withstand voltage. The higher the accuracy and the slower the reaction speed, the higher voltage models will not be conducive to future development. Therefore, improvement is needed and necessary.

The invention discloses a power supply control circuit. The technology of the invention can be widely applied in various aspects, effectively improving the hysteresis control of the traditional constant voltage form. The invention can also be applied to a wide range of loads and programmable load currents. In the current) circuit application, the application of its control circuit is simplified, which not only has fast response speed, but also can be used in high power and high current circuit applications.

A power supply control circuit of the present invention is used to drive a high-power and high-current load. The power supply control circuit includes: a DC input power source Vin; an input capacitor C1 connected in parallel with the DC input power source Vin: a first switching element Q1, the first terminal of the first switching element Q1 is coupled to the positive terminal of the DC input power source Vin; a second switching element Q2, the first terminal of the second switching element Q2 is coupled to the first switching element Q1 The second terminal of the second switching element Q2 is coupled to the negative terminal of the DC input power source Vin; an inductor L1, the first terminal of the inductor L1 is coupled to the second terminal of the first switching element Q1 Terminal, the inductor L1 outputs an output current Io in the form of pulse width modulation PWM; a current detector, the current detector is connected in series with the inductor L1 to detect the output current Io, and outputs a current detection Measurement signal CC; a diode D1, the anode terminal of the diode D1 is coupled to the second terminal of the inductor L1, and the cathode terminal of the diode D1 is coupled to the positive terminal of the DC input power source Vin; A third switching element Q3, and a first terminal of the third switching element Q3 is coupled to the third switching element Q3; The anode terminal of the electrode body D1, the second terminal of the third switching element Q3 is coupled to the negative terminal of the DC input power source Vin, and a load, the load is coupled to the first terminal of the third switching element Q3 and the first terminal Between the second ends of the three switching elements Q3 and driven by the output current Io; a hysteresis current controller, the hysteresis current controller is connected to the first switching element Q1, the second switching element Q2 and Individual control terminals of the third switching element Q3 are coupled, and the current detection signal CC is input, and a pulse wave and a current control signal PC are input. The hysteresis current controller is used to provide the first to third switching. The driving signals required by the components Q1 to Q3; the output current Io can be adjusted according to the demand of the load to have a displacement level.

According to an embodiment of the present invention, the hysteresis current controller in the power control circuit includes: a feedback comparator, and a non-inverting input terminal of the feedback comparator inputs the current detection signal CC. The inverting input of the feedback comparator is coupled to a resistor RCC1 and grounded, and is connected to the output of the feedback comparator via a resistor RCC2; a hysteresis amplifier, a non-inverting input of the hysteresis amplifier Terminal is coupled to the current control signal PC, and the inverting input terminal of the hysteresis amplifier is coupled to the feedback comparator An output terminal of the delay circuit, the input terminal of the delay circuit is coupled to the output of the hysteresis amplifier, and the delay circuit outputs a first delay signal Hin and a second delay signal Lin; a first drive circuit, The first delay signal Hin and the second delay signal Lin are input, and a first H driving signal and a first L driving signal are output. The first H driving signal is coupled to the control terminal of the first switching element Q1. The first L driving signal is coupled to the control terminal of the second switching element Q2; and a second driving circuit is for inputting the pulse wave and outputting a second OUT driving signal, and the second OUT driving signal is coupled At the control terminal of the third switching element Q3.

10‧‧‧ Hysteresis Current Controller

20‧‧‧Feedback comparator

22‧‧‧The first amplifier

25‧‧‧filter circuit

30‧‧‧ Hysteresis Amplifier

32‧‧‧Second Amplifier

40‧‧‧ Delay circuit

41‧‧‧First inverter

42‧‧‧Second Inverter

43‧‧‧third inverter

50‧‧‧first drive circuit

52‧‧‧amplifier

60‧‧‧Protection circuit

70‧‧‧Second driving circuit

72‧‧‧ Pulse Converter

80‧‧‧Current Detector

90‧‧‧ load

Vin‧‧‧DC input power

C1‧‧‧ input capacitor

Io‧‧‧Output current

L1‧‧‧Inductance

Q1 ~ Q3‧‧‧‧1st ~ 3rd switching element

D1, DL1 ~ DLN‧‧‧diodes

RCC1, RCC2‧‧‧ resistance

C1a, C1b, CZ1, CZ2‧‧‧Capacitors

RZ1, RZ2‧‧‧ resistance

DZ1 ~ DZ4‧‧‧Diode

Q101 ~ Q106, Q108 ~ Q110, Q200‧‧‧Switch

L11‧‧‧First inductor

L12‧‧‧Second inductor

D11, D12, D25, D26‧‧‧ diodes

R11 ~ R13, R25, R26‧‧‧ resistance

S1‧‧‧Switching element

PULSE‧‧‧pulse

PC‧‧‧Current control signal

CC‧‧‧Current detection signal

IPWM‧‧‧Current pulse control signal

ISET‧‧‧Current setting signal

ISIM‧‧‧Current displacement control signal

Hin‧‧‧First Delay Signal

Lin‧‧‧Second Delay Signal

HO‧‧‧The first HO drive signal

HS‧‧‧First HS driving signal

LO‧‧‧The first LO drive signal

LS‧‧‧The first LO drive signal

OUTH‧‧‧Second OUTH driving signal

OUTL‧‧‧Second OUTL drive signal

SH‧‧‧Current displacement

SP‧‧‧Surge

FIG. 1 is a schematic diagram of a circuit and a circuit block connection according to an embodiment of the present invention; FIG. 2 is a schematic diagram of a combination connection of FIG. 2A and FIG. 2B; FIG. 2A is a schematic diagram of a part of an implementation of a main circuit architecture in an embodiment of the present invention; Another embodiment of the main circuit architecture in the embodiment is implemented diagram; FIG. 3 is a schematic diagram of the internal implementation of a hysteresis current controller in part of the embodiment of the present invention; FIG. 4 is an implementation diagram of the first drive circuit output / input signal in the embodiment of the present invention ; Figure 5 is a schematic diagram of the implementation of the second drive circuit output / input signal according to the embodiment of the present invention; Figure 6 is a schematic diagram of the implementation of the current control signal of the embodiment of the present invention; Figure 7 is a schematic diagram of the implementation of the current pulse control signal of the embodiment of the present invention Figure 8 is a schematic diagram of an output current waveform according to an embodiment of the present invention; Figure 9 is a schematic diagram of an inductor implementation according to an embodiment of the present invention; Figure 10 is a schematic diagram of an inductor characteristic according to an embodiment of the present invention; 12 is a schematic diagram of another embodiment of the inductor L1 in the present invention.

In the following, reference is made to the accompanying drawings to describe more fully the various illustrative examples. Examples, and some exemplary embodiments are shown in the accompanying drawings. However, the concept of the invention may be embodied in many different forms and should not be construed as limited to the exemplary embodiments set forth herein. Rather, these exemplary embodiments are provided so that this invention will be thorough and complete, and will fully convey the scope of the inventive concept to those skilled in the art. In the drawings, the corresponding positions of circuit blocks and circuit elements and various devices may be exaggerated for the sake of clarity, and for similar English labels or numbers, similar elements are always indicated.

It should be understood that although the term switching element may be used in this document to include a switching element, a switching switch, or a switching element, which is an expression term for a switching element, it is not limited to using IGBT, BJT, MOS, CMOS, JFET, The N-channel or P-channel of the MOSFET, that is, these components should not be limited by the actual product term of these electronic components. And the first, second, third ... appearing in this article; or the first switching element Q1, the third switching element Q3; or the input capacitor C1, the capacitor C10, the capacitor CZ1; or the diode D1, the diode D2 ..., these terms are used to clearly distinguish one element from another, and do not have a sequential relationship between the numbers of certain elements, that is, there may be a first switching element Q1 and a third switching element Q3 and there may be no The implementation aspect of the second switching element Q2, that is, the number / number marked by the circuit element, does not necessarily have a continuous serial number as the marking relationship of the component symbol.

As used herein, the terms first, second, upper or lower, left or right, left (end) or right (end), primary or secondary, etc. are used for clarity. Dividing one end point of an element and the other end point of the element, or to distinguish the connection relationship between one element and another element, or the difference between one end point and the other end point, which is not intended to limit The sequence or positional relationship presented by the text serial number does not necessarily have a numerically continuous relationship. Also, the term "and / or" may be used to include all combinations of any one and one or more of the associated listed items. Furthermore, the term "plurality" or "at least two" may be used herein to describe having multiple elements, but such plural elements or at least two elements are not limited to two, three, or four implementations. And the number of components Applied technology.

The invention is used to drive a high-power and high-current load. In order to solve the lack of the conventional constant-voltage hysteresis control circuit, a solution for a complete set of power control circuits is proposed. The circuit is implemented with Hall current (Hall CT) type current detector and the current type hysteresis control circuit successfully developed by the applicant. As shown in FIG. 1, the power control circuit of the present invention includes a DC input power source Vin, an input capacitor C1, a first switching element Q1, a second switching element Q2, an inductor L1, and a current detector 80. , A diode D1, a third switching element Q3, a hysteresis current controller 10, and a load 90. The DC input power source Vin may be a DC power source outputted from another AC / DC converter that is converted from AC AC to DC DC at the front end, as the DC input power source Vin. The input capacitor C1 is connected in parallel with the DC input power source Vin; the first switching element Q1 has a first terminal (as shown in the upper end of the first switching element Q1 in FIG. 1) and a second terminal (as in the first switching element Q1 in FIG. 1). (Shown at the lower end) and a control terminal (ie, the gate terminal of Q1). The first terminal of the first switching element Q1 is coupled to the positive terminal of the DC input power source Vin. Under the same definition of the names of the terminals of the switching element, the first terminal of the second switching element Q2 is coupled to the second terminal of the first switching element Q1, and the second terminal of the second switching element Q2 is coupled to the DC The negative terminal of the input power Vin.

The first end of the inductor L1 (such as the left end of the inductor L1 in FIG. 1) is coupled to the second end of the first switching element Q1, and the inductor L1 outputs an output current Io in the form of a PWM. The current detector 80 is connected in series with the inductor L1 to detect the current state of the output current Io, and the current detector 80 outputs a current detection signal CC as a subsequent control current. Related operations. In an embodiment, the current detector 80 is implemented by a Hall current detection element (Hall CT) on the actual circuit, but it is not limited to the Hall current detection element currently sold in the market. . The anode terminal of the diode D1 of FIG. 1 is coupled to the second terminal of the inductor L1, and the cathode terminal of the diode D1 is coupled to the positive terminal of the DC input power source Vin; The first terminal of the third switching element Q3 is coupled to the anode terminal of the diode D1, and the second terminal of the third switching element Q3 is coupled to the negative terminal of the DC input power source Vin. The load 90 is coupled between the first terminal of the third switching element Q3 and the second terminal of the third switching element Q3, and is driven by the output current Io.

In one embodiment, the load 90 according to the present invention can be composed of a plurality of diodes DL1 to DLN connected in series. Among the diodes DL1 to DLN, each diode DL1 to DLN can It is a laser light emitting diode, that is, in the actual circuit implementation, the load 90 is a load 90 composed of a plurality of laser light emitting diodes connected in series. In addition, the power supply control circuit proposed by the present invention can also be applied to the LED pulse width modulation dimming circuit of LED PWM Dimming. At this time, the load 90 is the dimming lighting load of the LED PWM; and it can also be applied to UV coating. The source of power supply for the UV coating machine. At this time, the load 90 is the UV coating machine. It can also be used in various high-speed current pulse applications. It is obvious that the present invention has great application potential for future high voltage and high power models.

The hysteresis current controller 10 of FIG. 1 is a circuit designed by the inventor. The hysteresis current controller 10 is coupled to the control terminals of the first switching element Q1, the second switching element Q2, and the third switching element Q3, respectively. ; And the hysteresis current controller 10 is inputted with the current detection signal CC, and a pulse PULSE and a current control signal PC are input, and the hysteresis current controller 10 is used to provide the first to third switching elements Q1 to The driving signal required by Q3 is the main driving circuit for the hysteresis current controller 10 to drive the first to third switching elements Q1 to Q3 to perform high-frequency switching operations.

The internal circuit of the hysteresis current controller 10 includes a feedback comparator 20, a hysteresis amplifier 30, a delay circuit 40, a first driving circuit 50, a protection circuit 60, and a second driving circuit 70. The non-inverting input terminal (+) of the feedback comparator 20 is used to input the current detection signal CC. The inverting input terminal (-) of the feedback comparator 20 is coupled to a resistor RCC1 and grounded. RCC2 is connected to the output terminal of the feedback comparator 20. The non-inverting input terminal (+) of the hysteresis amplifier 30 is coupled to the current control signal PC, and the inverting input terminal (-) of the hysteresis amplifier 30 is coupled to the feedback Comparator 20 output. An input terminal of the delay circuit 40 is coupled to an output terminal of the hysteresis amplifier 30, and the delay circuit 40 also outputs a first delay signal Hin and a second delay signal Lin (as shown in FIG. 3). The first driving circuit 50 inputs the first delayed signal Hin and the second delayed signal Lin, and outputs a first H driving signal and a first L driving signal. The first H driving signal is coupled to the first switch. The control terminal of the element Q1. The first L driving signal is coupled to the control terminal of the second switching element Q2. Further description of the first H driving signal and the first L driving signal is described in FIG. 2A. In addition, the second driving circuit 70 inputs the pulse wave (PULSE) and outputs a second OUT driving signal. The second OUT driving signal is coupled to the control terminal of the third switching element Q3, which is further described in FIG. 2B. Again.

The output of the protection circuit 60 is coupled to the first driving circuit 50 to perform a circuit protection function. The protection circuit 60 is an OFF-Latch logic OR gate. The logic OR gate has an over-current signal OCP and an over-temperature signal OTP, and outputs a shutdown signal. The shutdown signal is connected to the first driving circuit 50; when an over-current or over-temperature situation occurs, the driving signal output of the first driving circuit 50 is cut off, so that the entire power control circuit stops the circuit operation.

In the main architecture circuit shown in FIG. 1 of the present invention, a large capacitor is not connected to the output terminal. Generally, a large capacitor is still provided at the output terminal of the buck converter circuit. It transfers energy successively, and on the other hand, it helps to reduce ripples. However, the present invention does not provide a large capacitor. This is because the output is in the form of pulse width modulation PWM when applied to a laser-related load 90, and does not need to continuously transfer energy, so the ripple is reduced. The work is completely placed on the main inductor L1. In a practical embodiment, the application of the output frequency of the present invention is 5k Hz, and the output current is 0-50 amps (A).

FIG. 2 is a circuit diagram connected to FIG. 2A and FIG. 2B, which is an embodiment description further corresponding to the main circuit architecture in FIG. 1. The aforementioned first switching element Q1 is a switching switch Q101, a Switch Q102 and a switch Q103 The third switching element Q2 is composed of a switching switch Q104, a switching switch Q105, and a switching switch Q106. The third switching element Q3 is composed of a switching switch. The three elements Q108, a changeover switch Q109 and a changeover switch Q110 are connected in parallel.

In addition, the first H driving signal includes a first HO driving signal and a first HS driving signal, and the first L driving signal includes a first LO driving signal and a first LS driving signal. The first HO driving signal is connected to the control terminal of the switch Q101, and is also connected to the control terminal of the switch Q102 and to the control terminal of the switch Q103. The first HS driving signal is connected to the control end of the changeover switch Q101 and is coupled to the second end of the changeover switch Q101, and is also connected to the control end of the changeover switch Q102 and coupled to the first end of the changeover switch Q102. Two terminals, and a control terminal connected to the switch Q103 and coupled to a second terminal of the switch Q103. In addition, the first LO driving signal is connected to a control terminal of the changeover switch Q104, at the same time connected to a control terminal of the changeover switch Q105, and a control terminal of the changeover switch Q106. In addition, a first LS driving signal is connected to a negative terminal of the DC input power source Vin, and the first LS driving signal is connected to a control terminal of the changeover switch Q104 and coupled to a second end of the changeover switch Q104, and is also connected to the A control terminal of the changeover switch Q105 is coupled to the second terminal of the changeover switch Q105, and a control terminal of the changeover switch Q106 is coupled to the second terminal of the changeover switch Q106.

In one embodiment, if there is only one first switching element Q1 (as shown in FIG. 1), the first HO driving signal is connected to the control end of the first switching element Q1; the first HS driving signal is connected to the first switching element Q1. The control terminal of the first switching element Q1 is coupled to the second terminal of the first switching element Q1. Similarly, if there is only a second switching element Q2, the first LO driving signal is connected to the control terminal of the second switching element Q2; the first LS driving signal is connected to the control terminal of the second switching element Q2 and is coupled Connected to the second terminal of the second switching element Q2.

In FIG. 2A, a first end and a second end of the switch Q103 are connected in parallel. Diode DZ1, the actual circuit is an embedded diode, so that the first and second ends of the switch Q103 can be embedded in a voltage level, the diode DZ1 and a resistor RZ1 and A series connection of a capacitor CZ1 is connected in parallel; similarly, a diode DZ2 is connected in parallel between the first end and the second end of the changeover switch Q106, which is an embedded diode in operation to make the changeover switch The first and second terminals of Q106 can be embedded in a voltage level. The diode DZ2 is connected in parallel with a series connection line of a resistor RZ2 and a capacitor CZ2.

FIG. 2B shows a second embodiment of the inductor L1, that is, the inductor L1 is composed of a first inductor L11 and a second inductor L12, and is formed by connecting the first inductor L11 and the second inductor L12 in series. The composition, that is to say, the current flowing through the inductor L1 is also the current flowing through the first inductor L11 and then flows through the second inductor L12 to be output. One end of the first inductor L11 is firstly coupled to one end of the current detector 80, and then the other end of the current detector 80 (ie, the current output end) is connected to one end of the second inductor L12 to output current. Io is output to the load 90. In this connection, the current detector 80 can detect the current state of the output current Io as a basis for subsequent current control. Diode D1 is composed of diode D11 and diode D12 connected in parallel. It needs to be stated that in actual application of the present invention, when the actual element winding of the inductive element is manufactured, it can be made as a single inductor L1 as described in FIG. 1, or it can be a first inductor L11 as shown in FIG. 2B. And the inductor element composed of two inductors L12 in series is not limited in the present invention.

The third switching element Q3 is composed of a switching switch Q108, a switching switch Q109, and a switching switch Q110 connected in parallel. The second OUT driving signal includes a second OUTH driving signal and a second OUTL driving signal. The second OUTH driving signal is connected to the control terminal of the changeover switch Q108, at the same time to the control terminal of the changeover switch Q109, and to the control terminal of the changeover switch Q110. The second OUTL driving signal is connected to the control terminal of the changeover switch Q108, at the same time to the control terminal of the changeover switch Q109, and to the control terminal of the changeover switch Q110.

In one embodiment, if there is only one third switching element Q3, the second OUTH driving signal is connected to the control terminal of the third switching element Q3; the second OUTL driving signal is connected to the third switching element Q3. Control terminal. In addition, in FIG. 2B, a series connection line of a diode DZ3 and a diode DZ4 is connected between both ends of the load 90, so that the voltage across the load 90 can be embedded between the diode DZ3 and The voltage level formed by DZ4 connected in series.

FIG. 3 further discloses related circuit configurations of the feedback comparator 20, the hysteresis amplifier 30, and the delay circuit 40. The non-inverting input terminal (+) of the feedback comparator 20 is connected to the current control signal CC; the inverting input terminal (-) of the feedback comparator 20 is connected to a DC 5V voltage source. In one embodiment, the feedback comparator 20 and the hysteresis amplifier 30 include a first amplifier 22 connected to the output amplifier 20 to amplify the output signal. The output of the first amplifier 22 is connected to the relevant circuit of the hysteresis amplifier 30.

A non-inverting input (+) of the hysteresis amplifier 30 is coupled to a filter circuit 25. The filter circuit 25 includes a resistor R11, a resistor R12, a resistor R13, and a switch Q200. The first end of the resistor R11 (such as the upper end of the resistor R11 in FIG. 3) is connected to the current control signal PC. One end (as the left end of the resistor R12 in FIG. 3) is coupled to the second end of the resistor R11 (as the lower end of the resistor R11 in FIG. 3); the first end of the resistor R13 (as the upper end of the resistor R13 in FIG. 3) Is coupled to the second terminal of the resistor R11, and the second terminal of the resistor R13 (as shown in the lower end of the resistor R13 in FIG. 3) is coupled to the non-inverting input terminal (+) of the hysteresis amplifier 30; The first terminal is coupled to the second terminal of the resistor R12, the second terminal of the changeover switch Q200 is grounded, and the control terminal of the changeover switch Q200 is connected to a current pulse wave control signal IPWM.

In addition, as shown in Fig. 3, when the PWM of the pulse wave (PULSE) is modulated, when the output of each switch is switched on / off in parallel (Shunt), a current pulse wave will be generated. Electrical energy is still stored in L1. When the current pulse is sent out when the output is open, due to the high-speed di / dt relationship, there will be a slight current surge and overshoot. In order to avoid this, Phenomenon, the circuit control of the present invention includes reducing the level of the current control signal PC at the same time when the output is short-circuited, thereby reducing the energy storage energy of the inductor L1, and reducing the current surge and overshoot. The phenomenon.

The above-mentioned circuit function of the filter circuit 25 that can eliminate the surge is mainly related to the switching effect of the switch Q200 to solve the problem of spikes. Please refer to the main circuit diagrams of FIG. 2A and FIG. 2B for the main architecture circuit of this case. There are two states:

(1) In the state of transmitting energy, the energy is output through the switches Q101, Q102, 103 to the first inductor L11, that is, the second inductor L12.

(2) In the state of no energy output, the switch Q104, Q105, 106 and the switch Q108, Q109, 110 are turned on, and the output is short-circuited.

Because the inductive element still has energy (continue mode) in the second state, when switching to another state, there will be a spike (Spike), as shown by the reference symbol SP in the state diagram of the output current Io in Figure 8 , SP is the surge. Therefore, the principle of the solution is to change the voltage value of the feedback (that is, turning on the switch Q200 will change the divided resistance of the feedback) in the second state, thereby reducing the stored energy in the inductive element and solving the problem. The problem of Spike; among them, the signal labeled PC is a current control signal, which is used for current control.

The reverse input terminal (-) of the hysteresis amplifier 30 of FIG. 3 is coupled to the output terminal of the first amplifier 22. In one embodiment, a second amplifier 32 is coupled between the hysteresis amplifier 30 and the delay circuit 40. The second amplifier 32 is used to amplify the output signal of the hysteresis amplifier 30. The output of the second amplifier 32 is then connected to the delay circuit 40.

The delay circuit 40 shown in FIG. 3 includes a first inverter 41 and a second inverter 42. The input terminal of the first inverter 41 is coupled to the resistor 24, and the output terminal of the first inverter is coupled to the input terminal of the second inverter 42. The output terminal of the second inverter 42 is coupled to a resistor R26, and the other end of the resistor R26 (the left end of the resistor R26 as shown in FIG. 3) is used to output the first delay signal Hin. The body D26 is connected in parallel, and the cathode terminal of the diode D26 is coupled to the output of the second inverter 42. Out. The output of the first inverter 41 is also coupled to a resistor R25, and the other end of the resistor R25 (the left end of the resistor R25 as shown in FIG. 3) is used to output the second delay signal Lin. The pole body D25 is connected in parallel, and the cathode terminal of the diode body D25 is coupled to the output terminal of the first inverter 41. In this way, FIG. 3 outputs the first delay signal Hin and the second delay signal Lin, and then transmits them to the first driving circuit 50 to further drive the first switching element Q1 and the second switching element Q2 to perform the switching operation.

FIG. 4 illustrates that the first driving circuit 50 inputs the first delayed signal Hin and the second delayed signal Lin, and then outputs a first HO driving signal, a first HS driving signal, a first LO driving signal, and a first LS driving signal. In practice, the first driving circuit 50 is completed by a single-chip IC component. By inputting power to the IC and related line connection specifications, the first delayed signal Hin and the second delayed signal Lin can be input. After that, the first HO driving signal, the first HS driving signal, the first LO driving signal, and the first LS driving signal are output.

Similarly, FIG. 5 is a schematic diagram of the second driving circuit 70. In practice, the second driving circuit 70 is also completed by a single-chip IC element, and the power is inputted to the IC element of the second driving circuit 70. And related line connection specifications, that is, it can convert the input current pulse control signal IPWM into outputting the second OUTH driving signal and the second OUTL driving signal.

However, in contrast to the way in which the pulse wave (PULSE) is input to the second driving circuit 70 in FIG. 1, in an embodiment, please refer to FIG. 6 to see how the pulse wave (PULSE) is converted into a current pulse wave. The description of the implementation of the control signal IPWM is mainly completed through the connection mode of a pulse wave converter 72. In FIG. 6, the pulse signal (PULSE) signal is coupled to an input terminal of a third inverter 43, and an output terminal of the third inverter 43 is connected to a control terminal of a switching element S1 and a first terminal of the switching element S1. (The upper end of the switching element S1 as shown in FIG. 6) is an input terminal of the pulse wave converter 72, and the second terminal of the switching element S1 is grounded.

On the other hand, the input of the pulse wave converter 72 also includes a current displacement control. The signal ISIM, wherein the ON and OFF of the current displacement control signal ISIM and the ON and OFF of the pulse wave (PULSE) described above can control different current control modes, thereby generating output currents Io of different current pulse wave patterns. In this way, the embodiments of the present invention can adjust different current control modes according to different load requirements, and can be used for programming current Program Current, which has a very wide application range. In practice, the pulse wave converter 72 is a single-chip IC, and the IC of the pulse wave converter 72 includes the current pulse wave control signal IPWM and a current setting signal ISET.

FIG. 7 shows the current setting signal ISET passing through the amplifier 52 to generate the current control signal PC. The current setting signal ISET is coupled to the non-inverting input terminal (+) of the amplifier 52, the inverting input terminal (-) of the amplifier 52 is coupled to the output terminal of the amplifier 52, and the output terminal of the amplifier 52 outputs the current control signal PC.

FIG. 8 is a waveform diagram of the output current Io, which shows that the output current Io is in the form of a pulse width modulation PWM, and the output current Io can have a current displacement according to the user's demand for the load 90 modulation. The level adjustment of SH does not necessarily start from the 0 level, and in subsequent adjustments, it can also meet the needs of the user to adjust the current level to the 0 level. Further, the output of the present invention The current Io can be adjusted according to the demand of the load and has a displacement level. This displacement level is the current displacement SH in FIG. 8. It is obvious that the power supply control circuit of the present invention has extremely different requirements according to different load characteristics, can perform different modulations of the output current Io, and effectively improves the defects of the prior art. The reference numeral SP in FIG. 8 is a surge, and is filtered by the filter circuit 25 shown in FIG. 3.

The embodiment disclosed in FIG. 9 may be an inductor L1 composed of a first inductor L11 in series with a second inductor L12. The core material of the inductor L1 is composed of a soft magnetic metal magnetic powder core in an embodiment, and the material is, for example, It consists of a composite of iron and silicon, the core is covered with epoxy resin as a whole, and the structure is a concentric circular cylinder. The core has two sets of windings, forming a first inductor L11 and a The second inductor L12, and the inductor L1 is connected in series by the first inductor L11 and the second inductor L12. The core material of the first inductor L11 and the second inductor L12 is also composed of a soft magnetic metal magnetic powder core. The same material includes, for example, a composite of iron and silicon, and the core is covered with epoxy resin as a whole. One end of the first inductor L11 is coupled to one end of the current detector 80, and the other end of the current detector 80 is connected to one end of the second inductor L12 to detect the output current. Io. The actual circuit of the current detector 80 can be completed by a Hall current conversion element.

FIG. 10 is a schematic diagram showing the magnetic permeability technical characteristics of the inductor L1. When the DC magnetization force Oe (shown on the horizontal axis) of the inductor L1 exceeds a critical value, the inductance L1 will be The initial permeability (Percent of Initial Permeability%, as shown on the vertical axis) will exhibit a gently decreasing non-linear permeability characteristic. Such characteristics will make the power supply control circuit of the present invention as a whole have a good ripple elimination effect on the ripple phenomenon at the load end. At the same time, the frequency bandwidth that the circuit architecture of the present invention can control is large and the transient response is fast. It is easy to control in the declining interval.

FIG. 11 is an embodiment of the inductor L1 in the present invention. As shown in FIG. 11, the single inductor L1 is a multi-turn cylindrical winding, and is wound around the soft magnetic metal powder core by winding or stacking. Composed of cores. FIG. 12 is another embodiment of the inductor L1 in the present invention. As can be seen from FIG. 12, a single inductor L1 is wound around the core of the soft magnetic metal powder core in a winding or stacking manner through multiple turns of flat windings. Composed of. In an embodiment, the core weight of the inductor L1 in the present invention is between 290g and 330g, wherein the output current Io may be greater than 50 amps. In addition, in the embodiment where the inductor L1 is connected in series by the first inductor L11 and the second inductor L12, the core weight of the first inductor L11 is between 145g and 165g, and the core weight of the second inductor L12 is Between 145g-165g; similarly, the output current Io can be greater than 50 amps. In addition, the cores of the first inductor L11 and the second inductor L12 may have different weights, and the layout on the circuit board may be adjusted accordingly, but the total weight needs to be greater than 250g.

In summary, the present invention provides a power supply control circuit, which can improve the existing lack of constant voltage hysteresis control and effectively achieve high accuracy and response speed. Fast and high power high voltage power control purpose. In addition, the technical effects of a wide range of loads and program current applications can be further realized, and the control of line applications can be simplified, and the shortcomings of the existing technology can be effectively improved. It is obvious that the present invention has the requirements for patent application.

However, what is described in the description of the present invention is only an example of a preferred embodiment. When the scope of protection of the present invention cannot be limited by it, any local changes, modifications or additions of technology still do not depart from the scope of protection of the present invention. in.

Claims (17)

A power control circuit is used to drive a high-power and high-current load. The power control circuit includes: a DC input power Vin; an input capacitor C1 connected in parallel with the DC input power Vin; and a first switching element Q1. The first terminal of the first switching element Q1 is coupled to the positive terminal of the DC input power source Vin; a second switching element Q2, and the first terminal of the second switching element Q2 is coupled to the second of the first switching element Q1. Terminal, the second terminal of the second switching element Q2 is coupled to the negative terminal of the DC input power source Vin; an inductor L1, the first terminal of the inductor L1 is coupled to the second terminal of the first switching element Q1, the The inductor L1 outputs an output current Io in the form of pulse width modulation PWM; a current detector, which is connected in series with the inductor L1 to detect the output current Io, and outputs a current detection signal CC A third switching element Q3, a first terminal of the third switching element Q3 is coupled to the second terminal of the inductor L1, and a second terminal of the third switching element Q3 is coupled to the negative terminal of the DC input power source Vin ; A load, the load is coupled to the third switching element Q3 Between one end and the second end of the third switching element Q3 and driven by the output current Io; a hysteresis current controller, the hysteresis current controller is connected to the first switching element Q1, the second The switching elements Q2 and the individual control terminals of the third switching element Q3 are coupled, and the current detection signal CC is input, and a pulse wave and a current control signal PC are input. The hysteresis current controller is used to provide the first ~ The driving signals required for the third switching elements Q1 ~ Q3; the hysteresis current controller includes a hysteresis amplifier, and the non-inverting input terminal of the hysteresis amplifier is coupled to the current control signal PC, and the hysteresis The inverting input of the amplifier is coupled to the output of a feedback comparator. The power supply control circuit according to claim 1, wherein in the feedback comparator, the non-inverting input terminal of the feedback comparator is to input the current detection signal CC, and the inversion of the feedback comparator is The input terminal is coupled to a resistor RCC1 and grounded, and is connected to the output terminal of the feedback comparator via a resistor RCC2. According to the power supply control circuit of claim 1, wherein the hysteresis current controller includes: a delay circuit, an input terminal of the delay circuit is coupled to an output terminal of the hysteresis amplifier, and the delay circuit outputs A first delay signal Hin and a second delay signal Lin. The power supply control circuit according to item 1 of the claim, wherein the hysteresis current controller includes: a first driving circuit that inputs the first delay signal Hin and the second delay signal Lin and outputs a first An H driving signal and a first L driving signal. The first H driving signal is coupled to a control terminal of the first switching element Q1, and the first L driving signal is coupled to a control terminal of the second switching element Q2. The power supply control circuit according to claim 1, wherein the hysteresis current controller includes: a second driving circuit that inputs the pulse wave and outputs a second OUT driving signal, the second OUT driving The signal is coupled to the control terminal of the third switching element Q3. The power control circuit according to claim 4, wherein the first H driving signal includes a first HO driving signal and a first HS driving signal, and the first HO driving signal is connected to the first switching element Q1. The first HS driving signal is connected to the control terminal of the first switching element Q1 and is coupled to the second terminal of the first switching element Q1. The power control circuit according to claim 4, wherein the first L driving signal includes a first LO driving signal and a first LS driving signal, and the first LO driving signal is connected to the second switching element Q2. Control end; the first LS The driving signal is connected to the control terminal of the second switching element Q2 and is coupled to the second terminal of the second switching element Q2. The power control circuit according to claim 5, wherein the second OUT driving signal includes a second OUTH driving signal and a second OUTL driving signal, and the second OUTH driving signal is connected to the third switching element Q3. The control terminal of the second OUTL driving signal is connected to the control terminal of the third switching element Q3. According to the power supply control circuit of claim 1, wherein the hysteresis current controller includes a filter circuit, the filter circuit includes: a resistor R11, a first end of the resistor R11 is connected to the current control signal PC; A resistor R12, a first terminal of the resistor R12 is coupled to a second terminal of the resistor R11; a resistor R13, a first terminal of the resistor R13 is coupled to a second terminal of the resistor R11, and a second terminal of the resistor R13 Coupled to the non-inverting input terminal of the hysteresis amplifier; and a changeover switch Q200, the first end of the changeover switch Q200 is coupled to the second end of the resistor R12, the second end of the changeover switch Q200 is grounded, and The control terminal of the changeover switch Q200 is connected with a current pulse control signal IPWM. According to the power supply control circuit described in claim 1, wherein the hysteresis current controller includes a protection circuit, the protection circuit is a logic OR gate that closes the latch, and the logic OR gate input has an overcurrent signal and an over Temperature signal, and output a shutdown signal, the shutdown signal is connected to the first drive circuit; when an over-current or over-temperature situation occurs, the drive signal output of the first drive circuit is cut off. The power supply control circuit according to item 1 of the claim, wherein the iron core of the inductor L1 is composed of a soft magnetic metal magnetic powder core, is a concentric circular flat cylinder, and the iron core is covered with epoxy resin. The power supply control circuit according to item 11 of the claim, wherein the inductor L1 further includes a first inductor L11 and a second inductor L12. At this time, the inductor L1 is connected in series by the first inductor L11 and the second inductor L12. One end of the first inductor L11 is coupled to one end of the current detector, and then the current detection The other end of the tester is connected to one end of the second inductor L12 for detecting the output current Io. According to the power supply control circuit of claim 11, wherein the magnetic permeability technical characteristic of the inductor L1 is that when the DC magnetization force of the inductor L1 exceeds a critical value, the initial magnetic permeability of the inductor L1 will be relaxed. Degraded nonlinear magnetic permeability. The power supply control circuit according to item 11 of the claim, wherein the inductor L1 is composed of a multi-turn cylindrical winding wound around the core in a winding or stacking manner. The power supply control circuit according to item 11 of the claim, wherein the inductor L1 is formed by winding or stacking the multi-turn flat wire around the core. According to the power supply control circuit described in claim 1, wherein the core weight of the inductor L1 is between 290g and 330g; wherein the output current Io may be greater than 50 amps. The power control circuit according to item 14, wherein the core weight of the first inductor L11 is between 145g and 165g, and the core weight of the second inductor L12 is between 145g and 165g. Between; where the output current Io can be greater than 50 amps.