TWI646766B - Oscillator and associated direct current-to-direct current converter applying the oscillator - Google Patents
Oscillator and associated direct current-to-direct current converter applying the oscillator Download PDFInfo
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Abstract
一種振盪器,其包括參考電流產生電路、調變器電路和振盪電路。 參考電流產生電路產生第一參考電流。 調變電路根據第一參考電流以及反饋電壓產生調變電流,其中調變電流與反饋電壓呈負相關。振盪電路至少接收調變電流,並且至少根據調變電流產生具有振盪頻率的振盪信號,其中振盪頻率根據調變電流而變化。振盪器可以被直流轉直流電壓轉換器所採用。An oscillator includes a reference current generating circuit, a modulator circuit, and an oscillating circuit. The reference current generating circuit generates a first reference current. The modulation circuit generates a modulation current according to the first reference current and the feedback voltage, wherein the modulation current is negatively correlated with the feedback voltage. The oscillating circuit receives at least the modulating current and generates an oscillating signal having an oscillating frequency based on at least the modulating current, wherein the oscillating frequency varies according to the modulating current. The oscillator can be used by a DC to DC voltage converter.
Description
本發明係關於一種振盪器及直流轉直流轉換器。The present invention relates to an oscillator and a DC to DC converter.
以電流模式為例,當電流模式工作的降壓型轉換器或升壓型轉換器初始啟動時,輸出電壓相對較低,電感電流因此具有較大的斜率,使得電流檢測電路需要時間來檢測表示電感電流。因此,當電感電流在高頻率下工作並且具有大的斜率時,電感電流會難以控制。為了使感測控制電路準確且高效地控制電感電流,降壓型轉換器或升壓型轉換器透過調變振盪器的頻率來抑制電感電流和輸出電壓的變化。另外,當在如降壓型轉換器的典型直流轉直流轉換器的輸出端處發生短路時,輸出端將短路到接地或者到低電源電壓。輸入端和輸出端之間產生的巨大電壓準位導致強電流通過直流轉直流轉換器的電感,而可能造成電路的損壞。為了在輸出端和輸入端之間的電壓準位相對較大時減輕強電感電流,需要對直流轉直流變換器的振盪器產生的振盪信號進行頻率調變,其中透過頻率調變,感測控制電路可以抑制電流。此外,與跳頻的方式相比,通過相對線性的頻率調變,從開始到穩態的過程將是相對穩定的。Taking the current mode as an example, when the current mode operation of the buck converter or the boost converter is initially started, the output voltage is relatively low, and the inductor current thus has a large slope, so that the current detecting circuit takes time to detect the representation. Inductor current. Therefore, when the inductor current operates at a high frequency and has a large slope, the inductor current can be difficult to control. In order for the sensing control circuit to accurately and efficiently control the inductor current, the buck converter or boost converter suppresses the change in the inductor current and the output voltage by the frequency of the modulating oscillator. In addition, when a short circuit occurs at the output of a typical DC to DC converter such as a buck converter, the output will be shorted to ground or to a low supply voltage. The large voltage level generated between the input and the output causes a strong current to pass through the inductance of the DC to DC converter, which may cause damage to the circuit. In order to reduce the strong inductor current when the voltage level between the output terminal and the input terminal is relatively large, the oscillating signal generated by the oscillator of the DC-to-DC converter needs to be frequency-modulated, wherein the frequency modulation and the sensing control are transmitted. The circuit can suppress current. In addition, the process from start to steady state will be relatively stable by relatively linear frequency modulation compared to frequency hopping.
本發明的其中一個目的是提供一種振盪器及使用該振盪器之關聯的直流轉直流轉換器,以藉此解決前述問題。It is an object of the present invention to provide an oscillator and associated DC to DC converter using the oscillator to thereby solve the aforementioned problems.
根據本發明的一個實施例,公開了一種振盪器。振盪器包括參考電流產生電路、調變器電路和振盪電路。參考電流產生電路被配置產生第一參考電流。調變器電路耦接參考電流產生電路,用以依據第一參考電流以及回授電壓產生調變電流,其中調變電流與回授電壓呈負相關。振盪電路耦接調變器電路,用以至少接收調變電流,並至少依據調變電流產生具有振盪頻率的振盪信號,其中振盪頻率根據調變電流而變化。According to one embodiment of the invention, an oscillator is disclosed. The oscillator includes a reference current generating circuit, a modulator circuit, and an oscillating circuit. The reference current generating circuit is configured to generate a first reference current. The modulating circuit is coupled to the reference current generating circuit for generating a modulating current according to the first reference current and the feedback voltage, wherein the modulating current is negatively correlated with the feedback voltage. The oscillating circuit is coupled to the modulating circuit for receiving at least the modulating current and generating an oscillating signal having an oscillating frequency according to at least the modulating current, wherein the oscillating frequency changes according to the modulating current.
根據本發明的一個實施例,公開了一種直流轉直流轉換器。直流轉直流轉換器包括電感-電容電路、反饋電路和振盪器。電感-電容電路至少包括電感和電容,並且被配置為從經由至少一開關從直流轉直流轉換器的輸入電壓源接收電感電流,以提供能量給隨後的負載。反饋電路耦接電感電容電路,用於根據電感電流產生反饋電壓。振盪器耦接反饋電路,用以根據反饋電壓產生振盪信號,其中開關根據振盪信號進行控制。振盪器包括參考電流產生電路、調變器電路和振盪電路。參考電流產生電路被配置產生第一參考電流。調變器電路耦接參考電流產生電路,用以依據第一參考電流以及回授電壓產生調變電流,其中調變電流與回授電壓呈負相關。振盪電路耦接調變器電路,用以至少接收調變電流,並至少依據調變電流產生具有振盪頻率的振盪信號,其中振盪頻率根據調變電流而變化。In accordance with an embodiment of the present invention, a DC to DC converter is disclosed. The DC to DC converter includes an inductor-capacitor circuit, a feedback circuit, and an oscillator. The inductor-capacitor circuit includes at least an inductor and a capacitor, and is configured to receive an inductor current from an input voltage source of the DC to DC converter via at least one switch to provide energy to a subsequent load. The feedback circuit is coupled to the inductor-capacitor circuit for generating a feedback voltage according to the inductor current. The oscillator is coupled to the feedback circuit for generating an oscillating signal according to the feedback voltage, wherein the switch is controlled according to the oscillating signal. The oscillator includes a reference current generating circuit, a modulator circuit, and an oscillating circuit. The reference current generating circuit is configured to generate a first reference current. The modulating circuit is coupled to the reference current generating circuit for generating a modulating current according to the first reference current and the feedback voltage, wherein the modulating current is negatively correlated with the feedback voltage. The oscillating circuit is coupled to the modulating circuit for receiving at least the modulating current and generating an oscillating signal having an oscillating frequency according to at least the modulating current, wherein the oscillating frequency changes according to the modulating current.
對於本領域普通技術人員來說,在閱讀以下各個附圖和附圖中所示的優選實施例的詳細描述後,本發明的這些和其它目的將無疑將變得顯而易見。These and other objects of the present invention will become apparent to those skilled in the <RTIgt;
整個說明書和權利要求中使用了某些術語來指代特定的部件。如本領域技術人員將認識到的,製造商可以通過不同的名稱來引用組件。本說明書未特定地區分名稱不同但功能卻相同的組件。在下面的描述和權利要求書中,術語「包括」和「包含」以開放式的方式使用,因此不應被解釋為諸如「由...組成」的封閉式術語。另外,術語「耦合」旨在表示間接或直接的電連接。因此,如果一個設備耦合到另一個設備,則此連接可以通過直接電連接,或者通過經由其他設備和連接的間接電連接。Certain terminology is used throughout the specification and claims to refer to the particular features. As those skilled in the art will recognize, manufacturers can reference components by different names. This manual does not specifically distinguish between components with different names but the same functions. In the following description and claims, the terms "including" and "comprising" are used in an open-ended manner and should not be construed as a closed term such as "consisting of." In addition, the term "coupled" is intended to mean an indirect or direct electrical connection. Thus, if one device is coupled to another device, the connection can be through a direct electrical connection, or through an indirect electrical connection via other devices and connections.
如現有技術中所述,對於諸如降壓型轉換器或升壓型轉換器的直流轉直流轉換器,其需要頻率調變。圖1舉例說明具有斜率補償機制的傳統電流模式降壓型轉換器。電流模式降壓型轉換器10包括輸入電壓源101、開關電路102、電感-電容電路103、反饋電路104與振盪器105。輸入電壓源101用於提供輸入電壓Vin。開關電路102包括開關SW 1和SW 2,開關SW 1和SW 2分別被脈寬調變(PWM)信號和反相PWM信號所控制,其中PWM信號和反相PWM信號根據來自振盪器105的振盪信號CLK產生。電感-電容電路103包括電感L和電容C,其中開關電路102響應於電感-電容電路103的電感L經由電感電流I L存儲/釋放能量,並且所釋放的能量被如圖1所示通過負載電流I load的隨後負載所利用。反饋電路104包括電阻R 1和R 2,其用於根據電感電流I L產生反饋電壓V FB於端子N 1,其中端子N 1耦合在電阻R 1和R 2之間。當負載電流I load具有顯著的變化,電流模式降壓型轉換器10無法立即地穩定輸出電壓V O,從而導致反饋電壓V FB的變化。電流模式降壓型轉換器10進一步包括典型的峰值電流模式控制器106。典型的峰值電流模式控制器106包括誤差放大器116、加法器126、斜率補償電路136、比較器146、控制邏輯電路156、高側電流感測電路166、電阻R'與電容C'。誤差放大器116包括負輸入端與兩正輸入端,負輸入端用於接收反饋電壓V FB,兩正輸入端分別用於接收軟啟動電壓Vss和參考電壓Vref1,以在誤差放大器116的輸出端產生電壓V C。加法器126用於接收電流感測電壓Vcs與斜坡電壓V R,其中高側電流感測電路166感測端子N 2上的電流以產生電流感測電壓Vcs,且斜坡電壓V R由斜率補償電路136產生。比較器146用以產生比較信號於其輸出端。控制邏輯電路156包括括SR鎖存器156_1,其中SR鎖存器156_1接收由振盪器105產生的振盪信號CLK以及由比較器146產生的比較信號,以分別產生PWM信號和反相PWM信號於其輸出端Q與反相輸出端 ,且WM信號和反相PWM信號被傳送到如圖1所示的開關電路102。誤差放大器116的輸出端連接串聯的電阻R'和電容C',其中電阻R'和電容C'構成補償電路。然而,補償電路不限於由電阻R'和電容C'實現。本領域技術人員應該理解,補償電路可以通過不同的架構來實現。具有斜率補償機制的電流模式降壓型轉換器10應該是本領域技術人員所熟知的。 As described in the prior art, for a DC to DC converter such as a buck converter or a boost converter, it requires frequency modulation. Figure 1 illustrates a conventional current mode buck converter with a slope compensation mechanism. The current mode buck converter 10 includes an input voltage source 101, a switching circuit 102, an inductor-capacitor circuit 103, a feedback circuit 104, and an oscillator 105. The input voltage source 101 is used to provide an input voltage Vin. Includes a switching circuit 102 out switch SW 1 and SW 2, out switch SW 1 and SW 2 are controlled by pulse width modulation (PWM) signal and an inverted PWM signal, wherein the PWM signal and the inverted PWM signal from the oscillation of the oscillator 105 The signal CLK is generated. The inductor-capacitor circuit 103 includes an inductor L and a capacitor C, wherein the switch circuit 102 stores/releases energy via the inductor current I L in response to the inductance L of the inductor-capacitor circuit 103, and the released energy is passed through the load current as shown in FIG. The subsequent load of I load is utilized. The feedback circuit 104 includes resistors R 1 and R 2 for generating a feedback voltage V FB from the inductor N L to the terminal N 1 , wherein the terminal N 1 is coupled between the resistors R 1 and R 2 . When the load current I load has a significant change, the current mode buck converter 10 cannot immediately stabilize the output voltage V O , resulting in a change in the feedback voltage V FB . The current mode buck converter 10 further includes a typical peak current mode controller 106. A typical peak current mode controller 106 includes an error amplifier 116, an adder 126, a slope compensation circuit 136, a comparator 146, a control logic circuit 156, a high side current sensing circuit 166, a resistor R' and a capacitor C'. The error amplifier 116 includes a negative input terminal for receiving the feedback voltage V FB and two positive input terminals for receiving the soft start voltage Vss and the reference voltage Vref1 for generating at the output of the error amplifier 116. Voltage V C . The adder 126 is configured to receive the current sensing voltage Vcs and the ramp voltage V R , wherein the high side current sensing circuit 166 senses the current on the terminal N 2 to generate the current sensing voltage Vcs, and the ramp voltage V R is determined by the slope compensation circuit 136 is produced. Comparator 146 is operative to generate a comparison signal at its output. The control logic circuit 156 includes an SR latch 156_1, wherein the SR latch 156_1 receives the oscillating signal CLK generated by the oscillator 105 and the comparison signal generated by the comparator 146 to generate a PWM signal and an inverted PWM signal, respectively. Output Q and inverting output And the WM signal and the inverted PWM signal are transmitted to the switching circuit 102 as shown in FIG. The output of the error amplifier 116 is connected to a series resistor R' and a capacitor C', wherein the resistor R' and the capacitor C' constitute a compensation circuit. However, the compensation circuit is not limited to being implemented by the resistor R' and the capacitor C'. Those skilled in the art will appreciate that the compensation circuit can be implemented by different architectures. A current mode buck converter 10 having a slope compensation mechanism should be well known to those skilled in the art.
本發明著重於具有頻率調變能力的振盪器105,以解決現有技術中提到的問題。在此請注意,本發明所公開的振盪器105不限於應用於如圖1所示的降壓型轉換器。在其他實施例中,振盪器105可以替代地應用於升壓型轉換器。The present invention focuses on an oscillator 105 having frequency modulation capability to solve the problems mentioned in the prior art. It is noted here that the oscillator 105 disclosed herein is not limited to application to a buck converter as shown in FIG. In other embodiments, the oscillator 105 can alternatively be applied to a boost converter.
圖2是根據本發明實施例的振盪器105的示意圖。振盪器105包括參考電流產生電路210、調變器電路220和振盪電路230。參考電流產生電路210包括電晶體MN1、MP1、MP2和MP3、電阻R和放大器211。如圖2所示,電晶體MP1和MP3構成用於根據電流I RT產生參考電流I s的第一電流鏡,電晶體MP1和MP2構成用於根據電流I RT產生參考電流I r的第二電流鏡。電流I RT由運算跨導放大器(OTA)產生,其中OTA由放大器211、電晶體MN1和電阻R組成,並構成電流源,OTA的工作和特性應為本領域技術人員所熟知,因此為了簡潔,在此省略細節。在此請注意,出於調變目的,參考電流I s的大小被配置為小於參考電流I r的大小,這意味著,根據電流淨的特性,電晶體MP3之寬度-長度比率被配置為小於電晶體MP2的寬度-長度比率,亦即(W MP3/ L MP3)<(W MP2/ L MP2)。調變器電路220被配置為根據參考電流I s和來自電流模式降壓型轉換器10的反饋電路104的反饋電壓V FB生成調變電流I d。更具體地,調變器電路220包括比較器221,且比較器221由參考電流I s驅動,以用於比較反饋電壓V FB與參考電壓Vref4,從而產生調變電流I d。 2 is a schematic diagram of an oscillator 105 in accordance with an embodiment of the present invention. The oscillator 105 includes a reference current generating circuit 210, a modulator circuit 220, and an oscillating circuit 230. The reference current generating circuit 210 includes transistors MN1, MP1, MP2, and MP3, a resistor R, and an amplifier 211. As shown, the transistors MP1 and MP3 2 constitute a first current mirror for generating a reference current according to the current I s I RT, the transistors MP1 and MP2 form a second current for generating a reference current I RT I r according to the current mirror. The current I RT is generated by an operational transconductance amplifier (OTA), which consists of an amplifier 211, a transistor MN1, and a resistor R, and constitutes a current source. The operation and characteristics of the OTA should be well known to those skilled in the art, so for the sake of brevity, Details are omitted here. Note here that for modulation purposes, the magnitude of the reference current I s is configured to be smaller than the magnitude of the reference current Ir , which means that the width-to-length ratio of the transistor MP3 is configured to be smaller than the net current characteristic. The width-to-length ratio of the transistor MP2, that is, (W MP3 / L MP3 ) < (W MP2 / L MP2 ). Modulator circuit 220 is configured to generate a modulation current in accordance with the feedback voltage V FB feedback circuit 104 and the reference current I s buck converter 10 from the current mode of the I d. More specifically, the modulator circuit 220 includes a comparator 221, and the comparator 221 is driven by a reference current I s for comparing the feedback voltage V FB with the reference voltage Vref4 to generate a modulation current I d .
調變器電路220的詳細操作和結構將在後面討論。振盪電路230包括振盪電容C s、電晶體Mosc、比較電路231和脈衝產生器電路232。如圖2所示,振盪電容C s的一端耦接參考電流I r、調變電流I d、電晶體Mosc的汲極與比較電路231的輸入端,而振盪電容C s的另一端則耦接至參考電壓(如,接地電壓),其中震盪電容C s接收參考電流I r與調變電流I d,以在比較電路231的輸入端產生電壓Vsense。比較電路231的另一輸入端耦接參考電壓Vref3,比較電路231將參考電壓Vref3與電壓Vsense進行比較,並將結果輸出至脈衝產生器電路232。脈衝產生器電路232根據比較電路231的輸出產生振盪信號CLK。振盪電路230的細節係是本領域技術人員所熟知者。由於本發明著眼於頻率調變,所以這裡省略了振盪電路230的詳細操作。在本實施例中,電晶體MP1、MP2和MP3由P型金屬氧化物半導體場效應電晶體(MOSFET)實現,而電晶體MN1由N型MOSFET實現。 The detailed operation and structure of the modulator circuit 220 will be discussed later. The oscillating circuit 230 includes an oscillating capacitor C s , a transistor Mosc, a comparison circuit 231, and a pulse generator circuit 232. As shown in FIG. 2, one end of the oscillating capacitor C s is coupled to the reference current I r , the modulating current I d , the drain of the transistor Mosc and the input end of the comparison circuit 231 , and the other end of the oscillating capacitor C s is coupled To a reference voltage (eg, a ground voltage), wherein the oscillating capacitor C s receives the reference current I r and the modulating current I d to generate a voltage Vsense at the input of the comparison circuit 231. The other input terminal of the comparison circuit 231 is coupled to the reference voltage Vref3, and the comparison circuit 231 compares the reference voltage Vref3 with the voltage Vsense and outputs the result to the pulse generator circuit 232. The pulse generator circuit 232 generates an oscillation signal CLK based on the output of the comparison circuit 231. The details of the oscillating circuit 230 are well known to those skilled in the art. Since the present invention focuses on frequency modulation, the detailed operation of the oscillation circuit 230 is omitted here. In the present embodiment, the transistors MP1, MP2 and MP3 are realized by a P-type metal oxide semiconductor field effect transistor (MOSFET), and the transistor MN1 is realized by an N-type MOSFET.
圖3是根據本發明實施例的振盪器105的調變器電路220的示意圖。調變器電路220包括電晶體MP4、MP5、MN2、MN3和MN4,其中電晶體MN3和MN4構成第三電流鏡。如圖3所示,電晶體MP4的閘極耦接電流模式降壓型轉換器10的反饋電壓V FB,電晶體MP4的汲極耦接電晶體MN3的汲極,電晶體MP4的源極耦接參考電流I s。此外,電晶體MP5的閘極耦接參考電壓Vref4,電晶體MP5的汲極耦接電晶體MN2的汲極,電晶體MN2藉由將其閘極與汲極相連而被配置為電阻,電晶體MP5的源極耦接參考電流I s。在其他實施例中,電晶體MN2可以由實際電阻來實現,且本發明非以此為限制。最後,電晶體MN4並聯到振盪電容C s(電晶體MN4的汲極耦接到振盪電容C s)。再者,電晶體MN3的閘極耦接電晶體MN4的閘極與電晶體MN3的汲極。在實施例中,電晶體MP4和MP5由P型MOSFET實現,而電晶體MN2~MN4由N型MOSFET實現。如上所述,當輸入電壓Vin和輸出電壓V O之間的電壓準位相對較大時,需進行頻率調變,並且在降壓型轉換器中,當輸出電壓V O太小時(這意味著反饋電壓V FB相對較小),更需要進行頻率調變。調變器電路220將反饋電壓V FB與參考電壓Vref4進行比較,以調整由振盪電容C s接收的電流。更具體而言,當反饋電壓V FB小於參考電壓Vref4時,電晶體MP4從參考電流I s汲取比電晶體MP5更多的電流,並且根據電流鏡的特性,電晶體MN4的汲極接收調變電流I d,其中調變電流I d為參考電流I r未通過振盪電容C s的一部分。因此,振盪電路230係根據調變電流I d與參考電流I r來產生具有振盪頻率的振盪信號CLK。這樣,振盪電容C s接收的電流較小,從而將振盪信號CLK的振盪頻率控制得較慢(較低)。當反饋電壓V FB變大時,電晶體MN4汲取較少的調變電流I d(亦即,調變電流I d與反饋電壓V FB為負相關),這意味著振盪信號CLK的振盪頻率變快(變高)。 3 is a schematic diagram of a modulator circuit 220 of an oscillator 105 in accordance with an embodiment of the present invention. The modulator circuit 220 includes transistors MP4, MP5, MN2, MN3, and MN4, wherein the transistors MN3 and MN4 form a third current mirror. As shown in FIG. 3, the gate of the transistor MP4 is coupled to the feedback voltage V FB of the current mode buck converter 10, the drain of the transistor MP4 is coupled to the drain of the transistor MN3, and the source of the transistor MP4 is coupled. Connect to the reference current I s . In addition, the gate of the transistor MP5 is coupled to the reference voltage Vref4, the drain of the transistor MP5 is coupled to the drain of the transistor MN2, and the transistor MN2 is configured as a resistor by connecting its gate to the drain, the transistor The source of the MP5 is coupled to the reference current I s . In other embodiments, the transistor MN2 can be implemented by actual resistance, and the invention is not limited thereto. Finally, in parallel to the oscillation transistor MN4 capacitance C (drain of transistor MN4 is coupled to a capacitance oscillating C s) s. Furthermore, the gate of the transistor MN3 is coupled to the gate of the transistor MN4 and the drain of the transistor MN3. In an embodiment, transistors MP4 and MP5 are implemented by P-type MOSFETs, while transistors MN2 - MN4 are implemented by N-type MOSFETs. As described above, when the voltage level between the input voltage Vin and the output voltage V O is relatively large, frequency modulation is required, and in the buck converter, when the output voltage V O is too small (this means The feedback voltage V FB is relatively small), and frequency modulation is more required. The modulator circuit 220 compares the feedback voltage V FB with the reference voltage Vref4 to adjust the current received by the oscillating capacitor C s . More specifically, when the feedback voltage V FB is smaller than the reference voltage Vref4, the transistor MP4 draws more current from the reference current I s than the transistor MP5, and according to the characteristics of the current mirror, the drain receiving modulation of the transistor MN4 The current I d , wherein the modulation current I d is a part of the reference current Ir that does not pass through the oscillation capacitor C s . Therefore, the oscillation circuit 230 generates the oscillation signal CLK having the oscillation frequency based on the modulation current I d and the reference current Ir . Thus, the received oscillation capacitor C s current is small, so that the oscillation frequency of the oscillation signal CLK is controlled to be slower (lower). When the feedback voltage V FB becomes large, the transistor MN4 draws less modulation current I d (that is, the modulation current I d is negatively correlated with the feedback voltage V FB ), which means that the oscillation frequency of the oscillation signal CLK changes. Fast (higher).
圖4是根據本發明實施例的反饋電壓VFB和調變電流I d的示意圖。如圖4所示,當反饋電壓V FB接近0V時,調變電流I d相對較大,以緩解(降低)振盪信號CLK的振盪頻率。當反饋電壓V FB逐漸增加時,調變電流I d逐漸減小,以加速振盪信號CLK的振盪頻率。這樣可以有效解決現有技術中提到的問題。需要說明的是,上述實施例以降壓型轉換器為例進行說明,然而,調變器電路220的概念也可用於控制施加到升壓型轉換器的振盪信號CLK的振盪頻率。例如,當電流模式升壓型轉換器的輸出電壓大於輸入電壓時,例如,V O= Vin~XVin,其中X是大於1的值,振盪電容接收的電流較小,以緩解(降低)振盪信號CLK的振盪頻率。在這種情況下,調變器電路220的架構應該稍微調整。本領域的技術人員應該理解應用於升壓型轉換器的振盪器105的調變器電路220的實現,為了簡潔起見,這裡省略了詳細描述。 The feedback voltage VFB and the modulation current I d. 4 is a schematic view of an embodiment of the present invention according to FIG. As shown in FIG. 4, when the feedback voltage V FB is close to 0V, the modulation current I d is relatively large to alleviate (reduce) the oscillation frequency of the oscillation signal CLK. When the feedback voltage V FB is gradually increased, the modulation current I d is gradually decreased to accelerate the oscillation frequency of the oscillation signal CLK. This can effectively solve the problems mentioned in the prior art. It should be noted that the above embodiment is described by taking a step-down converter as an example. However, the concept of the modulator circuit 220 can also be used to control the oscillation frequency of the oscillation signal CLK applied to the boost converter. For example, when the output voltage of the current mode boost converter is greater than the input voltage, for example, V O = Vin ~ XVin, where X is a value greater than 1, the oscillating capacitor receives less current to mitigate (reduce) the oscillating signal The oscillation frequency of CLK. In this case, the architecture of the modulator circuit 220 should be slightly adjusted. Those skilled in the art will appreciate the implementation of the modulator circuit 220 applied to the oscillator 105 of the boost converter, and a detailed description is omitted herein for the sake of brevity.
以上所述僅為本發明的較佳實施例,凡依本發明權利要求範圍所做的均等變化與修飾,皆應屬本發明的涵蓋範圍。 因此,上述公開內容應該被解釋為僅由所附權利要求的邊界限制。The above are only the preferred embodiments of the present invention, and all changes and modifications made within the scope of the claims of the present invention should fall within the scope of the present invention. Accordingly, the above disclosure should be construed as limited only by the scope of the appended claims.
10‧‧‧電流模式降壓型轉換器10‧‧‧ Current Mode Buck Converter
101‧‧‧輸入電壓源 101‧‧‧Input voltage source
102‧‧‧開關電路 102‧‧‧Switch circuit
103‧‧‧電感-電容電路 103‧‧‧Inductance-capacitor circuit
104‧‧‧反饋電路 104‧‧‧Feedback circuit
105‧‧‧振盪器 105‧‧‧Oscillator
106‧‧‧典型的峰值電流模式控制器 106‧‧‧Typical peak current mode controller
116‧‧‧誤差放大器 116‧‧‧Error amplifier
126‧‧‧加法器 126‧‧‧Adder
136‧‧‧斜率補償電路 136‧‧‧Slope compensation circuit
146、221‧‧‧比較器 146, 221‧‧‧ comparator
156‧‧‧控制邏輯電路 156‧‧‧Control logic
156_1‧‧‧SR鎖存器 156_1‧‧‧SR latch
166‧‧‧高側電流感測電路 166‧‧‧High-side current sensing circuit
210‧‧‧電流產生電路 210‧‧‧current generation circuit
211‧‧‧放大器 211‧‧Amplifier
220‧‧‧調變器電路 220‧‧‧ modulator circuit
230‧‧‧振盪電路 230‧‧‧Oscillation circuit
231‧‧‧比較電路 231‧‧‧Comparative circuit
232‧‧‧脈衝產生器電路 232‧‧‧pulse generator circuit
C、C'‧‧‧電容 C, C'‧‧‧ capacitor
Cs‧‧‧振盪電容 Cs‧‧‧Oscillation Capacitor
CLK‧‧‧振盪信號 CLK‧‧‧ oscillating signal
Id‧‧‧調變電流I d ‧‧‧ modulated current
IRT‧‧‧電流I RT ‧‧‧current
IL‧‧‧電感電流I L ‧‧‧Inductor current
Iload‧‧‧負載電流I load ‧‧‧Load current
Ir、Is‧‧‧參考電流I r , I s ‧‧‧reference current
L‧‧‧電感 MN1~MN3、MP1~MP5、Mosc‧‧‧電晶體 L‧‧‧Inductance MN1~MN3, MP1~MP5, Mosc‧‧•O crystal
N1、N2‧‧‧端子N 1 , N 2 ‧‧‧ terminals
PWM‧‧‧PWM信號 PWM‧‧‧PWM signal
‧‧‧反相PWM信號 ‧‧‧Inverted PWM signal
Q‧‧‧輸出端 Q‧‧‧output
‧‧‧反相輸出端 ‧‧‧inverting output
R、R1、R'、R2‧‧‧電阻R, R 1 , R', R 2 ‧ ‧ resistance
R‧‧‧重置輸入端 R‧‧‧Reset input
S ‧‧‧設定輸入端 S ‧‧‧Setting input
SW1、SW2‧‧‧開關SW 1 , SW 2 ‧‧ ‧ switch
Vin‧‧‧輸入電壓 Vin‧‧‧Input voltage
VO‧‧‧輸出電壓V O ‧‧‧Output voltage
Vss‧‧‧軟啟動電壓 Vss‧‧‧ soft start voltage
Vref1~Vref4‧‧‧參考電壓 Vref1~Vref4‧‧‧reference voltage
Vc、Vsense‧‧‧電壓 Vc, Vsense‧‧‧ voltage
Vcs‧‧‧電流感測電壓 Vcs‧‧‧ current sensing voltage
VR‧‧‧斜坡電壓V R ‧‧‧Ramp voltage
VFB‧‧‧反饋電壓V FB ‧‧‧ feedback voltage
VDD‧‧‧高電源電壓V DD ‧‧‧High power supply voltage
圖1是根據現有技術的降壓型轉換器的示意圖; 圖2是根據本發明實施例的振盪器的示意圖; 圖3是根據本發明實施例的振盪器的調變器電路的示意圖;以及 圖4是根據本發明實施例的反饋電壓和調變電流的示意圖。1 is a schematic diagram of a buck converter according to the prior art; FIG. 2 is a schematic diagram of an oscillator according to an embodiment of the present invention; FIG. 3 is a schematic diagram of a modulator circuit of an oscillator according to an embodiment of the present invention; 4 is a schematic diagram of a feedback voltage and a modulated current according to an embodiment of the present invention.
Claims (11)
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