TWI538309B - Dual - band circular polarization monopole antenna - Google Patents
Dual - band circular polarization monopole antenna Download PDFInfo
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- TWI538309B TWI538309B TW102125755A TW102125755A TWI538309B TW I538309 B TWI538309 B TW I538309B TW 102125755 A TW102125755 A TW 102125755A TW 102125755 A TW102125755 A TW 102125755A TW I538309 B TWI538309 B TW I538309B
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Description
本發明是有關於一種雙頻天線,特別是指一種雙寬頻圓極化單極天線 The invention relates to a dual frequency antenna, in particular to a double wide frequency circularly polarized monopole antenna
當電磁波的極化方向與接收天線的極化方向有差異時,容易形成接收死角,而電磁波在傳遞的路徑通常是非直線,使得傳遞過程因碰到許多障礙物,而產生多重路徑干擾效應,為了減少上述的問題,圓極化天線是較佳的選擇。此外,為了能應用在全球導航衛星系統(Global Navigation Satellite System,GNSS)及國際航海衛星系統(International Maritime Satellite,INMARSAT)操作頻帶,整體分為1164~1300MHz及1525MHz~1660.5MHz兩個頻帶,需要設計一支雙頻圓極化天線,圓極化頻寬分別相對於彼此的中心頻率為11%和8.5%。 When the polarization direction of the electromagnetic wave is different from the polarization direction of the receiving antenna, the receiving dead angle is easily formed, and the path of the electromagnetic wave is usually non-linear, so that the transmission process generates a multipath interference effect due to encountering many obstacles, in order to To reduce the above problems, a circularly polarized antenna is a better choice. In addition, in order to be applied to the Global Navigation Satellite System (GNSS) and the International Maritime Satellite (INMARSAT) operating band, the whole frequency is divided into two bands of 1164~1300MHz and 1525MHz~1660.5MHz, which needs to be designed. A dual-frequency circularly polarized antenna with a circular polarization bandwidth of 11% and 8.5% relative to each other.
參閱文獻「“Novel Broadband Monopole Antennas With Dual-Band Circular Polarization,”IEEE Transactions on Antennas and Propagation,Vol.57,No.4,pp.1027-1034,April.」所揭示的雙頻圓極化單極天線,圓極化頻寬分別為5.6%和23.1%,兩者頻寬相差太多,且低頻 頻寬5.6%未達所需要的標準11%。 See "Novel Broadband Monopole Antennas With Dual-Band Circular Polarization," IEEE Transactions on Antennas and Propagation, Vol. 57, No. 4, pp. 1027-1034, April. The antennas have a circular polarization bandwidth of 5.6% and 23.1%, respectively, and the bandwidths of the two are too different, and the low frequency bandwidth of 5.6% does not reach the required standard of 11%.
因此,本發明之目的,即在提供一種雙頻圓極化頻寬可分別達到11%和8.5%以上的雙寬頻圓極化單極天線。 Accordingly, it is an object of the present invention to provide a dual wide frequency circularly polarized monopole antenna having a dual frequency circular polarization bandwidth of 11% and 8.5%, respectively.
於是,本發明雙寬頻圓極化單極天線包含一輻射元件及一饋入元件。 Thus, the dual wide frequency circularly polarized monopole antenna of the present invention comprises a radiating element and a feed element.
該輻射元件形成於一第一平面上並包括一具有一穿槽的主體輻射片,及一自該主體輻射片向外延伸的耦合微擾片。 The radiating element is formed on a first plane and includes a main body radiating sheet having a through slot, and a coupled perturbation sheet extending outward from the main body radiating sheet.
該饋入元件形成於一第二平面上並包括二相間隔並用於接地的接地片、一位於該二接地片之間的饋電片、一自該饋電片延伸且向該輻射元件方向的正投影至少部分落入該耦合微擾片上的耦合片、一自該耦合片延伸的限波片,及一自該限波片遠離該耦合片的頂緣向該耦合片的方向形成的分割槽,該限波片和該分割槽向該輻射元件方向的正投影至少部分落入該主體輻射片上。 The feed element is formed on a second plane and includes a two-phase spacing and grounding piece for grounding, a feed piece between the two grounding plates, and a direction extending from the feeding piece and facing the radiating element a positive projection of a coupling piece at least partially falling on the coupling perturbation piece, a wave limiting piece extending from the coupling piece, and a dividing groove formed from the top edge of the limiting plate away from the top edge of the coupling piece toward the coupling piece And the orthographic projection of the wave limiting plate and the dividing groove toward the radiating element at least partially falls on the main body radiating sheet.
本發明之功效在於:該輻射元件收發圓形極化射頻訊號,該饋入元件耦合地與該輻射元件交換射頻訊號,並藉著該饋入元件的分割槽分割頻寬為雙頻寬,和該輻射元件和該饋入元件彼此對應的態樣,使該雙寬頻圓極化單極天線的雙頻寬可分別達到11%和8.5%以上,且使圓形極化射頻訊號更加純化。 The effect of the present invention is that the radiating element transmits and receives a circularly polarized RF signal, and the feeding element couples the RF signal with the radiating element, and divides the bandwidth into a double bandwidth by the dividing slot of the feeding component, and The radiating element and the feeding element correspond to each other such that the double-bandwidth of the double-wideband circularly polarized monopole antenna can reach 11% and 8.5%, respectively, and the circularly polarized RF signal is further purified.
1‧‧‧輻射元件 1‧‧‧radiation components
11‧‧‧主體輻射片 11‧‧‧Main Radiation
111‧‧‧圓弧周緣 111‧‧‧Circular circumference
112‧‧‧直徑長邊 112‧‧‧Long diameter
12‧‧‧耦合微擾片 12‧‧‧coupled perturbation
13‧‧‧穿槽 13‧‧‧through slot
131‧‧‧外緣 131‧‧‧ outer edge
132‧‧‧內緣 132‧‧‧ inner edge
2‧‧‧饋入元件 2‧‧‧Feed components
21‧‧‧第一接地片 21‧‧‧First grounding piece
22‧‧‧第二接地片 22‧‧‧Second grounding piece
23‧‧‧饋電片 23‧‧‧Feed
24‧‧‧耦合片 24‧‧‧ coupling piece
25‧‧‧限波片 25‧‧‧Limitor
251‧‧‧頂緣 251‧‧‧Top edge
26‧‧‧分割槽 26‧‧‧Segmentation slot
3‧‧‧介電基板 3‧‧‧ dielectric substrate
31‧‧‧第一平面 31‧‧‧ first plane
32‧‧‧第二平面 32‧‧‧ second plane
4‧‧‧反射元件 4‧‧‧reflecting elements
41‧‧‧底壁 41‧‧‧ bottom wall
42‧‧‧環繞壁 42‧‧‧ Surrounding wall
421‧‧‧壁高 421‧‧‧ wall height
本發明之其他的特徵及功效,將於參照圖式的實施方式中清楚地呈現,其中:圖1是一俯視圖,說明本發明雙寬頻圓極化單極天線的一第一較佳實施例於一第一平面的態樣;圖2是一仰視圖,輔助圖1說明該第一較佳實施例於一第二平面的態樣;圖3是一側視圖,輔助圖1說明本發明雙寬頻圓極化單極天線的該第一較佳實施例;圖4是一實驗量測圖,說明該第一較佳實施例的返回損失;圖5是一實驗量測圖,說明該第一較佳實施例的圓極化軸比;圖6是一立體圖,說明本發明雙寬頻圓極化單極天線的一第二較佳實施例;圖7是一實驗量測圖,說明該第二較佳實施例的返回損失;圖8是一實驗量測圖,說明該第二較佳實施例圓極化軸比;圖9是一實驗量測圖,說明該第二較佳實施例操作於1200MHz時的輻射場型;及圖10是一實驗量測圖,說明該第二較佳實施例操作於1525MHz時的輻射場型。 Other features and effects of the present invention will be apparent from the following description of the drawings. FIG. 1 is a plan view showing a first preferred embodiment of the dual wide frequency circularly polarized monopole antenna of the present invention. 1 is a bottom view, FIG. 2 is a bottom view, and FIG. 1 is a view showing the first preferred embodiment in a second plane; FIG. 3 is a side view, and FIG. 1 is a side view illustrating the double broadband of the present invention. The first preferred embodiment of the circularly polarized monopole antenna; FIG. 4 is an experimental measurement diagram illustrating the return loss of the first preferred embodiment; FIG. 5 is an experimental measurement diagram illustrating the first comparison The circular polarization axis ratio of the preferred embodiment; FIG. 6 is a perspective view showing a second preferred embodiment of the dual wide frequency circularly polarized monopole antenna of the present invention; FIG. 7 is an experimental measurement diagram illustrating the second comparison The return loss of the preferred embodiment; FIG. 8 is an experimental measurement diagram illustrating the circular polarization axis ratio of the second preferred embodiment; FIG. 9 is an experimental measurement diagram illustrating the operation of the second preferred embodiment at 1200 MHz. Radiation pattern of time; and FIG. 10 is an experimental measurement diagram illustrating that the second preferred embodiment operates at 1525M Radiation pattern at Hz.
在本發明被詳細描述之前,應當注意在以下的說明內容中,類似的元件是以相同的編號來表示。 Before the present invention is described in detail, it should be noted that in the following description, similar elements are denoted by the same reference numerals.
參閱圖1、圖2、圖3,本發明雙寬頻圓極化單極天線的一第一較佳實施例包含一材質為導體且用以收發圓形極化射頻訊號的輻射元件1、一材質為導體且耦合地與該輻射元件交換射頻訊號的饋入元件2,及一分別供該輻射元件1和該饋入元件2設置的介電基板3。 Referring to FIG. 1 , FIG. 2 and FIG. 3 , a first preferred embodiment of the dual wide frequency circularly polarized monopole antenna of the present invention comprises a radiating element 1 made of a conductor and transmitting and receiving circularly polarized RF signals. A feed element 2 for electrically and inductively exchanging RF signals with the radiating element, and a dielectric substrate 3 for the radiating element 1 and the feed element 2, respectively.
該饋入元件2與該輻射元件1交換射頻訊號時,該輻射元件1同時產生一第一線性極化及一第二線性極化,以合成圓形極化模態,以下為方便說明,定義該第一線性極化方向為x,該第二線性極化方向為y。 When the feeding component 2 exchanges the RF signal with the radiating component 1, the radiating component 1 simultaneously generates a first linear polarization and a second linear polarization to synthesize a circular polarization mode. The first linear polarization direction is defined as x, and the second linear polarization direction is y.
該介電基板3包括相反且彼此平行的一第一平面31和一第二平面32,該輻射元件1設置於該第一平面31上,該饋入元件2是共面波導饋入的型式且設置於該第二平面32上。在該第一較佳實施例中,該介電基板3為一長方體,長、寬、高分別為105、68、1.6毫米,介電常數εr為4.4和正切損失為0.02。 The dielectric substrate 3 includes a first plane 31 and a second plane 32 which are opposite and parallel to each other. The radiating element 1 is disposed on the first plane 31, and the feeding element 2 is of a coplanar waveguide feeding type. It is disposed on the second plane 32. In the first preferred embodiment, the dielectric substrate 3 is a rectangular parallelepiped having a length, a width, and a height of 105, 68, and 1.6 mm, a dielectric constant ε r of 4.4, and a tangent loss of 0.02.
該輻射元件1包括一具有一穿槽13的主體輻射片11,及一自該主體輻射片11向外延伸的耦合微擾片12。在該第一較佳實施例中,該主體輻射片11概成半圓形,半徑為20毫米,直徑長邊112垂直該第一線性極化方向x。該耦合微擾片12概成矩形,且自該主體輻射片11的圓弧周緣111延伸,該耦合微擾片12遠離該主體輻射片11 的邊線與該主體輻射片11的直徑長邊112平行,且長度為16毫米,該耦合微擾片12另一邊線長度為14毫米。該穿槽13概成寬度固定為8毫米的半圓弧形狀,且對稱於垂直該主體輻射片11的直徑長邊112的中心線,並該穿槽13的一外緣131與該主體輻射片11的圓弧周緣111等距,該穿槽13的一內緣132平行該第二線性極化方向y的兩邊線至該主體輻射片11的直徑長邊112的距離為3毫米,該內緣132的圓弧至該主體輻射片11的圓心距離為9毫米。該主體輻射片11藉由該穿槽13改變該主體輻射片11的表面電流分布,以產生更良好的圓極化特性。 The radiating element 1 includes a main body radiating sheet 11 having a through slot 13 and a coupled perturbation sheet 12 extending outward from the main body radiating sheet 11. In the first preferred embodiment, the main body radiating sheet 11 is substantially semi-circular with a radius of 20 mm and the long side 112 of the diameter is perpendicular to the first linear polarization direction x. The coupled perturbation sheet 12 is substantially rectangular and extends from a circular arc periphery 111 of the main body radiating sheet 11, and the coupled perturbation sheet 12 is away from the main body radiating sheet 11 The side line is parallel to the long side 112 of the main body of the main body radiating sheet 11, and has a length of 16 mm, and the other side of the coupled perturbation sheet 12 has a length of 14 mm. The through slot 13 is formed into a semicircular arc shape having a width fixed to 8 mm, and is symmetric with respect to a center line perpendicular to the long side 112 of the diameter of the main body radiating sheet 11, and an outer edge 131 of the through slot 13 and the main body radiating piece The arcuate circumference 111 of the 11 is equidistant, and an inner edge 132 of the through slot 13 is parallel to the two sides of the second linear polarization direction y to a distance of the long side 112 of the main body radiation sheet 11 by a distance of 3 mm. The circular arc of 132 is at a center distance of 9 mm from the main body radiation sheet 11. The main body radiation sheet 11 changes the surface current distribution of the main body radiation sheet 11 by the through grooves 13 to produce more favorable circular polarization characteristics.
該饋入元件2包括相間隔並用於接地的一第一接地片21、一第二接地片22、一位於該第一接地片21和該第二接地片22之間的饋電片23、一自該饋電片23延伸的耦合片24、一自該耦合片24延伸的限波片25,及一自該限波片25遠離該耦合片24的頂緣251向該耦合片24的方向形成的分割槽26。 The feed element 2 includes a first grounding strip 21 spaced apart and used for grounding, a second grounding strip 22, a feed piece 23 located between the first grounding strip 21 and the second grounding strip 22, and a feed element a coupling piece 24 extending from the feeding piece 23, a wave limiting piece 25 extending from the coupling piece 24, and a direction from the top edge 251 of the wave limiting piece 25 away from the coupling piece 24 toward the coupling piece 24 Split slot 26.
在該第一較佳實施例中,該饋入元件2的該第一接地片21和該第二接地片22概成矩形,且與該饋電片23形成一饋入用途的非對稱式五十歐姆共面波導,且該第一接地片21和該第二接地片22的長度不同,該第一接地片21的兩邊線分別為67、17毫米,該第二接地片22的兩邊線分別為32、17毫米,且該第一接地片21和該第二接地片22分別距離該饋電片23的間隔為0.5毫米。該饋電片23成向垂直於該主體輻射片11的直徑長邊112方向延伸的 矩形,且平行該主體輻射片11的直徑長邊112方向的邊線為5毫米,並另一邊線為18.5毫米。該耦合片24成向平行於該主體輻射片11的直徑長邊112方向延伸的矩形,該耦合片24向該輻射元件1方向的正投影至少部分落入該耦合微擾片12上,且不落入該主體輻射片11上,並其一邊線與該主體輻射片11的圓弧周緣111相切,該耦合片24平行該主體輻射片11的直徑長邊112方向的邊線為25毫米,且另一邊線為12.5毫米。因此,自該饋電片23饋入的能量能經由該耦合片24耦合至該耦合微擾片12,而傳遞給該主體輻射片11。 In the first preferred embodiment, the first grounding strip 21 and the second grounding strip 22 of the feeding element 2 are substantially rectangular, and form an asymmetric five with the feeding piece 23 for feeding. a ten-ohm coplanar waveguide, and the lengths of the first grounding strip 21 and the second grounding strip 22 are different, the two sides of the first grounding strip 21 are 67 and 17 mm, respectively, and the two sides of the second grounding strip 22 are respectively It is 32, 17 mm, and the distance between the first grounding piece 21 and the second grounding piece 22 from the feeding piece 23 is 0.5 mm. The feed piece 23 extends in a direction perpendicular to the long side 112 of the diameter of the main body radiation sheet 11. The rectangle is parallel to the side of the main body of the radiation sheet 11 in the direction of the long side 112 of the diameter of 5 mm, and the other side line is 18.5 mm. The coupling piece 24 is formed in a rectangular shape extending parallel to the long side 112 of the diameter of the main body radiation piece 11. The orthographic projection of the coupling piece 24 in the direction of the radiating element 1 at least partially falls on the coupling perturbation piece 12, and Falling into the main body radiation sheet 11 and having one side line tangential to the circular arc peripheral edge 111 of the main body radiation piece 11, the side of the coupling piece 24 parallel to the diameter long side 112 of the main body radiation piece 11 is 25 mm, and The other side line is 12.5 mm. Therefore, the energy fed from the feed piece 23 can be coupled to the coupled perturbation piece 12 via the coupling piece 24 and transmitted to the main body radiation piece 11.
該限波片25成向垂直於該主體輻射片11的直徑長邊112方向延伸的矩形,且向該輻射元件1方向的正投影完全落入該主體輻射片11上,並該限波片25的頂緣251的正投影與該主體輻射片11的直徑長邊112切齊,該限波片25平行該主體輻射片11的直徑長邊112方向的邊線為5毫米,且另一邊線為20毫米。該分割槽26延伸至部份的耦合片24內,且向該輻射元件1方向的正投影至少部分落入該主體輻射片11上,該分割槽26使該限波片25分隔成兩部份。該分割槽26具有切割頻帶的特徵,使單頻帶變成雙頻帶,且該分割槽26的周長為一雙頻的切割頻率所對應的一空間波長的二分之一。在該第一較佳實施例中,被該分割槽26分割成兩部份的限波片25彼此間隔1毫米,且該分割槽26向該耦合片24延伸的長度為31毫米。 The wave limiting plate 25 has a rectangular shape extending in a direction perpendicular to the long side 112 of the diameter of the main body radiating sheet 11, and the orthographic projection in the direction of the radiating element 1 completely falls onto the main body radiating sheet 11, and the wave limiting plate 25 The orthographic projection of the top edge 251 is aligned with the long side 112 of the main body of the radiation piece 11, the edge of the wave-limiting plate 25 parallel to the long side 112 of the main body of the radiation piece 11 is 5 mm, and the other side is 20 Millimeter. The dividing groove 26 extends into a portion of the coupling piece 24, and the orthographic projection in the direction of the radiating element 1 at least partially falls onto the main body radiating sheet 11, and the dividing groove 26 divides the limiting plate 25 into two parts. . The dividing groove 26 has a feature of cutting a frequency band such that the single frequency band becomes a dual frequency band, and the circumference of the dividing groove 26 is one-half of a spatial wavelength corresponding to a double frequency cutting frequency. In the first preferred embodiment, the wave limiting sheets 25 divided into two by the dividing groove 26 are spaced apart from each other by 1 mm, and the length of the dividing groove 26 extending toward the coupling piece 24 is 31 mm.
參閱圖4,為實際量測該第一較佳實施例的返回損失圖,在頻帶1097MHz~1418MHz和1420MHz~2000MHz中,返回損失皆大於10dB,需要應用的範圍1164~1300MHz及1525MHz~1660.5MHz皆包含在此設計的頻帶中。 Referring to FIG. 4, in order to actually measure the return loss map of the first preferred embodiment, the return loss is greater than 10 dB in the frequency bands 1097 MHz to 1418 MHz and 1420 MHz to 2000 MHz, and the application range is 1164 to 1300 MHz and 1525 MHz to 1660.5 MHz. Included in the frequency band of this design.
參閱圖5,為實際量測該第一較佳實施例的圓極化軸比圖,在頻帶1134MHz~1391MHz和1460.5MHz~1719MHz中,軸比值皆小於3dB,需要應用的頻帶範圍皆包含在此設計中,又1134MHz~1391MHz的中心頻率為1262.5MHz,則換算到的圓極化頻寬為20.4%,1460.5MHz~1719MHz的中心頻率為1589.8MHz,則換算到的圓極化頻寬為16.3%。因此該第一較佳實施例經由實際量測,證實確實能達到超過目標頻寬11%和8.5%以上。 Referring to FIG. 5, in order to actually measure the circular polarization axis ratio of the first preferred embodiment, in the frequency bands 1134 MHz to 1391 MHz and 1460.5 MHz to 1719 MHz, the axial ratios are all less than 3 dB, and the required frequency band ranges are included herein. In the design, the center frequency of 1134MHz~1391MHz is 1262.5MHz, the converted circular polarization bandwidth is 20.4%, the center frequency of 1460.5MHz~1719MHz is 1589.8MHz, and the converted circular polarization bandwidth is 16.3%. . Therefore, the first preferred embodiment confirms that it is possible to achieve 11% or more of the target bandwidth by actual measurement.
參閱圖1、圖2、圖6,本發明雙寬頻圓極化單極天線的一第二較佳實施例,與該第一較佳實施例相似,不同處在於該第二較佳實施例還包含一導電材質構成並供該介電基板3、該輻射元件1、該饋入元件2設置其中的反射元件4。 Referring to FIG. 1 , FIG. 2 and FIG. 6 , a second preferred embodiment of the dual wide frequency circularly polarized monopole antenna of the present invention is similar to the first preferred embodiment, except that the second preferred embodiment further A conductive material is formed and provided for the dielectric substrate 3, the radiating element 1, and the reflective element 4 in which the feeding element 2 is disposed.
該反射元件4包括一平行且間隔於該介電基板3的第二平面32的底壁41,及一從該底壁41的周緣沿該第二平面32向該第一平面31方向延伸的環繞壁42。為方便說明,定義該第二平面32向該第一平面31的方向為z方向。該介電基板3的第二平面32至該底壁41的距離等於該環繞壁42的壁高421,且該介電基板3的周緣至該環繞壁42的距離等於該壁高421,該壁高421是該雙寬頻圓 極化單極天線的一中心頻率所對應的一自由空間波長的四分之一。在該第二較佳實施例中,在還未加入該反射元件4的頻帶範圍為1134MHz~1391MHz和1460.5MHz~1719MHz,取1134MHz和1719MHz的中心頻率為1426.5MHz。 The reflective element 4 includes a bottom wall 41 parallel to and spaced apart from the second plane 32 of the dielectric substrate 3, and a surrounding extending from the periphery of the bottom wall 41 along the second plane 32 toward the first plane 31. Wall 42. For convenience of explanation, the direction of the second plane 32 to the first plane 31 is defined as the z direction. The distance from the second plane 32 of the dielectric substrate 3 to the bottom wall 41 is equal to the wall height 421 of the surrounding wall 42, and the distance from the periphery of the dielectric substrate 3 to the surrounding wall 42 is equal to the wall height 421, the wall Height 421 is the double wide frequency circle A center frequency of a polarized monopole antenna corresponds to a quarter of a free-space wavelength. In the second preferred embodiment, the frequency band that has not been added to the reflective element 4 ranges from 1134 MHz to 1391 MHz and 1460.5 MHz to 1719 MHz, and the center frequency of 1134 MHz and 1719 MHz is 1426.5 MHz.
該反射元件4的設置,因該壁高421為該中心頻率所對應的該自由空間波長的四分之一,使該輻射元件1和該饋入元件2產生的射頻訊號,碰到該底壁41的反射波為一建設性地增強z方向的射頻訊號,使得該第二較佳實施例於z方向可以得到更大的輻射增益,並經過實際量測證實,該第二較佳實施例的單向(z方向)輻射增益相較於移除該反射元件4後的雙向(z方向及-z方向)輻射增益大幅提升約6dBic,而應用頻帶內的增益最大值約為9.4dBic,因此該第二較佳實施例更適合需高指向性特性的應用。 The reflecting element 4 is disposed such that the wall height 421 is a quarter of the free space wavelength corresponding to the center frequency, so that the RF signal generated by the radiating element 1 and the feeding element 2 hits the bottom wall. The reflected wave of 41 is a constructively enhanced radio frequency signal in the z direction, so that the second preferred embodiment can obtain a larger radiation gain in the z direction, and is confirmed by actual measurement, the second preferred embodiment The unidirectional (z-direction) radiation gain is substantially increased by about 6 dBic compared to the bidirectional (z-direction and -z-direction) radiation gains after removal of the reflective element 4, and the maximum gain in the applied band is about 9.4 dBic, so The second preferred embodiment is more suitable for applications requiring high directivity characteristics.
參閱圖7,為實際量測該第二較佳實施例的返回損失圖,在頻帶1045MHz~2000MHz中,返回損失皆大於10dB,經由實際量測證實,該第二較佳實施例包含該反射元件4也不會造成阻抗頻寬的縮減。 Referring to FIG. 7, in order to actually measure the return loss map of the second preferred embodiment, the return loss is greater than 10 dB in the frequency band 1045 MHz to 2000 MHz, and the second preferred embodiment includes the reflective element. 4 will not cause a reduction in impedance bandwidth.
參閱圖8,為實際量測該第二較佳實施例的圓極化軸比圖,在頻帶1120MHz~1389MHz和1449MHz~1786MHz中,軸比值皆小於3dB,又1120MHz~1389MHz的中心頻率為1254.5MHz,則換算到的圓極化頻寬為21.4%,1449MHz~1786MHz的中心頻率為1617.5MHz,則換算到的圓極化頻寬為20.8%。經由實際量測證實,該第二較佳實 施例包含該反射元件4也不會造成圓極化頻寬的縮減。 Referring to FIG. 8, in order to actually measure the circular polarization axis ratio of the second preferred embodiment, in the frequency bands 1120 MHz to 1389 MHz and 1449 MHz to 1786 MHz, the axial ratio is less than 3 dB, and the center frequency of 1120 MHz to 1389 MHz is 1254.5 MHz. Then, the converted circular polarization bandwidth is 21.4%, and the center frequency of 1449 MHz to 1786 MHz is 1617.5 MHz, and the converted circular polarization bandwidth is 20.8%. Confirmed by actual measurement, the second best The embodiment includes that the reflective element 4 also does not cause a reduction in the circular polarization bandwidth.
參閱圖9與圖10,為該第二較佳實施例的輻射場型圖,圖9是在頻率1200MHz時量測的輻射場型,圖10是在頻率1525MHz時量測的輻射場型。圖9及圖10皆顯示:該反射元件4可以抑制-z方向輻射達20dB,因此能大幅提升z方向輻射增益。 Referring to Figures 9 and 10, there is shown a radiation pattern of the second preferred embodiment, Figure 9 is a radiation pattern measured at a frequency of 1200 MHz, and Figure 10 is a radiation pattern measured at a frequency of 1525 MHz. 9 and 10 show that the reflective element 4 can suppress radiation in the -z direction by 20 dB, thereby greatly increasing the z-direction radiation gain.
因此,藉由該反射元件4可以在不改變該輻射元件1、饋入元件2、介電基板3的態樣尺寸下,不僅未破壞原有的阻抗頻寬及圓極化頻寬,反而使-z方向的射頻訊號反射回z方向,且與z方向的射頻訊號建設性疊加,再加上該反射元件4的環繞壁42窄化射頻訊號的波束寬度,使該第二較佳實施例的單向輻射增益大幅提升。 Therefore, the reflective element 4 can not only destroy the original impedance bandwidth and the circular polarization bandwidth without changing the aspect size of the radiating element 1, the feeding element 2, and the dielectric substrate 3, but instead The RF signal in the -z direction is reflected back to the z direction, and is constructively superimposed with the RF signal in the z direction, and the surrounding wall 42 of the reflective element 4 narrows the beam width of the RF signal, so that the second preferred embodiment The one-way radiation gain is greatly improved.
需要補充說明的是,該介電基板3的介電常數和正切損失並不受限,該輻射元件1和該饋入元件2的尺寸可與該介電基板3相配合,稍作調整得到較佳的圓極化特性,同樣的,該輻射元件1和該饋入元件2的尺寸也可因應實際狀況稍作調整。 It should be noted that the dielectric constant and the tangential loss of the dielectric substrate 3 are not limited, and the size of the radiating element 1 and the feeding element 2 can be matched with the dielectric substrate 3, and the adjustment is slightly adjusted. The circular polarization characteristics are similar. Similarly, the size of the radiating element 1 and the feeding element 2 can be slightly adjusted according to actual conditions.
綜上所述,本發明雙寬頻圓極化單極天線是藉由該輻射元件1收發圓形極化射頻訊號,該饋入元件2耦合地與該輻射元件1交換射頻訊號,該饋入元件2的分割槽26分割所需的雙頻帶,而該輻射元件和該饋入元件彼此相對的態樣使該饋入元件2與該輻射元件1產生的二線性極化方向相同,使兩圓極化頻寬可分別達到20%和16%以上,並可再藉由該反射元件4在不影響圓極化頻寬的條件 下,增加單向輻射增益,使該雙寬頻圓極化單極天線的圓極化頻寬達到11%和8.5%以上,故確實能達成本發明之目的。 In summary, the dual wideband circularly polarized monopole antenna of the present invention transmits and receives a circularly polarized RF signal through the radiating element 1, and the feeding component 2 is coupled to the radiating element 1 for exchanging RF signals. The feeding component The dividing groove 26 of 2 divides the required dual frequency band, and the radiation element and the feeding element are opposite to each other such that the feeding element 2 and the radiating element 1 generate the same bilinear polarization direction, so that the two circular poles The bandwidth can reach 20% and 16% respectively, and can be further used by the reflective element 4 without affecting the circular polarization bandwidth. Next, the unidirectional radiation gain is increased to achieve a circular polarization bandwidth of 11% and 8.5% or more of the double-wideband circularly polarized monopole antenna, so that the object of the present invention can be achieved.
惟以上所述者,僅為本發明之較佳實施例而已,當不能以此限定本發明實施之範圍,即大凡依本發明申請專利範圍及專利說明書內容所作之簡單的等效變化與修飾,皆仍屬本發明專利涵蓋之範圍內。 The above is only the preferred embodiment of the present invention, and the scope of the present invention is not limited thereto, that is, the simple equivalent changes and modifications made by the patent application scope and patent specification content of the present invention, All remain within the scope of the invention patent.
1‧‧‧輻射元件 1‧‧‧radiation components
11‧‧‧主體輻射片 11‧‧‧Main Radiation
111‧‧‧圓弧周緣 111‧‧‧Circular circumference
12‧‧‧耦合微擾片 12‧‧‧coupled perturbation
13‧‧‧穿槽 13‧‧‧through slot
2‧‧‧饋入元件 2‧‧‧Feed components
21‧‧‧第一接地片 21‧‧‧First grounding piece
22‧‧‧第二接地片 22‧‧‧Second grounding piece
23‧‧‧饋電片 23‧‧‧Feed
24‧‧‧耦合片 24‧‧‧ coupling piece
25‧‧‧限波片 25‧‧‧Limitor
251‧‧‧頂緣 251‧‧‧Top edge
26‧‧‧分割槽 26‧‧‧Segmentation slot
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CN112952388B (en) * | 2021-02-18 | 2022-08-05 | 大连海事大学 | Broadband circularly polarized microstrip antenna with wide axial ratio wave beam |
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