TWI521911B - Signal processing unit employing diversity combining and method of operating a receiver apparatus - Google Patents

Description

Signal processing unit using diversity combining method and method for operating receiver device

Embodiments of the present invention are directed to signal processing units that utilize diversity combining. Other embodiments are directed to methods of operating a receiver device of an electronic device.

The electronic device may be provided with a plurality of receiving antennas, such as Equal Gain Combining (EGC), Maximum Ratio Combining (MRC), or Switch and Stay Combing (SSC). The diversity combining of the Selection Combining (SC) method and the like. The diversity and dependence on channel state information used to describe the transmission characteristics of each transmission channel. The amplitude and/or phase information of each transmission channel is obtained from the demodulated received signal by, for example, comparing the training symbols contained in the received signal with reference information such as a reference signal available from the receiver. Knowledge.

It is an object of the present invention to provide a cost-effective combination of diversity Benefits of the signal processing unit. This object is achieved by the subject matter of the independent subject matter of the scope of the invention. Further embodiments are clearly set forth in the dependent claims of the scope of the invention. The details and advantages of the present invention will be more readily understood from the description of the embodiments of the invention.

A receiver device receives a transmission signal via a plurality of transmission channels, wherein each transmission channel is described by its channel impulse response. An estimator unit (120) applies a blind channel estimation algorithm that uses the cross-correlation between pairs of received signals to estimate the channel impulse response of the transmission channels from the plurality of received signals. The intersections are derived from sample values of the received signals. A merging unit (130) combines the received signals based on the combined coefficients derived from the estimated channel impulse response of a preselected diversity combining scheme to obtain a combined received signal. The receiver device utilizes only the blinded diversity of a demodulator unit (180) using the combined received signal. The diversity set does not require demodulation of the received signals.

902‧‧‧ Radio Station

904‧‧‧transmitter antenna

900‧‧‧Receiver equipment

208,908‧‧‧Tuner circuit

110,910‧‧‧ Analog/Digital Converter Unit

940‧‧‧First demodulator

950‧‧ ‧ sub-units

980‧‧‧Second demodulator

200‧‧‧Electronic devices

205‧‧‧ receiving components

100‧‧‧Signal Processing Unit

132,290‧‧‧Control unit

294‧‧‧output device

296‧‧‧ input unit

298‧‧‧Interface unit

170‧‧‧Transfer unit

134‧‧‧Filter unit

136‧‧‧Superimposed unit

138‧‧‧Pre-equalizer unit

134a‧‧‧Delay unit

134b‧‧‧weighting unit

134c‧‧‧sum unit

1 is a schematic block diagram of a receiver device for illustrating the use of diversity combining that can be used to understand the background information of the present invention.

2A is a schematic block diagram of an electronic device including a plurality of tuner circuits in accordance with an embodiment related to a wireless communication system.

Figure 2B is a package according to an embodiment related to a wired communication system A block diagram of one of an electronic device including a plurality of tuner circuits.

Figure 3A is a schematic block diagram of one of the receiver devices utilizing diversity combining in accordance with an embodiment of a time domain directed cost function.

Figure 3B is a schematic block diagram showing the details of a signal processing unit of the receiver device of Figure 3A.

Fig. 3C is a schematic block diagram showing the details of a filter unit of the signal processing unit of Fig. 3B.

Figure 4 is a simplified flow diagram of one of the methods of operating a receiver device using diversity combining in accordance with a further embodiment.

In the following, embodiments of the invention are illustrated. The described embodiments may be combined in any manner, i.e., some of the described embodiments may be combined with other embodiments without limitation. Throughout the drawings, the same reference numerals are used to refer to the same or similar elements. Other embodiments may be utilized, and structural or logical changes may be made without departing from the scope of the invention. Therefore, the following detailed description is not to be taken in a limiting

Figure 1 is used to provide an understanding of the background of the embodiments. Assume that a broadcast station 902 modulates a transmission signal s(t) on a carrier signal and transmits the modulated signal via a transmitter antenna 904, and then utilizes the diversity combining one receiver device 900 at a plurality of M receptions. The modulated signal is received on element 905 (e.g., an antenna), wherein each receiving element 905 is coupled to one of the M tuner circuits 908. The tuner circuits 908 are tuned to the same channel or carrier signal used by the broadcast station 902 to transmit the transmitted signal s(t). Each of the M receiving elements 905 and the tuner circuit 908 receives the transmission signal s(t) via a respective transmission channel. Each transmission channel is described by its channel impulse response h _i (t), where i = 1, 2...M. Each tuner circuit 908 is assigned to a receive path and outputs an analog receive signal r _i (t), wherein each analog receive signal r _i (t) is assigned to one of the M transmit channels . The noise on the respective transmission channels is represented by n _i (t), and in each tuner circuit 908, equation (1) describes each received signal r _i (t) as a transmission signal of a time-varying transmission channel. s(t), each channel transfer function h _i (t), and one of the individual additive channel noises n _i (t): (1) r _i ( t )= s ( t )* h _i ( t )+ n _i ( t )

In each receive path, an analog/digital (A/D) converter unit 910 samples the analog received signal r _i (t) to obtain a digitally sampled received signal r _i (n. T _A ). In each receive path, a first demodulator 940 synchronizes with the respective sampled received signal r _i (n.T _A ) in time and frequency, and extracts a training signal (a pilot signal) to obtain Channel information related to the respective transmission channel. For example, each first demodulator 940 compares the extracted training symbols with reference symbols available at the receiver to obtain an estimate of one of the respective channel impulse responses h _i (t). Different transmission schemes require different types of DEMA-1, DEMB-1 of the first demodulator 940 for each received signal r _i (t).

A sub-set sum unit 950 determines a set of (vector) combining coefficients of each sampled received signal r _i (n.T _A ) based on the knowledge of the channel impulse response h _i (n.T _A ). . The diversity combining unit 950 uses the combining coefficient Weighting or filtering the sampled received signal r _i (n.T _A ) or a signal derived therefrom, and then combining the weighted or filtered received signals with each other to obtain a representative of the transmitted signal s ( The estimated received signal y _A (n.T _A ), y _B (n.T _A ) of t). Different transmission schemes may require different types of diversity combining units 950.

Providing at least a second demodulator 980, the at least one second demodulator 980 being synchronizable with the combined received signals y _A (n.T _A ), y _B (n.T _A ), and The payload portions of the combined received signals y _A (n.T _A ) and y _B (n.T _A ) are demodulated. For example, the second demodulator 980 provides demapping and decoding in accordance with the transmission scheme household transmission standard used by the broadcast station 902. The second demodulator 980 can further include some sub-units for bit error correction, as well as some specific sub-units for the transmission criteria of the broadcast station 902 application. Different transmission schemes may require different types of DEMA-2, DEMB-2 of the second demodulator 980.

The diversity combining unit 950 determines the combining coefficient according to the respective received signals r _i (n.T _A ) The way it depends on the specific consolidation technique. For example, for the MRC method, the estimated coefficient It depends on the individual Signal-to-Noise Ratio (SNR). When EGC is used, the phases of the received signals are adjusted first, and then the received signals having the same gain are added. For the SC, a received signal such as a received signal having the best SNR among the received signals can be selected as a signal representing the best estimate of the transmitted signal s(t). For the SSC, a previously selected received signal is maintained as the best estimate until the SNR of the received signal falls below a predetermined threshold.

It is assumed that the channel impulse response h _i (t) is known at the receiver side, and that the received signal is assumed to be interfered by an additive white Gaussian noise n _i (t) having a mean value of zero, and assuming n _i (t) and n _k (t) are generally statistically independent at i≠k (in other words, E[n _i (t).n _k (t)]=E[n _i (t )].E[n _k (t)]=0), then for MRC, the combination coefficient can be determined according to equation (2a) :

Equation (2b) provides the resulting combined received signal y(t).

For EGC, equation (3a) provides the estimated coefficients And equation (3b) provides the combined received signal y(t), where in equation (3a), the term Is a vector:

Equations (2a) and (3a) show the combining coefficients The calculation must be aware of the individual channel impulse response h _i (t). However, conventionally, at least a portion of each received signal containing training symbols is demodulated to obtain the channel impulse response h _i (t). Therefore, each received signal is demodulated, at least in part, before the signals can be combined.

Fig. 2A refers to an embodiment of the present invention related to a wireless communication system, and shows an electronic device 200 for receiving individual communication materials such as telephone calls or the like or broadcast materials such as television programs or radio programs. The electronic device 200 can be a fixture such as a radio device, a television set, a set-top box, or a computer device having the capability of a radio or television receiver. According to another embodiment, the electronic device 200 is a mobile device such as a cell phone, a number of assistants, a mobile radio, or a portable television device, wherein the mobile device can be a handheld device or can be installed. A device in the vehicle/vehicle. The electronic device 200 can include a plurality of suitably spaced antennas as receiving elements 205 for receiving electromagnetic radiation. The antennas can be disposed on different surfaces of the electronic device 200 or in different portions. In general, the following needs are met: the distance between the two antennas is greater than one-half the wavelength used for transmission to ensure that the received signal can pass through separate transmission channels.

In the illustrated embodiment, each receiving element 205 is coupled to one of a plurality of tuner circuits 208, wherein the tuner circuits 208 are configured to simultaneously tune to the same broadcast channel, for example, Simultaneously tune to the same carrier frequency. Each tuner circuit 208 outputs a received signal. A signal processing unit 100 estimates the channel impulse response according to a blind channel estimation method to analyze the received signals, according to the estimates As a result, the received signals are weighted or filtered, and the weighted or filtered received signals are superimposed to obtain a received one that can contain more information than the original received signal and the original transmitted signal is combined. signal. Additionally, signal processing unit 100 can provide a pre-equalizing of the combined received signals using information derived from the blinded channel estimates. Finally, the signal processing unit 100 demodulates the received signal that is combined or pre-equalized.

Thus, the receiver architecture of the embodiments provides for combining the received signals first and then demodulating only the combined received signals. Although the signal processing unit of FIG. 1 is required to handle one of the first demodulator units for each receive path and each transmission standard when coping with different transmission standards using different demodulation schemes, The receiver architecture of an embodiment is only required for a single instance of each transmission standard.

Signal processing unit 100 includes an estimator unit. The estimator unit estimates the channel impulse response using a blinded channel estimation algorithm and obtains an estimated channel impulse response based on all sampled received signals for each receive path. . The blinded channel estimation is applied prior to demodulating the received signals.

According to an embodiment, each estimated impulse response is calculated based on sample values of time domain instances of the sampled received signals and a cost function defined in the time domain . According to another embodiment, each estimated impulse response is calculated from a cost function defined in the frequency domain .

The signal processing unit 100 further includes a merging unit for estimating the estimated impulse response according to the blind channel estimation The received signals are combined. According to an embodiment, the estimated impulse response It is used to configure one of each receive path matched filter, where each matched filter matches the transmission channel assigned to the respective receive path. The merging unit may or may not pre-equalize the combined signal based on the information obtained by the blinded channel estimation. For example, the merging unit can include a unit that applies, for example, a equalization filter to the combined signal, and at least partially equalizes distortion caused by merging of the MRC or the like. The unit forwards the combined or pre-equalized received signal representing an estimate of the transmitted signal s(t) to a demodulator unit. The demodulator unit may include a further packet equalizer unit, the equalizer unit of the further packet may estimate the transmission channels and the merge using information contained in a transmission signal such as training symbols or signaling data Distortion of unit import. That is, complete equalization of the combined signal is performed based on information obtained from demodulation of the combined signal. The signal processing unit 100 can output the demodulated signal to a control unit 290.

Control unit 290 can control an output device 294 to output the encoded information in the demodulated signal. For example, output device 294 can be a screen for displaying a television program encoded in the transmitted signal s(t). According to another embodiment, the output unit 294 outputs the audio information encoded in the transmission signal s(t). The electronic device 200 can further include an input unit 296, such as a keypad or a sensor array applied to the output device 294, for the user to control the electronic device 200.

Figure 2B refers to the use of Single-Input-Multiple-Output (SIMO) for use in, for example, Digital Subscriber Line (DSL) or Power Line Communication (PLC). An embodiment of an electronic device 200 of a wired communication system of a Multiple-Input-Multiple-Output (MIMO) method. For example, the receiving elements 205 can be one, two, or three live wires, a neutral wire, and/or an earth wire for receiving a power line network. Some of the terminals of a connector block. Each tuner circuit 208 can tune to the same carrier frequency and supply the received signal r _i (t) to the signal processing unit 100. Signal processing unit 100 performs a blinded channel estimation to obtain channel information. The signal processing unit 100 may apply the diversity combining according to the result of the blind channel estimation to obtain a rough estimate of the transmission signal, and may or may not pre-equalize the result based on the blind channel estimation. The combined signals demodulate the combined or pre-equalized signals and output the demodulated signals to control unit 290. Control unit 290 can process the demodulated signal and an interface unit 298 can output the processed signal.

Figure 3A shows details of a signal processing unit 100 incorporated into a receiver device of an electronic device 200, such as a television receiver. The receiver device includes a number of receiving components 205 and some tuner circuits 208. The signal processing unit 100 can include a plurality of A/D converter units 110, wherein each A/D converter unit 110 samples the respective analog received signals r _i (t) at a predetermined sampling rate of 1/T _A . An estimation unit 120 from the received signal r sampled by the _{i (n.T A)} is derived for each sample of the received signal r _{i (n.T A)} of the estimated impulse response . A merging unit 130 is responsive to the estimated impulse The derived combining coefficients are combined to combine the sampled received signals r _i (n.T _A ) or derived signals thereof to obtain a combined received signal y(n.T _A ), the combined received signal y ( n.T _A ) is an estimate of one of the transmitted signals s(t) transmitted via the plurality of transmission channels.

One or more demodulator units 180 of different types of DEMA, DEMB, ... may multiply the combined received signal y(n.T _A ) by one of the analyzer signals having a demodulator frequency, and The combined received signal y(n.T _A ) is synchronized and demodulated. The one or more demodulator units 180 can use the combined received signal y(n.T _A ) in the time domain. According to an embodiment, at least one of the demodulator units 180 uses a frequency domain representation of the combined received signal y(n.T _A ). A conversion unit 170 can then be provided in one of the signal paths between the combining unit 130 and the demodulator unit 180 using the frequency domain representation. The converting unit 170 may apply a Discrete Fourier Transform (DFT) to the combined received signal to obtain a description corresponding to one of the combined received signals in the frequency domain. One or more of the demodulator units 180 can be configured to demodulate television broadcast signals that follow different television broadcast standards, while other demodulator units 180 can be adapted to digital television broadcast signals, digital radio broadcast signals, Or analogy to radio broadcast signal demodulation. According to an embodiment, at least one of the demodulator units 180 may include a quadrature demodulator or an Orthogonal Frequency Division Multiplexing (OFDM) demodulator. One or more of the demodulator units 180 may further modify the demodulated received signal using the encoded information in the received signal. The demodulator unit 180 can include a bit error correction unit that corrects bit errors in the digital data stream using bit error detection and correction methods.

As for the estimator unit 120, it is conceived to be a blinded diversity combining method which derives the combining coefficients of the received signal r _i (t) from a blind channel estimation of the individual channel impulse response h _i (t) . Obviously, although the blind channel estimation algorithm contains at least scalar uncertainty in its estimate, the diversity can still be applied due to the following advantages: as the inventor of the present invention can prove, the diversity and (or even the MRC) have Sufficient to counter the robustness of such scalar uncertainty introduced by the blind channel estimation algorithm.

Although the combined signals may have even greater distortion due to the merging operation, the blinded diversity combining still improves signal quality, for example, the fade is less severe and/or the SNR is improved. On average, the combined signal contains more information about the transmitted signal, and such additional information related to the transmitted signal typically leads to subsequent steps (eg, using conventional equalization steps such as training symbols contained in the transmitted signal) A better estimate of the transmitted signal.

The decision different from the response to the channel impulse relies heavily on knowledge about the structure of the transmitted signal (eg, knowledge about whether the transmitted signal is an OFDM signal, etc., and/or knowledge of the training information contained in the transmitted signal). And usually requires precise time, frequency, and sampling clocks before reference or training symbols can be identified and used for channel estimation The conventional method of synchronizing (sample clock), the blinded diversity set proposed by the present invention does not require frequency synchronization before the merging step, nor does it require sampling clock synchronization. Alternatively, the blinded diversity is used and the cross-correlation statistics between the received signals are utilized, and an undemodulated instance of the received signals is used. The blinded diversity set can be based on higher order statistical cross relationships. According to an embodiment, the blinded diversity combines and uses a second order statistical cross relationship. According to a further embodiment, the blinded diversity set does not rely on knowledge about the type of modulation applied to obtain the transmitted signal, and knowledge of the type of demodulation required to demodulate the received signal.

While conventional methods that take into account individual channel transfer functions must be instantiated using one of the demodulator units for each receive path demodulation and synchronization, the blinded channel estimate only needs to be used for that portion of the demodulator unit. The combined received signal is once. Although each system contains several types of demodulators, each of which is dedicated to a communication system technology, communication standard, or modulation technology, blinded diversity and allows for uniqueness for each communication system or communication standard. The single demodulator is instantiated. Thus, in a multiple input multiple output (MIMO) or single input multiple output (SIMO) communication system, blinded diversity is combined and the cost of the diversity receiver is significantly reduced.

FIG. 3B illustrates details of the estimator unit 120 and the merging unit 130 of a signal processing unit 100 in accordance with an embodiment of a blinded channel estimation that defines a cost function based on the time domain and incorporates MRC. The estimator unit 120 receives the sampled received signal r _i (n.T _A ). According to an embodiment, the estimator unit 120 applies a Multi-Channel Least Mean Squares (MCLMS) method.

The MCLMS method relies on the observation that Equation (4) applies to each received signal without noise: (4) r _i ( t ) * h _j ( t ) = r _j ( t ) * h _i ( t )

An observation deviating from this assumption is considered to represent an error signal regarding the intersection relationship between the received signals i and j. _A cost function is defined from all pairs of error signals of the sampled received signal r _i (n.T _A ). The cost function includes a cross-correlation matrix containing information relating to the intersection relationship between the received signals of all pairs. Based on the previously obtained value h _i ((a).T _A ), the updated error signal, and the updated cross-relationship matrix, one of the iterative methods used to estimate the channel impulse response h _i (n.T _A ) The updated value h _i ((a+1).T _A ). According to another embodiment, a Multi-Channel Newton (MCN) algorithm can be applied to speed up the convergence of the algorithm. According to a further embodiment, estimator unit 120 instantiates a plurality of different blinded channel estimation algorithms and may select an active blind channel estimation algorithm based on an internal state or in response to a first selection signal sel1 law. Estimator unit 120 continually estimates the result (eg, estimates channel impulse response) ) is output to a control unit 132.

According to the estimated impulse response And a predetermined or currently selected combination scheme, the control unit 132 can continuously update the filter coefficients of the filter unit 134 provided in the signal paths of the sampled received signals. Control unit 132 can be programmed and can switch between MRC, EC, and SC when there is an appropriate second selection signal sel2, or can respond to a change in an internal state. According to an embodiment providing the SC, the control unit 132 configures the estimated impulse response Identifying a filter unit 134 arranged in the signal path of the received signal of the received signal with the least interference to pass the received signal with the least interference, and all other filter units 134 are configured to block other received signals .

According to one embodiment of the reference MRC, control unit 132 derives some of the combining coefficients used to configure the filter units 134 to represent a matched filter that respectively matches the respective estimated transmission channels. Each filter unit 134 calculates a convolution of the respective received signals with the respective matched filter functions.

A superimposing unit 136 adds or superimposes the filtered or weighted received signals to produce a combined received signal y(n.T _A ) representative of the transmitted signal.

The merging unit 130 may further include a pre-equalizer unit 138 for outputting a pre-equalized signal z(n.T _A ). The pre-equalizer unit 138 can use the information obtained from the blinded channel estimation algorithm. According to an embodiment, the pre-equalizer unit 138 applies a equalization filter to the combined signal while at least partially equalizing the distortion caused by the MRC. Please note that it is not a complete equalization, but only a partial equalization.

For example, the combined received signal can have at least twice the length of the longest channel impulse response. This approach will directly increase the required order of one of the subsequent equalizer stages. In an OFDM system, a violation of a guard interval may occur. According to an embodiment, the pre-equalizer unit 138 applies a delay spread minimization algorithm. According to another embodiment, the pre-equalizer unit 138 is designed to mitigate inter-carrier interference (inter-carrier) in subsequent OFDM demodulator Fast time-varying channel effects such as interference). Pre-equalization is performed before demodulating the combined received signal. Pre-equalization may be performed before or after converting the combined received signal to the frequency domain by Fourier transform.

We can understand that blinded diversity is independent of the applied transmission standard and can be applied to different transmission systems and standards. Blind diversity is effective for both single and multiple carriers without the need to redesign existing demodulator.

According to FIG. 3C, each filter unit 134 may include delay units 134a for providing delayed instances in which the respective received signals r _i (t, n.T _A ) are delayed by a multiple of T _A . A configurable weighting unit 134b is assigned to each delayed instance, and the respective instances of the received received signal r _i (t, n.T _A ) are multiplied by the corresponding group of combining coefficients c _i (t, n .T _A ). The output signals of the equal weighting units 134b are added or superimposed using the summing unit 134c to produce a filtered signal y _i (t, n.T _A ).

The signal processing unit 100 of the present invention and each of its subunits as described above may be implemented in a combination of hardware, software, or a combination of hardware and software. Some or all of the sub-units of the signal processing unit 100 may be integrated in, for example, an integrated circuit (IC), an Application Specific Integrated Circuit (ASIC), or a digital signal processor ( Digital Signal Processor (DSP) for a common package.

Although the current best-in-class receiver diversity and techniques are based on partial knowledge of the channel transfer function, and thus need to be targeted before the merging unit One of the demodulator stages is instantiated for each received signal, but embodiments of the present invention implement blinded diversity combining prior to demodulation. This "blind" diversity and the knowledge of the cross-correlation between the channels is sufficient to advantageously apply the facts of the diversity. This method can be applied to a wide range of communication systems. The cost of the diversity receiver can be significantly reduced.

Figure 4 refers to a method in which a device can be included in a receiver device of an electronic device. In step 402, an estimator unit estimates the impulse response of each transmission channel from a plurality of received signals. , wherein each estimated impulse response is derived from a blinded channel estimate using the intersection relationship between each pair of received signals . Each received signal is assigned another transmission channel for transmitting signals. In step 404, a merging unit is responsive to the estimated impulse The derived combining coefficients, and in the case of a predetermined diversity combining scheme in which one of the combined received signals used to represent the estimation of the transmitted signal transmitted via the transmission channels is selected, combining the receiving signal.

100‧‧‧Signal Processing Unit

110‧‧‧ Analog/Digital Converter Unit

120‧‧‧ estimator unit

130‧‧‧Merge unit

170‧‧‧Transfer unit

180‧‧‧ demodulator unit

200‧‧‧Electronic devices

205‧‧‧ receiving components

208‧‧‧Tuner circuit

902‧‧‧ Radio Station

904‧‧‧transmitter antenna

Claims (25)

A signal processing unit comprising: an estimator unit (120) configured to self-complexly receive signals according to a blinded channel estimation algorithm using a cross relationship between pairs of received signals Estimating a channel impulse response of the transmission channel, wherein each received signal is assigned to another one of the transmission channels; a filter unit (134), each filter unit (134) being arranged in the received signals One of the signal paths of the received signal and outputting the filtered received signal; the control unit (132), the control unit (132) being configured to derive the combining coefficients from the estimated channel impulse responses according to the preselected diversity combining scheme And wherein the combining coefficients are used to control the filter units (134); and the merging unit (130) is configured to combine the received signals according to the combining coefficients to obtain Combined received signal. The signal processing unit of claim 1, wherein: the estimator unit (120) is configured to estimate an estimated coefficient of the complex array according to a multi-channel least mean square algorithm. A signal processing unit of claim 1, wherein: the estimator unit (120) is configured to estimate the channel impulse responses based on an iterative algorithm that minimizes a cost function, wherein the cost function is based on All pairs of received signals with error signals, each error The signal is caused by a convolution of a result of the convolution of the received signal received via the first transmission channel and the estimated impulse response of the second transmission channel with the received signal received via the second transmission channel and the estimated impulse response of the first transmission channel The deviation between the results, the iterative algorithm uses a cross-correlation matrix whose elements include the mathematical expectation of the cross-correlation of the paired received signals. The signal processing unit of claim 1, wherein: the control unit (132) is configured to apply a maximum ratio combining, wherein the filtering coefficients of the matched filters are determined from the estimated channel impulse responses, each matching The filter matches the estimated impulse response of one of the transmission channels. The signal processing unit of claim 1, wherein: the control unit (132) is configured to apply selection combining, wherein the received signal having the least interference is determined from the estimated channel impulse responses, and the filtering is performed. The unit (134) is controlled to pass only the received signal with the least interference. The signal processing unit of claim 1, further comprising: a superimposing unit (136) configured to superimpose the filtered received signals to obtain the combined received signals. The signal processing unit of claim 1, further comprising: a pre-equalizer unit (138) configured to derive information using the information output by the estimator unit (120) Filter The coefficients are partially equalized to the combined received signal. The signal processing unit of claim 1, further comprising: a conversion unit (170) configured to convert the combined received signal or a signal derived therefrom into a frequency domain to obtain The frequency representation of the combined received signal or the signal derived therefrom. The signal processing unit of claim 1, further comprising: a demodulator unit (180) configured to signal the combined received signal or derived therefrom, or Corresponding frequency representation demodulation. The signal processing unit of claim 9, further comprising: an equalization unit configured to be completely equalized according to information obtained by the demodulation performed by the demodulator unit (180) The combined received signal or signal derived therefrom, or the corresponding frequency representation. The signal processing unit of claim 1, further comprising: a plurality of demodulator units (180), each demodulator unit (180) being configured to combine the combined received signal or a signal derived therefrom , or such corresponding frequency representation demodulation, the demodulator units (180) are adapted to different transmission schemes and/or transmission standards. For example, the signal processing unit of claim 1 of the patent scope, wherein: The estimator unit (120) is configured to estimate the channel impulse responses without using information related to the training symbols contained in the transmitted signals. The signal processing unit of claim 1, wherein: the received signals do not include training symbols for channel estimation. The signal processing unit of claim 1, wherein: the estimator unit (120) is configured to select only unreduced instances of the received signals and/or selections not included in the received signals. The signal is estimated to estimate the impulse response of the channels. The signal processing unit of claim 1, wherein: the estimator unit (120) is configured to not know the type of modulation applied to obtain the transmission signal or the solution required to demodulate the received signal. In the case of the type of modulation, the channel impulse responses are estimated. An integrated circuit comprising a signal processing unit according to any one of claims 1 to 15. An electronic device comprising: a signal processing unit according to any one of claims 1 to 15; and a plurality of tuner circuits (208), each tuner circuit (208) being configured to tune to a transmission signal The carrier frequency and the analog analog receive signal, wherein each analog receive signal is assigned to one of the transport channels. A method of operating a receiver device, the method comprising: blinding a channel based on a cross relationship between pairs of received signals Estimating the algorithm and using the estimator unit (120) to estimate the channel impulse response of the transmission channel from the plurality of received signals, wherein each received signal is assigned to another of the transmission channels; using a filter unit (134) Filtering the received signals and outputting the filtered received signals; using a control unit (132) to derive combining coefficients from the estimated channel impulse responses according to the preselected diversity combining scheme, wherein the combining coefficients are used to control the filtering Units (134); and combining the received signals using the combining unit (130) in accordance with the combining coefficients to obtain the combined received signals. The method of claim 18, wherein estimating the channel impulse response comprises: applying an iterative algorithm that minimizes a cost function, wherein the cost function is based on considering all partial error signals between the received signals in pairs a total error signal, each partial error signal resulting from a convolution of a received signal received via the first transmission channel and an estimated impulse response of the second transmission channel and a received signal received via the second transmission channel and the first transmission a deviation between the results of the convolution of the estimated impulse response of the channel, the iterative algorithm using a cross-correlation matrix, the elements of the cross-correlation matrix including the mathematical expectation of the cross-correlation of the paired received signals, and the iterative algorithm produces An estimate of the impulse response of the channels. The method of claim 18, further comprising: converting the combined received signal or the signal derived therefrom to the frequency domain using a conversion unit (170) to obtain the combined received signal or Its frequency representation of the derived signal. The method of claim 18, further comprising: demodulating the combined received signal or a signal derived therefrom, or the corresponding frequency representation, using a demodulator unit (180). The method of claim 18, wherein the complex array estimation coefficient is estimated without using information related to the training symbols contained in the transmitted signal. The method of claim 18, wherein the received signals do not include training symbols for channel estimation. The method of any one of claims 18 to 23, wherein the complex array estimation coefficients are estimated solely based on the received signals and the selection signals. A signal processing unit comprising: estimator means for estimating a channel impulse response of a transmission channel from a plurality of received signals according to a blinded channel estimation algorithm using a cross relationship between the paired received signals, wherein each Receiving signals are assigned to another one of the transmission channels; filter means for filtering the received signals and outputting the filtered received signals; control means for self-selecting according to the preselected diversity combining scheme Equally estimating a channel impulse response to derive a combining coefficient, wherein the combining coefficients are used to control the filter device; and combining means for combining the received signals according to the combining coefficients Number to obtain a combined received signal, wherein the input of the merging device is electrically coupled to the output of the estimator device.