TWI497885B - Multiphase converting controller - Google Patents
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本發明係關於一種多相轉換控制器,尤指一種可根據模式訊號調整導通時間長度之多相轉換控制器。The invention relates to a multi-phase conversion controller, in particular to a multi-phase conversion controller capable of adjusting the length of an on-time according to a mode signal.
請參見第一圖,為傳統的多相轉換控制器之電路示意圖。在此以兩相(轉換電路)為例來說明。轉換電路2、4耦接一輸入電壓Vin,分別包含上臂電晶體MU1及MU2、下臂電晶體ML1及ML2、電感L1及L2,而其輸出端彼此耦接至一輸出電容C以共同提供一輸出電壓Vout。多相轉換控制器10依序控制轉換電路2、4。系統進入輕載時會提供一模式訊號Sm,一多相轉換控制器10接收模式訊號Sm時會進行減相操作,傳統做法是始終保持第一相進行工作,遮蔽第二相,即轉換電路2繼續操作而轉換電路4停止操作,如此,可達到降低切換損失,提高輕載效率之優點。Please refer to the first figure, which is a circuit diagram of a conventional multi-phase conversion controller. Here, a two-phase (conversion circuit) will be described as an example. The conversion circuit 2, 4 is coupled to an input voltage Vin, which includes an upper arm transistor MU1 and MU2, lower arm transistors ML1 and ML2, inductors L1 and L2, and an output terminal coupled to an output capacitor C to provide a common Output voltage Vout. The multiphase conversion controller 10 sequentially controls the conversion circuits 2, 4. When the system enters the light load, a mode signal Sm is provided. When the multi-phase conversion controller 10 receives the mode signal Sm, the phase-reduction operation is performed. The conventional method is to keep the first phase working, and shield the second phase, that is, the conversion circuit 2 The operation continues without the conversion circuit 4 being stopped, so that the switching loss can be reduced and the light load efficiency can be improved.
由於傳統做法始終保持某固定相(如第一相)工作,即如果進行減相動作,則會減少其他相,而始終保持該固定相工作,這樣會導致各相的功率電晶體和電感工作量並不平衡,常用的固定相會較其他相位更早損壞,影響整體電路的壽命。Since the traditional practice always keeps a stationary phase (such as the first phase) working, that is, if the phase-reduction action is performed, the other phases are reduced, and the stationary phase is always kept, which results in power transistor and inductive workload of each phase. Unbalanced, commonly used stationary phases will be damaged earlier than other phases, affecting the life of the overall circuit.
請參見第二圖,為立錡於台灣專利公開號第201034356號中所揭露的電源供應電路之控制電路示意圖。一誤差放大器EA比較一迴授訊號FB與一輸出電壓參考訊號Vref而產生一誤差放大訊號,且將誤差放大訊號輸入不同相 位的脈寬調變比較器PWM1、PWM2中。運算放大器OP1、OP2比較各相位電流偵測電阻(未繪出)兩端的電壓訊號ISEN1及ISEN1_N、ISEN2及ISEN2_N,據此量測出各相的電流並產生對應的一電流差值放大訊號,並輸入對應的脈寬調變比較器PWM1、PWM2。此外,一震盪電路12產生一鋸齒波訊號,和脈寬調變比較器PWM1、PWM2的輸出一同輸入一驅動閘控制電路14之中。驅動閘控制電路14產生驅動訊號UG1、LG1、UG2、LG2,透過驅動閘控制電路14驅動對應的功率電晶體。Please refer to the second figure for a control circuit diagram of the power supply circuit disclosed in Taiwan Patent Publication No. 201034356. An error amplifier EA compares a feedback signal FB with an output voltage reference signal Vref to generate an error amplification signal, and inputs the error amplification signal into different phases. The bit width modulation comparators PWM1, PWM2. The operational amplifiers OP1 and OP2 compare the voltage signals ISEN1 and ISEN1_N, ISEN2 and ISEN2_N across the phase current detecting resistors (not shown), and measure the currents of the respective phases and generate corresponding current difference amplification signals, and Input the corresponding pulse width modulation comparators PWM1 and PWM2. In addition, an oscillating circuit 12 generates a sawtooth wave signal, which is input into a driving gate control circuit 14 together with the outputs of the pulse width modulation comparators PWM1 and PWM2. The drive gate control circuit 14 generates drive signals UG1, LG1, UG2, LG2, and drives the corresponding power transistors through the drive gate control circuit 14.
一外部相位控制訊號PSC決定電路是否要進入減相操作。一選相電路16接收到外部相位控制訊號PSC後,即被動決定是否要進入減相操作,當其判斷需進入減相操作時,便控制驅動閘控制電路14以關閉其中一個或多個相位。進入減相操作時,暫停工作的相位不是固定的。An external phase control signal PSC determines if the circuit is to enter a phase decrement operation. After receiving the external phase control signal PSC, a phase selection circuit 16 passively decides whether to enter the phase-reduction operation. When it determines that it needs to enter the phase-reduction operation, it controls the drive gate control circuit 14 to turn off one or more phases. When entering the subtraction operation, the phase of the pause operation is not fixed.
立錡利用選相控制,在進行減相操作時不固定關閉相同的相位,在首次決定減相時,關閉多個轉換電路中至少一相;以及在另一次決定減相時,關閉多個轉換電路中至少另一個,以期望能“平均”各相的工作時間。實際上,每次電路重新啟動,電源供應電路之控制電路仍會重預設的第一相開始暫停工作,使得各相的功率電晶體和電感工作量仍會有明顯的不平衡。The vertical phase control uses the phase selection control to not close the same phase when performing the phase decrement operation, and turns off at least one of the plurality of conversion circuits when the phase loss is first determined; and turns off the multiple conversions when another phase loss is determined. At least one other of the circuits is expected to "average" the operating time of each phase. In fact, each time the circuit is restarted, the control circuit of the power supply circuit will still restart the first phase of the preset phase, so that the power transistor and the inductor workload of each phase will still have a significant imbalance.
換言之,先前技術在減相時,所關閉的相位並不改變。其缺點是,各相位的功率電晶體與電感工作量並不平衡,常用的相位將較其他相位更早損壞,影響整體電路的壽命。In other words, the prior art does not change the phase that is turned off when the phase is dephasing. The disadvantage is that the power transistor and the inductor workload of each phase are not balanced, and the commonly used phase will be damaged earlier than other phases, which affects the lifetime of the overall circuit.
鑑於先前技術中的多相轉換控制器於減相時,各相的功率電晶體和電感工作量不平衡,使常用的相位將較其他相位更早損壞,影響整體電路的壽命。本發明於輕載時不減相操作,如此不僅確保各相工作量的平均,而且延長各相 的導通時間使系統的頻率降低,達到等同於減相的效果而提高效率。In view of the prior art multiphase conversion controller, when the phase is dephasing, the power transistor and the inductance of each phase are unbalanced, so that the commonly used phase will be damaged earlier than other phases, affecting the life of the overall circuit. The invention does not reduce the phase operation at light load, thus not only ensuring the average of the workload of each phase, but also extending the phases The on-time reduces the frequency of the system and achieves an efficiency equivalent to the effect of subtraction.
為達上述目的,本發明提供一種多相轉換控制器,用以控制耦接一輸入電壓之複數個轉換電路,使複數個轉換電路共同提供一輸出電壓。多相轉換控制器包含一迴授控制電路、一導通時間控制電路以及一多相邏輯控制電路。迴授控制電路根據輸出電壓決定一導通時點並據此產生一導通訊號。導通時間控制電路決定一導通週期。多相邏輯控制電路根據導通訊號及導通週期依序控制複數個轉換電路導通。其中,導通時間控制電路根據一模式訊號調整導通週期之長度。To achieve the above objective, the present invention provides a multi-phase conversion controller for controlling a plurality of conversion circuits coupled to an input voltage such that a plurality of conversion circuits collectively provide an output voltage. The multiphase conversion controller includes a feedback control circuit, an on time control circuit, and a polyphase logic control circuit. The feedback control circuit determines a conduction time point according to the output voltage and generates a pilot communication number accordingly. The on-time control circuit determines a conduction period. The multi-phase logic control circuit sequentially controls the plurality of conversion circuits to be turned on according to the conduction number and the conduction period. The on-time control circuit adjusts the length of the on-period according to a mode signal.
本發明也提供了一種多相轉換控制器,用以控制耦接一輸入電壓之複數個轉換電路,使複數個轉換電路共同提供一輸出電壓。多相轉換控制器包含一時脈產生電路、一迴授控制電路以及一多相邏輯控制電路。時脈產生電路根據一操作頻率產生一時脈訊號以及一斜波訊號。迴授控制電路根據輸出電壓及斜波訊號產生一導通訊號。多相邏輯控制電路根據導通訊號及時脈訊號依序控制複數個轉換電路導通。其中,迴授控制電路根據一模式訊號調整時脈訊號以及斜波訊號之頻率。The present invention also provides a multi-phase conversion controller for controlling a plurality of conversion circuits coupled to an input voltage such that a plurality of conversion circuits collectively provide an output voltage. The multiphase conversion controller includes a clock generation circuit, a feedback control circuit, and a polyphase logic control circuit. The clock generation circuit generates a clock signal and a ramp signal according to an operating frequency. The feedback control circuit generates a pilot communication number based on the output voltage and the ramp signal. The multi-phase logic control circuit sequentially controls the plurality of conversion circuits to be turned on according to the conduction signal number and the time pulse signal. The feedback control circuit adjusts the clock signal and the frequency of the ramp signal according to a mode signal.
以上的概述與接下來的詳細說明皆為示範性質,是為了進一步說明本發明的申請專利範圍。而有關本發明的其他目的與優點,將在後續的說明與圖示加以闡述。The above summary and the following detailed description are exemplary in order to further illustrate the scope of the claims. Other objects and advantages of the present invention will be described in the following description and drawings.
2、4‧‧‧轉換電路2, 4‧‧‧ conversion circuit
10‧‧‧多相轉換控制器10‧‧‧Multiphase Conversion Controller
12‧‧‧震盪電路12‧‧‧ oscillating circuit
14‧‧‧驅動閘控制電路14‧‧‧Drive gate control circuit
16‧‧‧選相電路16‧‧‧ Phase selection circuit
C‧‧‧輸出電容C‧‧‧ output capacitor
EA‧‧‧誤差放大器EA‧‧‧Error Amplifier
FB‧‧‧迴授訊號FB‧‧‧ feedback signal
ISEN1及ISEN1_N、ISEN2及ISEN2_N‧‧‧電壓訊號ISEN1 and ISEN1_N, ISEN2 and ISEN2_N‧‧‧ voltage signals
L1、L2‧‧‧電感L1, L2‧‧‧ inductance
LG1、LG2、UG1、UG2‧‧‧驅動訊號LG1, LG2, UG1, UG2‧‧‧ drive signals
MU1、MU2‧‧‧上臂電晶體MU1, MU2‧‧‧ upper arm transistor
ML1、ML2‧‧‧下臂電晶體ML1, ML2‧‧‧ lower arm transistor
OP1、OP2‧‧‧運算放大器OP1, OP2‧‧‧Operational Amplifier
PSC‧‧‧外部相位控制訊號PSC‧‧‧ external phase control signal
PWM1、PWM2‧‧‧脈寬調變比較器PWM1, PWM2‧‧‧ pulse width modulation comparator
Sm‧‧‧模式訊號Sm‧‧‧ mode signal
Vin‧‧‧輸入電壓Vin‧‧‧Input voltage
Vout‧‧‧輸出電壓Vout‧‧‧ output voltage
Vref‧‧‧輸出電壓參考訊號Vref‧‧‧ output voltage reference signal
100‧‧‧多相轉換控制器100‧‧‧Multiphase Conversion Controller
102‧‧‧比較器102‧‧‧ comparator
103‧‧‧誤差放大器103‧‧‧Error amplifier
104‧‧‧導通時間控制電路104‧‧‧ On-time control circuit
105‧‧‧時脈產生電路105‧‧‧ Clock generation circuit
106‧‧‧多相邏輯控制電路106‧‧‧Multiphase logic control circuit
108、110、112‧‧‧驅動電路108, 110, 112‧‧‧ drive circuits
202‧‧‧參考電壓產生器202‧‧‧reference voltage generator
204‧‧‧電流源204‧‧‧current source
206‧‧‧比較器206‧‧‧ comparator
208‧‧‧D型正反器208‧‧‧D type flip-flop
CJ‧‧‧時脈輸入端CJ‧‧‧ clock input
Clk‧‧‧時脈訊號Clk‧‧‧ clock signal
COMP‧‧‧誤差放大訊號COMP‧‧‧ error amplification signal
CTON‧‧‧導通時間電容CTON‧‧‧ On-time capacitance
D‧‧‧輸入端D‧‧‧ input
FB‧‧‧迴授訊號FB‧‧‧ feedback signal
ITON‧‧‧電流ITON‧‧‧ current
K1‧‧‧重設開關K1‧‧‧Reset switch
LG1、LG2、LG3、UG1、UG2、UG3‧‧‧驅動訊號LG1, LG2, LG3, UG1, UG2, UG3‧‧‧ drive signals
PWM‧‧‧導通訊號PWM‧‧‧ communication number
Q‧‧‧輸出端Q‧‧‧output
Q’‧‧‧反向輸出端Q’‧‧‧inverted output
R‧‧‧重設端R‧‧‧Reset
RAMP‧‧‧斜波訊號RAMP‧‧‧ ramp signal
Sm‧‧‧模式訊號Sm‧‧‧ mode signal
Sp1、Sp2、Sp3‧‧‧相控制訊號Sp1, Sp2, Sp3‧‧‧ phase control signals
Sto‧‧‧導通時間訊號Sto‧‧‧ on time signal
Vref‧‧‧輸出電壓參考訊號Vref‧‧‧ output voltage reference signal
VTH‧‧‧導通時間參考電壓VTH‧‧‧ On-time reference voltage
VTON‧‧‧電容電壓VTON‧‧‧ capacitor voltage
VQN‧‧‧開關訊號VQN‧‧‧ switch signal
Vin‧‧‧輸入電壓Vin‧‧‧Input voltage
Vout‧‧‧輸出電壓Vout‧‧‧ output voltage
第一圖為傳統的多相轉換控制器之電路示意圖。The first picture shows the circuit diagram of a traditional multiphase conversion controller.
第二圖為立錡於台灣專利公開號第201034356號中所揭露的電源供應電路之控制電路示意圖。The second figure is a schematic diagram of the control circuit of the power supply circuit disclosed in Taiwan Patent Publication No. 201034356.
第三圖為根據本發明之一第一較佳實施例的多相轉換控 制器之電路示意圖。The third figure is a multi-phase switching control according to a first preferred embodiment of the present invention. Schematic diagram of the circuit of the controller.
第四圖為根據本發明之一第一較佳實施例的導通時間控制電路之電路示意圖。The fourth figure is a circuit diagram of an on-time control circuit in accordance with a first preferred embodiment of the present invention.
第五圖為根據本發明之一第二較佳實施例的導通時間控制電路之電路示意圖。Figure 5 is a circuit diagram of an on-time control circuit in accordance with a second preferred embodiment of the present invention.
第六圖為根據本發明之一第二較佳實施例的多相轉換控制器之電路示意圖。Figure 6 is a circuit diagram of a multiphase conversion controller in accordance with a second preferred embodiment of the present invention.
請參見第三圖,為根據本發明之一第一較佳實施例的多相轉換控制器之電路示意圖。多相轉換控制器100係用以控制耦接一輸入電壓之複數個轉換電路(未繪出,可參見第一圖),使複數個轉換電路共同提供一輸出電壓。在本實施例以兩個轉換電路為例說明。多相轉換控制器100包含一迴授控制電路、一導通時間控制電路104以及一多相邏輯控制電路106。迴授控制電路包含一比較器102,比較器102之一非反相端接收一輸出電壓參考訊號Vref,一反向端接收代表輸出電壓之一迴授訊號FB。比較器102於迴授訊號FB的一準位低於輸出電壓參考訊號Vref的一準位時,產生一導通訊號PWM。導通時間控制電路104接收到導通訊號PWM時開始計時,於計時達到一預定導通週期時產生一導通時間訊號Sto。因此,導通訊號PWM與導通時間訊號Sto的產生時點的時間間隔代表轉換電路的一導通週期長度。多相邏輯控制電路106根據導通訊號PWM及導通時間訊號Sto所代表的導通週期來依序控制複數個轉換電路逐一導通。例如:多相邏輯控制電路106計數導通訊號PWM的次數,以對應計數的次數導通複數個轉換電路中對應的轉換電路的上臂電晶體(可參見第一圖)。Referring to the third figure, there is shown a circuit diagram of a multiphase conversion controller according to a first preferred embodiment of the present invention. The multi-phase conversion controller 100 is configured to control a plurality of conversion circuits (not shown, see the first figure) coupled to an input voltage, so that the plurality of conversion circuits jointly provide an output voltage. In the embodiment, two conversion circuits are taken as an example for explanation. The multiphase conversion controller 100 includes a feedback control circuit, an on time control circuit 104, and a polyphase logic control circuit 106. The feedback control circuit includes a comparator 102. One non-inverting terminal of the comparator 102 receives an output voltage reference signal Vref, and a reverse terminal receives a feedback signal FB representing one of the output voltages. The comparator 102 generates a pilot signal PWM when a level of the feedback signal FB is lower than a level of the output voltage reference signal Vref. The on-time control circuit 104 starts counting when receiving the communication number PWM, and generates an on-time signal Sto when the timing reaches a predetermined conduction period. Therefore, the time interval at which the conduction signal PWM and the on-time signal Sto are generated represents a length of a conduction period of the conversion circuit. The multi-phase logic control circuit 106 sequentially controls the plurality of conversion circuits to be turned on one by one according to the conduction period represented by the conduction communication number PWM and the on-time signal Sto. For example, the multi-phase logic control circuit 106 counts the number of times of the communication number PWM, and turns on the upper arm transistor of the corresponding conversion circuit in the plurality of conversion circuits corresponding to the number of times of counting (refer to the first figure).
多相邏輯控制電路106於接收到導通訊號PWM 時,產生相控制訊號Sp1、Sp2,透過驅動電路108、110產生驅動訊號UG1、UG2中對應的驅動訊號而導通對應的轉換電路的上臂電晶體,而於後接收導通時間訊號Sto時,結束對應轉換電路的導通週期而停止導通對應的轉換電路的上臂電晶體並產生驅動訊號LG1、LG2中對應的驅動訊號而導通對應的轉換電路的下臂電晶體。下臂電晶體的驅動訊號LG1、LG2之產生是為了讓一電感的一電流續流,因此,可根據連續電流模式(CCM)、非連續電流模式(DCM)、電感電流偵測、模擬二極體模式(DEM)等方式來決定是否產生以及產生的驅動訊號的脈寬。當迴授訊號FB的準位再度低於輸出電壓參考訊號Vref的準位時,多相邏輯控制電路106導通下一個轉換電路。因此,本實施例的複數個轉換電路之導通週期彼此錯開。The polyphase logic control circuit 106 receives the pilot communication number PWM When the phase control signals Sp1 and Sp2 are generated, the corresponding driving signals of the driving signals UG1 and UG2 are generated by the driving circuits 108 and 110 to turn on the upper arm transistor of the corresponding conversion circuit, and when the conduction time signal Sto is received later, the corresponding end is ended. The on-period of the conversion circuit stops turning on the upper arm transistor of the corresponding conversion circuit and generates a corresponding driving signal of the driving signals LG1, LG2 to turn on the lower arm transistor of the corresponding conversion circuit. The driving signals LG1 and LG2 of the lower arm transistor are generated to allow a current of one inductor to flow, so that it can be based on continuous current mode (CCM), discontinuous current mode (DCM), inductor current detection, and analog diode. The mode (DEM) determines the pulse width of the generated and generated drive signals. When the level of the feedback signal FB is again lower than the level of the output voltage reference signal Vref, the polyphase logic control circuit 106 turns on the next conversion circuit. Therefore, the on periods of the plurality of conversion circuits of the present embodiment are shifted from each other.
導通時間控制電路104額外接收一模式訊號Sm。模式訊號Sm可得自負載電路,例如為負載電路中之微控制器或微處理器所發出之數位控制訊號,或為與負載電流有關的類比訊號。當模式訊號Sm代表一輕載狀態時,導通時間控制電路104延後產生導通時間訊號Sto,也就是導通訊號PWM及導通時間訊號Sto的產生時點的時間間隔被延長。如此,複數個轉換電路的上臂電晶體導通時間延長,可使每一個轉換電路每次傳送至負載的能量提高而延後迴授訊號FB的準位低於輸出電壓參考訊號Vref的準位的時間點。如此,本發明達到操作頻率降低的效果,因而減少切換損失,及提高輕載時的效率。而且,多相邏輯控制電路106仍依序控制複數個轉換電路導通而不進行減相操作,避免了先前技術中因各相工作量不均之問題。The on-time control circuit 104 additionally receives a mode signal Sm. The mode signal Sm can be obtained from a load circuit, such as a digital control signal sent by a microcontroller or microprocessor in the load circuit, or an analog signal related to the load current. When the mode signal Sm represents a light load state, the on-time control circuit 104 delays the generation of the on-time signal Sto, that is, the time interval at which the conduction signal PWM and the on-time signal Sto are generated is extended. In this way, the upper arm transistor on-time of the plurality of conversion circuits is extended, so that the energy of each conversion circuit is increased to the load and the timing of the feedback signal FB is lower than the level of the output voltage reference signal Vref. point. As such, the present invention achieves the effect of reducing the operating frequency, thereby reducing switching losses and improving efficiency at light loads. Moreover, the multi-phase logic control circuit 106 still controls the plurality of conversion circuits to be turned on without performing the phase-reduction operation, thereby avoiding the problem of uneven workload due to the respective phases in the prior art.
請參見第四圖,為根據本發明之一第一較佳實施例的導通時間控制電路之電路示意圖。導通時間控制電路主要包含一參考電壓產生器202、一電流源204、一比較器206 以及一導通時間電容CTON。電流源204產生一電流ITON對導通時間電容CTON充電以產生一電容電壓VTON。參考電壓產生器202產生一導通時間參考電壓VTH。比較器206比較電容電壓VTON及導通時間參考電壓VTH以產生一導通週期訊號。導通時間控制電路可包含一D型正反器208及一重設開關K1,以便使導通時間電容CTON的電容電壓VTON於下一相操作時能於零電壓開始。D型正反器208於一時脈輸入端CJ接收到導通訊號PWM時,根據一輸入端D接收的一邏輯訊號”1”,於一反向輸出端Q’輸出一低準位的一開關訊號VQN,以截止重設開關K1。電流源204開始對導通時間電容CTON充電,使導通時間參考電壓VTH開始上升。此時,電容電壓VTON低於導通時間參考電壓VTH。於經過預定導通週期之後,電容電壓VTON高於導通時間參考電壓VTH,比較器206輸出導通時間訊號Sto。D型正反器208的一重設端R接收導通時間訊號Sto時,重設輸出,使一輸出端Q輸出一低準位訊號,而反相輸出端Q’輸出一高準位的開關訊號VQN,以導通重設開關K1。此時,電容電壓VTON被歸零以等待下一次週期(即導通訊號PWM又回到高準位)。Please refer to the fourth figure, which is a circuit diagram of an on-time control circuit according to a first preferred embodiment of the present invention. The on-time control circuit mainly includes a reference voltage generator 202, a current source 204, and a comparator 206. And an on-time capacitor CTON. The current source 204 generates a current ITON to charge the on-time capacitor CTON to generate a capacitor voltage VTON. The reference voltage generator 202 generates an on-time reference voltage VTH. The comparator 206 compares the capacitor voltage VTON and the on-time reference voltage VTH to generate a turn-on period signal. The on-time control circuit can include a D-type flip-flop 208 and a reset switch K1 to enable the capacitor voltage VTON of the on-time capacitor CTON to start at zero voltage during the next phase operation. When receiving the communication number PWM, the D-type flip-flop 208 outputs a low-level switching signal at a reverse output terminal Q' according to a logic signal "1" received by an input terminal D. VQN, reset switch K1 with a cutoff. The current source 204 begins to charge the on-time capacitor CTON, causing the on-time reference voltage VTH to begin to rise. At this time, the capacitor voltage VTON is lower than the on-time reference voltage VTH. After a predetermined conduction period, the capacitor voltage VTON is higher than the on-time reference voltage VTH, and the comparator 206 outputs the on-time signal Sto. When a reset terminal R of the D-type flip-flop 208 receives the on-time signal Sto, the output is reset, so that an output terminal Q outputs a low-level signal, and the inverting output terminal Q' outputs a high-level switching signal VQN. To turn on the reset switch K1. At this time, the capacitor voltage VTON is reset to zero to wait for the next cycle (ie, the pilot communication number PWM returns to the high level).
電流源204根據複數個轉換電路耦接的一輸入電壓Vin或/及共同提供的一輸出電壓Vout來決定對導通時間電容CTON充電的電流ITON之大小,即決定了複數個轉換電路之導通週期之預定長度。電流源204也額外接收模式訊號Sm,於模式訊號Sm代表輕載狀態時,降低電流ITON之大小,使得轉換電路的導通週期延長。例如:當電流ITON降為1/N時,則導通週期變為原來的N倍,而達到等同相當於減了(N-1)相之效果。The current source 204 determines the magnitude of the current ITON for charging the on-time capacitor CTON according to an input voltage Vin coupled to the plurality of conversion circuits and/or a common output voltage Vout, that is, determining the on-period of the plurality of conversion circuits. The predetermined length. The current source 204 also receives the mode signal Sm additionally. When the mode signal Sm represents the light load state, the current ITON is reduced, so that the conduction period of the conversion circuit is extended. For example, when the current ITON is reduced to 1/N, the on-period becomes N times the original, and the equivalent is equivalent to the effect of subtracting the (N-1) phase.
請參見第五圖,為根據本發明之一第二較佳實施例的導通時間控制電路之電路示意圖。相較於第三圖所示之實施例,改以參考電壓產生器202對應模式訊號Sm進行調 變。當模式訊號Sm代表輕載狀態時,參考電壓產生器202提高導通時間參考電壓VTH的電壓,使得轉換電路的導通週期延長。其他電路的操作請參見第四圖對應的電路說明。Referring to FIG. 5, it is a circuit diagram of an on-time control circuit according to a second preferred embodiment of the present invention. Compared with the embodiment shown in the third figure, the reference voltage generator 202 is adjusted according to the mode signal Sm. change. When the mode signal Sm represents the light load state, the reference voltage generator 202 increases the voltage of the on-time reference voltage VTH, so that the on-period of the conversion circuit is extended. For the operation of other circuits, please refer to the circuit description corresponding to the fourth figure.
請參見第六圖,為根據本發明之一第二較佳實施例的多相轉換控制器之電路示意圖。多相轉換控制器100係用以控制耦接一輸入電壓之複數個轉換電路,使複數個轉換電路共同提供一輸出電壓。在本實施例以三個轉換電路為例說明,多相轉換控制器100產生相控制訊號Sp1、Sp2、Sp3,透過驅動電路108、110、112,產生驅動訊號UG1、LG1、UG2、LG2、UG3、LG3,以控制對應的轉換電路的上臂電晶體及下臂電晶體。本實施例為定頻電路架構。多相轉換控制器100包含一迴授控制電路、一時脈產生電路105以及一多相邏輯控制電路106。迴授控制電路包含一比較器102及誤差放大器103。誤差放大器103的一非反相端接收一輸出電壓參考訊號Vref,一反向端接收代表輸出電壓之一迴授訊號FB,並據此產生一誤差放大訊號COMP。時脈產生電路105根據預設的一操作頻率,產生一時脈訊號Clk以及一斜波訊號RAMP,因此時脈訊號Clk及斜波訊號RAMP的頻率相同。比較器102的一非反相端接收一誤差放大訊號COMP,一反向端接收斜波訊號RAMP,並據此產生導通訊號PWM。多相邏輯控制電路106根據一導通訊號PWM及時脈訊號Clk來依序控制複數個轉換電路逐一導通。6 is a circuit diagram of a multi-phase conversion controller according to a second preferred embodiment of the present invention. The multi-phase conversion controller 100 is configured to control a plurality of conversion circuits coupled to an input voltage, so that the plurality of conversion circuits jointly provide an output voltage. In the embodiment, the three conversion circuits are taken as an example to illustrate that the multi-phase conversion controller 100 generates phase control signals Sp1, Sp2, and Sp3, and generates driving signals UG1, LG1, UG2, LG2, and UG3 through the driving circuits 108, 110, and 112. LG3 controls the upper arm transistor and the lower arm transistor of the corresponding conversion circuit. This embodiment is a fixed frequency circuit architecture. The multiphase conversion controller 100 includes a feedback control circuit, a clock generation circuit 105, and a polyphase logic control circuit 106. The feedback control circuit includes a comparator 102 and an error amplifier 103. A non-inverting terminal of the error amplifier 103 receives an output voltage reference signal Vref, and a reverse terminal receives a feedback signal FB representing one of the output voltages, and accordingly generates an error amplification signal COMP. The clock generation circuit 105 generates a clock signal Clk and a ramp signal RAMP according to a preset operating frequency, so that the clock signal Clk and the ramp signal RAMP have the same frequency. A non-inverting terminal of the comparator 102 receives an error amplification signal COMP, and a reverse terminal receives the ramp signal RAMP, and generates a pilot signal PWM accordingly. The multi-phase logic control circuit 106 sequentially controls the plurality of conversion circuits to be turned on one by one according to a pilot communication number PWM and a timely pulse signal Clk.
時脈產生電路105接收一模式訊號Sm,於模式訊號Sm代表一輕載狀態時,降低時脈訊號Clk以及斜波訊號RAMP的頻率。當頻率降為1/N時,本實施例即達到減(N-1)相的效果。The clock generation circuit 105 receives a mode signal Sm, and reduces the frequency of the clock signal Clk and the ramp signal RAMP when the mode signal Sm represents a light load state. When the frequency is reduced to 1/N, the embodiment achieves the effect of reducing the (N-1) phase.
如上所述,本發明完全符合專利三要件:新穎性、進步性和產業上的利用性。本發明在上文中已以較佳實施例揭露,然熟習本項技術者應理解的是,該實施例僅用於 描繪本發明,而不應解讀為限制本發明之範圍。應注意的是,舉凡與該實施例等效之變化與置換,均應設為涵蓋於本發明之範疇內。因此,本發明之保護範圍當以下文之申請專利範圍所界定者為準。As described above, the present invention fully complies with the three requirements of the patent: novelty, advancement, and industrial applicability. The present invention has been disclosed above in the preferred embodiments, but it should be understood by those skilled in the art that this embodiment is only used for The invention is depicted and should not be construed as limiting the scope of the invention. It should be noted that variations and permutations equivalent to those of the embodiments are intended to be included within the scope of the present invention. Therefore, the scope of the invention is defined by the scope of the following claims.
100‧‧‧多相轉換控制器100‧‧‧Multiphase Conversion Controller
102‧‧‧比較器102‧‧‧ comparator
104‧‧‧導通時間控制電路104‧‧‧ On-time control circuit
106‧‧‧多相邏輯控制電路106‧‧‧Multiphase logic control circuit
108、110‧‧‧驅動電路108, 110‧‧‧ drive circuit
FB‧‧‧迴授訊號FB‧‧‧ feedback signal
LG1、LG2、UG1、UG2‧‧‧驅動訊號LG1, LG2, UG1, UG2‧‧‧ drive signals
PWM‧‧‧導通訊號PWM‧‧‧ communication number
Sm‧‧‧模式訊號Sm‧‧‧ mode signal
Sp1、Sp2‧‧‧相控制訊號Sp1, Sp2‧‧‧ phase control signals
Sto‧‧‧導通時間訊號Sto‧‧‧ on time signal
Vref‧‧‧輸出電壓參考訊號Vref‧‧‧ output voltage reference signal
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Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20050237040A1 (en) * | 2004-04-23 | 2005-10-27 | Semiconductor Components Industries, Llc. | Switch controller for a power control system and method therefor |
US20060164050A1 (en) * | 2005-01-27 | 2006-07-27 | Fujitsu Limited | Multi-phase DC-DC converter and control circuit for multi-phase DC-DC converter |
US20090167271A1 (en) * | 2004-09-10 | 2009-07-02 | Benjamim Tang | Active transient response circuits, system and method for digital multiphase pulse width modulated regulators |
TW201034356A (en) * | 2009-03-05 | 2010-09-16 | Richtek Technology Corp | Multi-phase power converter and control circuit and method thereof |
TW201131955A (en) * | 2009-06-23 | 2011-09-16 | Intersil Inc | System and method for PFM/PWM mode transition within a multi-phase buck converter |
-
2013
- 2013-03-12 TW TW102108701A patent/TWI497885B/en active
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20050237040A1 (en) * | 2004-04-23 | 2005-10-27 | Semiconductor Components Industries, Llc. | Switch controller for a power control system and method therefor |
US20090167271A1 (en) * | 2004-09-10 | 2009-07-02 | Benjamim Tang | Active transient response circuits, system and method for digital multiphase pulse width modulated regulators |
US20060164050A1 (en) * | 2005-01-27 | 2006-07-27 | Fujitsu Limited | Multi-phase DC-DC converter and control circuit for multi-phase DC-DC converter |
TW201034356A (en) * | 2009-03-05 | 2010-09-16 | Richtek Technology Corp | Multi-phase power converter and control circuit and method thereof |
TW201131955A (en) * | 2009-06-23 | 2011-09-16 | Intersil Inc | System and method for PFM/PWM mode transition within a multi-phase buck converter |
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