1360917 九、發明說明： 【發明所屬之技術領域】 本發明係有關於一種天線，特別是有關於一種適用於 行動通訊裝置之多頻環圈天線。 【先前技銜】 由於廣域無線網路（WWAN，Wireless Wide Area Network)技 術、無線區域網路（WLAN, Wireless Local Area Network)技術與 籲全球互通微波存取（WiMAX，Worldwide Interoperability for Micro-wave Access) 技術 的蓬勃 發展， 未來單 一行動 通訊裝 置同時 具備通訊與上網之功能已成為必然的趨勢。而若要達到此 一目的，如何能在單一行動通訊裝置内完成涵蓋多頻帶操 作之天線設計就成為相當關鍵的技術問題。 若選擇在單一行動通訊裝置内配置多天線系統，會遭 遇到多天線擺放空間的浪費、電磁干擾等問題需要解決。 因此設計出可涵蓋多系統操作頻帶之單一天線為較佳之問 籲題解決方案。先前相關美國專利第6,727,854號“平面倒F 形天線（Planar inverted-F antenna)” ’其揭示一種可雙頻操作之 天線設計，該天線僅能涵蓋歐規GSM900/1800系統操作’且 該天線結構較為複雜。台灣發明專利第519,779號"雙頻平 面式單偶極天線之輻射金屬片"，其揭示一種可三頻操作 之天線設計，該天線雖能涵蓋GSM900/1800/1900系統，但其 在實際運用上受到操作頻帶的限制較大。為解決這些問題 ,我們提出一種適用於行動通訊裴置之創新内藏式多頻環 1360917 包3 . 一連接線15、一耦合部16以及一微調部丨7〇該連接 線b，其一端大致位於該接地面一邊緣處，且為該天線之 s γ貝入點151。該耦合部16，其電氣連接於該連接線15 ，同時該耦合部丨6與該輻射金屬線13之一區間ι31形成一 搞合部分18。該微調部17，由一金屬線所組成，⑽該接 ，面12之-邊緣⑵與_合料之間，該微調部口並電 氣連接至該連接線15。 _本發明天線主要是藉由該饋入金屬部14來耦合激發該 ::金屬線13 ’並且藉由適當調整該耦合部與該輻射金 、·之d Μ 131形成之輕合部分18，可使得該輻射金 屬線13之較低與較高共振模態均形成雙共振激發狀態，並 由該微調部17來微調共振模態之阻抗匹配，如此可大幅增 加共振模態之操作頻寬。 第2圖為本發明天線一實施例i之返回損失㈣m 2實驗量測圖，本實施例選擇下列尺寸進行實驗量測·· …I質基板11長度為112mm、寬度為6〇_、厚度為⑽ 咖，該接地面區間⑴與接地面⑴句長度為95麵、寬 度為6〇mm ;該介質面區間Π2長度為17mm、寬产為 6〇_ ;該輕射金屬線13總長度約為235 _，其為:平面 ，構’以印刷或餘刻之方式形成於該介質面區間之表面上 :3 ;該饋入金屬部14之連接線15長度為9_、寬度為 =ϊ7由該=部16長度為出咖、寬度為〇·5—·該微 金屬線所組成，長度為2〇5_、寬度為一。 ，實施例1能成功於較低頻帶共振出-第一 1360917 ' 雙共振激發模態21，於較高頻帶共振出一第二雙共振激發 模態22與一第三雙共振激發模態23。並且由所得的測試結 果，縱軸表示返回損失，橫軸表示操作頻率，在6 dB返回 損失的定義下，該第一雙共振激發模態21能完全涵蓋行動 通訊系統GSM850/900(824-894 /890-960 MHz)之頻寬需求，而該 乐一與乐二！共振激:货換恐“、u所合成之見頻杈悲能元 全涵蓋 GSM1800/1900 (1710-1880/1850-1990 MHz)與 UMTS (1920-2170 MHz)行動通訊系統之頻寬需求。本發明天線具 鲁備了結構簡單、製作成本低並且可多頻操作的優點，因而 相當適合内藏應用於各種行動通訊裝置中。 第3圖為實施例1之較低操作頻帶天線增益圖與輻射 效率圖。左邊縱軸表示天線增益，右邊縱軸表示天線輻射 效率，橫軸表示操作頻率；由所得之結果，在GSM850/900 頻帶内，天線增益曲線31分佈於1.5〜2.0 dBi之間，天線輻 射效率曲線32分佈於80%〜90%之間，能滿足行動通訊系統 φ實際操作之增益與效率需求。 第4圖為實施例1之較高操作頻帶天線增益圖與輻射 效率圖。在GSM180CV1900與UMTS頻帶内，天線增益曲線 41分佈於0.5〜3.0 dBi之間，天線輻射效率曲線42分佈於 65%〜90%之間，能滿足行動通訊系統實際操作之增益與效 率需求。 第5圖為本發明天線第一其他實施例5結構圖。實施 例5雖然其饋入金屬部54之形狀與實施例1有所差異，但 其也能有效的耦合激發該輻射金屬線13。只要適當調整該 丄360917 ，合部56與㈣射金屬線13之—區間131形成之輕合部分 2樣能使得該ϋ射金屬線13之較低與較高共振模態均 /又共振激發狀態，而大幅增加共振模態之阻抗頻寬， 並且同樣能由該微調部57來微調共振模態之阻抗匹配。’因 此2施例5也能達成同時涵蓋多頻行動通訊系統頻寬之應 甩需求。 μ 第6圖為本發明天線第二其他實施例6結構圖。實施 例6雖然其饋入金屬部64之微調部67改由兩金屬線組成， .而與實施例1有所差異，但其同樣也能有效的由該微調部 67來微調共振模態之阻抗匹配。因此實施例6也能達成同 時涵蓋多頻行動通訊系統頻寬之應用需求。 第7圖為本發明天線第三其他實施例7結構圖。實施 例7雖然其輻射金屬線13與饋入金屬部μ位於同一平面上 而與實施例1有所差異，但其同樣也能藉由適當調整該耦 合部16與該輻射金屬線13之一區間131形成之耦合部分” 鲁，可使得該輻射金屬線13之較低與較高共振模態均形成雙 共振激發狀態。因此實施例7也能達成同時涵蓋多頻行動 通訊系統頻寬之應用需求。 第8圖為本發明天線之第四其他實施例8結構圖。實 施例8之該輻射金屬線13為一立體結構，其以印刷或蝕刻 之方式形成於一介質塊81之表面上’成為一可表面點著之 元件，並具有大致平行之二彎折線82、83。如此可以大幅 減少天線整體所佔用之總體積，而達到縮小化的目的，並 且減少天線組裝成本。實施例8亦可同時完全涵蓋Wwan 1360917 •五頻帶（GSM850/900/1800/1900 與 UMTS)、WLAN 2.4 GHz 頻帶 以及WiMAX 2.5 GHz頻帶等共7系統頻帶操作之頻寬需求。 第9圖為本發明天線第四其他實施例8之返回損失實 驗量測結果。參考第8圖，實施例8選擇下列尺寸進行實 驗量測.該介質基板11長度為1〇5 mm、寬度為60 mm、厚 度為0.8 mm ;該接迪面區間111與接地面12均長度為95 mm、寬度為60mm ;該介質面區間112長度為i〇mm、 寬度為60 mm ;該輻射金屬線π總長度約為245 mm，其為 _ 一立體結構，以印刷或蝕刻之方式形成於一介質塊8丨之表 面上，該介質塊81長度為60 mm、寬度為1〇 mm，其垂直 該接地面12方向之高度為3 mm(該彎折線82至該彎折線83 之距離）；該饋入金屬部14之該連接線15長度為9mm、寬 度為1.5mm ;該耦合部16長度為135mm、寬度為〇5mm ; 該微調部17由一金屬線所組成，長度為2〇 mm、寬度為2 mm。如第9圖所示，實施例8能成功於較低頻帶共振出 癱一第一雙共振激發模態91，於較高頻帶共振出一第二與一 第三雙共振激發模態92、％。並且由所得的測試結果了該 第一雙共振激發模態91能涵蓋行動通訊系統GSM85〇/9〇〇之 頻寬需求，而該第二與第三雙共振激發模態92、％所合成 之寬頻模態能涵蓋行動通訊系統GSM1800/1900與UMTS之 頻寬需求。此外實施例8還能涵蓋^ΑΝ2·4(}Ηζ頻帶以及 WiMAX2.5GHZ頻帶，而達成共7系統頻帶操作之頻寬需求 。本發明天線具備了結構簡單、製作成本低並且可多頻操 作的優點，因而適合内藏應用於各種行動通訊裝置中。、 1360917 第10圖為實施例8之較低操作頻帶天線增益盘輕射效 率圖。左邊縱輪表示天線增益，右邊縱轴表示天線輕射效 率，橫轴表示操作頻卜由所得之結果，在GSM850/900頻 帶内，天線增益曲線101分佈於〇5〜15dBi之間天線輻 射效率曲線102分佈於70%〜80%之間，能滿足行動通訊系 統實際操作之增益與效率需求。 第11圖為實施例8之較高操作頻帶天線增益與輻射效 率圖。由所得之結果，在GSM18〇〇/19〇〇與頻帶内， 鲁天線增益曲線！03分佈於05〜35dBi之間，輻射效率曲線 104 刀佈於 50〇/〇 〜85% 之間；在 WLAN 2.4 GHz 與 WiMAX 2.5 GHZ頻帶内’天線增益曲線103分佈於2.5〜3,5 dBi之間， 天線輻射效率曲線104分佈於70%〜9〇%之間，均能滿足行 動通訊系統與無線上網系統實際操作之增益與效率需求。 綜合上述的說明，本發明天線具有結構簡單、製作成 本低、可多頻帶操作以及縮小化的優點，功能明確，因此 鲁本發明天線具高度產業應用價值，足以符合發明之範疇。 在上述說明中所敘述之實施例僅為說明本發明裝置之 原理及其功效，而非限制本發明。因此，習於此技術之人 士可在不違背本發明之精神對上述實施例進行修改及變化 。本發明之權利範圍應如後述之申請專利範圍所列。 【圖式簡單說明】 第1圖為本發明天線一實施例結構圖。 第2圖為本發明天線一實施例之返回損失實驗測量圖。 12 1360917 第3圖為本發明天線一實施例之較低操作頻帶天線增益與 輪射效率圖。 第4圖為本發明天線一實施例之較高操作頻帶天線増益與 輻射效率圖。 ' 第5圖為本發明天線第一其他實施例結構圖。 第6圖為本發明天線第二其他實施例結構圖。 第7圖為本發明天線第三其他實施例結構圖。 第8圖為本發明天線第四其他實施例結構圖。 鲁第9圖為本發明天線第四其他實施例之返回損失實驗測量 圖。 第10圖為本發明天線第四其他實施例之較低操作頻帶天線 增益與輻射效率圖。 第11圖為本發明天線第四其他實施例之較高操作頻帶天線 增益與輻射效率圖。 Φ【主要元件符號說明】 I 本發明天線一實施例 5 本發明天線第一其他實施例 6 本發明天線第二其他實施例 7 本發明天線第三其他實施例 8 本發明天線第四其他實施例 II 介質基板或一行動通訊裝置之系統電路板 III 接地面區間 介質面區間 13 112 1360917 113 介質面區間之一表面 12 接地面 121 接地面之一邊緣 122 第一接地點 123 第二接地點 13 輻射金屬線1360917 IX. Description of the Invention: [Technical Field] The present invention relates to an antenna, and more particularly to a multi-frequency loop antenna suitable for use in a mobile communication device. [Previous Skills] Due to Wide Area Wireless Network (WWAN) technology, Wireless Local Area Network (WLAN) technology and Worldwide Interoperability for Microwave (WiMAX) Access) The rapid development of technology, the future of a single mobile communication device with the function of communication and Internet has become an inevitable trend. To achieve this goal, how to complete the antenna design covering multi-band operation in a single mobile communication device becomes a very critical technical problem. If you choose to configure a multi-antenna system in a single mobile communication device, you will encounter problems such as waste of multiple antenna placement space and electromagnetic interference. Therefore, designing a single antenna that can cover multiple operating bands of the system is a preferred solution. Prior to the "Planar inverted-F antenna" of the U.S. Patent No. 6,727,854, which discloses a dual-frequency operation antenna design that can only cover the operation of the European standard GSM900/1800 system and the antenna structure More complicated. Taiwan Invention Patent No. 519,779 "Double-Frequency Planar Single Dipole Antenna Radiation Metal Sheet", which discloses a three-frequency operation antenna design that can cover GSM900/1800/1900 systems, but in practice The use is limited by the operating frequency band. In order to solve these problems, we propose an innovative built-in multi-frequency ring 1360917 package 3 suitable for mobile communication devices. A connecting line 15, a coupling portion 16 and a fine adjustment portion 〇7, the connecting line b, one end of which is substantially Located at an edge of the ground plane and is the s gamma entry point 151 of the antenna. The coupling portion 16 is electrically connected to the connecting line 15, and the coupling portion 6 forms a engaging portion 18 with a portion ι31 of the radiating metal wire 13. The fine adjustment portion 17 is composed of a metal wire (10) between the edge-to-edge (2) of the surface 12 and the material, and the fine adjustment portion is electrically connected to the connection line 15. The antenna of the present invention is mainly coupled by the feeding metal portion 14 to excite the:: metal wire 13' and by appropriately adjusting the coupling portion and the light-emitting portion 18 formed by the radiation gold, d Μ 131, The lower and higher resonance modes of the radiation metal line 13 are both in a double resonance excitation state, and the fine adjustment portion 17 is used to finely adjust the impedance matching of the resonance mode, so that the operation bandwidth of the resonance mode can be greatly increased. 2 is a return loss (four) m 2 experimental measurement chart of an embodiment i of the antenna of the present invention. In this embodiment, the following dimensions are selected for experimental measurement. The length of the substrate 11 is 112 mm, the width is 6 〇, and the thickness is (10) Coffee, the grounding surface interval (1) and the grounding surface (1) have a length of 95 faces and a width of 6 mm; the medium face interval Π2 has a length of 17 mm and a wide yield of 6 〇 _; the total length of the light-radiating metal wire 13 is approximately 235 _, which is: plane, structure 'formed on the surface of the medium surface section by printing or engraving: 3; the connecting line 15 of the feeding metal part 14 has a length of 9_, and the width is ϊ7 by the = The length of the portion 16 is a coffee, and the width is 〇·5—·the micro metal wire is composed of a length of 2〇5_ and a width of one. Embodiment 1 can successfully resonate in the lower frequency band - the first 1360917 'double resonance excitation mode 21, and a second dual resonance excitation mode 22 and a third double resonance excitation mode 23 are resonated in the higher frequency band. And from the test results obtained, the vertical axis represents the return loss, and the horizontal axis represents the operating frequency. Under the definition of 6 dB return loss, the first dual resonance excitation mode 21 can fully cover the mobile communication system GSM850/900 (824-894). /890-960 MHz) bandwidth requirements, and the music and music two! Resonance: The goods are exchanged for fear, and the synthesis of the frequency of sorrow and energy covers the bandwidth requirements of GSM1800/1900 (1710-1880/1850-1990 MHz) and UMTS (1920-2170 MHz) mobile communication systems. The invention antenna has the advantages of simple structure, low production cost and multi-frequency operation, and thus is suitable for being built into various mobile communication devices. Fig. 3 is a lower operating band antenna gain map and radiation of the embodiment 1. Efficiency graph. The vertical axis on the left represents the antenna gain, the vertical axis on the right represents the radiation efficiency of the antenna, and the horizontal axis represents the operating frequency. As a result, the antenna gain curve 31 is distributed between 1.5 and 2.0 dBi in the GSM850/900 band. The radiation efficiency curve 32 is distributed between 80% and 90%, which can meet the gain and efficiency requirements of the actual operation of the mobile communication system φ. Figure 4 is a diagram of the higher operating band antenna gain map and radiation efficiency of the embodiment 1. In GSM180CV1900 In the UMTS band, the antenna gain curve 41 is distributed between 0.5 and 3.0 dBi, and the antenna radiation efficiency curve 42 is distributed between 65% and 90%, which can meet the gain and efficiency requirements of the actual operation of the mobile communication system. Figure 5 is a structural view of the first embodiment 5 of the antenna of the present invention. Although the shape of the feeding metal portion 54 is different from that of the embodiment 1, the radiant metal wire can be effectively coupled and excited. 13. As long as the 丄360917 is properly adjusted, the light-bonding portion 2 formed by the merging portion 56 and the (four) radiant metal line 13 may cause the lower and higher resonant modes of the radiant metal line 13 to be/resonant. The state is excited, and the impedance bandwidth of the resonant mode is greatly increased, and the impedance matching of the resonant mode can also be finely adjusted by the fine adjustment portion 57. Thus, the second embodiment 5 can also achieve the bandwidth of the multi-frequency mobile communication system. The sixth embodiment is a structural view of the second embodiment 6 of the antenna of the present invention. Although the fine adjustment portion 67 of the feeding metal portion 64 is composed of two metal wires, the embodiment 6 has The difference, but it can also effectively fine-tune the impedance matching of the resonant mode by the fine adjustment portion 67. Therefore, the embodiment 6 can also achieve the application requirement covering the bandwidth of the multi-frequency mobile communication system. Third other embodiment 7 structure diagram The seventh embodiment differs from the first embodiment in that the radiation metal wire 13 and the feeding metal portion 51 are on the same plane, but it can also be adjusted by appropriately adjusting the coupling portion 16 and the radiation metal wire 13 The coupling portion formed by the interval 131 is such that the lower and higher resonance modes of the radiation metal line 13 form a double resonance excitation state. Therefore, Embodiment 7 can also achieve the application requirements that cover the bandwidth of the multi-frequency mobile communication system. Figure 8 is a structural view showing a fourth embodiment 8 of the antenna of the present invention. The radiant metal line 13 of the embodiment 8 is a three-dimensional structure formed on the surface of a dielectric block 81 by printing or etching, and becomes a surface-engaging component, and has substantially parallel two bending lines 82, 83. In this way, the total volume occupied by the entire antenna can be greatly reduced, and the reduction is achieved, and the antenna assembly cost is reduced. Embodiment 8 can also fully cover the bandwidth requirements of a total of 7 system band operations such as Wwan 1360917 • Five Bands (GSM850/900/1800/1900 and UMTS), WLAN 2.4 GHz band, and WiMAX 2.5 GHz band. Fig. 9 is a graph showing the results of the return loss test of the fourth embodiment 8 of the antenna of the present invention. Referring to Fig. 8, the following dimensions are selected for the experimental measurement. The dielectric substrate 11 has a length of 1 〇 5 mm, a width of 60 mm, and a thickness of 0.8 mm. The length of the interface between the interface 111 and the ground plane 12 is 95 mm, width 60 mm; the medium surface section 112 has a length of i〇mm and a width of 60 mm; the total length of the radiation metal line π is about 245 mm, which is a three-dimensional structure formed by printing or etching. On the surface of a dielectric block 8丨, the dielectric block 81 has a length of 60 mm and a width of 1 mm, and its height perpendicular to the ground plane 12 is 3 mm (the distance between the bending line 82 and the bending line 83); The connecting wire 15 of the feeding metal portion 14 has a length of 9 mm and a width of 1.5 mm; the coupling portion 16 has a length of 135 mm and a width of 〇5 mm; the fine adjustment portion 17 is composed of a metal wire and has a length of 2 mm. The width is 2 mm. As shown in FIG. 9, Embodiment 8 can successfully resonate with a first dual resonant excitation mode 91 in the lower frequency band and a second and a third dual resonance excitation mode 92, % in the higher frequency band. . And the obtained test results show that the first dual resonance excitation mode 91 can cover the bandwidth requirement of the mobile communication system GSM85〇/9〇〇, and the second and third dual resonance excitation modes 92,% are synthesized. The wideband mode covers the bandwidth requirements of the mobile communication system GSM1800/1900 and UMTS. In addition, Embodiment 8 can also cover the bandwidth of the ΑΝ2·4 (} Ηζ band and the WiMAX 2.5 GHz band, and achieve the bandwidth requirement of a total of 7 system band operations. The antenna of the present invention has a simple structure, low manufacturing cost, and multi-frequency operation. The advantages are therefore suitable for the built-in application in various mobile communication devices. 1360917 Fig. 10 is a diagram showing the lower operating band antenna gain disk light-emission efficiency diagram of Embodiment 8. The left vertical wheel represents the antenna gain, and the right vertical axis represents the antenna light shot. Efficiency, the horizontal axis represents the result of the operation frequency. In the GSM850/900 band, the antenna gain curve 101 is distributed between 〇5 and 15dBi. The antenna radiation efficiency curve 102 is distributed between 70% and 80%, which can satisfy the action. The gain and efficiency requirements of the actual operation of the communication system. Figure 11 is a graph showing the gain and radiation efficiency of the antenna in the higher operating band of Example 8. From the results obtained, the radiant gain curve is in the GSM18〇〇/19〇〇 and band. !03 is distributed between 05~35dBi, the radiation efficiency curve 104 is between 50〇/〇~85%; in the WLAN 2.4 GHz and WiMAX 2.5 GHZ band, the antenna gain curve 103 is distributed in 2 Between .5 and 3,5 dBi, the antenna radiation efficiency curve 104 is distributed between 70% and 9〇%, which can meet the gain and efficiency requirements of the actual operation of the mobile communication system and the wireless Internet access system. The invention has the advantages of simple structure, low manufacturing cost, multi-band operation and reduction, and has clear functions. Therefore, the invention has a high industrial application value, which is sufficient for the scope of the invention. The embodiment described in the above description is only The present invention may be modified and changed without departing from the spirit and scope of the invention, and the scope of the present invention should be as described below. BRIEF DESCRIPTION OF THE DRAWINGS [FIG. 1] FIG. 1 is a structural diagram of an embodiment of an antenna according to the present invention. FIG. 2 is a diagram showing an experimental measurement of return loss of an antenna according to an embodiment of the present invention. 12 1360917 A lower operating band antenna gain and a roll efficiency diagram of an embodiment of the inventive antenna. FIG. 4 is a diagram showing a higher operating band of an embodiment of the antenna of the present invention. Figure 5 is a structural view of a first embodiment of the antenna of the present invention. Figure 6 is a structural view of a second embodiment of the antenna of the present invention. Figure 7 is a structural view of a third embodiment of the antenna of the present invention. Figure 8 is a structural view of a fourth embodiment of the antenna of the present invention. Figure 9 is a measurement diagram of return loss of the fourth embodiment of the antenna of the present invention. Figure 10 is a fourth embodiment of the antenna of the present invention. The lower operating band antenna gain and radiation efficiency map. Fig. 11 is a diagram showing the higher operating band antenna gain and radiation efficiency of the fourth embodiment of the antenna of the present invention. Φ [Main component symbol description] I The antenna of the present invention is an embodiment 5 Antenna of the Invention Other Embodiment 6 Antenna of the Invention Second Embodiment 7 Antenna of the Invention Third Embodiment 8 The fourth embodiment of the antenna of the present invention II The dielectric substrate or the system board III ground plane of a mobile communication device Interval medium surface interval 13 112 1360917 113 One of the dielectric surface sections Surface 12 Ground plane 121 One of the ground plane edges 122 First ground point 123 Second ground point 13 Radiation metal wire
131 輻射金屬線之耦合區間 14，54, 64饋入金屬部 15, 55, 65連接線 151 訊號饋入點 16, 56, 66耦令部或一耦合金屬線 17, 57, 67微調部或一微調金屬線 18, 58, 68, 71耦合部與輻射金屬線之一區間形成之耦 合部分 21，91本發明天線之第一雙共振激發模態131 The radiating metal wire coupling section 14, 54, 64 is fed into the metal part 15, 55, 65 connecting line 151 signal feeding point 16, 56, 66 coupling part or a coupling metal line 17, 57, 67 fine adjustment part or one a first dual resonant excitation mode of the antenna of the present invention is formed by a coupling portion 21, 91 formed by a portion of the coupling portion and the radiating metal line
22,92本發明天線之第二雙共振激發模態 23, 93本發明天線之第三雙共振激發模態 31, 101 32, 102 41， 103 42, 104 81 本發明天線較低操作頻帶之增益曲線 本發明A線較低操作頻帶之輕射效率 本發明天線較高操作頻帶之增益曲線、， 本發明天線較高操作頻帶之輻射效率曲線 介質塊 咏 82, 83彎折線 1422,92 second dual resonance excitation mode of the antenna of the invention 23, 93 third dual resonance excitation mode of the antenna of the invention 31, 101 32, 102 41, 103 42, 104 81 gain of the lower operating band of the antenna of the invention Curve The light-emitting efficiency of the lower operating band of the A-line of the present invention. The gain curve of the higher operating band of the antenna of the present invention, the radiation efficiency curve of the higher operating band of the antenna of the present invention, the dielectric block 咏82, 83 bending line 14