200952259 九、發明說明： .【發明所屬之技術領域】 本發明係有關於一種天線，特別是有關於一種適用於 行動通訊裝置之多頻環圈天線。 【先前技術】 由於廣域無線網路（WWAN，Wireless Wide Area Network)技 術、無線區域網路（WLAN，Wireless Local Area Network)技術與 © 全球互通微波存取（WiMAX, Worldwide Interoperability for Micro-wave Access)技術的蓬勃發展，未來單一行動通訊裝置同時 具備通訊與上網之功能已成為必然的趨勢。而若要達到此 一目的，如何能在單一行動通訊裝置内完成涵蓋多頻帶操 作之天線設計就成為相當關鍵的技術問題。 若選擇在單一行動通訊裝置内配置多天線系統，會遭 遇到多天線擺放空間的浪費、電磁干擾等問題需要解決。 ❿因此設計出可涵蓋多系統操作頻帶之單一天線為較佳之問 題解決方案。先前相關美國專利第6,727,854號“平面倒F 形天線（planar inverted-F antenna)，，，其揭示一種可雙頻操作之 天線設計，該天線僅能涵蓋歐規GSM9〇〇/18〇〇*統操作，且 該天線結構較為複雜。台灣發明專利第519,779號，，雙頻平 面式單偶極天線之輻射金屬片"，其揭示一種可三頻操作 之天線設計，該天線雖能涵蓋GSM9〇〇/18〇〇/19〇〇系統，但其 在實際運用上爻到操作頻帶的限制較大。為解決這些問題 ，我們提出一種適用於行動通訊裝置之創新内藏式多頻環 5 200952259 •圈天線設計，本發明天線除了結構簡單以及製作成本低外 •，更可以輕易達成多系統頻帶操作的需求，最多可同時涵 盍 WWAN 五頻帶（GSM850/900/1800/1900 與 UMTS)、WLAN 2.4 GHz 頻帶（2.4〜2.484 GHz)以及 WiMAX 2.5 GHz 頻帶（2.5〜2.69 GHz)等共7系統頻帶操作之頻寬需求。 【發明内容】 本發明之目的在於提供一種適用於行動通訊裝置之創 ❹新内藏式多頻環圈天線設計，其除了具備天線結構簡單、 製作成本低以及可縮小化的優點外，同時其更可以輕易達 成多系統頻帶操作，因此相當符合業界實際應用需求。 本發明天線之-實施例，包含：一介質基板、一輕射 金屬線以及-饋入金屬部。該介質基板具有一接地面區間 以及-介質面區間’該接地面區間具有一接地面，在該接 地面之一邊緣附近並具有一第一接地點與—第二接地點。 ❹該輻射金屬線位於該介質面區間，其兩端點分別電氣連 7該第-接地點與該第二接地點，使該輕射金屬線與該接 地面之-邊緣形成-封閉迴路。該饋入金屬部 面區間，包含：一i車垃砼甘 ^ 貝 ^. 接線，其一编大致位於該接地面一邊 緣處’且為該天線之訊號饋入點；一麵合部，電氣 =接線，同時該耗合部與該輕射金屬線之一區間形成二 耦&部分；以及一微調部，位於該接地面之一 合部之間’該微調部並電氣連接至該連接線。i —輕 本發明天線主要是藉由該饋入金屬部來麵合激發該輕 6 200952259 . 射金屬線，並且適當調整該耦合部與該輻射金屬線之—區 間形成之耦合部分，可使得該輻射金屬線之較低與較高= 振模態均形成雙共振激發狀態，並由該微調部來微調=振 模態之阻抗匹配，如此可大幅增加共振模態之操作頻寬。 實驗結果顯示，本發明天線之一實施例能完全涵蓋 WWAN 五系統頻帶（GSM850/900/1800/1900 與 UMTS)操作，且 本發明天線之增益與輻射效率也均能符合行動通訊之實際 應用需求。 $ ❹ 配合下列圖式、實施例之詳細說明及申請專利範圍， 將上述本發明之其他目的與優點詳述於後。 【實施方式】 第1圖為本發明天線之一實施例丨結構圖，包含：一 =質基板11、一輻射金屬線13以及一饋入金屬部14。該介 質基板11，具有一接地面區間U1以及一介質面區間112 ❹，該接地面區間m具有一接地面12，在該接地面12之一 邊緣121附近並具有一第一接地點122與一第二接地點 123。該輻射金屬線13，位於該介質面區間112 ，其為一 平面結構，並以印刷或蝕刻之方式形成於該介質面區間之 表面上113 ，其兩端點分別電氣連接於該第一接地點122 與該第二接地點123 ’使該輻射金屬線13與該接地面以之 一邊緣121形成一封閉迴路。該饋入金屬部14，位於該介 質面區間112 ’包含：-連接線15、一耗合部㈣及一微 調部Π。該連接線15，其—端大致位於該接地面一邊緣處 7 200952259 ，，且為該天線之訊號饋入點151。該耦合部16，其電氣連 • f於及連接線15，同時該耦合部16與該輻射金屬線13之一 區間131形成一耦合部分18。該微調部17，由一金屬線所 組成，位於該接地面12之一邊緣121與該耦合部16之間， 該微調部17並電氣連接至該連接線15。 _本發明天線主要是藉由該饋入金屬部14來搞合激發該 輻射金屬線13，並且藉由適當調整該耦合部16與該輻射金 屬線13之一區間131形成之耦合部分以，可使得該輻射金 屬線13之較低與較高共振模態均形成雙共振激發狀態，並 由該微調部Π來微調共振模態之阻抗匹配，如此可大幅婵 加共振模態之操作頻寬。 θ 第2圖為本發明天線一實施例！之返回損失扣触 ㈣實驗量測圖，本實施例選擇下列尺寸進行實驗量測： 該介質基板11長度為112mm、寬度為6〇mm、厚度為〇8 mm ;該接地面區間m與接地面12均長度為、寬 ❹度為60mm ;該介質面區間112長度為nmm、寬度為' 60mm ;該輻射金屬線13總長度約為235mm，其為一平面 結構，以印刷或钱刻之方式形成於該介質面區間之表面上 113 ;該饋入金屬部14之連接線15長度為9聰、寬产為 Umm ; _合部16長度為135刪、寬度為〇5聰「該微 調部η由-金屬線所組成，長度為2〇5麵、寬度為2醜。 如第2圖所示，實施例！能成功於較低頻帶共振出 ===態21，於較高頻帶共振出-第二雙共振激發 核H、-第二雙共振激發模態23。並且由所得的測試結 200952259 果，縱軸表示返回損失，橫轴表示操作頻率，在6册返回 損失的定義下，該第一雙共振激發模態21能完全涵笔行動 通訊系統GSM850/900(824-894 /890-960 MHz)之頻寬需求，而該 第二與第三雙共振激發模態22、23所合成之寬頻模態能完200952259 IX. INSTRUCTIONS: 1. FIELD OF THE INVENTION The present invention relates to an antenna, and more particularly to a multi-frequency loop antenna suitable for use in a mobile communication device. [Prior Art] Due to Wide Area Wireless Network (WWAN) technology, Wireless Local Area Network (WLAN) technology and © Worldwide Interoperability for Microwave Access (WiMAX) The rapid development of technology, the future of a single mobile communication device with the function of communication and Internet has become an inevitable trend. To achieve this goal, how to complete the antenna design covering multi-band operation in a single mobile communication device becomes a very critical technical problem. If you choose to configure a multi-antenna system in a single mobile communication device, you will encounter problems such as waste of multiple antenna placement space and electromagnetic interference. Therefore, designing a single antenna that can cover multiple operating bands of the system is a better solution. Prior to the "planar inverted-F antenna" of the U.S. Patent No. 6,727,854, which discloses a dual-frequency antenna design that can only cover the European standard GSM9〇〇/18〇〇* Operation, and the structure of the antenna is relatively complicated. Taiwan Invention Patent No. 519,779, a radiating metal sheet of a dual-frequency planar single dipole antenna, which discloses a three-frequency operation antenna design, which can cover GSM9〇 〇/18〇〇/19〇〇 system, but its practical application to the operating band is very limited. To solve these problems, we propose an innovative built-in multi-frequency ring for mobile communication devices 5 200952259 • The loop antenna design, in addition to the simple structure and low production cost of the antenna of the present invention, can easily achieve the requirements of multi-system band operation, and can cover up to the WWAN five-band (GSM850/900/1800/1900 and UMTS) and WLAN 2.4 at the same time. The bandwidth requirement of a total of seven system band operations, such as the GHz band (2.4 to 2.484 GHz) and the WiMAX 2.5 GHz band (2.5 to 2.69 GHz). SUMMARY OF THE INVENTION The object of the present invention is to provide A new built-in multi-frequency loop antenna design suitable for mobile communication devices, in addition to the advantages of simple antenna structure, low production cost and downsizing, it can easily achieve multi-system band operation. Therefore, the antenna of the present invention includes: a dielectric substrate, a light-emitting metal wire, and a feed metal portion. The dielectric substrate has a ground plane interval and a dielectric surface interval. The ground section has a grounding surface, and has a first grounding point and a second grounding point near one edge of the grounding surface. The radiation metal line is located in the medium surface section, and the two ends of the grounding point are respectively electrically connected. a grounding point and the second grounding point, such that the light-emitting metal line forms a closed loop with the edge of the grounding surface. The feeding metal surface area includes: a vehicle, a cable, and a wiring. The first part of the grounding surface is located at an edge of the grounding surface and is a signal feeding point of the antenna; one side of the joint, electrical=wiring, and the portion of the consumable portion and the light-radiating metal line is formed. a coupling portion; and a trimming portion located between the junction portions of the ground plane' the trimming portion and electrically connected to the connecting line. i - lightly, the antenna of the present invention is mainly covered by the feeding metal portion Exciting the light wire, and appropriately adjusting the coupling portion formed by the coupling portion and the radiation metal line, the lower and upper = vibration modes of the radiation metal wire form a double resonance excitation. State, and fine-tuned by the trimming section = impedance matching of the mode of the vibration mode, which can greatly increase the operating bandwidth of the resonant mode. Experimental results show that one embodiment of the antenna of the present invention can completely cover the WWAN five-system band (GSM850/ The 900/1800/1900 and UMTS) operate, and the gain and radiation efficiency of the antenna of the present invention are also compatible with the practical application requirements of the mobile communication. Other objects and advantages of the present invention will be described in detail below with reference to the following drawings, detailed description of the embodiments, and claims. [Embodiment] FIG. 1 is a structural view of an embodiment of an antenna according to the present invention, comprising: a substrate 11, a radiation metal wire 13, and a feed metal portion 14. The dielectric substrate 11 has a ground plane section U1 and a dielectric surface section 112 ❹ having a ground plane 12 adjacent to an edge 121 of the ground plane 12 and having a first ground point 122 and a Second grounding point 123. The radiant metal line 13 is located in the dielectric surface section 112 and is a planar structure formed on the surface 113 of the medium surface section by printing or etching. The two ends are electrically connected to the first grounding point respectively. 122 and the second grounding point 123' cause the radiant metal line 13 and the ground plane to form a closed loop with one of the edges 121. The feed metal portion 14 is located in the media surface section 112 ′ including: a connecting line 15, a consuming portion (four), and a fine adjustment portion Π. The connecting line 15 has a terminal end substantially at an edge of the grounding surface 7 200952259 , and is a signal feeding point 151 of the antenna. The coupling portion 16 is electrically connected to the connecting line 15, and the coupling portion 16 forms a coupling portion 18 with a section 131 of the radiating metal line 13. The fine adjustment portion 17 is composed of a metal wire between the edge 121 of the ground plane 12 and the coupling portion 16, and the fine adjustment portion 17 is electrically connected to the connection line 15. The antenna of the present invention mainly engages and excites the radiating metal line 13 by the feeding metal portion 14, and the coupling portion formed by the coupling portion 16 and the interval 131 of the radiating metal line 13 is appropriately adjusted. The lower and higher resonance modes of the radiation metal line 13 form a double resonance excitation state, and the fine adjustment portion Π is used to finely adjust the impedance matching of the resonance mode, so that the operation bandwidth of the resonance mode can be greatly increased. θ Fig. 2 is an embodiment of the antenna of the present invention! The return loss buckle (four) experimental measurement chart, the present embodiment selects the following dimensions for experimental measurement: the dielectric substrate 11 has a length of 112 mm, a width of 6 〇 mm, and a thickness of 〇 8 mm; the ground plane interval m and the ground plane 12 is the length of the length, the width is 60mm; the length of the dielectric surface 112 is nmm, the width is '60mm; the total length of the radiation metal wire 13 is about 235mm, which is a plane structure, formed by printing or money carving On the surface of the medium surface section 113; the length of the connecting line 15 of the feeding metal portion 14 is 9 Cong, and the width is Umm; the length of the _ joint portion 16 is 135, and the width is 〇5 Cong "The fine adjustment part η is - composed of metal wires, having a length of 2〇5 faces and a width of 2 ugly. As shown in Fig. 2, the embodiment can successfully resonate in the lower frequency band === state 21, and resonate in the higher frequency band - the first The two double resonances excite the core H, the second double resonance excitation mode 23. And from the resulting test junction 200952259, the vertical axis represents the return loss and the horizontal axis represents the operating frequency, which is defined by the six volumes of return loss. The dual resonance excitation mode 21 can fully cover the mobile communication system GSM850/900 (824-894 /890- 960 MHz) bandwidth requirement, and the wideband modes synthesized by the second and third dual resonant excitation modes 22, 23 can be completed
全涵蓋 GSM1800/1900 (1710-1880/1850-1990 MHz)與 UMTS (1920-2170 MHz)行動通訊系統之頻寬需求。本發明天線具 備了結構簡單、製作成本低並且可多頻操作的優點，因而 相當適合内藏應用於各種行動通訊裝置中。 ® 第3圖為實施例1之較低操作頻帶天線增益圖與輻射 效率圖。左邊縱軸表示天線增益，右邊縱軸表示天線輻射 效率，橫轴表示操作頻率；由所得之結果，在GSM850/900 頻帶内，天線增益曲線31分佈於1.5〜2.0dBi之間，天線輻 射效率曲線32分佈於80%〜90%之間，能滿足行動通訊系統 實際操作之增益與效率需求。 第4圖為實施例1之較高操作頻帶天線增益圖與輻射 ❽效率圖。在GSM1800/1900與UMTS頻帶内，天線增益曲線 41分佈於0.5〜3.0 dBi之間，天線輻射效率曲線42分佈於 65%〜90%之間，能滿足行動通訊系統實際操作之增益與效 率需求。 第5圖為本發明天線第一其他實施例5結構圖。實施 例5雖然其饋入金屬部54之形狀與實施例1有所差異，但 其也能有效的耦合激發該輻射金屬線13。只要適當調整該 耦合部56與該輻射金屬線13之一區間131形成之耦合部分 58，同樣能使得該輻射金屬線13之較低與較高共振模態均 9 200952259 升> 成雙共振激發狀態’而大幅增加共振模態之阻抗頻寬， 並且同樣此由該微調部5 7來微調共振模態之阻抗匹配。因 此實施例5也能達成同時涵蓋多頻行動通訊系統頻寬之應 用需求。 ’ 第6圖為本發明天線第二其他實施例6結構圖。實施 例6雖然其饋入金屬部64之微調部67改由兩金屬線組成， 而與實施例1有所差異，但其同樣也能有效的由該微調部 ❹67來微調共振模態之阻抗匹配。因此實施例6也能達成同 時涵蓋多頻行動通訊系統頻寬之應用需求。 第7圖為本發明天線第三其他實施例7結構圖。實施 例7雖然其輻射金屬線13與饋入金屬部14位於同一平面上 而與實施例1有所差異，但其同樣也能藉由適當調整該耦 合部16與該輻射金屬線13之一區間131形成之耦合部分” ，可使得該輻射金屬線13之較低與較高共振模態均形成雙 共振激發狀態。因此實施例7也能達成同時涵蓋多頻行動 ©通訊系統頻寬之應用需求。 第8圖為本發明天線之第四其他實施例8結構圖。實 施例8之該輻射金屬線13為一立體結構，其以印刷或蝕刻 之方式形成於一介質塊81之表面上，成為一可表面黏著之 元件，並具有大致平行之二彎折線82、83。如此可以大幅 減少天線整體所佔用之總體積，而達到縮小化的目的，並 且減少天線組裝成本。實施例8亦可同時完全涵蓋w猶 五頻帶（GSM850/900/18_900 與 umts)、饥倾 2 4 GHz 頻帶 以及MMAX2.5 GHz頻帶等共7⑽頻帶操作之頻寬需求。 200952259 第9圖為本發明天線第四其他實施例8之返回損失實 驗量測結果。參考第8圖，實施例8選擇下列尺寸進行實 驗量測：該介質基板11長度為105 mm、寬度為60 mm、厚 度為0.8 mm ;該接地面區間111與接地面12均長度為95 mm、寬度為60 mm ;該介質面區間112長度為10 mm、 寬度為60 mm ;該輕射金屬線13總長度約為245 mm，其為 一立體結構，以印刷或蝕刻之方式形成於一介質塊81之表 面上；該介質塊81長度為60 mm、寬度為10 mm，其垂直 ®該接地面12方向之高度為3 mm(該彎折線82至該彎折線83 之距離）；該饋入金屬部14之該連接線15長度為9mm、寬 度為1.5 mm ;該耦合部16長度為13.5 mm、寬度為0.5 mm ; 該微調部17由一金屬線所組成，長度為20mm、寬度為2 mm。如第9圖所示，實施例8能成功於較低頻帶共振出 一第一雙共振激發模態91，於較高頻帶共振出一第二與一 第三雙共振激發模態92、93。並且由所得的測試結果，該 _第一雙共振激發模態91能涵蓋行動通訊系統GSM850/900之 頻寬需求，而該第二與第三雙共振激發模態92、93所合成 之寬頻模態能涵蓋行動通訊系統GSM1800/1900與UMTS之 頻寬需求。此外實施例8還能涵蓋WLAN 2.4 GHz頻帶以及 WiMAX2.5GHz頻帶，而達成共7系統頻帶操作之頻寬需求 。本發明天線具備了結構簡單、製作成本低並且可多頻操 作的優點，因而適合内藏應用於各種行動通訊裝置中。 第10圖為實施例8之較低操作頻帶天線增益與輻射效 率圖。左邊縱轴表示天線增益，右邊縱轴表示天線輻射效 11 200952259 率，秩轴表示操作頻率；由所得之結果，在GSM85〇/9⑻頻 - 〒内，天線增益曲線101分佈於〇.5〜L5 dBi之間，天線輻 射效率曲線1〇2分佈於7〇%〜之間，能滿足行動通訊系 統實際操作之增益與效率需求。 第11圖為實施例8之較高操作頻帶天線增益與輻射效 率圖。由所得之結果，在GSM1800/1900與UMTS頻帶内， 天線增盃曲線103分佈於0.5〜3.5dBi之間，輻射效率曲線 ❹104刀佈於5〇%〜85%之間；在肌顺24〇也與斯以^25 GHZ頻帶内’天線增益曲線103分佈於2.5〜3.5 dBi之間， 天線輻射效率曲線1〇4分佈於7〇%〜9〇%之間，均能滿足行 動通1系統與無線上網系統實際操作之增益與效率需求。 练合上述的說明，本發明天線具有結構簡單、製作成 本低可夕頻帶操作以及縮小化的優點，功能明確，因此 本發明天線具高度產業應用價值，足以符合發明之範疇。 在上述說明中所敘述之實施例僅為說明本發明裝置之 ❿原理及其功效，而非限制本發明。因此，習於此技術之人 士可在不違背本發明之精神對上述實施例進行修改及變化 。本發明之權利範圍應如後述之申請專利範圍所列。 【圖式簡單說明】 第1圖為本發明天線一實施例結構圖。 第2圖為本發明天線一實施例之返回損失實驗測量圖。 第3圖為本發明天線一實施例之較低操作頻帶天線增益與 輻射效率圖。 θ皿/' 12 200952259 Ο 第4圖為本發明天線一 輻射效率圖。 第5圖為本發明天線第 第6圖為本發明天線第 第7圖為本發明天線第 第8圖為本發明天線第 第9圖為本發明天線第 圖。 第10圖為本發明天線第 增益與輻射效率 第11圖為本發明天線第 增益與輻射效率 實施例之較高操作頻帶天線增益與 一其他實施例結構圖。 二其他實施例結構圖。 三其他實施例結構圖。 四其他實施例結構圖。 四其他實施例之返回損失實驗測量 四其他實施例之較低操作頻帶天線 圖。 四其他實施例之較高操作頻帶天線 圖。 【主要元件符號說明】 I 本發明天線一實施例 5 本發明天線第一其他實施例 6 本發明天線第二其他實施例 7 本發明天線第三其他實施例 8 本發明天線第四其他實施例 II 介質基板或一行動通訊裝置之系統電路板 III 接地面區間 112 介質面區間 113 介質面區間之一表面 !2 接地面 13 200952259 121 接地面之一邊緣 122 第一接地點 123 第二接地點 13 輻射金屬線 131輻射金屬線之輕合區間 14，54，64饋入金屬部 15, 55, 65 連接線 151 訊號饋入點 ❹Covers the bandwidth requirements of GSM1800/1900 (1710-1880/1850-1990 MHz) and UMTS (1920-2170 MHz) mobile communication systems. The antenna of the present invention has the advantages of simple structure, low manufacturing cost, and multi-frequency operation, and is therefore quite suitable for use in various mobile communication devices. ® Figure 3 is a graph of the lower operating band antenna gain and radiation efficiency for Example 1. The vertical axis on the left represents the antenna gain, the vertical axis on the right represents the radiation efficiency of the antenna, and the horizontal axis represents the operating frequency. As a result, in the GSM850/900 band, the antenna gain curve 31 is distributed between 1.5 and 2.0 dBi, and the antenna radiation efficiency curve 32 is distributed between 80% and 90%, which can meet the gain and efficiency requirements of the actual operation of the mobile communication system. Figure 4 is a diagram showing the higher operating band antenna gain map and the radiation ❽ efficiency map of the first embodiment. In the GSM1800/1900 and UMTS bands, the antenna gain curve 41 is distributed between 0.5 and 3.0 dBi, and the antenna radiation efficiency curve 42 is distributed between 65% and 90%, which satisfies the gain and efficiency requirements of the actual operation of the mobile communication system. Fig. 5 is a structural view showing the first other embodiment 5 of the antenna of the present invention. Although the shape of the feed metal portion 54 of the embodiment 5 is different from that of the first embodiment, it can also be effectively coupled to excite the radiation metal wire 13. As long as the coupling portion 58 formed by the coupling portion 56 and the section 131 of the radiation metal wire 13 is appropriately adjusted, the lower and higher resonance modes of the radiation metal wire 13 can be made 9 200952259 liters> double resonance excitation The state 'is greatly increased the impedance bandwidth of the resonant mode, and the impedance matching of the resonant mode is also finely adjusted by the fine adjustment portion 57. Therefore, Embodiment 5 can also meet the application requirements that cover the bandwidth of the multi-frequency mobile communication system. Fig. 6 is a structural view showing a second embodiment 6 of the antenna of the present invention. In the sixth embodiment, although the trimming portion 67 of the feeding metal portion 64 is composed of two metal wires, which is different from the first embodiment, it is also effective to finely adjust the impedance matching of the resonant mode by the fine adjustment portion ❹67. . Therefore, Embodiment 6 can also achieve the application requirements covering the bandwidth of the multi-frequency mobile communication system at the same time. Figure 7 is a structural view showing a third embodiment 7 of the antenna of the present invention. Embodiment 7 is different from Embodiment 1 in that the radiation metal wire 13 and the feeding metal portion 14 are on the same plane, but the interval between the coupling portion 16 and the radiation metal wire 13 can also be appropriately adjusted. The coupling portion formed by 131" can make the lower and higher resonance modes of the radiation metal line 13 form a dual resonance excitation state. Therefore, Embodiment 7 can also achieve the application requirement of covering the bandwidth of the multi-frequency mobile communication system. Figure 8 is a structural view of a fourth embodiment 8 of the antenna of the present invention. The radiant metal line 13 of the embodiment 8 is a three-dimensional structure formed on the surface of a dielectric block 81 by printing or etching. a surface-adhesive component having substantially parallel bend lines 82, 83. This can greatly reduce the total volume occupied by the antenna as a whole, thereby achieving the purpose of downsizing and reducing the antenna assembly cost. Embodiment 8 can also simultaneously Full coverage of the bandwidth requirements for a total of 7 (10) band operations, such as the GSM850/900/18_900 and umts, the hunger 2 4 GHz band, and the MMAX 2.5 GHz band. 200952259 Figure 9 The return loss experimental measurement result of the antenna of the fourth other embodiment 8. Referring to Fig. 8, the following dimensions were selected for the experimental measurement: the dielectric substrate 11 has a length of 105 mm, a width of 60 mm, and a thickness of 0.8 mm; The ground plane section 111 and the ground plane 12 have a length of 95 mm and a width of 60 mm; the medium section 112 has a length of 10 mm and a width of 60 mm; and the light-emitting metal line 13 has a total length of about 245 mm, which is a three-dimensional structure formed on the surface of a dielectric block 81 by printing or etching; the dielectric block 81 has a length of 60 mm and a width of 10 mm, and the vertical direction of the ground plane 12 is 3 mm (the bend) The length of the connecting line 15 of the feeding metal portion 14 is 9 mm and the width is 1.5 mm; the length of the coupling portion 16 is 13.5 mm and the width is 0.5 mm; A metal wire consisting of a length of 20 mm and a width of 2 mm. As shown in Fig. 9, the embodiment 8 can successfully resonate a first dual resonance excitation mode 91 in the lower frequency band and resonate in the higher frequency band. The second and a third dual resonant excitation modes 92, 93. and the resulting measurements As a result, the first dual resonant excitation mode 91 can cover the bandwidth requirement of the mobile communication system GSM850/900, and the wideband modes synthesized by the second and third dual resonant excitation modes 92, 93 can cover the mobile communication. The bandwidth requirements of the system GSM1800/1900 and UMTS. In addition, Embodiment 8 can cover the WLAN 2.4 GHz band and the WiMAX 2.5 GHz band, and achieve the bandwidth requirement of a total of 7 system band operations. The antenna of the present invention has a simple structure and a manufacturing cost. The advantages of low and multi-frequency operation make it suitable for use in a variety of mobile communication devices. Figure 10 is a graph showing the gain and radiation efficiency of the lower operating band antenna of the eighth embodiment. The vertical axis on the left represents the antenna gain, the vertical axis on the right represents the radiation efficiency of the antenna, and the rank axis represents the operating frequency. As a result, in the GSM85〇/9(8) frequency-〒, the antenna gain curve 101 is distributed in 〇.5~L5. Between dBi, the antenna radiation efficiency curve 1〇2 is distributed between 7〇%~, which can meet the gain and efficiency requirements of the actual operation of the mobile communication system. Figure 11 is a graph showing the gain and radiation efficiency of the higher operating band antenna of the eighth embodiment. As a result, in the GSM1800/1900 and UMTS bands, the antenna cupping curve 103 is distributed between 0.5 and 3.5 dBi, and the radiation efficiency curve ❹104 is between 5% and 85%; The antenna gain curve 103 is distributed between 2.5 and 3.5 dBi in the ^25 GHZ band, and the antenna radiation efficiency curve 1〇4 is distributed between 7〇% and 9〇%, which can satisfy the mobile communication system and wireless. The gain and efficiency requirements of the actual operation of the Internet system. According to the above description, the antenna of the present invention has the advantages of simple structure, low cost operation and reduction in manufacturing cost, and clear function. Therefore, the antenna of the present invention has high industrial application value and is sufficient to meet the scope of the invention. The embodiments described in the above description are merely illustrative of the principle and function of the device of the present invention and are not intended to limit the invention. Therefore, those skilled in the art can modify and change the above embodiments without departing from the spirit of the invention. The scope of the invention should be as set forth in the appended claims. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a structural view showing an embodiment of an antenna according to the present invention. Fig. 2 is a graph showing the experimental measurement of the return loss of an embodiment of the antenna of the present invention. Figure 3 is a graph showing the gain and radiation efficiency of the lower operating band antenna of an embodiment of the antenna of the present invention. θ 皿 / ' 12 200952259 Ο Figure 4 is a radiation efficiency diagram of the antenna of the present invention. Fig. 5 is an antenna of the present invention. Fig. 6 is an antenna of the present invention. Fig. 7 is an antenna of the present invention. Fig. 8 is an antenna of the present invention. Figure 10 is a diagram showing the gain and radiation efficiency of the antenna of the present invention. Figure 11 is a block diagram showing a higher operating band antenna gain and an embodiment of the antenna gain and radiation efficiency embodiment of the present invention. 2. Structure diagram of other embodiments. Three other structural diagrams of the embodiment. A structural diagram of four other embodiments. Four Return Loss Experimental Measurements of Other Embodiments Four lower operating band antenna diagrams of other embodiments. A higher operating band antenna pattern of four other embodiments. [Explanation of main components] I. Embodiment 5 of the antenna of the present invention. First embodiment of the antenna of the present invention. Second embodiment of the antenna of the present invention. Embodiment 7 of the antenna of the present invention. Third Embodiment 8 of the antenna of the present invention. Medium substrate or system board of a mobile communication device III Ground plane section 112 Media surface section 113 Surface of one of the dielectric surface sections! 2 Ground plane 13 200952259 121 One edge of the ground plane 122 First ground point 123 Second ground point 13 Radiation The light-emitting section 14, 54, 64 of the metal wire 131 radiating the metal wire is fed into the metal portion 15, 55, 65, the connecting line 151, the signal feeding point ❹
16,56,66耦合部或一耦合金屬線 17, 57, 67微調部或一微調金屬線 18, 58, 68, 71耦合部與輻射金屬線之一區間形成之耦 合部分 21，91本發明天線之第一雙共振激發模態 22, 92本發明天線之第二雙共振激發模態 23, 93本發明天線之第三雙共振激發模態 31，101本發明天線較低操作頻帶之增益曲線 32,102本發明天線較低操作頻帶之輻射效率曲線 41，103本發明天線較高操作頻帶之增益曲線 42, 104本發明天線較高操作頻帶之輻射效率曲 81 介質塊 ^ 82, 83彎折線16,56,66 coupling portion or a coupling metal wire 17, 57, 67 fine adjustment portion or a fine adjustment metal wire 18, 58, 68, 71 coupling portion and a portion of the radiation metal line forming a coupling portion 21, 91 antenna of the present invention The first dual resonant excitation mode 22, 92 the second dual resonant excitation mode of the antenna of the present invention 23, 93 the third dual resonant excitation mode of the antenna of the present invention 31, 101 the gain curve of the lower operating band of the antenna of the present invention 32,102 Radiation efficiency curve 41, 103 of the lower operating band of the antenna of the present invention, gain curve 42 of the higher operating band of the antenna of the present invention, 104 radiation efficiency of the higher operating band of the antenna of the present invention 81 dielectric block ^ 82, 83 bending line