TWI339506B - Phase lock loop circuit and corresponding frequency conversion method - Google Patents
Phase lock loop circuit and corresponding frequency conversion method Download PDFInfo
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1339506 丨059年12月dU日修正替換頁 六、發明說明: 【發明所屬之技術領域】 [0001]本發明涉及一種鎖相環電路(Phase_L〇cked L的P, PLL)及其相應之頻率轉化方法,尤其涉及_種可精確地 轉換鎖相環電路頻率之方法。 [先前技術] [_2]數位電視(Dlgital Television)是為了於家庭裏能夠 感受到劇場強烈氛圍而開發之一種電視系統。與現於廣 泛應用之類比電視比較,其大大提高了畫面之清晰度、 幅寬,而且和:供〇)(〇)〇1!103<:1;1)丨5(:)水準之多聲道伴音 。對於數位電視,美國、歐辨及曰本等;國家都正於分別 制定符合自身之廣播制式及,美國採用殘留 邊帶(Vestigial Sideband,VSB)制式1具體可參見 Wayne等人於文獻iEEE Transactions on c〇nsumei·1339506 12 丨 丨 d d d d d d 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六 六The method, in particular, relates to a method for accurately converting the frequency of a phase locked loop circuit. [Prior Art] [_2]Dlgital Television is a television system developed for the family to feel the strong atmosphere of the theater. Compared with the widely used analog TV, it greatly improves the clarity and width of the picture, and it is: 〇)(〇)〇1!103<:1;1)丨5(:) Road sound. For digital TV, the United States, Europe, and transcripts; the state is in the process of formulating its own broadcasting system, and the United States adopts the Vestigial Sideband (VSB) system. For details, see Wayne et al. C〇nsumei·
Electronics,Vol. 41,No. 3 中於 1 995 年 8 月發表 之VSB Modem Subsystem Design for Grand Alliance Digital Television Receivers— 文。 [0003] 前述數位電視之接收機内通常設置有鎖相環電路。常用 之鎖相環電路請參閱圖1,其包括一鑒相器11,一與黎相 器11之輸出端相連接之濾波器1 2,一與濾波器1 2之輸出 端相連接之壓控振盪器13,一與壓控振盪器13 —輸出端 相連接Μ倍數分頻器14,以及一連接該鑒相器11之一輸入 端與該壓控振盪器13之另一輸出端之Ν倍數分頻器15。其 中,Μ與Ν均為整數。 [0004] 該鑒相器11之另一個輸入端輸入一參考頻率f ,該Μ倍 ref 096147845 表單編號A0101 第4頁/共18頁 0993469765-0 1339506 • » 099年12月30日梭正替換頁 數分頻器14之輸出端輸出一通路頻率。利用該通 路頻率f channel可计异出壓控振盪器13之輸出端所需要之 輸出頻率、。’即“且該壓控振盡器以, N倍數分頻器15與鑒相器11所組成之反饋回路使該壓控 振盪器之輸出頻率f vcoVSB Modem Subsystem Design for Grand Alliance Digital Television Receivers, published in Electronics, Vol. 41, No. 3, August 995. [0003] A phase locked loop circuit is generally provided in the receiver of the aforementioned digital television. Referring to FIG. 1 , a commonly used phase-locked loop circuit includes a phase detector 11 , a filter 12 connected to the output end of the phase detector 11 , and a voltage control connected to the output end of the filter 12 . The oscillator 13 is connected to the output of the voltage controlled oscillator 13 and the multiple frequency divider 14 , and a multiple of the input terminal connected to the phase detector 11 and the other output terminal of the voltage controlled oscillator 13 Frequency divider 15. Among them, Μ and Ν are both integers. [0004] The other input end of the phase detector 11 inputs a reference frequency f, which is ref ref 096147845 Form No. A0101 Page 4 / Total 18 Page 0993469765-0 1339506 • » December 30, 2010 The output of the digital divider 14 outputs a channel frequency. The output frequency of the output terminal of the voltage controlled oscillator 13 can be calculated by using the path frequency f channel. That is, and the voltage controlled oscillator has a feedback loop composed of the N-multiplier 15 and the phase detector 11 to make the output frequency of the voltage-controlled oscillator f vco
VCO :Nf 等於Ν倍之參考頻率f ref ,即 ref ο [0005] &於壓控振盪器η之輪出頻率丨卩能是參考頻率f vco ref 之正數倍數,因此當需要之壓控振盥器13之輸出頻率 • fVC〇並不是參考頻率~“之整數倍數時,則無法利用該鎖 相環電路而產生所需要之壓控振盪器丨3之輸出頻率f vco ,其極大地限制了該鎖相環電路之通路頻率f 。 channel [0006] 有鑒於此,提供一種輸出之通路頻率不受限制之鎖相環 電路及其相對應之頻率轉換之方法實為必要。 【發明内容】 [0007]VCO: Nf is equal to Ν times the reference frequency f ref , that is, ref ο [0005] & the voltage of the voltage controlled oscillator η is not a positive multiple of the reference frequency f vco ref, so when the pressure is controlled The output frequency of the buffer 13 • fVC〇 is not the reference frequency ~ “integer multiple, the phase-locked loop circuit cannot be used to generate the required output frequency f vco of the voltage-controlled oscillator 丨3, which greatly limits the output frequency f vco The path frequency of the phase-locked loop circuit f. channel [0006] In view of this, it is necessary to provide a phase-locked loop circuit whose output path frequency is not limited and a corresponding frequency conversion method thereof. 0007]
[0008] 下面將以實施例說明一種鎖相環電路及其相應之頻率轉 換方法’其通路頻率不受任何限制。 一種鎖相環電路,其包括一鑒相器,一與該鑒相器之輸 出端相連接之濾波器,一與該濾波器之輸出端相連接之 壓控振盈器,以及-與該壓控振盈器之—個輸出端相連 接之Μ倍數分頻器以接收該壓控振盪器輸出端所輸出之一 輸出頻率,該鑒相器之一個輸入端輸入一參考頻率,該Μ 倍數分頻器之輸出端輸出一需要之通路頻率,其中,該 鎖相環電路進一步包括一Ν/Ν + 1倍數分頻器及一個Ν/Ν+ι 倍數分頻控制器,該Ν/Ν + 1倍數分頻器設置於該鑒相器與 096147845 壓控振盪器之間,其一輸入端連接至該壓控振盪器 表單編號Α0101 第5頁/共18頁 ,其 0993469765-0 1339506 [0009] [0010] [0011] [0012] [0013] [0014] [0015][0008] Hereinafter, a phase-locked loop circuit and its corresponding frequency conversion method will be described by way of an embodiment, and its path frequency is not limited at all. A phase locked loop circuit comprising a phase detector, a filter connected to an output end of the phase detector, a voltage controlled oscillator connected to an output end of the filter, and - and the voltage The output frequency of the control oscillator is connected to a multiple frequency divider to receive an output frequency outputted by the output of the voltage controlled oscillator, and one input end of the phase detector inputs a reference frequency, the multiple of the reference frequency The output end of the frequency converter outputs a desired channel frequency, wherein the phase-locked loop circuit further comprises a Ν/Ν + 1 multiple frequency divider and a Ν/Ν+ι multiple frequency divider controller, the Ν/Ν + 1 The multiplier is placed between the phase detector and the 096147845 voltage controlled oscillator, and an input is connected to the voltage controlled oscillator form number Α0101, page 5 of 18, which is 0993469765-0 1339506 [0009] [ [0015] [0015] [0015] [0015]
丨099年υ月30日核正替换頁I 輸出端連接至該鑒相器之另一輸入端,且該N/N + 1倍數分 頻Is之另一輸八端連接至該n/n + 1倍數分頻控制器以接收 該N/N+1倍數分頻控制器所產生之控制訊號;該n/n + i控 制器通過計算得出通路頻率與參考頻率之比值,對該比 值進行處理得到整數資料及小數資料;該整數資料和該 小數資料通過計算得出第一時間段和第二時間段,使該 N/N + 1倍數分頻器於一個工作週期之第一時間段内輸出n 倍數,而於第二時間段内輸出N+1倍數。 一種鎖相環電路之頻率轉換方法,其包括以下步驟: 步驟一:利用通路頻率計算出亨篆控振聿p所需要輸出 之輸出頻率; . 步驟二:利用Μ倍之通路頻拳及頻率知到該M倍之通 路頻率與參考頻率間之比值,對該比值進行處理以得到 一整數資料及一小數資料; 步驟三:對該整數資料進行處理以得到一第一處理訊號p 及一第二處理訊號a ; 步驟四:判斷該第二處理訊號a是否小於一最小值min, 並從而得H輕減及—第二調整訊號 aadjust Ϊ 步驟五:對該小數資料進行離散處理以得到一離散訊號 xin ; 步驟六:將該離散訊號xin加入該第二調整訊號a 中 adjust 得到調整後之第二調整訊號a ; adjust 096147845 表單編號A0101 第6頁/共18頁 0993469765-0 1339506 099年12月30日俊正替換頁 [0016] 步驟七:利用調整後之第二調整訊號a」 及第一調整 adjust 訊號Padjust得到一第一終端訊號Pfinal及一第二終端訊 號〜—丨; [0017] 步驟八:利用該第一終端訊號P ,、第二终端訊號af. 11 na1 f 1 - na 1及最小值m i η計算出該第一時間段Τ1及該第二時間段 Τ2,該Ν/Ν+1倍數分頻器於第一時間段T1内輸出ν倍數, 而於第二時間段T2内輸出N+1倍數。 [0018] 相較於先前技術,本發明之鎖相環電路及其相應之頻率 • 轉換方法’由於利用N/N+1倍數分頻控制器設定N/N+1倍 數分頻器於T1時刻輸出N倍數,而於T2時刻輸出N + 1倍數 ’因此,該壓控振盪器所需要輸出之輸出頻率並不需要 是參考頻率之整數倍數,其極大地擴展了該壓控振盪器 之輸出頻率之範圍,同時也極大地擴展了該鎖相環電路 之通路頻率之範圍。且由於該鎖相環電路於頻率轉化過 程中採用之是數學演算法,節省了電路之面積。 【實施方式】 Φ [0019] 下麵面結合附圖將對本發明實施例作進一步之詳細說明 〇 [0020] 參見圖2,本發明實施例提供之一種鎖相環電路1〇〇。該 096147845 鎖相環電路100包括一蓉相器11〇,一與該赛相器之 輸出端相連接之濾波器,一與該鑒相器110之輸出端相連 接之壓控振盪器130,以及一與該壓控振盪器13〇之一輸 出端相連接之Μ倍數分頻器14〇。該鎖相環電路1〇〇進一步 包括一 Ν/Ν + 1倍數分頻器150及一 Ν/Ν + 1倍數分頻控制器 160,該Ν/Ν + 1倍數分頻器15〇與該鑒相器11〇之一輸入端 表軍編號Α010Ι 第7頁/共18頁 0993469765-0 1339506 [0021] [0022] [0023] [0024] [0025] |〇33年12月30~^给止替换锭|1 · 及該壓控振盪器130之另一輸出端相連接,且該N/N + i倍 數分頻器150與該N/N+1倍數分頻控制器16〇相連接,以 接收該N / N +1倍數分頻控制器1 6 〇所產生離散控制訊號, 控制該N/N+1倍數分頻器150於T1時刻輸出N倍數,而於 T2時刻輸出N+1倍數。該鑒相器之另一輸入端輸入—參考 頻率Fref,該Μ分頻器140之輸出端輸出一通路頻率 F channe1 ° 請參閱圖3,為本發明實施例所提供之鎖相環電路1〇〇之 頻率轉換方法,其包括以下步驟: I 步驟一:利用通路頻率計算出該壓控振盪器所需要輸出 之輸出頻率。 於本步驟中,該壓控振盪器130¾需要之輸出頻率 Fvco為Μ分頻器140之輸出端所需要輸出之通路頻率之 Fchannel 之Μ倍,即F =MF 。 vc〇 channel 步驟二:利用Μ倍之通路頻率Fvc〇(即該壓控振盪器13〇所 需要輸出之輸出頻率)及參考頻率Frd得到Μ倍之通路頻 鲁 率'(:0與參考頻率^以間之比值,對該比值進行處理以得 到一整數資料及一小數資料。 於本步驟中,可採取round function之方式對該Μ倍之 通路頻率Fvco與參考頻率Fref之比值進行處理,以得到整 數資料f.+ 及小數資料f 。冬缺 & — 之運用並不僅限於round function之方式,其也可採用 floor function或者是ceu function之方式對該比 值進行處理。 096147845 表單編號A0101 第8頁/共18頁 0993469765-0 1339506 • · 旦 .. 一 099年12月30日梭正替換頁 [0026]其中,若採取厂如“ functi〇n之方式對比值進行處理, ^正數貧料^integer round(Fvc/Fref);而小數資料 ffractlonal = (Fvc〇/Fref) — finteger,其中該小數資料 fractional 了為正數或負數。若採取H〇〇r function之 方式對該比值進行處理,則整數資料 integer i1〇〇r(Fvco/Fref);而小數資料 fractional (Fvc〇/Fref)【i nteger ’ 其中該小數資料 ffractiona丨僅可為正數。同樣地,若採取Ceil function之方式對該比值進行處理,則整數資料f teger = Ceil(Fvcc/Fref);而小數資料 fractional =(Fvc〇/Fref) 一 fin,tegei•,其中該小數資料 僅為負數。 [0027]步驟三:對該整數資料進行處理以得到一第一處理訊號p 及一第二處理訊號a。 [0028]υAugust 30th, the nuclear replacement page I output is connected to the other input of the phase detector, and the other input terminal of the N/N + 1 multiple division Is is connected to the n/n + a multiple frequency dividing controller receives the control signal generated by the N/N+1 multiple frequency dividing controller; the n/n + i controller calculates the ratio of the path frequency to the reference frequency, and processes the ratio Obtaining an integer data and a decimal data; the integer data and the decimal data are calculated to obtain a first time period and a second time period, so that the N/N + 1 multiple frequency divider is outputted during a first time period of one working cycle n multiples, and output N+1 multiples in the second time period. A frequency conversion method for a phase-locked loop circuit includes the following steps: Step 1: Calculate the output frequency of the output required by the 篆 篆 篆 ; ; ; ; ; ; ; ; ; ; ; ; ; ; ; ; ; ; . The ratio of the frequency of the M times to the reference frequency is processed to obtain an integer data and a decimal data. Step 3: processing the integer data to obtain a first processed signal p and a second Processing signal a; Step 4: determining whether the second processing signal a is less than a minimum value min, and thus subtracting H and - second adjusting signal aadjust Ϊ Step 5: discrete processing the fractional data to obtain a discrete signal Xin; Step 6: Add the discrete signal xin to the second adjustment signal a adjust to obtain the adjusted second adjustment signal a; adjust 096147845 form number A0101 page 6 / total 18 page 0993469765-0 1339506 099 December 30 Japanese Junzheng Replacement Page [0016] Step 7: Use the adjusted second adjustment signal a" and the first adjustment adjust signal Padjust to obtain a first terminal signal Pfinal a second terminal signal 〜1丨; [0017] Step 8: calculating the first time period 利用1 by using the first terminal signal P, the second terminal signal af.11 na1 f 1 - na 1 and the minimum value min η And the second time period Τ2, the Ν/Ν+1 multiple frequency divider outputs a ν multiple in the first time period T1, and outputs a N+1 multiple in the second time period T2. [0018] Compared with the prior art, the phase-locked loop circuit of the present invention and its corresponding frequency conversion method 'set the N/N+1 multiple frequency divider to the T1 time by using the N/N+1 multiple frequency dividing controller. Output N multiple, and output N + 1 multiple at time T2' Therefore, the output frequency of the output required by the voltage controlled oscillator does not need to be an integer multiple of the reference frequency, which greatly expands the output frequency of the voltage controlled oscillator. The range also greatly expands the range of the path frequency of the phase-locked loop circuit. Moreover, since the phase-locked loop circuit uses a mathematical algorithm in the frequency conversion process, the area of the circuit is saved. [Embodiment] Φ [0019] The embodiment of the present invention will be further described in detail below with reference to the accompanying drawings. [0020] Referring to FIG. 2, a phase-locked loop circuit 1〇〇 according to an embodiment of the present invention is provided. The 096147845 phase-locked loop circuit 100 includes a phaser 11〇, a filter coupled to the output of the phase detector, a voltage controlled oscillator 130 coupled to the output of the phase detector 110, and A Μ multiplier 14 连接 connected to one of the output terminals of the voltage controlled oscillator 13 。. The phase-locked loop circuit 1 further includes a Ν/Ν + 1 multiple frequency divider 150 and a Ν/Ν + 1 multiple frequency divider controller 160, the Ν/Ν + 1 multiple frequency divider 15〇 and the Phase 1 〇 输入 表 表 表 Α Ι Ι 7 7 7 7 7 7 7 7 7 7 7 7 7 7 7 7 7 993 993 993 993 993 993 993 993 993 993 993 993 993 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换 替换The ingot|1 is connected to the other output end of the voltage controlled oscillator 130, and the N/N + i multiple frequency divider 150 is connected to the N/N+1 multiple frequency dividing controller 16 to receive The N/N +1 multiple frequency divider controller 16 generates a discrete control signal, and controls the N/N+1 multiple frequency divider 150 to output an N multiple at time T1, and outputs a multiple of N+1 at time T2. The other input end of the phase detector is input-reference frequency Fref, and the output end of the Μ frequency divider 140 outputs a channel frequency F channe1 °. Please refer to FIG. 3 , which is a phase-locked loop circuit provided in an embodiment of the present invention. The frequency conversion method includes the following steps: I Step 1: Calculate the output frequency of the output of the voltage controlled oscillator by using the path frequency. In this step, the output frequency Fvco required by the voltage controlled oscillator 1303⁄4 is twice the Fchannel of the path frequency required for the output of the chirp divider 140, that is, F = MF. Vc〇channel Step 2: Use the channel frequency Fvc〇 (that is, the output frequency of the required output of the voltage controlled oscillator 13〇) and the reference frequency Frd to obtain the channel frequency of the channel frequency '(:0 and reference frequency^ The ratio is processed to obtain an integer data and a decimal data. In this step, the ratio of the channel frequency Fvco to the reference frequency Fref can be processed by a round function to obtain The integer data f.+ and the decimal data f. Winter use & - is not limited to the round function, it can also be processed in the form of floor function or ceu function. 096147845 Form No. A0101 Page 8 / Total 18 pages 0993469765-0 1339506 • · Dan.. December 30, 099 shuttle is replacing page [0026], if the factory such as "functi〇n way to compare values for processing, ^ positive poor ^integer Round(Fvc/Fref); and the decimal data ffractlonal = (Fvc〇/Fref) — finteger, where the fractional data is fractional positive or negative. If H采取r function is used, the ratio is Line processing, the integer data integer i1〇〇r (Fvco / Fref); and the decimal data fractional (Fvc 〇 / Fref) [i nteger ' where the decimal data ffractiona 丨 can only be a positive number. Similarly, if you take the Ceil function The ratio is processed, the integer data f teger = Ceil(Fvcc/Fref); and the fractional data fractional = (Fvc〇/Fref) a fin, tegei•, where the fractional data is only negative. [0027] Step 3 The integer data is processed to obtain a first processing signal p and a second processing signal a. [0028]
於本步驟中,該第一處理訊號P為該整數資料f 除 x integer 以N後通過fl〇〇r functi〇n方式得到,即p = fi〇〇r(f in teger/N);而該第二處理訊號a為該整數資料f 減 integer 去該第一處理訊號P與N之乘積後而得到,即 [0029] a: integerIn this step, the first processing signal P is the integer data f divided by x integer and then obtained by fl〇〇r functi〇n, that is, p = fi〇〇r(f in teger/N); The second processing signal a is obtained by subtracting the integer data f from the integer of the first processing signal P and N, that is, [0029] a: integer
p*Np*N
[0030]步驟四:判斷該第二處理訊號a是否小於一最小值min, 並從而得到一第一調整訊號paqust及一第二調整訊號 Bad just 0 當泫第一處理訊號a較小時,其易於被鎖相環電路10D過 濾掉,為避免此現象發生,需要對第一處理訊號?及第二 096147845 表單編號A0101 第9頁/共18頁 0993469765-0 [0031] 1339506 [0032] [0033] [0034] [0035] [0036] [0037] [0038] 處理訊號a進行調整從而相應地得到該第一調整訊號p[0030] Step 4: determining whether the second processing signal a is less than a minimum value min, and thereby obtaining a first adjustment signal paqust and a second adjustment signal Bad just 0 when the first processing signal a is small, It is easy to be filtered by the phase-locked loop circuit 10D. To avoid this phenomenon, need to process the first signal? And second 096147845 Form No. A0101 Page 9 / Total 18 Page 0993469765-0 [0031] [0033] [0036] [0037] [0038] [0038] Processing signal a is adjusted to correspondingly Obtaining the first adjustment signal p
Had -Had -
just及一第二調整訊號aadjust。因此,於此步驟中設定 一最小值min ’該最小值mi η為一整數,當該第二處理訊 號β小於該最小值miη時,則p ^. =p _ ] , a = a + N ,若不是,則Padjust = p,aad」ust = a,從而避免上述現象 之發生。 步驟五‘對該小數資料進行離散處理以得到一離散訊號 xin 〇 於本步驟中,將該小數資料ffractlQnal進行離散處理從 而可得到一離散訊號Xin ,該離散處理可為將該小數資料 fractional 乘以一離散位數餘i:t: nu祕er) ,如2bit等, 然後將得到之乘積取整,從破得鱗满散^訊號^in,即 xin = f l〇〇r( f 氺 fractional ’ 步驟六:將該離散訊號Xin加入該第二調整訊號a 中 adjust 得到調整後之第二調整訊號a 。 adjust 於本步驟中’將步驟五所得到之離散訊號xin加入到該第 —調整訊號aadjust從而得到調整後之第二調整訊號 just,即aadjust = aadjust+xiri。 步驟七:利用調整後之第二調整訊號a 及第一調整 ^ ad just 汛號Padjust得到一第—終端訊號Pf .,及一第二終端訊 final 號 .。 final 於本步驟中,需要對第二調整訊號3 及第一調整訊 adjust 、Padjust進行進一步地處理,從而得到第一終端訊號 096147845 表單編號A0101 第丨0頁/共18頁 0993469765-0 1339506 _ 099年12月30日孩正脊换頁 fina丨及第二終端訊號afin£^,其進一步包括以下步驟: [0039] a :判斷該調整後第二調整訊號aadjust是否大於n與最小 值mi η之和,若大於,則p」.=ρ +1 » adjust adjust aadjust = aadjust - N,並返回繼續執行a,若不是,則執 行b ; [0040] b :判斷調整後之第二調整訊號是否小於最小值min,若 是,則 Pf. . =p .. - 1 5 a .. + + N,若不是 final adjust final adjust & ,則Pf. ,=p」.‘,而af. .=a .. + ° final ad just final ad justJust and a second adjustment signal aadjust. Therefore, in this step, a minimum value min ' is set to the minimum value mi η as an integer. When the second processing signal β is smaller than the minimum value miη, then p ^. =p _ ] , a = a + N , If not, Padjust = p, aad"ust = a, to avoid the above phenomenon. Step 5: discrete processing the fractional data to obtain a discrete signal xin. In this step, the fractional data ffractlQnal is discretely processed to obtain a discrete signal Xin, and the discrete processing may multiply the fractional data fractional A discrete number of bits i:t: nu secret er), such as 2bit, etc., and then the product is rounded up, from the broken scales full signal ^in, ie xin = fl〇〇r ( f 氺 fractional ' step 6: adding the discrete signal Xin to the second adjustment signal a adjust to obtain the adjusted second adjustment signal a. In this step, 'add the discrete signal xin obtained in step 5 to the first adjustment signal aadjust to obtain Adjusted second adjustment signal just, ie aadjust = aadjust+xiri. Step 7: Use the adjusted second adjustment signal a and the first adjustment ^ ad just 汛 Pa Padjust to get a first terminal signal Pf ., and a first Second terminal final number. final In this step, the second adjustment signal 3 and the first adjustment signal adjust, Padjust need to be further processed to obtain the first terminal signal 09 6147845 Form No. A0101 Page / 0/18 pages 0993469765-0 1339506 _ December 30, 1999, the child's ridge page fina丨 and the second terminal signal afin£^, which further includes the following steps: [0039] a : Determining whether the adjusted second adjustment signal aadjust is greater than the sum of n and the minimum value min η, if greater than, then p".=ρ +1 » adjusts aadjust = aadjust - N, and returns to continue to perform a, if not, then Executing b; [0040] b: determining whether the adjusted second adjustment signal is less than the minimum value min, and if so, then Pf. . =p .. - 1 5 a .. + + N, if not final adjust final adjust & , then Pf. , =p".', and af. .=a .. + ° final ad just final ad just
[0041] 通過上述兩個步驟,將第二調整訊號a ^ 及第一調整 d d j U s t 訊號p .進一步地處理得到第一終端訊號pf.,及第 adjust final 二终端訊號a,.,。 final [0042] 步驟八:利用該第一終端訊號pf.,、第二終端訊號a . 11 η 31 f [ n a 1及最小值m i η計算出該第一時間段Τ1及該第二時間段 Τ2,該Ν/Ν+1倍數分頻器於第一時間段Τ1内輸出Ν倍數, 而於第二時間段Τ2内輸出Ν+1倍數。 [0043] 於本步驟中,利用該第一終端訊號卩,.,、第二終端訊號 afinal及最小值min可計算出需要輸出N倍數之第一時間 段T1及輸出N+1倍數之第二時間段T2,其中,T1為(p,. f卜 na 1 ~a ,)*N*T ,而該第二時間段T2為 final vco a,. ,*(N+1)*T ,T 是F 之週期(1/F )。 final vco vco vco vco [0044] 相較於先前技術,本發明之鎖相環電路100及其相應之頻 率轉換方法,由於利用N/N+1倍數分頻控制器160設定N/ N + 1倍數分頻器150於T1時刻輸出N倍數,而於T2時刻輪 • 出N+1倍數,因此,該壓控振盪器130所需要輸出之輸出 096147845 表單編拢 A0101 第 11 頁/共 18 頁 0993469765-0 1339506[0041] Through the above two steps, the second adjustment signal a ^ and the first adjustment d d j U s t signal p are further processed to obtain a first terminal signal pf., and a second final terminal signal a, . Final [0042] Step 8: calculating the first time period Τ1 and the second time period 利用2 by using the first terminal signal pf., the second terminal signal a.11 η 31 f [na 1 and the minimum value min η The Ν/Ν+1 multiple frequency divider outputs a Ν multiple in the first time period Τ1, and outputs a Ν+1 multiple in the second time period Τ2. [0043] In this step, the first terminal signal 卩, ., the second terminal signal afinal and the minimum value min are used to calculate a first time period T1 and a second multiple of the output N+1 that need to output N times. Time period T2, where T1 is (p, .fbu na 1 ~a ,)*N*T , and the second time period T2 is final vco a,. ,*(N+1)*T , T is The period of F (1/F). Final vco vco vco vco [0044] Compared to the prior art, the phase-locked loop circuit 100 of the present invention and its corresponding frequency conversion method are set to N/N + 1 multiples by using the N/N+1 multiple frequency dividing controller 160. The frequency divider 150 outputs N times at the time T1, and the N+1 multiple is output at the time T2. Therefore, the output of the voltage controlled oscillator 130 needs to be output 096147845. The form is spliced A0101 page 11/18 page 0993469765- 0 1339506
I 099年12月3ϋ Η修正頁I 頻率F 並不需要是參考頻率F f之整數倍數,其極大地 , vco ref 擴展了該壓控振盪器130之輸出頻率F 之範圍,同時也I. December 3, 099 Η Amendment page I The frequency F does not need to be an integer multiple of the reference frequency F f , which greatly expands the range of the output frequency F of the voltage controlled oscillator 130, and also
V CO 極大地擴展了該鎖相環電路100之通路頻率F u ,之範 channel 圍。且由於該鎖相環電路100於頻率轉化過程中採用之是 數學演算法,節省了電路之面積。 [0045] 綜上所述,本發明確已符合發明專利之要件,遂依法提 出專利申請。惟,以上所述者僅為本發明之較佳實施方 式,自不能以此限制本案之申請專利範圍。舉凡熟悉本 案技藝之人士援爰依本發明之精神所作之等效修飾或變 φ 化,皆應涵蓋於以下申請專利範圍内。 【圖式簡單說明】 [0046] 圖1係一種先前技術所提供之鎖相碟電-路名.示意圖。 [0047] 圖2係本發明實施例所提供之鎖相環電路之示意圖。 [0048] 圖3係本發明實施例所提供之鎖相環電路之頻率轉換方法 之示意圖。 【主要元件符號說明】 · [0049] 鎖相環電路:1 0,1 0 0 [0050] 鑒相器:11,110 [0051] 濾波器:12,120 [0052] 壓控振盪器:13,130 [0053] Μ倍數分頻器:14,140 [0054] Ν倍數分頻器:15 096147845 表單編號Α0101 第12頁/共18頁 0993469765-0 1339506 099年12月30日梭正替换頁 [0055] N/N + 1倍數分頻器:150 [0056] N/N + 1倍數分頻控制器:160V CO greatly expands the path frequency F u of the phase-locked loop circuit 100. Moreover, since the phase-locked loop circuit 100 adopts a mathematical algorithm in the frequency conversion process, the area of the circuit is saved. [0045] In summary, the present invention has indeed met the requirements of the invention patent, and the patent application is filed according to law. However, the above description is only a preferred embodiment of the present invention, and it is not possible to limit the scope of the patent application of the present invention. Any equivalent modifications or variations made by those skilled in the art to the spirit of the present invention are intended to be included in the scope of the following claims. BRIEF DESCRIPTION OF THE DRAWINGS [0046] FIG. 1 is a schematic diagram of a phase-locked disk electric-road name provided by the prior art. 2 is a schematic diagram of a phase locked loop circuit according to an embodiment of the present invention. 3 is a schematic diagram of a frequency conversion method of a phase locked loop circuit according to an embodiment of the present invention. [Main component symbol description] · [0049] Phase-locked loop circuit: 1 0,1 0 0 [0050] Phase detector: 11,110 [0051] Filter: 12,120 [0052] Voltage-controlled oscillator: 13, 130 [0053] Μ Multiplier: 14,140 [0054] ΝMultiplier: 15 096147845 Form No. 1010101 Page 12/Total 18 Page 0993469765-0 1339506 December 30, 2017 Shuttle Replacement Page [0055 ] N/N + 1 multiple divider: 150 [0056] N/N + 1 multiple divider: 160
096147845 表單編號A0101 第13頁/共】8頁 0993469765-0096147845 Form No. A0101 Page 13/Total] Page 8 0993469765-0
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