501334 經濟部智慧財產局員工消費合作社印製 A7 B7 五、發明說明（1) 發明領域： 本發明係一種可應用於功率轉換器之無振鈴零電位切換方法’尤指一種可 令功率轉換器在進行高效率及高密度切換過程中，有效降低所產生之磁損失及 開關切換損失，並令其次級整流子之耐壓一併降低之無振鈴零電位切換方法。 先前技藝·· 按，近年來，爲了追趕電子產品快速小型化之趨勢，切換式功率轉換器之 技術一直朝向高頻率、高效率及高密度之方向發展。一般而言，由於場效應功率 電晶體(Power MOSFET)之切換速度，較雙極性電晶體(Bipolar Transistor)快很 多，因此常被業界廣泛應用於切換式功率轉換器中，作爲其上之功率開關，然而， 該種場效應功率電晶體(Power MOSFET)上寄生電容所存留之能量，在該電晶 體每次被導通時，都會在其通道中，以歐姆熱之形式耗盡，切換頻率越高，其損 耗越大，此一問題，若不加以有效解決，將令該切換式功率轉換器難以朝向高效 率及高密度之設計目標繼續發展。 自從1988年，美國亨芝(C· P· Henze)、馬丁(H. C· Martin)及巴司萊(D· W· Paraley)等三位專家，共同在IEEE刊物上，發表零電位切換(Zero-Voltage Switching)槪念以來，各種實用電路即陸續被提出，有效地解決了傳統上場效應 功率電晶體(Power MOSFET)上所發生之導通損失問題，茲將其中較具代表性之 先前技藝，分述如下： ⑴順向式零電位切換電路（Forward Zero-Voltage · Switching Power Converter) · 參閱第1(a)圖所示，爲Bruce Wilkinson於1989年6月申請之美國第383,594 號發明專利之電路實施例，該專利係藉適當控制該電路，令其變壓器工作在正負 磁區，因此在相同之輸出功率下，具有可選用較小之變壓器之優點。由於該電路 2 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公爱） (請先閱讀背面之注意事項再填寫本頁) — — — — — — I— ^ · I--— 111— 罾 501334 A7 B7 五、發明說明（£) 設計之啓7K，Putrice R· Lethellier發明了第一個具零電位切換之實用電路，參 閱第l(b薦所示，係其於1990年10月獲准之美國第4,975,821號發明專利之電 路架構圖，該專利達成零電位切換之目的，其變壓器係採用鬆交連型式，並在其 磁蕊上加入氣隙(gap)，以得到必要之磁化電感及漏感，俾該磁化電感及漏感能 與倂聯在開關SW1上之寄生電容Cs，形成L-C共振電路，令開關SW2：gE剛關 掉後之瞬間，因該L-C共振電路之共振，使開關SW:獲得零電位切換之條件， 同樣地，在開關SWi岡[(關掉後之瞬間，亦將因該L-C共振電路之共振，令開關 SW2亦獲得零電位切換之條件，惟，此時，由於該變壓器之磁蕊上加了氣隙及漏 感，造成不容忽視之磁損失，使得該電路在獲得零電位切換條件之同時，亦爲該 變壓器帶來了異常發熱及效率下滑之缺點。 參閱第2(a)與2(b)圖所示，係Paul Imbertson於1991年10月提出申請， 且於1993年9月獲准之美國第5,245,520號發明專利之電路實施例，其中第2⑻ 圖可稱之爲「半橋式非對稱順向轉換器(Half bridge asymmetrical buck converter)」’第2 (b)圖可稱之爲「全橋式非對稱順向轉換器(Full bridge asymmetrical buck converter)」，由於該二電路均外加有等同於其變壓器漏感之 輔助電感La (auxiliary inductor)，因此在達成零電位切換功效時，該變壓器並 沒有異常發熱之問題，但該輔助電感La卻與該變壓器之初級繞組兩端之雜散電 容間，產生了不容忽視之振鈴(ringing)現象，由於該振鈴電流在電感器與變壓器 之繞組上’來回振盪，將對磁蕊產生感應加熱(induction heating)之效應，致其 效率隨之惡化，另該寄生振盪除了會增加EMI雜訊外，還會反映到該變壓器之 次級繞組，令該次級整流零件之耐壓需提高至少1·5倍以上，此即Imbertson之 橋式非對稱順向轉換器上因振鈴而引起之諸多缺點。參閱第3圖所示，乃 Imbertscm之電路在變壓器之初級繞組及次級繞組上，所產生之振鈴現象。 (2)返馳式零電位切換電路(Flyback Zero-Voltage Switching Power Converter): 本紙張尺度適用中國國家標準（CNS)A4規格（210 χ 297公釐） (請先閱讀背面之注意事項再填寫本頁) -裝 ---------訂---------· 經濟部智慧財產局員工消費合作社印製 經濟部智慧財產局員工消費合作社印製 501334 A7 B7 ___ 五、發明說明) 參閱第 4(¾與 1(b)圖所示，爲 Christopher R Henze 與 Hubert C. Martin，Jr. 於1991年10月獲准之美國第5,057,986號發明專利之電路實施例，在該實施例 中，由於無外加的輔助電感，因此若欲達成零電位切換，需加大其變壓器之氣隙， 令該變壓器之初級磁化電流之峰對峰値，大於次級側反射到初級側之負載電流， 該項需求與Putrke R· Lethellier之發明專利相同，同樣會造成變壓器異常地發 熱，爲解決此問題，需加大該變壓器之尺寸，以增加其散熱能力。 參閱第 5(a)與 5(b)圖所示，爲 Wittenbreder，Jr·與 Ernest H·於 1995 年 3 月獲准之美國第5,402,329號發明專利之電路實施例，由於該實施例中力有輔 助電感，其變壓器之初級磁化電流之峰對峰値，無需大於次級側反射到初級側之 負載電流値，即可輕易達成零電位切換之效果，該輔助電感可爲一利用該變壓器 以鬆交連繞製時之漏電感，也可爲一外加電感，但，無論係以何種方式形成者， 該專利與前述Imbertsoii之專利上均會發生因振鈴而引起之副作用。參閱第ό圖 所示，乃Wittenbreder，Jr·與Ernest Η·之電路在變壓器之初級繞組及次級繞組 上，所產生之振鈴現象。 發明綱要： 有鑒於前述傳統功率轉換器在進行零電位切換時，其功率整流開關(Power Rectifier Switches)切換瞬間所產生之寄生振鈴(Parasitic Ringing)，對磁蕊產生 了感應加熱(induction heating)之效應，致其在效率提升上受到極大之限制，同 時增加了電磁干擾之雜訊，並對整流零件產生較高之逆向電壓衝擊，本發明乃針 對該等因振鈴現象所產生之諸多缺點，硏發出一種可應用於功率轉換器之無振鈴 零電位切換方法，該項方法在功率轉換器進行高效率及高密度之零電位切換過 程中，可針對其變壓器初級側會產生振盪之一 L-C共振電路(電感-電容共振電 路）’在開始發生振鈴現象時，令其電感上之電流短路，並箝制住其電容上之電 — — — — · I I I I I I I ^ ·11111111 L I Ϊ (請先閱讀背面之注意事項再填寫本頁) 1 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） " " 經濟部智慧財產局員工消費合作社印製 501334 A7 B7 五、發明說明（4) 壓，有效根除傳統零電位切換電路所產生之寄生振鈴，令其不受該寄生振鈴之影 響。 本發明之一目的，係將傳統功率轉換器上具有輔助電感（auxiliaryinductor) 與平衡電容（balance capacitor)之零電位切換電路，重新作一安排’令該等電 路在適當位置上可加設至少一電感電流短路二極體(inductor current shorted diode)，俾藉該等二極體抑制輔助電感與該功率轉換器上之一變壓器之初級側上 之雜散電容(stray capacitance)所形成之寄生振盪(parasitic oscillation)，避免該 輔助電感與主變壓器因該寄生振盪而產生電磁雜訊干擾之問題’並有效減輕對 次級側整流零件之耐壓額度(reverse voltage rating)之要求’令具有輔助電感之 零電壓切換電路可達成更高之能量轉換效率及功率密度，同時更容易通過國際 電磁干擾規範(international EMI regulations)之要求。 本發明之另一目的，係將該零電位切換電路上之一輔助電感，設置在該變 壓器之初級繞組與二場效應功率電晶體(power MOSFETs，以下簡稱功率開關) 之串接線路接點之間，再在該變壓器之初級繞組與外加電感器間之線路接點上’ 分別加設至少一二極體，俾該等二極體可在該外加電感器開始要產生振鈴時，可 分別與對應之該等功率開關作用，將該輔助電感器上之電流予以短路’並箝制住 該變壓器之初級側雜散電容上之電壓，制止其產生振盪，有效避免發生振鈴現象， 達成高效率、高密度及_訊之零電位切換目的。 本發明之又一目的，係令該無振鈴技術可應用至各式返馳式、昇壓式及降壓 式等功轉換器上，該等功率轉換器能有效避免發生振纖象 > 以在高頻切換 作業下，有效降低功率損失，大幅提升其功率密度，並減少該等功率開關上所累 積之熱能及所需散熱片之体積大小，令該等功率轉換器更易於被應用至各種小型 化電子產品之設計中，免除了不具輔助電感器之共振型零電位切換電路，因過於 依賴變壓器之漏電感量來實現零電位切換之目的，致在設計及製造時，不易達成 5 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） " " (請先閱讀背面之注音？事項再填寫本頁) --------訂--------- 501334 A7 B7 五、發明說明（5) 其設計規格，且難以大量生產之缺點。 附圖說明： 第1圖(a)所示爲美國第383,594號發明專利之主要電路圖。 第1圖(b)所示爲美國第4,975,821號發明專利之主要電路圖。 第2圖(a)與第2圖(b)所示爲美國第5,245,520號發明專利之主要電路圖。 第3圖所示爲Imberts〇n之專利電路所產生之寄生振鈴現象。 第4陳a)與第4圖(b)所示爲美國第5,057,986號發明專利之主要電路圖。 第5圖(a)與第5圖(b)所示爲美國第5,402,329號發明專利之主要電路圖。 第ό圖所示爲Wittenbreder，Jr•與Ernest Η·之專利電路所產生之寄生振鈴 現象。 第7圖所示爲本發明之第一個具體實施例。 第8圖所示爲第7圖不加無振鈴抑制電路時所產生之寄生振鈴現象。 第9圖所示爲第7睡口入無振鈴抑制電路時寄生振鈴消失之波形圖。 第10圖所示爲第7圖分成1〇個時段之等效電路圖。 第11圖所示爲下臂振鈴箝制電路之時段圖。 第12圖所示爲下臂振鈴箝制電路之電壓與電流波形圖。 第13圖所示上臂振鈴箝制電路之時段圖。 第14圖所示爲上臂振鈴箝制電路之電壓與電流波形圖。 第15圖所示爲本發明第7圖之具體實施例，在效率上所獲致之成果圖。 第16圖所示爲本發明第7圖之具體實施例，在電磁干擾上所獲致之成果圖。 第17圖所示爲本發明之第二個具體實施例。 第18圖所示爲本發明之第三個具體實施例。 第19圖所示爲本發明之第四個具體實施例。 本紙張(CNS)A4規格⑽X 297公爱) (請先閱讀背面之注意事項再填寫本頁) ---------訂-------- '1 經濟部智慧財產局員工消費合作社印製 501334 A7 B7 五、發明說明（0 ) 第20圖所示爲本發明之第五個具體實施例。 第21圖所示爲本發明之第六個具體實施例。 圖號說明： 輸入電壓濾波電容器· 功率開關…............. 効及織且................ 輔助電感................ (請先閱讀背面之注音？事項再填寫本頁)501334 Printed by the Consumer Property Cooperative of the Intellectual Property Bureau of the Ministry of Economic Affairs A7 B7 V. Description of the invention (1) Field of the invention: The present invention is a ringing-free zero-potential switching method that can be applied to a power converter. The high-efficiency and high-density switching process is a zero-potential-free switching method that effectively reduces the magnetic loss and switching switching losses that occur, and reduces the withstand voltage of its secondary commutator. Previous techniques ... In recent years, in order to keep up with the trend of rapid miniaturization of electronic products, the technology of switching power converters has been developing in the direction of high frequency, high efficiency and high density. Generally speaking, because the switching speed of the field effect power transistor (Power MOSFET) is much faster than the bipolar transistor, it is often widely used in the industry as a switching power converter. However, the energy stored in the parasitic capacitance of this type of field effect power transistor (Power MOSFET) will be depleted in the form of ohmic heat in its channel each time the transistor is turned on, the higher the switching frequency The larger the loss, this problem, if not effectively solved, will make it difficult for the switching power converter to continue to develop towards the design goals of high efficiency and high density. Since 1988, three experts including C. Henze, H. C. Martin and D. W. Paraley have jointly published zero-potential switching in IEEE publications ( Since the idea of Zero-Voltage Switching, various practical circuits have been proposed one after another, which effectively solves the conduction loss problem that occurs in traditional field effect power transistors (Power MOSFETs). The description is as follows: ⑴ Forward Zero-Voltage · Switching Power Converter · Refer to Figure 1 (a), which is the invention patent No. 383,594 filed by Bruce Wilkinson in June 1989. For the circuit embodiment, the patent is to properly control the circuit to make the transformer work in the positive and negative magnetic regions. Therefore, at the same output power, it has the advantage of using a smaller transformer. As this circuit 2 this paper size applies to Chinese National Standard (CNS) A4 specifications (210 X 297 public love) (Please read the precautions on the back before filling this page) — — — — — — I— ^ · I --— 111— 罾 501334 A7 B7 V. Description of the invention (£) Design 7K, Putrice R. Lethellier invented the first practical circuit with zero potential switching. Refer to No. 1 (b recommendation, which was published in October 1990) The circuit architecture diagram of the US Patent No. 4,975,821 approved every month. This patent achieves the purpose of zero potential switching. The transformer adopts a loosely-connected type and adds a gap to its core to obtain the necessary magnetizing inductance. And leakage inductance, the magnetizing inductance and leakage inductance can form an LC resonance circuit with the parasitic capacitance Cs on the switch SW1, so that the switch SW2: gE immediately after turning off, due to the resonance of the LC resonance circuit, Switch SW: The condition for obtaining zero potential switching. Similarly, at the moment when the switch SWi Gang [(is turned off, the switch SW2 will also obtain the condition for zero potential switching due to the resonance of the LC resonance circuit. However, at this time Because of the magnetic core of the transformer The air gap and leakage inductance are added, causing magnetic losses that cannot be ignored, which makes the circuit bring the disadvantages of abnormal heat generation and decreased efficiency of the transformer at the same time as the zero potential switching condition is obtained. Refer to Section 2 (a) and Figure 2 (b) shows a circuit embodiment of the US Patent No. 5,245,520, filed by Paul Imbertson in October 1991 and approved in September 1993. Figure 2⑻ can be called "half-bridge type" Asymmetrical forward converter (Half bridge asymmetrical buck converter) "Figure 2 (b) can be called" Full bridge asymmetrical buck converter (Full bridge asymmetrical buck converter) ". There is an auxiliary inductor La (auxiliary inductor) equivalent to the leakage inductance of the transformer, so when the zero potential switching effect is achieved, the transformer does not have abnormal heating problems, but the auxiliary inductor La is different from the two ends of the primary winding of the transformer. There is a ringing phenomenon that cannot be ignored between the bulk capacitors. Because the ringing current oscillates back and forth on the windings of the inductor and the transformer, it will induce induction heating of the core. The effect of ting) causes its efficiency to deteriorate. In addition, the parasitic oscillation will not only increase EMI noise, but also be reflected to the secondary winding of the transformer, so that the withstand voltage of the secondary rectifier parts needs to be increased by at least 1.5 More than this, this is the many shortcomings caused by ringing on the bridge asymmetric forward converter of Imbertson. Refer to Figure 3, which is the ringing produced by Imbertscm's circuit on the primary and secondary windings of the transformer. phenomenon. (2) Flyback Zero-Voltage Switching Power Converter: This paper size applies to China National Standard (CNS) A4 (210 χ 297 mm) (Please read the precautions on the back before filling in this (Page)-Install --------- Order --------- · Printed by the Employees 'Cooperatives of the Intellectual Property Bureau of the Ministry of Economic Affairs Printed by the Employees' Cooperatives of the Intellectual Property Bureau of the Ministry of Economic Affairs 501334 A7 B7 ___ V. Description of the Invention) Refer to Figures 4 (¾ and 1 (b) for a circuit embodiment of US Patent No. 5,057,986, approved by Christopher R Henze and Hubert C. Martin, Jr. in October 1991. In the example, because there is no additional auxiliary inductance, if you want to achieve zero potential switching, you need to increase the air gap of the transformer, so that the peak of the transformer's primary magnetizing current is peak-to-peak larger than the load reflected from the secondary side to the primary side. This requirement is the same as Putrke R. Lethellier's invention patent, which will also cause abnormal heating of the transformer. To solve this problem, the size of the transformer needs to be increased to increase its heat dissipation capacity. See Sections 5 (a) and 5 (b) Wi is shown Ttenbreder, Jr. and Ernest H. The circuit embodiment of US Patent No. 5,402,329, which was approved in March 1995. Due to the auxiliary inductance in this embodiment, the peak to peak of the primary magnetizing current of the transformer need not be greater than The load current 値 reflected from the secondary side to the primary side can easily achieve the effect of zero potential switching. The auxiliary inductor can be a leakage inductance when the transformer is loosely wound and wound, or an external inductance, but, Regardless of how it is formed, the side effects caused by ringing in this patent and the aforementioned Imbertsoii patent will occur. See the figure below, the circuit of Wittenbreder, Jr · and Ernest Η · is in the primary winding of the transformer And the secondary winding, the ringing phenomenon. Summary of the invention: In view of the aforementioned traditional power converter when the zero potential switching, the power rectifier switches (Power Rectifier Switches) switching moments generated by the parasitic ringing (Parasitic Ringing), The induction heating effect on the magnetic core has caused it to be greatly limited in its efficiency improvement, and at the same time In order to overcome the noise of electromagnetic interference and generate a high reverse voltage impact on the rectifying parts, the present invention aims at many shortcomings caused by the ringing phenomenon, and provides a ringing-free zero-potential switching method applicable to power converters. In this method, during the high-efficiency and high-density zero-potential switching of the power converter, one of the LC resonance circuits (inductance-capacitance resonance circuits) that will oscillate on the primary side of its transformer is used. Short the current on its inductor and clamp the electricity on its capacitor — — — — · IIIIIII ^ · 11111111 LI Ϊ (Please read the precautions on the back before filling out this page) 1 This paper size applies to Chinese national standards (CNS ) A4 specification (210 X 297 mm) " " Printed by the Intellectual Property Bureau of the Ministry of Economic Affairs's Consumer Cooperatives 501334 A7 B7 V. Description of the invention (4) The voltage can effectively eliminate the parasitic ringing generated by the traditional zero potential switching circuit. It is not affected by this parasitic ringing. One object of the present invention is to re-arrange the zero-potential switching circuit with auxiliary inductor and balance capacitor on the conventional power converter, so that at least one Inductor current shorted diodes. These diodes are used to suppress parasitic oscillations formed by auxiliary inductance and stray capacitance on the primary side of a transformer on the power converter ( parasitic oscillation), to avoid the problem of electromagnetic interference caused by the auxiliary inductor and the main transformer due to the parasitic oscillation, and to effectively reduce the requirement for the reverse voltage rating of the secondary-side rectifier parts. The zero-voltage switching circuit can achieve higher energy conversion efficiency and power density, and it is easier to pass the requirements of international EMI regulations. Another object of the present invention is to provide an auxiliary inductor on the zero-potential switching circuit between a primary winding of the transformer and two line-effect contacts of two field effect power transistors (power MOSFETs (hereinafter referred to as power switches)). Then, at least one diode is added to the line contact between the primary winding of the transformer and the external inductor. When the external inductor starts to ring, the two diodes can be separately connected with Corresponding to the role of these power switches, the current on the auxiliary inductor is short-circuited, and the voltage on the primary-side stray capacitance of the transformer is clamped to prevent it from oscillating, effectively avoiding ringing, and achieving high efficiency, high The purpose of zero density switching of density and signal. Another object of the present invention is to make the ringing-free technology applicable to various flyback, boost, and step-down power converters. These power converters can effectively avoid the occurrence of vibrating fiber images > Under high frequency switching operation, it can effectively reduce power loss, greatly increase its power density, and reduce the heat energy accumulated on these power switches and the size of the required heat sink, making these power converters easier to be applied to various In the design of miniaturized electronic products, the resonance-type zero-potential switching circuit without an auxiliary inductor is eliminated. Because it is too dependent on the leakage inductance of the transformer to achieve the purpose of zero-potential switching, it is difficult to achieve 5 papers during design and manufacturing. Standards are applicable to China National Standard (CNS) A4 specifications (210 X 297 mm) " " (Please read the note on the back? Matters before filling out this page) -------- Order ------ --- 501334 A7 B7 V. Description of the invention (5) The disadvantages of its design specifications and its difficulty in mass production. Brief Description of the Drawings: Figure 1 (a) shows the main circuit diagram of US Patent No. 383,594. Figure 1 (b) shows the main circuit diagram of US Patent No. 4,975,821. Figures 2 (a) and 2 (b) show the main circuit diagrams of US Patent No. 5,245,520. Figure 3 shows the parasitic ringing produced by Imbertson's patented circuit. Figure 4a) and Figure 4 (b) show the main circuit diagram of US Patent No. 5,057,986. Figures 5 (a) and 5 (b) show the main circuit diagrams of US Patent No. 5,402,329. Figure 6 shows the parasitic ringing caused by the patented circuits of Wittenbreder, Jr • and Ernest Η ·. Fig. 7 shows a first specific embodiment of the present invention. Figure 8 shows the parasitic ringing phenomenon in Figure 7 when no ring suppression circuit is added. Figure 9 shows the waveform diagram of the parasitic ringing disappearing when the seventh sleeping mouth enters the non-ringing suppression circuit. Figure 10 shows the equivalent circuit diagram of Figure 7 divided into 10 periods. Figure 11 shows the timing diagram of the lower arm ringer clamp circuit. Figure 12 shows the voltage and current waveforms of the lower arm ringer clamp circuit. Figure 13 shows the timing diagram of the upper arm ringer clamp circuit. Figure 14 shows the voltage and current waveforms of the upper arm ringer clamp circuit. Fig. 15 is a diagram showing the results obtained in the specific embodiment of Fig. 7 of the present invention in terms of efficiency. FIG. 16 is a diagram showing the results obtained in the specific embodiment of FIG. 7 of the present invention on electromagnetic interference. Fig. 17 shows a second specific embodiment of the present invention. Fig. 18 shows a third specific embodiment of the present invention. Fig. 19 shows a fourth embodiment of the present invention. This paper (CNS) A4 size ⑽X 297 public love) (Please read the precautions on the back before filling this page) --------- Order -------- '1 Intellectual Property Bureau, Ministry of Economy Printed by the employee consumer cooperative 501334 A7 B7 V. Description of the invention (0) Figure 20 shows the fifth specific embodiment of the present invention. Fig. 21 shows a sixth specific embodiment of the present invention. Description of figure number: Input voltage filter capacitor · Power switch .................. and auxiliary ... ............. (Please read the Zhuyin on the back? Matters before filling out this page)
Cm 輸入電壓.....................Cm input voltage ...
Ql、Q2 初級顯·····........... NpQl, Q2 Elementary display ......... Np
Nsl、Ns2 平衡電容……············ cbNsl, Ns2 balance capacitors ... cb
La 短路二極體........... D3 ^ D4 D1 D2 直流輸出顧............V〇 詳細說明： 本發明係一種可應用於功率轉換器之無振鈴零電位切換方法，該方法係針 對一功率轉換器上之零電位切換電路，在進行高效率及高密度之零電位切換過程 中，其變壓器之初級側上會產生振盪之一 L-C共振電路，在開始發生振鈴現象 時，令其電感上之電流短路，並箝制住其電容上之電壓，有效根除該零電位切換 電路所產生之寄生振鈴。 經濟部智慧財產局員工消費合作社印製 本發明主要係將傳統功率轉換器上具有輔助電感（auxiliary inductor)與平 衡電容（balance capacitor)之零電位切換電路，重新作一安排，令該零電位切換 電路上之一輔助電感器，被設置在該變壓器之初級繞組與二場效應功率電晶體 (power MOSFETs ’以下簡稱功率開關)之串接接點之間，再針對該功率轉換器 係半波整流，或全波整流，而在該變壓器之初級繞組與外加電感器間之線路接點 上’加設一短路二極體，或加設二短路二極體，俾該外加輔助電感器與該變壓 器之初級側上之雜散電容(stray capacitance)所形成之L-C電路，在開始產生振 胃#二®體可分別與對應之該功率開關發生作用，將該外加電感器上之電 ’ MltM住該變壓器之初級側雜散電容上之電壓，以制止其產生振盪， 7 本紙張尺度適用中國國豕標準（CNS)A4規格（21〇 X 297公輩) 501334 A7 B7 五、發明說明) 有效避免發生振鈴現象，達成高效率、高密度及低雜訊之零電位切換目的。 (請先閱讀背面之注意事項再填寫本頁) 參閱第7圖所示，乃本發明之第一個具體實施例，係將本發明之無振鈴零 電位切換方法應用至一半橋順向式全波整流電路之設計中，在此可稱之爲「半橋 順向式無振鈴零電位切換全波整La short-circuit diode .............. D3 ^ D4 D1 D2 DC output Gu ............ V〇 Detailed description: The present invention is applicable to power conversion No-potential zero-potential switching method of the converter, which is directed to the zero-potential switching circuit on a power converter. During the high-efficiency and high-density zero-potential switching process, one of the oscillations on the primary side of the transformer will generate LC. The resonance circuit, when the ringing phenomenon starts, shorts the current on its inductance and clamps the voltage on its capacitor, effectively eradicating the parasitic ringing generated by the zero potential switching circuit. Printed by the Consumer Cooperative of the Intellectual Property Bureau of the Ministry of Economics The present invention is mainly to re-arrange a zero potential switching circuit with an auxiliary inductor and a balance capacitor on a traditional power converter to make the zero potential switch An auxiliary inductor on the circuit is placed between the primary winding of the transformer and the series connection point of two field effect power transistors (power MOSFETs' hereinafter referred to as power switches), and then the power converter is half-wave rectified Or full-wave rectification, and a short-circuit diode is added to the line contact between the primary winding of the transformer and the external inductor, or two short-circuit diodes are added, and the external auxiliary inductor and the transformer are added. The LC circuit formed by the stray capacitance on the primary side of the primary side can start to generate vibration stomach # 二 ® body can interact with the corresponding power switch, respectively, the electricity on the external inductor 'MltM The voltage on the primary side stray capacitance of the transformer to prevent it from oscillating. 7 This paper size applies to China National Standard (CNS) A4 (21〇X 297) (Public generation) 501334 A7 B7 V. Description of the invention) Effectively avoid ringing and achieve zero-potential switching with high efficiency, high density and low noise. (Please read the precautions on the back before filling this page.) Refer to Figure 7, which is the first specific embodiment of the present invention, which applies the ringless zero potential switching method of the present invention to a half-bridge forward type full In the design of the wave rectifier circuit, it can be called "half-bridge forward-type ringing-free zero-potential switching full-wave rectification.
Voltage-Switching Full-Wave Converter)」。在該實施例中，該括一輸入 經濟部智慧財產局員工消費合作社印製 電壓濾波電容器Cm，該電容器Cin之正負極係跨接在一輸入電壓Vin之正負極 上，其上並聯有一組串接之功率開關Ql、Q2，該功率開關Q2之汲極係與該電 容器Chi之正極相連接，其源極係與該功率開關Q1之汲極相連接，該功率開關 Q1之源極則連接至該電容器Cin之負極，俾該電容器Ciii可提供一穩定之輸入 電壓予一變壓器使用。該變壓器主要係用以儲存及釋放電能，其上設有一初級繞 組Np及二次級繞組Ns卜Ns2，其電感量分別爲Lp及Ld、Ls2，該等纖&± 之標記如第7圖所示·，該初級繞組Np之一端係與一平衡電容Cb之負極相連接， 其另端係透過一輔助電感La連接至該二功率開關Ql、Q2間之線路，該電容Cb 之正極則係與該功率開關Q2之汲極相連接，在該實施例中，該初級繞組Np及 輔助電感La間之線路係藉二極體D4及D3，分別連接至該功率開關Q2之汲極 及Q1之源極，俾該二極體D4(或D3)可分別配合該功率開關Q2(或Q1)，在該 電路發生振鈴現象時，可令該輔助電感La上之電流L立刻被功率開關Ω2與二 極體D4(或功率開關Q1與二極體D3)—起短路，以終止該振鈴現象；該二次級 繞組Nsl、Ns2之一端髓接至一輸出電壓濾波電容器Co之負極，其另端貝盼 別與二極體Dl、D2之正端相連接，該等二極體Dl、D2之負端則透過一電感Lo， 與該電容器Co之正極相連接，俾該電容器Co可讎一穩定之直流輸出電壓V〇 予輸出端上所跨接之負載。 本發明爲凸顯前述振鈴現象所造成之影響，可先自第7圖所示之實施例中， 除去用來短路電感器La之兩個二極體D3與EM，俟該電路工作穩定後，再利用 8 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） 501334 A7 B7 五、發明說明（8) (請先閱讀背面之注音心事項再填寫本頁) 一不波器，量測其電壓及電流之波开多圖’如第8圖所示，由該等波形圖可輕易得 知，振鈴現象係出現在時間《與t8後。嗣，再將該等二極體D3與D4裝回原位 置’在相同測量點所測得之電壓與電流波形圖’則如第9圖所示，由該等波开多圖 可知，在時間t3與t8後，雖開始仍發生振鈴現象，惟，到時間料IS t9時，即 被箝制住，直到時間t5與tlO始再出現很輕微之餘振。由此可知，本發明針對該 實施例中會產生振盪之L-C電路，利用二個二極體，將其電感上之電流予以短 路，即可箝制住其電容上之電壓，並制止其產生振盪，有_免#生振鈴現象。 本發明爲具體說明該實施例中該等功率開關Q1和Q2在各別導通時，能分 別與該二個二極體D3和D4相互作用，以箝制住振鈴之原理，特將第9⑷圖所 示之波形圖放大並區分成10個時段，參閱第9(b)圖所示，並於第1〇圖中，分別 顯Tpc在該10個時段之等效電路圖，在該等電路圖中，粗線部份代表電路中正在 工作之線路，細線部份則代表電路中未工作之線路，虛線部份代表電路在可被零 電位導通時線路之變化狀態，茲謹就各該時段下，該等電路之行爲，詳細說明如 下： (1) tio〜tl時段： 經濟部智慧財產局員工消費合作社印製 參閱第10-1⑻圖所不之等效電路，該時段與前一時段均係在傳送能量。在 該時段內，功率開關Q1與二極體D1係呈導通狀態，電流由輸入端Vin之正端 流入，經平衡電容Cb、初級繞組Np、輔助電感La及功率開關以後，流回輸 入端Vhi之負端；此時，在初級側之平衡電容Cb與輔助電感u被充電，在次 級側之電感Lo與電容Co亦被充電。 (2) tl〜t2時段： 參閱第10-l(b耀所不之等效電路，該時段係形成功率開關Q2可被零電位 導通機會之共振期。在時間tl時，功率開關Q1被開路，輔助電感La及變壓器 初級側之等效電感LNp將與功率開關Ql、Q2上之寄生電容Cqi、cQ2形成—L· 9 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） 501334 經濟部智慧財產局員工消費合作社印製 A7 B7 五、發明說明（0) C共振槽(L-C tank)，並以時間tl時輔助電感La上之電流iLa，爲共振之起始電 流，分別開始向寄生電容CQ1與CQ2進行充電，此一共振，將令功率開關Q2獲 得零電位切換之可能。當初級繞組Np上之電壓減爲零時，二極體D2開始導通， 與還在導通中之二極體D1相互作用，對變壓器之次級繞組形成了短路狀態，嗣， 由於輔助電感La之幫助，寄生電容CQ1與CQ2才能持續被充電，俟電容CQ1上 之電壓Vds高過Viii時，寄生二極體DQ2被導通，即形成了功率開關Q2可被零 電位導通之機會。 (3)t2〜t3時段： 參閱第10-2(a)圖所示之等效電路，該時段係輔助電感La上電流之轉向 期。在該時段內，二極體D1與D2均處於導通狀態，因此，初級繞組Np上並 無電壓，此時，由於寄生二極體DQ2與功率開關(J2均已導通，使得輔助電感La 上之電壓等於電容Cb之電壓Vcb，電流込之斜率即爲-Vcb/La，當該電流iLa 還爲正値時，表示電容Cb正被充電，當電流i,a變爲負値時，即表示電容Cb開 始被放電。 (4”3〜14時段： 參閱第l〇-2(b)圖所示之等效電路，該時段係上讎鈴(ringing in upper side) 之形成期。在時間t3時，由於電容Cb之放電，初級繞組Np上之《Μ由零轉負， 使二極體D1被逆偏而截止，輔助電感La遂與變壓器初級側之雜散電容CNp，形 成一共振槽，此時，若沒有二極體D4，雜散電容CNp將被充放電，而出現振鈴 現象。 (5)t4〜t5時段： 參閱第l〇-3(a)圖所示之等效電路，該時段係上臂振鈴電流之短路期。在該 時段內，自二極體D1被截止開始，電壓Vd3就急速上升，俟電壓Vd3高過輸 入端電壓Vin時(即時間t4時），二極體D4被導通，輔助電感La上之電流立刻 10 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） (請先閱讀背面之注意事項再填寫本頁) 訂·———· 501334 A7 _B7_ 五、發明說明（ID) (請先閱讀背面之注意事項再填寫本頁) 被功率開關Q2與二極體D4 —起短路，振鈴現象即因而停止，實現了上臂無振 鈴(ring free in upper side)之目標；俟時間t5時，由於二極體D4上之電流，已 不足以再令二極體D4導通，故，嗣後，輔助電感La上之倉gM只夠形成極爲輕 微之餘振，不致對電路構成影響。 (6) t5〜t6時段： 參閱第10-3(b)圖所示之等效電路，該時段與前一時段均係能量傳送期。在 該時段內，功率開關Q2與二極體D2均處於導通狀態，電流由電容Cb之正端 流出，經功率開關Q2、輔助電感La及初級繞組Np後，流回電容Cb之負端， 此時，電容Cb上之能量將經由變壓器交連到次級側電路，並經過二極體D2， 醒感Lo與電容Co進行充電。 (7) t6〜t7時段： 經濟部智慧財產局員工消費合作社印製 參閱第10-4⑻圖所示之等效電路，該時段係形成功率開關Q1可被零電位 導通機會之共振期。在時間t6時，功率開關Q2被開路，輔助電感La與變壓器 初級繞組上之等效電感LNp將與寄生電容CQ1、CQ2形成一 L-C共振槽(L-C tank)， 並以時間t6時輔助電感上之電流iLa，爲共振之起始電流，分別開始對寄生 電容CQ1與（:卬進行放電，此一共振，將令功率開關Q1因而獲得零電位切換之 可能性。當初級繞組Np上之電壓減爲零時，二極體D1開始導通，與還在導通 中之二極體D2相互作用，對變壓器之次級繞組形成了短路狀態，嗣，由於輔助 電感La之幫助，寄生電容CQ1與CQ2才能持續被放電，俟寄生電容CQ1上之電 壓Vds低過零電位時，寄生二極體DQ1被導通，即形成了功率開關Q1可被零電 位導通之機會。 (8) t7〜t8時段： 參閱第1〇_4⑻圖所示之等效電路，該時段係輔助電感La上電流iLa之轉向 期。在該時段內，二極體D1與D2均處於導通狀態，因此，初級繞組Np上並 11 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） 501334 經濟部智慧財產局員工消費合作社印製 A7 B7______ 五、發明說明（11) 無電壓，此時，由於寄生二極體DQ1與功率開關Q1均已導通，使得輔助電感La 上之電壓等於輸入端電壓Vin與電容Cb上電壓Vcb間之差Vin-Vcb ’電流iLa 之斜率即爲（Vin-Veb)/La，當該電流iLa還爲負値時，表示電容Cb正被放電， 當電流iLa變爲正値時，即表示電容Cb開始被充電。 (9)t8 -19 時段： 參閱第10-S⑷圖所示之等效電路，該時段係下臂振鈴(ringing in lower side) 之形成期。在時間t8時，由於電容Cb被充電，初級繞組Np上之驅由零轉正， 使二極體D2被逆偏而截止，輔助電感La遂與變壓器初級側之雜散電容CNp，形 成一共振槽，此時，若沒有二極體D3，雜散電容CNp將被充放電，而出現振鈴 現象。 (10)t9 - tlO 時段： 參閱第10-5⑼圖所示之等效電路，該時段係下臂振鈴電流之短路期。在該 時段內，自二極體D2被截止開始，電壓Vd3就急速下降，俟電壓Vd3低過零 電位(即時間t9時），二極體D3就被導通，輔助電感La上之電流立刻被功率開 關Q1與二極體D3 —起短路，振鈴現象即因而停止，實現了下臂無振鈴(ring free in lower side)之目標；俟時間tlO時，由於二極體D3上之電流，已不足以再令 二極體D3導通，故，嗣後，輔助電感La上之能量只夠形成極爲輕微之餘振， 而不致tfTO構成影響。 由上述說明可知，該實施例在t4〜t5時段時，可令上臂之振鈴電流被短路， 在t9〜tlO時段時，可令下臂之振鈴電流被短路，如此，該實施例即可在無振鈴 之情況下，順利進行零電位切換之動作° 此外，由前述說明可知，一般功率轉換器在應用零電位切換技術時所產生 之振鈴麵，可槪分爲下臂振鈴及上臂振鈴兩種，本發明再就抑制該二振鈴效應 之原理及其優點，配合第11〜14圖所示之等效電路，詳細分析說明如下： 12 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公爱） """ 4 i U.--U----------^--------- (請先閱讀背面之注音？事項再填寫本頁) 501334 A7 _B7_ 五、發明說明（1¾ (a)下臂振鈴被抑制之原理及其優點： (1) 在t7-t8時段內： (請先閲讀背面之注意事項再填寫本頁) 參閱第11⑻圖所示之等效電路，該時段係輔助電感La上電流ita之轉 向期。在該時段內，自時間t7開始，變壓器被二極體D2與D1短路，輔助 電感La上之電流L急速向上升，俟時間t7a時，電流iu由負値轉成正値， 俟時間爲t8後，該電流iLa由於二極體D2之開路，而改以較緩和之斜率，繼 續上升。 (2) t8-19 時段： 經濟部智慧財產局員工消費合作社印製 參閱第11(b)圖所示之等效電路，該時段係下臂振鈴之起始期。茲爲方 便說明，請參閱第12圖所示之下臂振鈴箝制電路之電壓與電流波形圖，其中 輔助電感La上之電流L可分成兩部份，標示爲iP者係流經變壓器初級側之 電流部份，其大小僅與負載有關，並不影響振鈴之行爲；標示爲iCs與iD3者 係分別爲流經該初級側之雜散電容Cs及二極體D3之電流部份，其大小與負 載無關，僅與振鈴有關。當時間爲t8時，二極體D2開路，變壓器之短路解 除，輔助電感La與變壓器初級側上之雜散電容Cs，形成L-C共振槽，並以 啊，-FO，FfC㈣爲起始條件，開始共振，由於雜散電容Cs開始被 充電，二極體D3上之電壓Vd3急速下降，俟降到負値時，二極體D3被導 通，輔助電感La上之共振電流立刻被二極體D3與功率開關Q1短路，制止 了將要發生之振鈴。在時間爲t9時，雜散電容Cs與輔助電感La上所累積 之能量相同，均爲： E(cs) = E(ia) = ^Cs(Vin - Vcbf-------------(1) (3) t9 - tlO 時段： 參閱第11(c)圖所示之等效電路，在該時段內，下臂振鈴被制止。若振鈴 13 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） 期334 A7 B7 五、發明說明(13) 未被二極體D3制止，且共振無阻尼(damping ratio = 0)時，變壓器初級個1上 之雜散電容Cs之電壓將可被充滿至Vin-VCb之2倍，令雜散電容Cs累積到 最大之能量，其讎： E(cs) = ~Cs[2(Vin^Vcb)]2-------------(2) 又，若振鈴未被二極體D3制止，但電路上加有RC阻尼電路(RC simbber dmiit)時，雜散電容Cs上所累積到之最大能量，應被RC阻尼電路耗盡， 才能完全免除振鈴之影響。在下臂振鈴被二極體D3制止後，輔助電感La在 時間t9時所累積到之能量，將在t9〜tlO時段內，被二極體D3耗盡。由此 推算，由於下臂振鈴被制止，電路之耗損將會減少，其所減少之耗損爲公式(2) 減去公式⑴，得到·· 減少之耗損=- Κα〇2------------(3) 由以上之分析可知，該實施例在加上本發明之無振鈴方法於其下臂後， 可減少4分之3由於下臂振鈴所帶來之能量損耗。 (b)上臂振鈴被抑制之原理與優點： 上臂振鈴被抑制之原理基本上與下臂振鈴被抑制之原理完全相同，但所 節省之能量卻不相同，兹詳細說明如下： (1) t2-13 時段： 參閱第13⑻圖所示之等效電路，該時段係輔助電感La上電流i,a之轉 向期。在該時段內，自時間t2開始，變壓器被二極體D1與D2短路，輔助 電感La上之電流iu急速下降，俟時間t2a時，電流由正値轉成負値，俟時 間爲t3後，該電流由於二極體D1開路，而改以較緩和之斜率，繼續下降。 (2) t3 -14 時段： 14 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） <請先閱讀背面之注意事項再填寫本頁)Voltage-Switching Full-Wave Converter) ". In this embodiment, the input filter capacitor Cm is printed by the input consumer employee cooperative of the Intellectual Property Bureau of the Ministry of Economic Affairs. The positive and negative electrodes of the capacitor Cin are connected across the positive and negative electrodes of the input voltage Vin, and a series connection is connected in parallel. Power switch Q1, Q2, the drain of the power switch Q2 is connected to the positive electrode of the capacitor Chi, its source is connected to the drain of the power switch Q1, and the source of the power switch Q1 is connected to the The negative electrode of the capacitor Cin, the capacitor Ciii can provide a stable input voltage to a transformer. This transformer is mainly used to store and release electric energy. It has a primary winding Np and a secondary winding Ns and Ns2. The inductances are Lp and Ld and Ls2. The marks of these fibers & ± are shown in Figure 7. As shown, one end of the primary winding Np is connected to the negative pole of a balanced capacitor Cb, and the other end is connected to the line between the two power switches Q1 and Q2 through an auxiliary inductor La, and the positive pole of the capacitor Cb is It is connected to the drain of the power switch Q2. In this embodiment, the line between the primary winding Np and the auxiliary inductor La is connected to the drain of the power switch Q2 and the Q1 via diodes D4 and D3, respectively. Source, the diode D4 (or D3) can cooperate with the power switch Q2 (or Q1) respectively. When ringing occurs in the circuit, the current L on the auxiliary inductor La can be immediately switched by the power switch Ω2 and two. The pole D4 (or the power switch Q1 and the diode D3) is short-circuited to terminate the ringing phenomenon; one end of the secondary winding Nsl and Ns2 is connected to the negative pole of an output voltage filtering capacitor Co, and the other end thereof is Don't connect with the positive ends of the diodes D1, D2, the negative of the diodes D1, D2 Is an inductor through the Lo, is connected to the positive electrode of the capacitor Co, the capacitor Co may serve a stabilizing Chou V〇 I of the DC output voltage across the load on the output terminal. In order to highlight the influence caused by the aforementioned ringing phenomenon, the present invention can remove the two diodes D3 and EM used to short-circuit the inductor La from the embodiment shown in FIG. 7 after the circuit works stably, and then Use 8 paper sizes to apply Chinese National Standard (CNS) A4 specifications (210 X 297 mm) 501334 A7 B7 V. Description of the invention (8) (Please read the phonetic notes on the back before filling this page) Measure the voltage and current wave graphs as shown in Figure 8. From these waveform graphs, it can be easily known that the ringing phenomenon occurs after time "and t8. Alas, the diodes D3 and D4 are put back into their original positions. 'Voltage and current waveforms measured at the same measurement point' are shown in Figure 9. From these graphs, it can be seen that in time, After t3 and t8, the ringing phenomenon still started, but when the time is expected to be t9, it will be clamped, and there will be a slight aftershock until time t5 and t10. It can be known that the present invention is directed to the LC circuit that generates oscillation in this embodiment. By using two diodes to short-circuit the current on its inductor, the voltage on its capacitor can be clamped and its oscillation can be prevented. Have _ free # ringing phenomenon. The present invention specifically illustrates that the power switches Q1 and Q2 in this embodiment can interact with the two diodes D3 and D4 respectively when they are turned on to clamp the ringing principle. The waveform diagram shown is enlarged and divided into 10 periods. Refer to Fig. 9 (b), and in Fig. 10, the equivalent circuit diagrams of Tpc during the 10 periods are shown. In these circuit diagrams, the rough The line part represents the working line in the circuit, the thin line part represents the non-working line in the circuit, and the dashed line part represents the change state of the line when the circuit can be turned on by the zero potential. The behavior of the circuit is described in detail as follows: (1) tio ~ tl period: printed by the Consumer Cooperatives of the Intellectual Property Bureau of the Ministry of Economic Affairs, refer to the equivalent circuit shown in Figure 10-1. This period and the previous period are all transmitting energy. . During this period, the power switch Q1 and the diode D1 are in a conducting state, and the current flows from the positive terminal of the input terminal Vin, and flows back to the input terminal Vhi after passing through the balancing capacitor Cb, the primary winding Np, the auxiliary inductor La, and the power switch. At this time, the balancing capacitor Cb and auxiliary inductor u on the primary side are charged, and the inductance Lo and capacitor Co on the secondary side are also charged. (2) Period from tl to t2: Refer to Section 10-1 (b), which is equivalent to the equivalent circuit. This period forms a resonance period when power switch Q2 can be turned on by zero potential. At time t1, power switch Q1 is opened. , The equivalent inductance LNp of the auxiliary inductor La and the transformer primary side will be formed with the parasitic capacitances Cqi and cQ2 on the power switches Ql and Q2—L · 9 This paper size applies to the Chinese National Standard (CNS) A4 specification (210 X 297 mm) 501334 A7 B7 printed by the Consumer Cooperatives of the Intellectual Property Bureau of the Ministry of Economic Affairs 5. Description of the invention (0) C tank (LC tank), and the current iLa on the inductor La at time t1 is the starting current of the resonance, respectively Began to charge the parasitic capacitors CQ1 and CQ2. This resonance will make the power switch Q2 obtain the potential of zero potential switching. When the voltage on the primary winding Np is reduced to zero, the diode D2 starts to conduct, and it is still conducting. Diode D1 interacts to form a short circuit on the secondary winding of the transformer. Alas, parasitic capacitors CQ1 and CQ2 can be continuously charged due to the help of the auxiliary inductor La. When the voltage Vds on the capacitor CQ1 is higher than Viii, the parasitic Diode D Q2 is turned on, which means that the power switch Q2 can be turned on by zero potential. (3) Period t2 ~ t3: Refer to the equivalent circuit shown in Figure 10-2 (a). This period is the current on the auxiliary inductor La. Turning period. During this period, diodes D1 and D2 are both on, so there is no voltage on the primary winding Np. At this time, since the parasitic diode DQ2 and the power switch (J2 are both on, the auxiliary The voltage on the inductor La is equal to the voltage Vcb of the capacitor Cb. The slope of the current 込 is -Vcb / La. When the current iLa is still positive 値, it means that the capacitor Cb is being charged. When the current i, a becomes negative 値, It means that the capacitor Cb is starting to be discharged. (4 "3 ~ 14 period: Refer to the equivalent circuit shown in Figure 10-2 (b), this period is the period of ringing in upper side). At time t3, due to the discharge of capacitor Cb, "M" on the primary winding Np turns from zero to negative, so that the diode D1 is reverse-biased and cut off, and the auxiliary inductance La and the stray capacitance CNp on the primary side of the transformer form a At this time, if there is no diode D4, the stray capacitance CNp will be charged and discharged, and ringing will occur. (5 ) t4 ~ t5 period: Refer to the equivalent circuit shown in Fig. 10-3 (a), this period is the short-circuit period of the ringing current of the upper arm. During this period, the voltage Vd3 starts from the time when the diode D1 is turned off. When the voltage Vd3 rises higher than the input terminal voltage Vin (that is, time t4), the diode D4 is turned on, and the current on the auxiliary inductor La immediately 10 This paper size applies the Chinese National Standard (CNS) A4 specification (210 X 297 mm) (Please read the precautions on the back before filling this page) Order · ———— · 501334 A7 _B7_ V. Invention Description (ID) (Please read the precautions on the back before filling this page) Power switch Q2 Short-circuiting with diode D4, the ringing phenomenon stops, thus achieving the goal of ring free in upper side; at time t5, due to the current on diode D4, it is not enough to make the second The pole body D4 is turned on. Therefore, after a while, the bin gM on the auxiliary inductor La is only enough to form a very slight aftershock, which will not affect the circuit. (6) Period t5 ~ t6: Refer to the equivalent circuit shown in Figure 10-3 (b). This period and the previous period are both energy transfer periods. During this period, the power switch Q2 and the diode D2 are both on, and the current flows from the positive terminal of the capacitor Cb. After the power switch Q2, the auxiliary inductor La, and the primary winding Np, it flows back to the negative terminal of the capacitor Cb. At this time, the energy on the capacitor Cb will be connected to the secondary-side circuit via the transformer and passed through the diode D2, and the awake Lo and the capacitor Co will be charged. (7) Period t6 ~ t7: Printed by the Consumer Cooperative of Intellectual Property Bureau of the Ministry of Economic Affairs Refer to the equivalent circuit shown in Figure 10-410. This period forms a resonance period when power switch Q1 can be turned on by zero potential. At time t6, the power switch Q2 is opened, the auxiliary inductance La and the equivalent inductance LNp on the primary winding of the transformer will form an LC tank with the parasitic capacitances CQ1 and CQ2, and the auxiliary inductance will be added at time t6. The current iLa, the starting current of the resonance, starts to discharge the parasitic capacitances CQ1 and (: 卬) respectively. This resonance will make the power switch Q1 thus obtain the possibility of zero potential switching. When the voltage on the primary winding Np is reduced to zero At this time, the diode D1 starts to conduct, and interacts with the diode D2 which is still conducting, forming a short circuit state to the secondary winding of the transformer. Alas, the parasitic capacitances CQ1 and CQ2 can be continuously maintained by the help of the auxiliary inductance La. Discharge, when the voltage Vds on the parasitic capacitor CQ1 is lower than the zero-crossing potential, the parasitic diode DQ1 is turned on, forming a chance that the power switch Q1 can be turned on by the zero potential. (8) t7 ~ t8 period: refer to Section 1〇 _4 The equivalent circuit shown in the figure, this period is the turning period of the current iLa on the auxiliary inductor La. During this period, the diodes D1 and D2 are both on, so the primary winding Np is bound to 11 paper sizes. Printed in Chinese National Standard (CNS) A4 (210 X 297 mm) 501334 Printed by A7 B7______ of the Consumer Cooperatives of the Intellectual Property Bureau of the Ministry of Economic Affairs 5. Description of the invention (11) At this time, due to parasitic diode DQ1 and power The switch Q1 has been turned on, so that the voltage on the auxiliary inductor La is equal to the difference between the input terminal voltage Vin and the voltage Vcb on the capacitor Cb Vin-Vcb 'The slope of the current iLa is (Vin-Veb) / La. When the current iLa is also When it is negative, it means that the capacitor Cb is being discharged, and when the current iLa becomes positive, it means that the capacitor Cb is being charged. (9) t8 -19 period: refer to the equivalent circuit shown in Figure 10-S, This period is the formation period of ringing in lower side. At time t8, because the capacitor Cb is charged, the drive on the primary winding Np turns from zero to positive, so that the diode D2 is reverse biased and cut off, and the auxiliary inductance is cut off. La then forms a resonance slot with the stray capacitance CNp on the primary side of the transformer. At this time, if there is no diode D3, the stray capacitance CNp will be charged and discharged and ringing will occur. (10) t9-tlO period: see The equivalent circuit shown in Fig. 10-5, this period is The short-circuit period of the arm ringing current. During this period, since the diode D2 is turned off, the voltage Vd3 drops rapidly, and when the voltage Vd3 is lower than the zero crossing potential (that is, at time t9), the diode D3 is turned on to assist The current on the inductor La was immediately short-circuited by the power switch Q1 and the diode D3, and the ringing phenomenon stopped, thereby achieving the goal of ring free in lower side. At time t10, due to the diode The current on D3 is not enough to turn on the diode D3. Therefore, after that, the energy on the auxiliary inductor La is only enough to form a very slight aftershock without tfTO. It can be known from the above description that in this embodiment, the ringing current of the upper arm can be short-circuited during the period from t4 to t5, and the ringing current of the lower arm can be short-circuited during the period from t9 to t10, so that this embodiment can In the case of ringing, the operation of zero potential switching is smoothly performed. In addition, from the foregoing description, it can be known that the ringing surface generated by general power converters when applying zero potential switching technology can be divided into two types: lower arm ringing and upper arm ringing. In the present invention, the principle and advantages of suppressing the two-ringing effect are matched with the equivalent circuit shown in Figs. 11-14, and the detailed analysis and description are as follows: 12 This paper size applies the Chinese National Standard (CNS) A4 specification (210 X 297) Public love) " " " 4 i U .-- U ---------- ^ --------- (Please read the note on the back? Matters before filling out this page) 501334 A7 _B7_ 5. Description of the invention (1¾ (a) The principle of the lower arm ringing is suppressed and its advantages: (1) During the period of t7-t8: (Please read the precautions on the back before filling this page) Refer to Figure 11⑻ Equivalent circuit shown, this period is the turning period of the current ita on the auxiliary inductor La. At this time During the period, starting from time t7, the transformer is short-circuited by the diodes D2 and D1, and the current L on the auxiliary inductance La rises rapidly. At time t7a, the current iu changes from negative 値 to positive 値. After 俟 time t8, Due to the open circuit of the diode D2, the current iLa continues to rise with a gentler slope. (2) Time period t8-19: Printed by the Consumer Cooperative of the Intellectual Property Bureau of the Ministry of Economic Affairs, see figure 11 (b) Equivalent circuit, this period is the beginning of the lower arm ringing. For convenience, please refer to the voltage and current waveforms of the lower arm ringing clamp circuit shown in Figure 12, where the current L on the auxiliary inductor La can be divided into two The part marked as iP is the current flowing through the primary side of the transformer. Its size is only related to the load and does not affect the behavior of ringing. The parts marked as iCs and iD3 are stray capacitances flowing through the primary side. The current part of Cs and diode D3 has nothing to do with the load, only the ringing. When the time is t8, the diode D2 is open, the short circuit of the transformer is released, the auxiliary inductance La and the stray on the primary side of the transformer Capacitor Cs, forming an LC resonance slot, and With -FO, FfC㈣ as the initial conditions, resonance starts. As the stray capacitance Cs starts to be charged, the voltage Vd3 on the diode D3 drops rapidly. When 俟 falls to negative 値, the diode D3 is turned on and assists. The resonance current on the inductor La is immediately shorted by the diode D3 and the power switch Q1, which prevents the ringing that will occur. At time t9, the stray capacitance Cs and the energy accumulated on the auxiliary inductor La are the same, both are: E (cs) = E (ia) = ^ Cs (Vin-Vcbf ------------- (1) (3) t9-tlO period: see etc. as shown in Figure 11 (c) Effective circuit, during this period, the lower arm ringing is stopped. If ringing 13 this paper size applies Chinese National Standard (CNS) A4 specification (210 X 297 mm) Period 334 A7 B7 V. Description of the invention (13) Not stopped by diode D3 and resonance is not damped (damping ratio = 0 ), The voltage of the stray capacitance Cs on the primary element 1 of the transformer can be fully charged to twice the Vin-VCb, so that the stray capacitance Cs can accumulate the maximum energy, where: E (cs) = ~ Cs [2 (Vin ^ Vcb)] 2 ------------- (2) Also, if the ringing is not stopped by diode D3, but an RC damping circuit (RC simbber dmiit) is added to the circuit, The maximum energy accumulated in the stray capacitance Cs should be depleted by the RC damping circuit in order to completely avoid the effect of ringing. After the ringing of the lower arm is stopped by the diode D3, the energy accumulated by the auxiliary inductor La at time t9 will be depleted by the diode D3 within the period of t9 ~ t10. From this calculation, because the lower arm ringing is stopped, the loss of the circuit will be reduced. The reduced loss is the formula (2) minus the formula ⑴ to get the reduced loss =-Κα〇2 ------ ------ (3) From the above analysis, it can be seen that after adding the non-ringing method of the present invention to its lower arm, this embodiment can reduce the energy loss caused by the lower arm ringing by three-quarters. (b) The principle and advantages of suppressing the ringing of the upper arm: The principle of suppressing the ringing of the upper arm is basically the same as the principle of suppressing the ringing of the lower arm, but the energy saved is different. Details are as follows: (1) t2- Period 13: Refer to the equivalent circuit shown in Figure 13⑻. This period is the turning period of the current i, a on the auxiliary inductor La. During this period, starting from time t2, the transformer is short-circuited by diodes D1 and D2, and the current iu on the auxiliary inductance La drops rapidly. At time t2a, the current changes from positive to negative 値, and after time t3, Since the current of the diode D1 is open, the current is reduced to a more gentle slope and continues to decrease. (2) t3 -14 period: 14 This paper size applies to China National Standard (CNS) A4 (210 X 297 mm) < Please read the precautions on the back before filling this page)
-----I I 訂 *---I I 經濟部智慧財產局員工消費合作社印製 501334 經濟部智慧財I局員工消費合作社印製 A7 B7 五、發明說明（14) 麵办_麻之等效職’該時段爲振鈴起始期。賴方讎明， 請麵第關所示之上髓鈴箝制腦之電流波形圖，其中輔廳感 La上之飢可分成兩部份，標示爲賴經變壓_及側之職部份， 其大小僅與負載有關’並不腿鈴之行爲;檩示爲ics與‘之電流部份， 其大賴負載無關，僅與振鈴有關。當時間爲t3時，‘極體：開路口,國 器之短路解除’輔助電感La與變壓器初級側上之雜散電容&，形成共 臓,並以啊.，狗功爲起始條件，開始共振，由_散電容& 開始被充電，二極體D3上之顆Vd3急速往上升，升到輸入電壓Vin以上 時’ 一極體D4被導通，輔助電感La上之共振電流立亥撇二極體D4與功率 開關Q2短路’制止了將要發生之振鈴。在時間爲抖時，雜散電容cs與輔 助電感La上所累積之能量相同，均爲： E(Cs) = E(La)^^VCb2-------------(4) (3)t4 -15 時段： 參閱第13(c)圖所示之等效電路，在該時段內，上臂振鈴被制止。若振鈴 未被D4給制止，且共振無阻尼(damoing ratio = 0)時，變壓器初級側上之雜 散電容Cs之電壓將可被充滿至VCb之2倍，令雜散電容Cs累積到最大之 能量，其麵： E(cs) = ICsVcb1---------.----(5) 又，若振鈴未被二極體D4制止，但電路上加有RC阻尼電路(RC snubber circuit)時，雜散電容Cs上所累積到之最大能量，應被RC阻尼讎嫌盡， 才能完全免除振鈴的影響。在上臂振鈴被二極體04制止後’輔助電感La在 時間t4所累積到之能量，將在t4〜t5時段內，被二極體D4耗盡。由此推算， 15 本紙張尺度適用中國國家標準(CNS)A4規格（210 X 297公釐） ,---r I.---rile s--------^—------ (請先閱讀背面之注音？事項再填寫本頁) 501334 經濟部智慧財產局員工消費合作社印製 A7 B7 五、發明說明 (15) 由於上臂振鈴被制止，電路之耗損將會減少，其所減少之耗損爲公式(5)減去 公式⑷，得到： 減少之耗損=鲁GFa>2------------⑹ 由以上之分析可知，該實施例在加上本發明之無振鈴方法於其上臂後，可減 少4分之3由於上臂振鈴所帶來之能量損耗。 合計公式(2)與式(5)，即爲上下臂振鈴一起帶來之總能量損耗： 振鈴總損失=2&[(% - Fa)2 +Fa2]------------⑺ 合計公式(1)與式(4)，即爲上下臂振鈴均被抑制時，帶來之總能量損耗： 無振鈴總損失^- Fa〇2 + Fa2]------------⑻ 在該實施例中，若該變壓器初級側上之雜散電容Cs爲lOOpF，輸入電壓Vin 爲400V，電容Cb上之電壓VCb爲100V，則該功率轉換器的振鈴是以RC阻 尼電路來消耗時，其總會gi損耗爲20微焦耳(UJ)，無振鈴時之能量損耗爲5·0微 焦耳 > 故無振鈴時每次減少之能量耗損爲15微焦耳 > 此時 > 若該功率轉換雛 ΙΟΟΚΗζ之頻率下工作，則RC阻尼電路之功率損耗爲2·0瓦，無振鈴時之功率 損耗爲〇·5瓦，故無振鈴時之功率耗損減少了 1.5瓦。又，若其工作頻率提高爲 200ΚΗΖ，則RC阻尼電路之功率損耗爲4.0瓦，無振鈴時之功率損耗爲1.0瓦， 故無振鈴時之功率耗損將減少3.0瓦。由此可知，振鈴所造成之損失，係隨電路 之工作頻率而遞增，此亦爲傳統功率轉換器之設計及製造業者，在設計其零電位 切換電路時，始終無法突破其最高工作頻率之重要原因，惟該項障礙在加入本發 明之無振鈴機制後，由於可有效降低因振鈴所造成之能量損耗，故可大幅提升零 16 本紙張尺度適用中國國家標準（CNS)A4規格（21(^ 297公釐） •f I .—-----I----------- (請先閱讀背面之注意事項再填寫本頁) 經濟部智慧財產局員工消費合作社印製 501334 A7 B7 五、發明說明（1β) 電位切換職之工作頻率及功率轉換器之功率密度。 參閱第15圖所示，爲本發明第7圖之實施例在效率上所獲致之成果，在該 實施例中輸入電壓Vin爲370V之直流電，輸出電壓v〇ut爲12V/5A，工作頻率 爲60KHz，主變壓器之初級繞組上之電感Lp爲1.2mH，漏感爲4·5ιιΗ，外加 輔助電感La爲35uH，其中第1條曲線係以RC阻尼電路來消減振鈴，因此效 率只達91%。第2條曲線係在相同於第1條曲線之工作條件下，改以加設可抑 制振鈴之二極體D3與D4來消除振鈴，由於沒有阻尼電路之消耗，其效率提升 至92°/。。第3條曲線係在相同於第2條曲線之工作條件下，由於無振鈴，故將 次級側之整流二極體’改用耐壓爲1〇〇伏，順向壓降Vf爲0.65伏之蕭基二極體， 其效率將因而再提升至94% 〇 參閱第16圖所示，爲本發明第7圖之實施例在電磁干擾雜訊上之成果，其 中上圖爲有振鈴時之頻譜，下圖爲無振鈴時之頻譜，在2·5ΜΗζ附近，有約6dB 之改善，事實上，2·5ΜΗζ大約就是振鈴之頻率，振鈴被抑制後，在頻譜上當然 就看不到該雜訊了。 在本發明之第二個具體實施例中，係將本發明之無振鈴零電位切換方法應 用至一半橋升壓順向式全波整流電路之設計中，參閱第17圖所示，在此可稱之 爲「半橋升壓順向式無振鈴零電位切換全波整流電路(Half-Bridge Boost-Forward Ring-Free Zero-Voltage-Switching Full-Wave Converter)」。在該實施例中，該 電路包括一輸人電壓濾波電容器Cm，該電容器Cm之正負極係跨接在一輸人電 壓Vin之正負極上，其上並聯有一組串接之功率開關Ql、Q2及一電容Cb，該 電容Cb之負極係與該電容Cin之正極相連接，其正極係與該功率開關Q2之汲 極相連接，該功率開關Q2之源極係與該功率開關Q1之汲極相連接，該功率開 關Q1之源極則連接至該電容器Cm之負極，俾該電容器Cin可提供一穩定之輸 17 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） ----I---------------"訂--------- (請先閱讀背面之注意事項再填寫本頁) 經濟部智慧財產局員工消費合作社印製 501334 A7 B7 五、發明說明 (17) 入電壓予一變壓器使用。該變壓器上設有一初級繞組Np及二次級繞組Nsl、Ns2， 該等繞組上之標記如第17圖所示；該初級繞組Np之一端係與該電容cb之負極 相連接，其另端係透過一輔助電感連接至該二功率開關Q1、Q2間之線路， 在該實施例中，該初級繞組Np及輔助電感La間之線路係藉二極體D4及D3， 分別連接至該功率開關Q2之汲極及Q1之源極，俾該二極體D4(或D3)可分別 配合該功率開關Q2(或Q1)，在該電路發生振鈴現象時，可令該輔助電感！^上 之電流込立刻被功率開關Q2與二極體D4(或功率開關Qi與二極體D3)一起短 路，以終止該振鈴現象；該二次級繞組Nsl、Ns2之電路連接方式則與第一個實 施例之次級側電路完全相同。 在本發明之第三個具體實施例中，係將本發明之無振鈴零電位切換方法應 用至一半橋順向式半波整流電路之設計中，參閱第18圖所示，在此可稱之爲「半 橋順向式無振鈴零電位切換半波整流電路(Half-Bridge Forward Ring_Free Zero-Voltage-Switching Half-Wave Converter)」。在該實施例中，該電路包括一輸 入電壓濾波電容器Cm，該電容器Chi之正負極係跨接在一輸入電壓Vin之正負 極上’其上並聯有一組串接之功率開關Ql、Q2，該功率開關Q2之汲極係與該 電容器Cin之正極相連接，其源極係與該功率開關Q1之汲極相連接，該功率開 關Q1之源極則連接至該電容器Cin之負極，俾該電容器Cm可提供一穩定之輸 入電壓予一變壓器使用。該變壓器上設有一初級繞組Np及一次級繞組Ns，該等 繞IBJl之標s己如第18圖所τκ ;該初級繞組Np之一端係與一電容Cb之負極相連 接.，其另端係透過一輔助電感La連接至該二功率開關Q卜Q2間之線路，該電 容Cb之正極則係與該功率開關q2之汲極相連接，在該實施例中，該初級繞組 Np及輔助電感La間之線謝系藉二極體D4，連接至該功率開關Q2之汲極，俾 該二極體D4可配合該功率開關q2，在該電路發生振鈴現象時，令該輔助電感u 上之電流iLa立刻被功率開關Q2與二極體D4 —起短路，以終止該振鈴現象；該 18 本紙張尺度適用中國國豕標準（CNS)A4規格（210 X 297公爱） ^ ： *---Μ---------11 -------— (請先閱讀背面之注意事項再填寫本頁) 經濟部智慧財產局員工消費合作社印製 501334 A7 B7____ 五、發明說明 (18) 次級繞組Ns之一端係依序分別連接至一一極體D2之正端及一輸出電壓濾波電 容器Co之負極，其另端則依序透過一二極體D1及一電感Lo，與該電容器c〇 之正極相連接，該二極體D2之負端則連接至該二極體D1及電容器Co間之線路。 由於，該實施例係利用半波整流，故其振鈴效應僅發生在D1被截止時，因此只 需加設該二極體D4，即可實現無振鈴之目的。 在本發明之第四個具體實施例中，係將本發明之無振鈴零電位切換方法應 用至一半橋升壓順向式半波整流電路之設計中，參閱第19圖所示，在此可稱之 爲「半橋升壓順向式無振鈴零電位切換半波整流纖(Half-Bridge Boost-Forward Ring-Free Zero-Voltage-Switching Half-Wave Converter)」。在該實施例中， 該電路包括一輸入電壓濾波電容器Cm，該電容器Cm之正負極係跨接在一輸入 電壓Vin之正負極上，其上並聯有一組串接之功率開關Ql、Q2及一電容Cb， 該電容Cb之負極係與該電容Cm之正極相連接，其正極係與該功率開關Q2之 汲極相連接，該功率開關Q2之源極係與該功率開關Q1之汲極相連接，該功率 開關Q1之源極則連接至該電容器Ciii之負極，俾該電容器Chi可提供一穩定之 輸入電壓予一變壓器使用。該變壓器上設有一初級繞組Np及一次級繞組Ns，該 等繞組上之標記如第19圖所示；該初級繞組Np之一端係與該電容Cb之負極相 連接，其另端係透過一輔助電感La連接至該二功率開關Q卜Q2間之線路，在 該實施例中，該初級繞組Np及輔助電感La間之線路係藉一二極體D4，連接至 該功率開關Q2之汲極，俾該二極體D4可配合該功率開關Q2，在該電路發生振 鈴現象時，可令該輔助電慼La上之電流込立刻被功率開關Q2與二極體D4 — 起短路，以終止該振鈴現象；該次級繞組Ns之電路連接方式則與第三個實施例 之次級側電路完全相同。由於該實施例係利用半波整流，故其振鈴效應僅發生在 D1被截止時，因此只需加設該二極體D4，即可實現無振鈴之目的。 在本發明之第五個具體實施例中，係將本發明之無振鈴零電位切換方法應 19 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） 會—丨丨i------裝*-------訂---------^9. (請先閱讀背面之注意事項再填寫本頁) 501334 A7 B7 五、發明說明(19) 用至一半橋返磁式切換電路之設計中，參閱第20圖所示，在此可稱之爲「半橋 返fe式無振鈴零電位切換電路(Half-Bridge Flyback Ring-Free Zero-Voltage Switching Converter)」〇在該實施例中，該電路包括一輸入電壓濾波電容器Cin， 該電容器Cin之正負極係跨接在一輸入電壓Vin之正負極上，其上並聯有一組 串接之功率開關Ql、Q2，該功率開關Q2之汲極係與該電容器Cin之正極相連 接，其源極係與該功率開關Q1之汲極相連接，該功率開關Q1之源極則連接至 該電容器Cin之負極，俾該電容器Cin可提供一穩定之輸入電壓予一變壓器T1 使用。該變壓器T1上設有一初級繼且Np及一次級^且Ns，該等繞組上之標記 如第20圖所示；該初級繞組Np之一端係與一電容Cb之負極相連接，其另端係 分別透過一輔助電感La及一二極體D3，連接至該二功率開關Ql、Q2間之線 路及該功率開關Q1之源極，在該實施例中，由於該初級繞組Np及輔助電感La 間之線路係藉該二極體D3，連接至該功率開關Q1之源極，故該二極體D3可配 合該功率開關Q1，在該電路發生振鈴現象時，令該輔助電感La上之電流立 刻被功率開關Q1與二極體D3 —起短路，以終止該振鈴現象；該次級繞組Ns之 一端係透過一二極體D1，與一輸出電壓濾波電容器Co之正極相連接，其另端則 與該電容器Co之負極相連接，俾該電容器Co可提供一穩定之直流輸出電壓v〇 予輸出端上所跨接之負載。由於，該實施例係利用半波整流，故其振鈴效應僅發 生在D1被截止時，因此只需加設該二極體D3，即可節見無振鈴之目的。 在本發明之第六個具體實施例中，係將本發明之無振鈴零電位切換方法應 用至半橋昇壓返磁式切換電路之設計中，參閱第21圖所示，在此亦可稱之爲「半 橋昇壓返磁式無振鈴零電位切換電路(Half-Bridge Boost-Flyback Ring-Free Zero-Voltage-Switching Converter)」。在該實施例中，該電路包括一輸入電壓 濾波電容器Cin，該電容器Cm之正負極係跨接在一輸人電壓Vin之正負極上， 其上並聯有一組串接之功率開關（Jl、Q2及一電容Cb，該電容Cb之負極係與 20 本紙張尺度適用中國國家標準（CNS)A4規格（210 x 297公釐） (請先閱讀背面之注意事項再填寫本頁) ----- 訂---------. 經濟部智慧財產局員工消費合作社印製 經濟部智慧財產局員工消費合作社印製 501334 A7 B7 五、發明說明 (20 _ ——. ...... 該電容Cin之正極相連接，其正極係與該功率開關Q2之汲極相連接，該功率開 關Q2之源極係與該功率開關Q1之汲極相連接，該功率開關Q1之源棚犍接 至該電容器Cin之負極，俾該電容器Cm可提供一穩定之輸入電壓予一變壓器使 用。該變壓器T1上設有一初級繞組Np及一次級繞組Ns，該等繞組上之標記如 第21圖所示：該初級繼且Np之一端係與一電容Cb之負極相連接，其另端係分 SiJ透過一輔助電感La及一二極體D3連接至該一功率開關Ql、Q2間之線路及 該功率開關Q1之源極，在該實施例中，由於該初級繞組Np及輔助電感La間 之線路係藉該二極體D3，連接至該功率開關Q1之源極，故該二極體D3可配合 該功率開關Q1，在該電路發生振鈴現象時，令該輔助電感La上之電流iLa立刻 被功率開關Q1與二極體D3 —起_，以終止該振鈴現象；該二次級繞組之電 路連接方式則與第五個實施例之次級側電路完全相同。由於’該實施例係利用半 波整流，故其振鈴纏僅發生在D1被截止時，因此只需加設該二極體D3，即可 實現無振鈴之目的。 據上所述，利用本發明之無振鈴零電位切換方法，可令該等功率轉換器在 高頻環境下，進行零電位切換作業’避免該輔助電感因該寄生振盪而產生異常 發熱之問題，有效降低功率損失’並有效減輕對次級側整流零件之耐壓額度 (reverse voltage rating)之要求，大幅提升其工作頻率及功率密度，並減少電磁 干擾之雜訊，及其功率開關所累積之熱能及所需散熱片之体積大小，令該等功率 轉換器易於通過國際電磁干擾之規範，且更易於被應用至各種小型化電子產品 之設計中。 以上所述，僅係本發明之較佳實施例，惟，本發明所主張之權利範圍，並 不局限於此，按凡熟悉該項技藝人士，依據本發明所揭露之技術內容，可輕易思 及之等效變化，均應屬不脫離本發明之保護範疇。 21 本紙張尺度適用中國國家標準（CNS)A4規格（210 X 297公釐） (請先閱讀背面之注意事項再填寫本頁) ▼裝------ 訂--------4_----- II Order * --- II Printed by the Consumer Cooperatives of the Intellectual Property Bureau of the Ministry of Economy 501334 Printed by the Consumer Cooperatives of the I Bureau of the Ministry of Economic Affairs A7 B7 V. Description of the invention (14) Face-to-face _ hemp equivalent This period is the beginning of the ringing. Lai Fang Mingming, please refer to the current waveform of the brain clamped on the brain as shown in the level. The hunger on the auxiliary hall La can be divided into two parts, which are marked as the part of Lai Jing's pressure and side. Its size is only related to the load. It is not the behavior of leg bells; it is shown as the current part of ics and '. It depends on the load and has nothing to do with ringing. When the time is t3, the 'pole body: the opening, the short circuit of the national device is lifted', the auxiliary inductor La and the stray capacitance on the primary side of the transformer form a common line, and ah. Began to resonate and start to be charged by _ bulk capacitor & Vd3 on diode D3 rises rapidly, when it rises above the input voltage Vin 'One pole D4 is turned on and the resonance current on the auxiliary inductor La stands The short circuit of diode D4 and power switch Q2 'suppresses the ringing that will occur. When the time is shaking, the energy accumulated on the stray capacitance cs and the auxiliary inductance La is the same, both are: E (Cs) = E (La) ^^ VCb2 ------------- ( 4) (3) t4 -15 period: Refer to the equivalent circuit shown in Figure 13 (c). During this period, the upper arm ringing is stopped. If the ringing is not stopped by D4 and the resonance is not damped (damoing ratio = 0), the voltage of the stray capacitance Cs on the primary side of the transformer can be fully charged to twice the VCb, so that the stray capacitance Cs is accumulated to the maximum Energy, its surface: E (cs) = ICsVcb1 ---------.---- (5) Also, if the ringing is not stopped by diode D4, but the circuit has an RC damping circuit (RC snubber circuit), the maximum energy accumulated on the stray capacitance Cs should be exhausted by the RC damping in order to completely avoid the effect of ringing. After the ringing of the upper arm is stopped by the diode 04, the energy accumulated by the auxiliary inductor La at time t4 will be depleted by the diode D4 within a period of t4 to t5. From this calculation, 15 paper sizes are applicable to the Chinese National Standard (CNS) A4 specification (210 X 297 mm), --- r I .--- rile s -------- ^ ----- -(Please read the phonetic on the back? Matters before filling out this page) 501334 Printed by the Consumer Cooperative of the Intellectual Property Bureau of the Ministry of Economic Affairs A7 B7 V. Description of the invention (15) Since the ringing of the upper arm is stopped, the circuit loss will be reduced, and its The reduced loss is the formula (5) minus the formula ⑷, and we get: Reduced loss = LuGFa> 2 ------------ 以上 From the above analysis, we can see that this embodiment adds this The invented non-ringing method can reduce the energy loss caused by the upper arm ringing by three-quarters after the upper arm. The sum of formula (2) and formula (5) is the total energy loss brought by the ringing of the upper and lower arms: total ringing loss = 2 & [(%-Fa) 2 + Fa2] ---------- --⑺ To sum up formulas (1) and (4), that is, the total energy loss caused when ringing of both the upper and lower arms is suppressed: no total ringing loss ^-Fa〇2 + Fa2] ------- ----- ⑻ In this embodiment, if the stray capacitance Cs on the primary side of the transformer is 100 pF, the input voltage Vin is 400V, and the voltage VCb on the capacitor Cb is 100V, the ringing of the power converter is When the RC damping circuit is used, the total gi loss is 20 microjoules (UJ), and the energy loss when there is no ringing is 5.0 microjoules. Therefore, the energy loss per reduction when there is no ringing is 15 microjoules. ≫ At this time > If the power converter works at a frequency of 100KΗζ, the power loss of the RC damping circuit is 2.0 watts, and the power loss without ringing is 0.5 watts, so the power loss without ringing is reduced by 1.5 watt. In addition, if the operating frequency is increased to 200KΗZ, the power loss of the RC damping circuit is 4.0 watts, and the power loss when there is no ringing is 1.0 watt, so the power loss when there is no ringing will be reduced by 3.0 watts. It can be seen that the loss caused by ringing increases with the operating frequency of the circuit. This is also the design and manufacturing of traditional power converters. When designing its zero-potential switching circuit, it cannot always break the importance of its maximum operating frequency. The reason is that, after adding the non-ringing mechanism of the present invention, this obstacle can effectively reduce the energy loss caused by ringing, so it can be greatly improved. 16 This paper standard is applicable to the Chinese National Standard (CNS) A4 specification (21 (^ 297 mm) • f I .—----- I ----------- (Please read the notes on the back before filling out this page) Printed by the Employees ’Cooperatives of the Intellectual Property Bureau of the Ministry of Economic Affairs 501334 A7 B7 V. Description of the invention (1β) The operating frequency of the potential switching function and the power density of the power converter. Refer to Fig. 15 for the results obtained in the efficiency of the embodiment of Fig. 7 of the present invention. In the example, the input voltage Vin is 370V DC, the output voltage vout is 12V / 5A, the operating frequency is 60KHz, the inductance Lp on the primary winding of the main transformer is 1.2mH, the leakage inductance is 4.5m, and the auxiliary inductance La is 35uH, of which One curve uses RC damping circuit to reduce the ringing, so the efficiency is only 91%. The second curve is under the same working conditions as the first curve, and the diodes D3 and D4 can be used to suppress ringing. To eliminate ringing, the efficiency is increased to 92 ° /. Because there is no consumption of the damping circuit. The third curve is under the same operating conditions as the second curve, because there is no ringing, so the secondary side rectifier diode The body is replaced with a Schottky diode with a withstand voltage of 100 volts and a forward voltage drop Vf of 0.65 volts, and its efficiency will be further increased to 94%. 〇 Refer to FIG. 16, which is the seventh diagram of the present invention The results of the embodiment on electromagnetic interference noise. The upper picture shows the spectrum when there is ringing, and the lower picture shows the spectrum when there is no ringing. There is an improvement of about 6dB in the vicinity of 2.5MΗζ. In fact, 2.5MΗζ is about It is the frequency of ringing. After the ringing is suppressed, of course, the noise will not be seen in the frequency spectrum. In the second specific embodiment of the present invention, the ringless zero-potential switching method of the present invention is applied to a half bridge In the design of step-up forward full-wave rectifier circuit, refer to Figure 17 It can be called "Half-Bridge Boost-Forward Ring-Free Zero-Voltage-Switching Full-Wave Converter" in this embodiment. In this embodiment In the circuit, the input voltage filtering capacitor Cm is connected. The positive and negative electrodes of the capacitor Cm are connected across the positive and negative electrodes of the input voltage Vin. A series of power switches Ql, Q2 and a capacitor Cb are connected in parallel. The negative electrode of the capacitor Cb is connected to the positive electrode of the capacitor Cin. The positive electrode is connected to the drain of the power switch Q2. The source of the power switch Q2 is connected to the drain of the power switch Q1. The power The source of the switch Q1 is connected to the negative electrode of the capacitor Cm. The capacitor Cin can provide a stable output. 17 This paper size applies to the Chinese National Standard (CNS) A4 specification (210 X 297 mm) ---- I- -------------- " Order --------- (Please read the notes on the back before filling out this page) Printed by the Consumer Cooperative of the Intellectual Property Bureau of the Ministry of Economic Affairs 501334 A7 B7 V. Description of the invention (17) The input voltage is used for a transformer. The transformer is provided with a primary winding Np and secondary windings Nsl and Ns2. The markings on these windings are shown in Figure 17; one end of the primary winding Np is connected to the negative electrode of the capacitor cb, and the other end is It is connected to the line between the two power switches Q1 and Q2 through an auxiliary inductor. In this embodiment, the line between the primary winding Np and the auxiliary inductor La is connected to the power switch Q2 through diodes D4 and D3, respectively. The drain and source of Q1, the diode D4 (or D3) can be matched with the power switch Q2 (or Q1) respectively. When the circuit is ringing, the auxiliary inductor can be made! The current 上 is immediately shorted by power switch Q2 and diode D4 (or power switch Qi and diode D3) to terminate the ringing phenomenon; the circuit connection of the secondary windings Nsl and Ns2 is the same as the first The secondary side circuits of one embodiment are identical. In the third specific embodiment of the present invention, the ring-free zero potential switching method of the present invention is applied to the design of a half-bridge forward half-wave rectifier circuit, as shown in FIG. 18, which may be referred to herein as It is a "Half-Bridge Forward Ring-Free Zero-Voltage-Switching Half-Wave Converter". In this embodiment, the circuit includes an input voltage filtering capacitor Cm. The positive and negative electrodes of the capacitor Chi are connected across the positive and negative electrodes of an input voltage Vin. A series of power switches Q1 and Q2 are connected in parallel. The drain of the switch Q2 is connected to the positive pole of the capacitor Cin, and the source is connected to the drain of the power switch Q1. The source of the power switch Q1 is connected to the negative pole of the capacitor Cin, and the capacitor Cm Can provide a stable input voltage for a transformer. The transformer is provided with a primary winding Np and a primary winding Ns, and the standards s of IBJ1 are as shown in FIG. 18; τκ; one end of the primary winding Np is connected to the negative electrode of a capacitor Cb, and the other end is An auxiliary inductor La is connected to the line between the two power switches Q2 and Q2, and the positive electrode of the capacitor Cb is connected to the drain of the power switch q2. In this embodiment, the primary winding Np and the auxiliary inductor La The interval wire is connected to the drain of the power switch Q2 through a diode D4. The diode D4 can cooperate with the power switch q2 to make the current on the auxiliary inductor u when the circuit is ringing. iLa was immediately short-circuited by power switch Q2 and diode D4 to terminate the ringing phenomenon; the 18 paper sizes are applicable to China National Standard (CNS) A4 (210 X 297 public love) ^: * --- Μ --------- 11 -------— (Please read the notes on the back before filling out this page) Printed by the Consumer Cooperatives of the Intellectual Property Bureau of the Ministry of Economic Affairs 501334 A7 B7____ V. Description of Invention (18 ) One end of the secondary winding Ns is sequentially connected to the positive end of a one-pole body D2 and an output voltage filter, respectively. The other end of the capacitor Co is connected to the positive electrode of the capacitor c0 in sequence through a diode D1 and an inductor Lo, and the negative end of the diode D2 is connected to the diode D1 and the capacitor. Co line. Since this embodiment uses half-wave rectification, its ringing effect only occurs when D1 is cut off, so only the diode D4 needs to be added to achieve the purpose of no ringing. In the fourth specific embodiment of the present invention, the ring-free zero potential switching method of the present invention is applied to the design of a half-bridge step-up forward half-wave rectifier circuit, as shown in FIG. 19, where It's called "Half-Bridge Boost-Forward Ring-Free Zero-Voltage-Switching Half-Wave Converter". In this embodiment, the circuit includes an input voltage filtering capacitor Cm, the positive and negative terminals of the capacitor Cm are connected across the positive and negative terminals of an input voltage Vin, and a series of power switches Q1, Q2 and a capacitor are connected in parallel. Cb, the negative electrode of the capacitor Cb is connected to the positive electrode of the capacitor Cm, the positive electrode of which is connected to the drain of the power switch Q2, and the source of the power switch Q2 is connected to the drain of the power switch Q1, The source of the power switch Q1 is connected to the negative of the capacitor Ciii. The capacitor Chi can provide a stable input voltage for use by a transformer. The transformer is provided with a primary winding Np and a primary winding Ns, and the markings on these windings are shown in Figure 19; one end of the primary winding Np is connected to the negative electrode of the capacitor Cb, and the other end is connected through an auxiliary The inductor La is connected to the line between the two power switches Q2 and Q2. In this embodiment, the line between the primary winding Np and the auxiliary inductor La is connected to the drain of the power switch Q2 through a diode D4.俾 The diode D4 can cooperate with the power switch Q2, and when the circuit is ringing, the current on the auxiliary electrical switch La can be immediately shorted by the power switch Q2 and the diode D4 to terminate the ringing. Phenomenon; the circuit connection method of the secondary winding Ns is exactly the same as that of the secondary side circuit of the third embodiment. Since this embodiment uses half-wave rectification, its ringing effect only occurs when D1 is turned off, so the diode D4 can be added to achieve the purpose of no ringing. In the fifth embodiment of the present invention, the non-ringing zero-potential switching method of the present invention should be 19 paper sizes applicable to the Chinese National Standard (CNS) A4 specification (210 X 297 mm). ----- Equipment * ------- Order --------- ^ 9. (Please read the precautions on the back before filling this page) 501334 A7 B7 V. Description of the invention (19) In the design of the half-bridge flyback switching circuit, refer to Figure 20, which can be called "Half-Bridge Flyback Ring-Free Zero-Voltage Switching Converter) ”In this embodiment, the circuit includes an input voltage filtering capacitor Cin, the positive and negative terminals of the capacitor Cin are connected across the positive and negative terminals of an input voltage Vin, and a series of power switches Ql, Q2, the drain of the power switch Q2 is connected to the positive pole of the capacitor Cin, its source is connected to the drain of the power switch Q1, and the source of the power switch Q1 is connected to the negative pole of the capacitor Cin,电容器 The capacitor Cin can provide a stable input voltage for use by a transformer T1. The transformer T1 is provided with a primary relay Np and a primary transformer Ns. The markings on the windings are shown in Figure 20. One end of the primary winding Np is connected to the negative electrode of a capacitor Cb, and the other end is Connected to the line between the two power switches Ql, Q2 and the source of the power switch Q1 through an auxiliary inductor La and a diode D3, respectively. In this embodiment, since the primary winding Np and the auxiliary inductor La The line is connected to the source of the power switch Q1 by the diode D3, so the diode D3 can cooperate with the power switch Q1, and when the circuit ringing occurs, the current on the auxiliary inductor La is immediately The power switch Q1 is shorted with the diode D3 to terminate the ringing phenomenon; one end of the secondary winding Ns is connected to the positive electrode of an output voltage filter capacitor Co through a diode D1, and the other end is Connected to the negative electrode of the capacitor Co, the capacitor Co can provide a stable DC output voltage v0 to the load connected across the output terminal. Since this embodiment uses half-wave rectification, its ringing effect only occurs when D1 is cut off. Therefore, it is only necessary to add the diode D3 to see the purpose of no ringing. In the sixth specific embodiment of the present invention, the ring-free zero-potential switching method of the present invention is applied to the design of a half-bridge boosted flyback switching circuit, as shown in FIG. 21, which can also be referred to herein as It is called "Half-Bridge Boost-Flyback Ring-Free Zero-Voltage-Switching Converter". In this embodiment, the circuit includes an input voltage filtering capacitor Cin, the positive and negative terminals of the capacitor Cm are connected across the positive and negative terminals of an input voltage Vin, and a series of power switches (Jl, Q2 and A capacitor Cb, the negative electrode of the capacitor Cb and 20 paper sizes are applicable to China National Standard (CNS) A4 specifications (210 x 297 mm) (Please read the precautions on the back before filling this page) ----- Order ---------. Printed by the Consumer Cooperatives of the Intellectual Property Bureau of the Ministry of Economic Affairs, printed by the Consumer Cooperatives of the Intellectual Property Bureau of the Ministry of Economic Affairs, printed by 501334 A7 B7 V. Invention Description (20 _ ---- The positive pole of the capacitor Cin is connected, and its positive pole is connected to the drain of the power switch Q2. The source of the power switch Q2 is connected to the drain of the power switch Q1. The source shed of the power switch Q1 is connected to The negative electrode of the capacitor Cin, the capacitor Cm can provide a stable input voltage for use by a transformer. The transformer T1 is provided with a primary winding Np and a primary winding Ns. The markings on these windings are shown in Figure 21: The primary and one terminal of Np are connected to a capacitor Cb. The negative terminal is connected, and the other end is connected to SiJ through an auxiliary inductor La and a diode D3 to the line between the power switch Q1 and Q2 and the source of the power switch Q1. In this embodiment, because the The line between the primary winding Np and the auxiliary inductor La is connected to the source of the power switch Q1 via the diode D3, so the diode D3 can cooperate with the power switch Q1. When the circuit is ringing, make The current iLa on the auxiliary inductor La is immediately started by the power switch Q1 and the diode D3 to terminate the ringing phenomenon; the circuit connection of the secondary winding is completely the same as that of the secondary side circuit of the fifth embodiment. Same. 'This embodiment uses half-wave rectification, so its ringing only occurs when D1 is cut off, so only the diode D3 can be added to achieve the purpose of no ringing. According to the above, the use of The ring-free zero-potential switching method of the present invention enables these power converters to perform zero-potential switching operations in a high-frequency environment, 'avoiding the problem that the auxiliary inductor generates abnormal heating due to the parasitic oscillation, and effectively reducing power loss' and Effective reduction The requirements for the reverse voltage rating of the secondary-side rectifier components greatly increase their operating frequency and power density, and reduce the noise of electromagnetic interference, and the heat energy accumulated by the power switch and the volume of the required heat sink The size makes these power converters easier to pass the international electromagnetic interference specifications and easier to be applied to the design of various miniaturized electronic products. The above description is only the preferred embodiments of the present invention, but the present invention The scope of the claimed rights is not limited to this. According to the equivalent changes that can be easily considered by those skilled in the art based on the technical content disclosed by the present invention, they should not depart from the protection scope of the present invention. 21 This paper size applies to China National Standard (CNS) A4 (210 X 297 mm) (Please read the precautions on the back before filling out this page) ▼ Install ------ Order -------- 4_