TW385611B - Current source and threshold voltage generation method and apparatus for HHK video circuit - Google Patents
Current source and threshold voltage generation method and apparatus for HHK video circuit Download PDFInfo
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- TW385611B TW385611B TW87106914A TW87106914A TW385611B TW 385611 B TW385611 B TW 385611B TW 87106914 A TW87106914 A TW 87106914A TW 87106914 A TW87106914 A TW 87106914A TW 385611 B TW385611 B TW 385611B
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N5/00—Details of television systems
- H04N5/04—Synchronising
- H04N5/08—Separation of synchronising signals from picture signals
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- G—PHYSICS
- G05—CONTROLLING; REGULATING
- G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
- G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
- G05F1/10—Regulating voltage or current
- G05F1/46—Regulating voltage or current wherein the variable actually regulated by the final control device is dc
- G05F1/56—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices
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- Automation & Control Theory (AREA)
- Manipulation Of Pulses (AREA)
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Abstract
Description
A7 ________ B7 五、發明説明(彳) Μ領域 本發明與從複合視頻信號中分離出同步化脈波有關。 更正確地說’本發明與爲均衡脈波移除電路產生時序電流 及臨限電壓的領域有關。 發明背景 複合視頻信號包含的資料供視頻系統使用,以便在顯 示器、監視器或電視螢幕上產生視頻畫面。在複合視頻信 號的每一個周期所含的資料中,水平部分代表一條輸出到 視頻顯示器、監視器或電視螢幕上的水平輸出線。每一個 水平周期包括水平同步脈波、色同步信號(burst signal ) 及視頻資料信號。在很多視頻傳輸系統中,彩色或色度資 料是以色度副載波信號的特定相位來代表,它與顏色資料 的振幅調諧。鎖相迴路使用水平同步脈波與系統同步,供 顯示視頻資料的下一條水平線。色同步信號是用來使取樣 脈波與彩色副載波信號的相位同步。分離電路(separator )是將水平同步信號與色同步信號從進入的視頻信號中分 離。色同步信號是由頻率爲3.58MHz的正弦波所構 成,它是色度副載波f s c的頻率。因此視頻資料信號包括 色度副載波,具有與色度資料不同相位的振幅調制。複合 彩色視頻信號包括亮度與色度資料。 視頻圖像或畫面是由視頻顯示器內的許多水平線所構 成。爲顯示一個畫面或圖像,視頻系統自螢幕的頂端開始 顯示複合視頻信號內的資料,一次顯示一條水平線。每一 -4- (請先閱讀背面之注f項再填寫本頁) 本紙張尺度適用中國國家標率(CNS ) A4規格(2丨0><297公釐) A7 ______________B7__ 五、發明説明& ) (請先閲讀背面之注f項再填艿本頁) 條水平線的資料是包含在複合視頻信號的水平周期內。在 每一個水平周期結束後,視頻系統移到下一條線,並顯示 複合視頻信號下一個水平周期內的資料。此程序不斷進行 ’直到視頻系統到達視頻顯示器的底線。 在顯示完視頻顯示器底線的視頻資料後,傳統的視頻 系統將其本身重置到顯示器的頂端,以便開始顯示下一個 畫面。爲允許系統將本身重置到視頻顯示器的頂端,在複 合視頻信號內的每一個畫面的視頻資料之後,需包括一個 垂直的空白周期。此垂直空白周期允許視頻系統有足夠的 時間重置到視頻顯示器的頂端,並開始顯示下一個畫面的 水平線資料。因此,足以構成一個畫面或螢幕的水平周期 數量被串集在複合視頻信號中》複合視頻信號包括介於每 一個畫面之間的垂直空白周期,它允許視頻系統遂行垂直 重置,並藉此移回視頻顯示器的頂端,準備顯示下一個畫 面。 在垂直空白期間,複合視頻信號包括第一周期的均衡 脈波,鋸齒脈波周期及第二周期的均衡脈波。在垂直空白 周期期間,視頻系統將其重置到視頻顯示器的頂端,因此 ,它準備好開始顯示下一個畫面的資料。不過,視頻系統 必須被告知或是能偵測到垂直空白的周期,以便能將其本 身重置到視頻顯示器的頂端。鋸齒脈波攜帶同步資料,供 視頻系統內的本地垂直振盪器於垂直重置期間使用。 水平同步脈波與垂直同步脈波結合成複合同步信號 C S YN C。一裝置接收此複合同步信號接著從該複合信 本紙張尺度適用中國國家標率(CNS > A4規格(2丨0·〆297公嫠) -5- A7 _B7___ 五、發明説明(3 ) (請先閲讀背面之注意事項再填寫本頁) 號中抽出水平同步脈波與垂直同步脈波。在垂直空白周期 期間產生所有的均衡與鋸齒脈波,其頻率等於水平同步脈 波之頻率的兩倍。 同步分離電路10 (如圖1所示)將複合視頻信號中 的所有同步脈波分離,包括水平、均衡與鋸齒脈波。不過 ,同步分離電路的做法是將它們的振幅與信號空白位準做 比較,因此無法區分水平同步脈波、均衡脈波、及鋸齒脈 波間的差異。每個畫面的水平周期期間,水平鎖相迴路使 用同步分離電路的輸出鎖定視頻系統與複合視頻信號的相 位。在垂直空白期間,同步分離電路被架構成輸出均衡與 鋸齒脈波,其頻率是水平同步脈波的兩倍。因此,在垂直 空白周期期間所需產生的同步脈波是水平期間的兩倍。因 此,在此周期期間,水平鎖相迴路無法保持鎖定,除非在 垂直空白周期期間以某些方法產生不同頻率的同步脈波。 傳統電路中使用電壓斜坡中精確的時序信號,以提供 均衡脈波一遮蔽。此類電路典型上稱之爲半Η抑制器( Half H Killer,ΗΗΚ )電路,原因是它將多餘的脈波除去, 包括水平同步脈波附近間的多餘脈波。ΗΗΚ電路所使用 的電壓斜坡信號是由儲存於電容器中的電荷所產生。典型 上,這些斜坡的周期很長,通常長達6 4毫秒。因此,需 很非常小的電流與非常大的電容器才能有效支援如此長的 周期。當使用非常小的電流時,電晶體中基極電流很小的 改變,即會在很小的參考電流中導致很大百分比的差異, 因而影響到斜坡電路之精準時序的特性》傳統上使用外部 本紙張尺度適Λ1中國國家標率(CNS ) Α4規格(210Χ297公釐) ~~ A7 _B7__ 五、發明説明Q ) 組件來產生所需的電流與臨限電壓信號,因爲它們可挑選 絕對高度精確的組件。不過,這類外部組件並不是吾人所 希望的,因爲它會增加系統的成本,佔據系統內主機板上 額外的空間,以及積·體電路上需要額外的專用接腳以耦合 這些外部組件。符合吾人需求的是能產生內部電流源及臨 限電壓的電路,在沒有外部組件的情況下,有能力產生很 小的精準電流及對應的臨限電壓信號。 發明槪述 一種電流源與臨限電壓的產生電路,經由一比例裝置 產生電流與對應的臨限電壓信號供時序電路產生時序斜坡 ,並決定時序斜坡何時跨過臨限電壓信號。該電流是由使 用比例匹配裝置的電流產生電路所產生,匹配裝置以電晶 體式爲佳。該電流接著供時序電路將電荷儲存裝置充電至 臨限電壓信號位準以上的位準。該電流也被鏡射,適度地 增加並用來產臨限電壓信號,並與儲存在電荷儲存裝置內 的電荷做比較。因此,電流所產生的任何錯誤都將反應在 臨限電壓信號的位準,藉以消除時序電路所產生之時序斜 坡信號中可能的錯誤。其中電荷儲存裝置最好是電容器, 時序電路以HHK視頻電路爲佳。電流源與臨限電壓產生 電路的較佳實施例是在積體電路內實施,不需要任何外部 組件。 圖式簡述 ---------Q-------1T------气.r --f?:% (請先閲讀背面之注意事項再填寫本頁) 本&張尺度適用中國囷家標準([灿)六4规格(2丨0父297公釐) ~ A7 B7 五、發明說明(5 ) 圖1說明將同步脈波從複合視頻信號中分離出的同步 分離電路的方塊圖。 圖2說明在垂直空白周期期間移除每隔一個均衡脈波 的電路設計方塊圖。 圖,3 a說明複合視頻信號的時序圖。 圖3 b說明圖1中同步分離電路的輸出時序圖。 圖3 c說明電壓信號▽(;31)的時序圖,它代表儲存在 電容器C1內的電壓位準》 圖3 d說明比較器2 0之輸出的時序圖。 *·. 圖3 e說明代表RS鎖存器2 4的輸出Q-的信號B的 時序圖。 圖3 f說明本發明之電路的輸出信號c的時序圖。 圖4說明根據本發明之電流源與臨限電壓產生電路的 設計圖》 圖5 A及5 B說明根據本發明之電流源與臨限電壓產 生電路的詳細設計圖。 (請先W讀背面之注§項再填寫本頁) -Γ裝 • I I 1· ----訂---------. 經齊部眢慧材4¾員1.¾ tivn咋it卬製 元件對照表 10 同步分離電路 20 比較器 24 RS鎖存器 26 邏輯NOR閘 22 邏輯NOR閘 40 放大器 42 npn電晶體 44 npn電晶體 本紙張尺度適用中國國家標準(CNS)A4規格(210 X 297公爱) _ 8 - A7 B7 五、發明説明(6 ) 50 電阻器 52 電阻器 54 電阻器 46 ρηρ電晶體 48 ρηρ電晶體 56 電阻器 58 電阻器 60 電阻器 62 電阻器 (銪先聞讀背面之注f項再填寫本頁) 較佳實施例詳細說明: 圖2說明在垂直空白周期期間移除每隔一個均衡脈波 之電路的設計方塊圖。此電路在共同待審之序號〇 8/ 583,972的美國專利申請案,名稱爲“Method of and Apparatus For Removing Equalizing Pulses Without Using External Pins”中有詳細描述,該文列爲本文之參考。此電 路產生一輸出信號C,代表複合視頻信號中的每一個水平 同步脈波及每隔一個的垂直同步脈波。 輸出信號C提供回授控制並耦合到圖2電路內電阻器 R 1的第一端點。電阻器R 1的第二端點耦合到η ρ η電 晶體Q 1的基極。電晶體Q 1的射極耦合到地。電晶體 Q 1的集極耦合到電容器C 1、電流源I。的第一端以及比 較器2 0的正輸入端,藉以形成一電壓節點VCap,該電 壓表示電容器C 1上所儲存的電壓位準》電容器C 1的第 本紙張尺度適用中國囷家標準(CNS ) A4規格(210X297公釐)A7 ________ B7 V. Description of the Invention (ii) M Field The present invention relates to the separation of synchronized pulses from a composite video signal. More specifically, the invention relates to the field of generating sequential currents and threshold voltages for an equalized pulse wave removal circuit. BACKGROUND OF THE INVENTION Composite video signals contain material used by video systems to produce video pictures on a display, monitor, or television screen. In the data contained in each cycle of the composite video signal, the horizontal portion represents a horizontal output line output to a video display, monitor, or television screen. Each horizontal period includes a horizontal sync pulse, a burst signal, and a video data signal. In many video transmission systems, color or chroma data is represented by a specific phase of the chroma subcarrier signal, which is tuned to the amplitude of the color data. The phase-locked loop uses horizontal synchronization pulses to synchronize with the system for displaying the next horizontal line of video data. The burst signal is used to synchronize the phase of the sampling pulse with the color subcarrier signal. A separator circuit separates the horizontal sync signal and the burst signal from the incoming video signal. The burst signal is composed of a sine wave with a frequency of 3.58 MHz, which is the frequency of the chrominance subcarrier f s c. Therefore, the video data signal includes a chrominance subcarrier, which has amplitude modulation with a phase different from that of the chrominance data. The composite color video signal includes luminance and chrominance data. A video image or picture is made up of many horizontal lines in a video display. To display a picture or image, the video system displays the data in the composite video signal from the top of the screen, one horizontal line at a time. Each -4- (please read the note f on the back before filling this page) This paper scale is applicable to China National Standard (CNS) A4 specification (2 丨 0 > < 297 mm) A7 ______________B7__ 5. Description of the invention &) (Please read the note f on the back before filling this page) The information of the horizontal lines is included in the horizontal period of the composite video signal. At the end of each horizontal period, the video system moves to the next line and displays the data in the next horizontal period of the composite video signal. This process continues until the video system reaches the bottom line of the video display. After displaying the video material of the bottom line of the video display, the traditional video system resets itself to the top of the display so that the next picture can be displayed. To allow the system to reset itself to the top of the video display, a vertical blank period needs to be included after the video data of each picture in the video signal is combined. This vertical blank period allows the video system sufficient time to reset to the top of the video display and start displaying horizontal line data for the next frame. Therefore, the number of horizontal periods sufficient to form a picture or screen is concatenated in the composite video signal. The composite video signal includes a vertical blank period between each frame. It allows the video system to perform a vertical reset and thereby shift Back to the top of the video display, ready to display the next picture. During the vertical blank period, the composite video signal includes an equalized pulse wave of the first period, a sawtooth pulse wave period, and an equalized pulse wave of the second period. During the vertical blanking period, the video system resets it to the top of the video display, so it is ready to start displaying data for the next frame. However, the video system must be informed or able to detect the period of vertical blanking in order to reset itself to the top of the video display. The sawtooth pulses carry synchronization data for use by the local vertical oscillator in the video system during vertical reset. The horizontal synchronization pulse and the vertical synchronization pulse are combined into a composite synchronization signal C S YN C. A device receives the composite synchronization signal and then applies the Chinese national standard (CNS > A4 specification (2 丨 0 · 〆297) 嫠) from the composite letter paper size. -5- A7 _B7___ V. Description of the invention (3) (Please Read the notes on the back first and then fill out this page) to extract the horizontal and vertical sync pulses. During the vertical blank period, all the equalized and sawtooth pulses are generated, with a frequency equal to twice the frequency of the horizontal sync pulses. The sync separation circuit 10 (shown in Figure 1) separates all sync pulses in the composite video signal, including horizontal, equalized, and sawtooth pulses. However, the practice of the sync separation circuit is to separate their amplitude from the signal blank level For comparison, it is impossible to distinguish the difference between the horizontal synchronous pulse, the equalized pulse, and the sawtooth pulse. During the horizontal period of each picture, the horizontal phase-locked loop uses the output of the synchronous separation circuit to lock the phase of the video system and the composite video signal. During the vertical blanking period, the synchronous separation circuit is framed to form an output equalization and sawtooth pulse, which has twice the frequency of the horizontal synchronous pulse. Therefore, in Synchronous pulses required during a straight blank period are twice that of a horizontal period. Therefore, during this period, the horizontal phase-locked loop cannot remain locked unless a synchronous pulse of a different frequency is generated during the vertical blank period in some way Traditional circuits use precise timing signals in voltage ramps to provide equalized pulse-shadowing. This type of circuit is typically called a Half H Killer (ΗΗΚ) circuit because it removes excess pulses In addition, the extra pulses in the vicinity of the horizontal synchronization pulse are included. The voltage ramp signal used by the ΗΗK circuit is generated by the charge stored in the capacitor. Typically, the period of these ramps is very long, usually as long as 64 milliseconds. Therefore, very small currents and very large capacitors are needed to effectively support such a long period. When very small currents are used, the small change in the base current in the transistor will result in a small reference current A large percentage difference, which affects the characteristics of the precise timing of the ramp circuit. "Traditionally, the external paper size is suitable for Λ1. National standard rate (CNS) Α4 Specification (210Χ297 mm) ~~ A7 _B7__ V. invention described Q) components to produce a desired threshold voltage and current signals, because they can be highly accurate absolute pick assembly. However, this type of external component is not what we want, because it will increase the cost of the system, occupy additional space on the motherboard on the system, and require additional dedicated pins on the integrated circuit to couple these external components. What meets my needs is a circuit that can generate an internal current source and a threshold voltage. Without external components, it has the ability to generate a small accurate current and a corresponding threshold voltage signal. The invention describes a current source and a threshold voltage generating circuit. A proportional device generates a current and a corresponding threshold voltage signal for a timing circuit to generate a timing ramp, and determines when the timing ramp crosses the threshold voltage signal. This current is generated by a current generating circuit using a ratio matching device, and the matching device is preferably an electric crystal type. This current is then used by the sequential circuit to charge the charge storage device to a level above the threshold voltage signal level. This current is also mirrored, moderately increased and used to generate a threshold voltage signal, and compared with the charge stored in the charge storage device. Therefore, any error caused by the current will be reflected in the threshold voltage signal level, thereby eliminating possible errors in the timing ramp signal generated by the sequential circuit. The charge storage device is preferably a capacitor, and the sequential circuit is preferably an HHK video circuit. The preferred embodiment of the current source and threshold voltage generating circuit is implemented in an integrated circuit and does not require any external components. Schematic description --------- Q ------- 1T ------ qi. R --f?:% (Please read the precautions on the back before filling this page) This & Zhang scale is applicable to the Chinese family standard ([chan) 6 4 specifications (2 丨 0 father 297 mm) ~ A7 B7 V. Description of the invention (5) Figure 1 illustrates the separation of the synchronous pulse wave from the composite video signal Block diagram of a synchronous separation circuit. Figure 2 illustrates a block diagram of a circuit design that removes every other equalizing pulse during a vertical blanking period. Fig. 3a illustrates a timing diagram of a composite video signal. Figure 3b illustrates the output timing diagram of the synchronous separation circuit in Figure 1. Figure 3c illustrates the timing diagram of the voltage signal ▽ (; 31), which represents the voltage level stored in the capacitor C1. "Figure 3d illustrates the timing diagram of the output of the comparator 20. * ·. Fig. 3e illustrates a timing diagram of the signal B representing the output Q- of the RS latch 24. Figure 3f illustrates a timing diagram of the output signal c of the circuit of the present invention. Fig. 4 illustrates a design diagram of a current source and a threshold voltage generating circuit according to the present invention. Figs. 5A and 5B illustrate a detailed design diagram of a current source and a threshold voltage generating circuit according to the present invention. (Please read the note § item on the back before filling this page) -Γ 装 • II 1 · ---- Order ---------. Jing Qi Department 眢 慧 材 4¾member 1.¾ tivn 咋It control components comparison table 10 Synchronous separation circuit 20 Comparator 24 RS latch 26 Logic NOR gate 22 Logic NOR gate 40 Amplifier 42 npn transistor 44 npn transistor This paper is applicable to China National Standard (CNS) A4 specification (210 X 297 public love) _ 8-A7 B7 V. Description of the invention (6) 50 resistor 52 resistor 54 resistor 46 ρηρ transistor 48 ρηρ transistor 56 resistor 58 resistor 60 resistor 62 resistor (铕 先 闻Read the note f on the back and fill in this page again) The detailed description of the preferred embodiment: Figure 2 illustrates a block diagram of a circuit that removes every other equalizing pulse during the vertical blank period. This circuit is described in detail in commonly pending US Patent Application No. 08 / 583,972, entitled "Method of and Apparatus For Removing Equalizing Pulses Without Using External Pins", which is incorporated herein by reference. This circuit generates an output signal C, which represents each horizontal sync pulse and every other vertical sync pulse in the composite video signal. The output signal C provides feedback control and is coupled to a first terminal of a resistor R 1 in the circuit of FIG. 2. The second terminal of the resistor R 1 is coupled to the base of the η ρ η transistor Q 1. The emitter of transistor Q 1 is coupled to ground. The collector of transistor Q 1 is coupled to capacitor C 1 and current source I. And the positive input of comparator 20 to form a voltage node VCap, which represents the voltage level stored on capacitor C1. The first paper size of capacitor C1 applies the Chinese standard (CNS) ) A4 size (210X297 mm)
,1T 鉀浐部中央榀苹而只工消货Ae作社印製 -9 - A7 ___ _B7 _ 五、發明説明(7 ) 二端耦合到地。電流源I。的第二端耦合到電源電壓V C C 。比較器2 0的負輸入端耦合到臨限電壓信號Vt。 比較器2 0的輸出信號V<^mP輸入到R S鎖存器2 4 的S輸入端,及NO’R邏輯閘2 6的輸入端。從同步分離 電路1 0來的輸出信號A耦合到NOR邏輯閘2 6的輸入 。反向信號I是同步分離電路1 0之輸出信號A的反向信 號,耦合到NOR邏輯閘2 2的輸入。NOR邏輯閘2 2 的輸出耦合到RS鎖存器24的輸入R=RS鎖存器24 的輸出Q提供信號B。RS鎖存器2 4的反向輸出1耦合 到NOR邏輯閘2 6的輸入。NOR邏輯閘2 6的輸出提 供輸出信號C,它即是在垂直空白周期期間移去均衡脈波 之電路的輸出。 圖1與圖2之電路的相關信號時序圖如圖3的說明。 輸入的複合視頻信號如圖3 a。從同步分離電路1 〇反應 複合視頻信號信號A的輸出如圖3 b所示。代表電容器 C 1上所儲存的電壓位準Vcap如圖3 c所示。比較器 2 0的輸出信號VhPm如圖3 d所示。代表R S鎖存器 2 4輸出Q的信號B如點3 e所示。圖3 f代表垂直空白 周期期間移去每隔一個均衡脈波之電路的輸出信號C。圖 3所說明的時序圖,其時間相互對應。 圖3 a顯示的複合視頻信號包括兩個水平周期,接著 是畫面結束之垂直空白周期期間的五個均衡脈波。從同步 分離電路輸出的信號A (如圖3 b )代表僅只有複合視頻 信號中的同步脈波。接著,輸出信號A及反向信號T"輸入 本紙張尺度適用中國困家標準(CNS ) Α4規格(210Χ297公釐) ---------Γ:衣------1T------es (讳先閱讀背面之注意事項再填寫本页) -10- 經术部中决榀孪^以工消費合作^卬^ A7 B7 五、發明説明(8 ) 到電路以移除垂直空白周期期間的均衡脈波,如圖2所示 〇 當NOR邏輯閘2 6及2 2的輸入在高電壓邏輯位準 時,它們的輸出在低電壓邏輯位準。當NOR邏輯閘2 6 及2 2的輸入在低電壓邏輯位準時,它們的輸出在高電壓 邏輯位準。在輸出信號A的上升緣,當輸出信號A從低電 壓邏輯位準轉換到高電壓邏輯位準時,輸出信號C將降到 低電壓邏輯位準,關閉電晶體Q 1 »當電晶體Q 1被關閉 時,電容器C 1被電流源I。充電。當儲存在電容器C 1的 電壓位準Vcap高於臨限電壓Vt時,比較器2 0的輸出信 號Vc〇mP將上升到高電壓邏輯位準。當比較器2 0的輸出 信號上升到高電壓邏輯位準時,R S鎖存器2 4被 設定,致使輸出Q上升到高電壓邏輯位準,同時反相輸出 i降到低電壓邏輯位準。由於反相輸出"^是在低電壓邏輯 位準,在同步分離電路1 0之輸出信號的下一個下降緣, 它的輸出信號Α從高電壓邏輯位準轉換到低電壓邏輯位準 ,輸出信號C將上升到邏高電壓輯位準。 當輸出信號C上升到高電壓邏輯位準,電晶體Q 1被 打開,並提供電容器C 1的放電路徑。由於儲存在電容器 c 1的電壓位準VCap被放電到低於臨限電壓VT的位準, 比較器2 0的輸出信號從高電壓邏輯位準轉換到低 電壓邏輯位準。由於反向輸入信號X是在高電壓邏輯位準, NOR邏輯閘2 2仍保持在低電壓邏輯位準,且RS鎖存 器2 4的輸出Q仍保持在高電壓邏輯位準。R S鎖存器 本紙張尺度適扣中圏國家標準(CNS ) Α4洗格(210Χ297公釐) :丨~:1ο-I (請先閲讀背面之注意事項再填寫本頁), 1T The central part of the potash department is printed by Ae Zuosha, only -9-A7 ___ _B7 _ 5. Description of the invention (7) The two terminals are coupled to the ground. Current source I. The second terminal is coupled to the supply voltage V C C. The negative input of the comparator 20 is coupled to a threshold voltage signal Vt. The output signal V < ^ mP of the comparator 20 is input to the S input terminal of the RS latch 24 and the input terminal of the NO'R logic gate 26. The output signal A from the synchronous separation circuit 10 is coupled to the input of the NOR logic gate 26. The reverse signal I is the reverse signal of the output signal A of the synchronous separation circuit 10 and is coupled to the input of the NOR logic gate 22. The output of the NOR logic gate 2 2 is coupled to the input R of the RS latch 24 = the output Q of the RS latch 24 provides a signal B. The inverted output 1 of the RS latch 24 is coupled to the input of the NOR logic gate 26. The output of the NOR logic gate 26 provides an output signal C, which is the output of a circuit that removes the equalizing pulses during the vertical blank period. The related signal timing diagrams of the circuits of FIG. 1 and FIG. 2 are illustrated in FIG. 3. The input composite video signal is shown in Figure 3a. The output of the composite video signal A from the synchronous separation circuit 10 is shown in Figure 3b. The voltage level Vcap stored on the representative capacitor C1 is shown in Fig. 3c. The output signal VhPm of the comparator 20 is shown in Figure 3d. The signal B representing the output Q of the RS latch 24 is shown at point 3e. Figure 3f represents the output signal C of the circuit that removes every other equalized pulse during the vertical blanking period. The timing chart illustrated in FIG. 3 corresponds to time. The composite video signal shown in Figure 3a consists of two horizontal periods, followed by five equalizing pulses during the vertical blank period at the end of the picture. The signal A (as shown in Figure 3b) output from the synchronous separation circuit represents only the synchronous pulse wave in the composite video signal. Next, the output signal A and the reverse signal T " are input to this paper. The size of the paper applies to the Chinese Standard for Standards (CNS) A4 (210 × 297 mm) --------- Γ: clothing ------ 1T- ----- es (Please read the notes on the back before filling in this page) -10- Decision in the Department of Economics and Technology ^ Icon and Consumer Cooperation ^ 卬 ^ A7 B7 V. Invention Description (8) Move to the circuit to move Except for the equalizing pulse wave during the vertical blank period, as shown in FIG. 0, when the inputs of the NOR logic gates 26 and 22 are at a high voltage logic level, their outputs are at a low voltage logic level. When the inputs of NOR logic gates 2 6 and 2 2 are at a low voltage logic level, their outputs are at a high voltage logic level. On the rising edge of the output signal A, when the output signal A is switched from a low voltage logic level to a high voltage logic level, the output signal C will fall to a low voltage logic level, and the transistor Q 1 is turned off. When closed, capacitor C 1 is powered by current source I. Charging. When the voltage level Vcap stored in the capacitor C1 is higher than the threshold voltage Vt, the output signal Vc0mP of the comparator 20 will rise to a high voltage logic level. When the output signal of the comparator 20 rises to the high-voltage logic level, the RS latch 24 is set so that the output Q rises to the high-voltage logic level and at the same time the inverting output i drops to the low-voltage logic level. Since the inverted output is at the low voltage logic level, at the next falling edge of the output signal of the synchronous separation circuit 10, its output signal A is switched from the high voltage logic level to the low voltage logic level. Signal C will rise to the logic high voltage level. When the output signal C rises to a high voltage logic level, the transistor Q 1 is turned on and provides a discharge path for the capacitor C 1. Since the voltage level VCap stored in the capacitor c 1 is discharged to a level lower than the threshold voltage VT, the output signal of the comparator 20 is switched from a high voltage logic level to a low voltage logic level. Since the inverted input signal X is at a high voltage logic level, the NOR logic gate 22 remains at a low voltage logic level, and the output Q of the RS latch 24 remains at a high voltage logic level. R S latch This paper is suitable for the standard of Chinese Standard (CNS) Α4 Washing (210 × 297 mm): 丨 ~: 1ο-I (Please read the precautions on the back before filling this page)
*1T -11 - 好浐部中央"_而κ-τ消费合作妇卬^ A7 __ B7 五、發明説明(9 )* 1T -11-Good central ministry " _ and κ-τ consumer cooperation women and children ^ A7 __ B7 V. Description of the invention (9)
2 4的反相輸出仍在低電壓邏輯位準,致使輸出信號C 保持在高電壓邏輯位準,直到從同步分離電路1 〇輸出的 信號A上升到高電壓邏輯位準》 當同步脈波結束·從同步分離電路1 0輸出的信號A上 升到高電壓邏輯位準,輸出信號C從高電壓邏輯位準轉換 到低電壓邏輯位準。由於R S鎖存器2 4預先被設定且尙 未被重置,當從同步分離電路1 0輸出的信號A轉換時, 輸出信號C也將轉換。因此,輸出信號C的寬度等於輸出 信號A之同步脈波的寬度。 當輸出信號C降到低電壓邏輯位準,電晶體Q 1被關 閉,並致使儲存在電容器C 1的電壓位準始再被 充電。當儲存在電容器C 1的電壓位準V c a P上升超過臨 限電壓VT的位準時,比較器2 0的輸出信號Vc。Pm將上 升到高電壓邏輯位準,再度設定R S鎖存器2 4。接著+, 輸出信號C將在輸出信號A的下一個同步脈波開始時,上 升到高電壓邏輯位準,且在下一個同步脈波結束時下降到 低電壓邏輯位準。 電容器C 1與電流源I 〇的値經過選擇,因此在水平 周期期間,儲存在電容器C 1的電壓位準Vcap將在每一 個水平同步脈波之前到達臨限電壓Vt的位準,並設定R S 鎖存器以使輸出信號C在下一個脈波開始時轉換。不過’ 在垂直空白周期期間,當同步脈波的頻率是水平同步脈波 的兩倍,當電容器C 1在脈波結束開始充電時’儲存在電 容器C 1的電壓位準Vcap在下一個脈波前不會到達臨限 本紙張尺度適用中圈國家橾準(CNS ) Α4说格(210Χ297公釐) ---------Q------1T------嫂、 (請先閲讀背面之注意事項再填寫本頁) -12- 經浐部中戎糅^^以二消处合作衫印^ A7 B7 — --——— --—11 — " 五、發明説明(10 ) 電壓ντ的位準。因此,RS鎖存器24將不會被設定,且 在下一個脈波期間,輸出信號C不會轉換。不過,儲存在 電容器C 1的電壓位準VcaP將在後續脈波之前到達臨限 電壓Vt的位準,設定RS鎖存器2 4並允許輸出信號C隨 脈波的邊緣轉換。 圖3說明R S鎖存器2 4設定的時序。儲存在電容器 C 1的電壓位準從完全放電的位準到達臨限電壓VT 的位準所需的時間是時間周期t 1。在垂直空白周期期間 兩均衡脈波間的時間是時間周期t 2。電容器C 1與電流 源I。的値經過選擇,以使時間周期t 1大於時間周期t 2 ,但小於兩水平同步脈波間的時間。因此,如前所述,在 垂直空白周期期間,圖2的電路對每隔一個脈波不予理會 0 根據本發明的電流源與臨限電壓產生電路如圖4所示 。電流源與臨限電壓產生電路使用比例式裝置產生一很小 的電流與臨限電壓信號,供HHK電路使用,如圖2所示 。小電流是由使用比例匹配元件的電流產生電路所產生。 電流源I。所提供之電流爲HHK電路所用,用來對電容器 C 1充電,如前所述。該電流也被映射並用來產生臨限電 壓,該臨限電壓與電容器C 1上的電壓比較。因此,電流 中的任何錯誤都會反應在臨限電壓,且因此相互抵消且不 會改時間周期的長度以封鎖均衡脈波。如果錯誤造成供應 給電容器C 1的電流較少,那麼臨限電壓位準就會降低一 適當量。相應地,如果錯誤造成供應給電容器C 1的電流 本紙張尺度適用中國國家梂準(CNS ) Α4規格(210X297公釐) : iQ—I (請先閲讀背面之注意事項再填寫本買)The inverting output of 2 4 is still at the low voltage logic level, so that the output signal C remains at the high voltage logic level until the signal A output from the synchronous separation circuit 10 rises to the high voltage logic level. The signal A output from the synchronous separation circuit 10 rises to a high voltage logic level, and the output signal C switches from a high voltage logic level to a low voltage logic level. Since the RS latch 24 is set in advance and 尙 is not reset, when the signal A output from the synchronous separation circuit 10 is switched, the output signal C is also switched. Therefore, the width of the output signal C is equal to the width of the synchronous pulse wave of the output signal A. When the output signal C falls to a low voltage logic level, the transistor Q 1 is turned off, and the voltage level stored in the capacitor C 1 is recharged. When the voltage level V c a P stored in the capacitor C 1 rises above the level of the threshold voltage VT, the output signal Vc of the comparator 20. Pm will rise to the high voltage logic level, and the RS latch 2 4 will be set again. Then +, the output signal C will rise to the high-voltage logic level at the beginning of the next synchronization pulse of the output signal A, and will drop to the low-voltage logic level at the end of the next synchronization pulse. The capacitor C 1 and the current source I 0 are selected so that during the horizontal period, the voltage level Vcap stored in the capacitor C 1 will reach the threshold voltage Vt level before each horizontal synchronization pulse and set RS The latch is such that the output signal C switches at the beginning of the next pulse. However, 'During the vertical blank period, when the frequency of the sync pulse is twice that of the horizontal sync pulse, when capacitor C 1 starts to charge at the end of the pulse', the voltage level Vcap stored in capacitor C 1 is before the next pulse It will not reach the threshold. The paper size is applicable to the Central Countries Standards (CNS) Α4 grid (210 × 297 mm) --------- Q ------ 1T ------ 嫂, (Please read the precautions on the back before filling in this page) -12- Zhong Rong 浐 ^^ Cooperative shirt printed on the second consumer ^ A7 B7 — --———— --— 11 — " V. Invention Explain (10) the level of the voltage ντ. Therefore, the RS latch 24 will not be set, and the output signal C will not be switched during the next pulse period. However, the voltage level VcaP stored in the capacitor C1 will reach the threshold voltage Vt level before the subsequent pulse, set the RS latch 24 and allow the output signal C to switch with the edge of the pulse. Figure 3 illustrates the timing of the RS latch 24 setting. The time required for the voltage level stored in the capacitor C 1 to reach the threshold voltage VT from the fully discharged level is the time period t 1. The time between two equalizing pulses during the vertical blank period is time period t2. Capacitor C 1 and current source I.値 is selected so that time period t 1 is greater than time period t 2, but less than the time between two horizontal synchronization pulses. Therefore, as mentioned before, during the vertical blanking period, the circuit of FIG. 2 ignores every other pulse. The current source and threshold voltage generating circuit according to the present invention are shown in FIG. 4. The current source and threshold voltage generating circuit uses a proportional device to generate a small current and threshold voltage signal for HHK circuit use, as shown in Figure 2. The small current is generated by a current generating circuit using a ratio matching element. Current source I. The current provided is used by the HHK circuit to charge the capacitor C 1 as described previously. This current is also mapped and used to generate a threshold voltage, which is compared to the voltage on capacitor C1. Therefore, any errors in the current will be reflected in the threshold voltage and therefore cancel each other out without changing the length of the time period to block the equalizing pulse. If the error causes less current to be supplied to capacitor C1, the threshold voltage level will be reduced by an appropriate amount. Correspondingly, if the current supplied to capacitor C 1 is caused by mistake, the paper size is applicable to China National Standard (CNS) Α4 specification (210X297 mm): iQ—I (Please read the precautions on the back before filling in this purchase)
,1T •13- A7 —-_____—___ 五、發明説明(n ) 較多,那麼臨限電壓位準就會上升一適當量》 圖4的產生電路中,1.2伏的帶隙參考電壓信號親 合到放大器4 0的正輸入。放大器4 0的輸出耦合到 η Ρ η電晶體4 2的基極與η ρ η電晶體4 4的基極。電 晶體4 2的集極耦合到電源電壓V C C。電晶體4 2的射 極耦合到電阻器5 2的第一端。電晶體4 4的射極耦合到 電阻器5 4的第一端》電阻器5 2的第二端、電阻器5 4 的第一端、電阻器5 0的第二端與放大器4 0的負輸入端 耦合。電阻器5 4的第二端耦合到地。 經浐部中呔"'4,·ΛΡ-Τ·消资合作私印製 (請先間讀背面之注意事項再填寫本頁) 電晶體4 4的集極耦合到ρ η ρ電晶體4 6的基極與 集極,以及ρ η ρ電晶體4 8的基極。電晶體4 6的射極 耦合到電阻器5 6的第一端。電阻器5 6的第二端耦合到 電源電壓V C C。電晶體4 8的射極耦合到電阻器5 8的 第一端。電阻器5 8的第二端耦合到電源電壓V C C。電 晶體4 8的集極耦合到電阻器6 0的第一端。電阻器6 0 的第二端耦合到電阻器6 2的第一端,藉以構成一輸出節 點,從該點輸出臨限電壓信號。電阻器6 2的第二端耦合 到地》 工作時,放大器40將1.2伏的帶隙參考位準映射 到負輸入及電阻器5 4的第一端。因此,在電阻器5 4上 有1.2伏的電壓降》在本發明的較佳實施例中,電阻器 5 4的値等於5 2 Κ歐姆。流經電阻器5 4的電流以等於 2 3微安爲佳。此電流供應給分路電晶體對4 2與4 4。 電晶體4 4的射極最好是比電晶體4 2的射極大9倍。射 本紙張尺度適Λ中國國家標準(CNS } Α4规格(210X297公釐) -14- 經".部中夾^^-而只工消资合作私印^ A7 — _._B7 _ 五 '發明説明(12 ) 極電阻器5 0與5 2也是經過挑選,根據電阻器5 4的總 電阻値,接近電晶體4 2與4 4之射極的比例。不過,在 本發明的較佳實施例中,爲補償系統內基極電流的損失, 電阻器5 2並非正好是1/1 0,且電阻器5 0也不剛好 是電阻器5 2値的9/1 0。因此,流過電阻器5 4的1 /1 0電流供應給電晶體4 2並流過電阻器5 0。在本發 明的較佳實施例中,供應給電晶體4 2的電流等於2 . 3 微安》接著此電流被映射且做爲從電流源I。供應的參考電 流,以對時序斜坡產生電路內的電容器C 1充電,如前所 述。 爲補償放大器4 0內因低貝它電晶體以及使用如此小 之電流所導致的任何不匹配,經由對應之電晶體4 4供應 的電流用來產生臨限電壓信號供時序斜坡電路使用,並與 儲存在電容器C 1上的電壓做比較,以觸發比較器2 0之 輸出信號的轉換。因此,流經電晶體4 2之電流所 發生的任何錯誤,都會反應在臨限電壓,藉以消除電路所 產生之時序斜坡信號中潛在的錯誤,以移去垂直空白周期 期間的均衡脈波。如果電流的位準因電路中的錯誤而降低 或升高,臨限電壓位準也相對地降低或升高一適當量以補 償這些錯誤,並當跨於電容器C 1上的電壓上升到臨限電 壓位準以上時保持正確的時序周期。 流過電晶體4 4的電流比供應給電容器c 1的電流大 9倍,並流過電晶體4 6被映射通過電晶體4 8。由於電 晶體4 8的體積是電晶體4 6的3倍,因此,流過電晶體 (請先閲讀背面之注意事項再填寫本頁) .C裒·, 1T • 13- A7 —-_________ 5. The description of the invention (n) is too much, then the threshold voltage level will rise by an appropriate amount. In the generating circuit of Figure 4, the 1.2 volt band gap reference voltage signal is pro- Close to the positive input of amplifier 40. The output of amplifier 40 is coupled to the base of η ρ η transistor 42 and the base of η ρ transistor 4 4. The collector of transistor 42 is coupled to the supply voltage V C C. The emitter of the transistor 42 is coupled to the first end of the resistor 52. The emitter of transistor 4 4 is coupled to the first end of resistor 54, the second end of resistor 5 2, the first end of resistor 5 4, the second end of resistor 50, and the negative of amplifier 40. Input coupling. The second end of the resistor 54 is coupled to ground. Printed in the Ministry of Economic Affairs " '4, · ΛΡ-Τ · Private cooperation printing (please read the precautions on the back before filling this page) Transistor 4 The collector of 4 is coupled to ρ η ρ transistor 4 6 base and collector, and ρ η ρ transistor 4 8 base. The emitter of transistor 46 is coupled to the first end of resistor 56. The second terminal of the resistor 56 is coupled to the power supply voltage V C C. The emitter of the transistor 48 is coupled to the first end of the resistor 58. The second terminal of the resistor 58 is coupled to the power supply voltage V C C. The collector of transistor 48 is coupled to the first terminal of resistor 60. The second terminal of the resistor 60 is coupled to the first terminal of the resistor 62 to form an output node from which a threshold voltage signal is output. When the second end of resistor 62 is coupled to ground, the amplifier 40 maps the 1.2 volt band gap reference level to the negative input and the first end of resistor 54. Therefore, there is a voltage drop of 1.2 volts on the resistor 54. In the preferred embodiment of the present invention, 値 of the resistor 54 is equal to 5 2 K ohms. The current flowing through the resistor 54 is preferably equal to 23 microamperes. This current is supplied to the shunt transistor pairs 4 2 and 4 4. The emitter of transistor 44 is preferably 9 times larger than the emitter of transistor 42. The size of the paper is suitable for Chinese national standard (CNS) Α4 size (210X297mm) -14- Economic " .Ministry folder ^^-and only private consumption and cooperation cooperation private printing ^ A7 — _._ B7 _ Five 'invention Note (12) The pole resistors 50 and 52 are also selected, and according to the total resistance 値 of the resistor 54, it is close to the ratio of the emitters of the transistors 42 and 44. However, in the preferred embodiment of the present invention, In order to compensate for the base current loss in the system, the resistor 5 2 is not exactly 1/1 0, and the resistor 50 is not exactly 9/1 0 of the resistor 5 2 値. Therefore, the resistor flows through the resistor A current of 1 4/10 of 5 4 is supplied to the transistor 4 2 and flows through the resistor 50. In a preferred embodiment of the present invention, the current supplied to the transistor 4 2 is equal to 2.3 microamperes. Then this current is mapped And as the reference current supplied from the current source I, to charge the capacitor C 1 in the timing ramp generating circuit, as described above. To compensate for the low beta transistor in the amplifier 40 and the use of such a small current Any mismatch, the current supplied by the corresponding transistor 4 4 is used to generate a threshold voltage signal for the timing ramp And compare it with the voltage stored in capacitor C 1 to trigger the conversion of the output signal of comparator 20. Therefore, any error in the current flowing through transistor 42 will be reflected in the threshold voltage To eliminate potential errors in the timing ramp signal generated by the circuit in order to remove the equalizing pulse during the vertical blanking period. If the current level is lowered or increased due to errors in the circuit, the threshold voltage level is also relatively To reduce or raise an appropriate amount to compensate for these errors and maintain the correct timing cycle when the voltage across capacitor C 1 rises above the threshold voltage level. The current flowing through transistor 44 is supplied to the capacitor The current of c 1 is 9 times larger and flows through transistor 4 6 and is mapped through transistor 4 8. Since the volume of transistor 4 8 is 3 times that of transistor 4 6, it flows through the transistor (please read the back first) (Please fill in this page for the precautions) .C 裒 ·
、1T 本紙張尺度適用中國國家標準(CNS > Α4規格(210X297公釐) -15- 好浐部中夾"•^•而只工消Φί合作扣卬^ A7 B7 五、發明説明(13 ) 4 8的電流是流過電晶體4 6的3倍。流過電晶體4 8的 電流接著提供給包括電阻器6 0、6 2的電阻梯》臨限電 壓信號VT從電阻器6 0與6 2間的節點輸出,因此它代表 電阻器6 2上的電壓降。 流過電阻器6 2的電流是用來產生對應於電流源I。所 供應之電流的臨限電壓信號Vt,它映射流過電晶體4 2的 電流。因此,流過電晶體4 2之電流的位準發生的任何錯 誤,都會反映在流過電晶體48與電阻器62的電流中, 最後反映在臨限電壓信號Vt的位準中。因此,當電流源 I。所供應的電流位準改變,臨限電壓信號乂1的位準也對 應地改變一比例量,確保儲存於電容器C 1上之電壓所產 生的時序斜坡能在適當的時間區間橫過臨限電壓位準,無 論電流源I。所供應的電流內是否有任何錯誤。 圖4的電流與臨限電壓電路以在一個積體電路內實施 爲佳,因此不需要使用任何外部的精密組件,藉以節省系 統的空間。本發明的電流源與臨限電壓電路的較佳實施例 的詳細電路設計圖如圖5所示。本發明的較佳實施例是在 類比視頻解碼器電路內實施,Part No . CXA2015Q,可從 美國新力公司獲得,3300 Zanker Road, San Jose, California 95134 。 雖然前所說明之本發明的較佳實施例是使用雙極電晶 體的積體電路,但熟悉此方面技術的人士可瞭解,本發明 也可以使用其的裝置技術實施,包括但不限於CMOS、 MOS、分離的組件及ECL。還需瞭解的是,可以使用 本紙張尺度適用中國國家標準(CNS ) Α4規格(210X297公釐) (請先閲讀背面之注意事項再填寫本頁) Q.、 1T This paper size applies to Chinese national standards (CNS > Α4 size (210X297mm) -15- Goods in the middle folder " • ^ • 而 工 消 Φ 合作 Cooperation deduction 卬 ^ A7 B7 V. Description of the invention (13 ) The current of 48 is three times that of the current flowing through the transistor 46. The current flowing through the transistor 4 8 is then provided to a resistor ladder including the resistors 60 and 62. The threshold voltage signal VT is transmitted from the resistor 60 and The node output between 6 and 2 therefore represents the voltage drop across resistor 62. The current flowing through resistor 62 is used to generate a threshold voltage signal Vt corresponding to the current source I, which maps The current flowing through transistor 42. Therefore, any error in the level of current flowing through transistor 42 will be reflected in the current flowing through transistor 48 and resistor 62, and finally reflected in the threshold voltage signal The level of Vt. Therefore, when the level of the current supplied by the current source I changes, the level of the threshold voltage signal 乂 1 is correspondingly changed by a proportional amount to ensure that the voltage The timing ramp can cross the threshold voltage level in the appropriate time interval, regardless of the electrical Source I. Are there any errors in the current supplied. The current and threshold voltage circuit of Figure 4 is better implemented in an integrated circuit, so there is no need to use any external precision components to save system space. This A detailed circuit design diagram of a preferred embodiment of the current source and threshold voltage circuit of the invention is shown in Figure 5. The preferred embodiment of the invention is implemented in an analog video decoder circuit, Part No. CXA2015Q, available from the United States Acquired by Sony Corporation, 3300 Zanker Road, San Jose, California 95134. Although the preferred embodiment of the present invention described above is an integrated circuit using a bipolar transistor, those skilled in the art will appreciate that the present invention also It can be implemented using its device technology, including but not limited to CMOS, MOS, separate components and ECL. It should also be understood that this paper size can be used in accordance with China National Standard (CNS) Α4 specification (210X297 mm) (please first (Read the notes on the back and fill out this page) Q.
、1T -16- A7 B7 五、發明説明(14 ) 其它不同的邏輯電路架構取代前述執行較佳實施例之功能 的邏輯電路。 本發明已利用特定的實施例詳細說明,以易於瞭解本 發明的動作與結構原理。本文中參考的特定實施例及細節 並非是對後文所附申請專利範圍的限制。很明顯地,實施 例中所選擇的這些技術都可修改,且都不會偏離本發明的 精神與範圍。特別是,雖然較佳實施例的電流源與電壓產 生電路包括在HHK電路內,但此電路可用於任何時序電 路內。同時需瞭解的是,本發明之較佳實施例中所使用的 組件的値也可改變或變化,都不會偏離本發明的精神與範 圍。 (請先閲讀背面之注意事項再填容本頁)1T -16- A7 B7 V. Description of the Invention (14) Other different logic circuit architectures replace the aforementioned logic circuits that perform the functions of the preferred embodiment. The present invention has been described in detail using specific embodiments in order to easily understand the operation and structural principles of the present invention. The specific embodiments and details referred to herein are not intended to limit the scope of the patents attached below. Obviously, the techniques selected in the embodiments can be modified without departing from the spirit and scope of the present invention. In particular, although the current source and voltage generating circuit of the preferred embodiment is included in the HHK circuit, this circuit can be used in any timing circuit. It should also be understood that the components of the components used in the preferred embodiments of the present invention may be changed or changed without departing from the spirit and scope of the present invention. (Please read the notes on the back before filling this page)
*1T* 1T
A 好浐部屮夹irSKTM-T消贽合作ii印繁 本紙張尺度適用中國國家標準(CNS ) A4规格(210X297公釐) -17-A 浐 部 部 屮 irSKTM-T Elimination cooperation ii Printing and printing This paper size is applicable to China National Standard (CNS) A4 specification (210X297 mm) -17-
Claims (1)
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US08/848,387 US6018370A (en) | 1997-05-08 | 1997-05-08 | Current source and threshold voltage generation method and apparatus for HHK video circuit |
US08/853,046 US6028640A (en) | 1997-05-08 | 1997-05-08 | Current source and threshold voltage generation method and apparatus for HHK video circuit |
Publications (1)
Publication Number | Publication Date |
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TW385611B true TW385611B (en) | 2000-03-21 |
Family
ID=27126770
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
TW87106914A TW385611B (en) | 1997-05-08 | 1998-05-05 | Current source and threshold voltage generation method and apparatus for HHK video circuit |
Country Status (3)
Country | Link |
---|---|
AU (1) | AU7276298A (en) |
TW (1) | TW385611B (en) |
WO (1) | WO1998051071A2 (en) |
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US3898377A (en) * | 1973-11-23 | 1975-08-05 | Xerox Corp | Video mixer |
US3883756A (en) * | 1973-12-27 | 1975-05-13 | Burroughs Corp | Pulse generator with automatic timing adjustment for constant duty cycle |
JPS5350613A (en) * | 1976-10-19 | 1978-05-09 | Matsushita Electric Ind Co Ltd | Synchronous signal processing circuit |
CA1152582A (en) * | 1979-11-05 | 1983-08-23 | Takashi Okada | Current mirror circuit |
US4282549A (en) * | 1979-12-11 | 1981-08-04 | Rca Corporation | Pulse generator for a horizontal deflection system |
US4292654A (en) * | 1979-12-20 | 1981-09-29 | Rca Corporation | Deflection system and switched-mode power supply using a common ramp generator |
US4364091A (en) * | 1981-02-18 | 1982-12-14 | Tokyo Shibaura Denki Kabushiki Kaisha | Equalizing pulse removal circuit |
JPH069326B2 (en) * | 1983-05-26 | 1994-02-02 | ソニー株式会社 | Current mirror circuit |
US4594565A (en) * | 1984-08-30 | 1986-06-10 | Cordis Corporation | Clock oscillator for a cardiac pacer having frequency compensation for temperature and voltage fluctuations |
US4689549A (en) * | 1986-06-30 | 1987-08-25 | Motorola, Inc. | Monolithic current splitter for providing temperature independent current ratios |
US4677368A (en) * | 1986-10-06 | 1987-06-30 | Motorola, Inc. | Precision thermal current source |
US4827341A (en) * | 1986-12-16 | 1989-05-02 | Fuji Photo Equipment Co., Ltd. | Synchronizing signal generating circuit |
FR2649505B1 (en) * | 1989-07-07 | 1991-10-25 | Sgs Thomson Microelectronics | INTEGRATED CIRCUIT WITH ADJUSTABLE OSCILLATOR WITH FREQUENCY INDEPENDENT OF THE SUPPLY VOLTAGE |
US5029295A (en) * | 1990-07-02 | 1991-07-02 | Motorola, Inc. | Bandgap voltage reference using a power supply independent current source |
US5059820A (en) * | 1990-09-19 | 1991-10-22 | Motorola, Inc. | Switched capacitor bandgap reference circuit having a time multiplexed bipolar transistor |
US5189515A (en) * | 1991-02-04 | 1993-02-23 | Industrial Technology Research Institute | Television synchronization signal separator |
US5124632A (en) * | 1991-07-01 | 1992-06-23 | Motorola, Inc. | Low-voltage precision current generator |
US5250879A (en) * | 1992-03-02 | 1993-10-05 | Thomson Consumer Electronics, S.A. | Deflection circuit having a controllable sawtooth generator |
US5428287A (en) * | 1992-06-16 | 1995-06-27 | Cherry Semiconductor Corporation | Thermally matched current limit circuit |
US5479091A (en) * | 1992-12-11 | 1995-12-26 | Texas Instruments Incorporated | Output current reference circuit and method |
US5394020A (en) * | 1992-12-30 | 1995-02-28 | Zenith Electronics Corporation | Vertical ramp automatic amplitude control |
DE4302221C1 (en) * | 1993-01-27 | 1994-02-17 | Siemens Ag | Integrated current source circuit using bipolar pnp transistors - uses current source connected to emitter of one transistor coupled in circuit with three transistors |
US5565915A (en) * | 1993-06-15 | 1996-10-15 | Matsushita Electric Industrial Co., Ltd. | Solid-state image taking apparatus including photodiode and circuit for converting output signal of the photodiode into signal which varies with time at variation rate depending on intensity of light applied to the photodiode |
US5349286A (en) * | 1993-06-18 | 1994-09-20 | Texas Instruments Incorporated | Compensation for low gain bipolar transistors in voltage and current reference circuits |
US5570243A (en) * | 1993-06-22 | 1996-10-29 | Fujitsu Limited | Variable delay circuit including current mirror and ramp generator circuits for use in the read channel of a data storage device |
GB2283630B (en) * | 1993-11-03 | 1997-11-19 | Plessey Semiconductors Ltd | Drive circuit |
GB9417267D0 (en) * | 1994-08-26 | 1994-10-19 | Inmos Ltd | Current generator circuit |
JP2682470B2 (en) * | 1994-10-24 | 1997-11-26 | 日本電気株式会社 | Reference current circuit |
EP0735677B1 (en) * | 1995-03-31 | 1999-12-22 | Co.Ri.M.Me. Consorzio Per La Ricerca Sulla Microelettronica Nel Mezzogiorno | Oscillator circuit having oscillation frequency independent from the supply voltage value |
-
1998
- 1998-05-01 WO PCT/US1998/008869 patent/WO1998051071A2/en active Application Filing
- 1998-05-01 AU AU72762/98A patent/AU7276298A/en not_active Abandoned
- 1998-05-05 TW TW87106914A patent/TW385611B/en not_active IP Right Cessation
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WO1998051071A2 (en) | 1998-11-12 |
AU7276298A (en) | 1998-11-27 |
WO1998051071A3 (en) | 1999-02-04 |
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