TW201944190A - Low dropout voltage regulator - Google Patents
Low dropout voltage regulatorInfo
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Abstract
Description
本發明係關於一種低壓降電壓穩壓器(low dropout voltage regulator),且更特地而言,係關於一種具有可控制緩啟動機制的低壓降穩壓器。 The present invention relates to a low dropout voltage regulator, and more particularly, to a low dropout regulator with a controllable slow-start mechanism.
低壓降電壓穩壓器是一種具有很小的輸入和輸出電壓差值的直流線性電壓穩壓器(DC linear voltage regulator)。低壓降電壓穩壓器的優點包含可運作於較低的電源電壓、高運作效率和低熱消耗量。典型的低壓降電壓穩壓器的元件包含一功率電晶體和一誤差放大器。藉由該功率電晶體和該誤差放大器形成的負回授迴路,低壓降電壓穩壓器可以維持穩定的輸出電壓值。 The low dropout voltage regulator is a DC linear voltage regulator with a small difference between the input and output voltages. The advantages of low-dropout voltage regulators include low power supply voltage, high operating efficiency, and low heat consumption. The components of a typical low-dropout voltage regulator include a power transistor and an error amplifier. Through the negative feedback loop formed by the power transistor and the error amplifier, the low dropout voltage regulator can maintain a stable output voltage value.
然而,低壓降電壓穩壓器在電源電壓初始供應時若未進行良好的控制,可能會損害內部元件或是對負載造成損害。例如,在緩啟動期間,若誤差放大器偵測到輸出電壓一直未到達預期電壓值,則該功率電晶體將會被過度驅動而產生湧浪(inrush)電流,或者是輸出電壓在緩啟動結束後發生一電壓過衝(overshoot)現象。湧浪電流和電壓過衝現象都會對 低壓降電壓穩壓器的內部元件或對負載造成損害。因此,有必要提供一種具有可控制緩啟動機制的低壓降電壓穩壓器以解決上述問題。 However, if the low-dropout voltage regulator is not well controlled during the initial supply of the power supply voltage, it may damage internal components or cause damage to the load. For example, during the slow start, if the error amplifier detects that the output voltage has not reached the expected voltage value, the power transistor will be over-driven to generate an inrush current, or the output voltage is at the end of the slow start A voltage overshoot occurs. Both inrush current and voltage overshoot can cause damage to the internal components of the LDO regulator or to the load. Therefore, it is necessary to provide a low dropout voltage regulator with a controllable slow start mechanism to solve the above problems.
根據本發明一實施例之一種低壓降電壓穩壓器,包含一主要誤差放大器、一輔助誤差放大器、一第一緩衝電路、一第二緩衝電路、一控制電路以及一N通道功率電晶體。該N通道功率電晶體具有用以接收一電源電壓的一汲極和用以產生一輸出電壓的一源極。該主要誤差放大器具有用以接收比例於該輸出電壓的一回授電壓的一正輸入端,用以接收一參考電壓的一負輸入端,和一放大輸出端。該第一緩衝電路耦接至該主要誤差放大器的該放大輸出端和該N通道功率電晶體的一閘極之間。該輔助誤差放大器具有用以接收比例於該輸出電壓的該回授電壓的一第一正輸入端,一第二正輸入端,用以接收該參考電壓的一負輸入端,和一放大輸出端。該第二緩衝電路耦接至該輔助誤差放大器的該放大輸出端和該N通道功率電晶體的該閘極之間。該控制電路用以比較比例於該輸出電壓的該回授電壓的電壓值和一偏壓電壓的電壓值以控制該N通道功率電晶體的該閘極。該輔助誤差放大器比該主要誤差放大器消耗較少的電流。該參考電壓的電壓值大於該偏壓電壓的電壓值。 A low dropout voltage regulator according to an embodiment of the present invention includes a main error amplifier, an auxiliary error amplifier, a first buffer circuit, a second buffer circuit, a control circuit, and an N-channel power transistor. The N-channel power transistor has a drain for receiving a power voltage and a source for generating an output voltage. The main error amplifier has a positive input terminal for receiving a feedback voltage proportional to the output voltage, a negative input terminal for receiving a reference voltage, and an amplified output terminal. The first buffer circuit is coupled between the amplified output terminal of the main error amplifier and a gate of the N-channel power transistor. The auxiliary error amplifier has a first positive input terminal for receiving the feedback voltage proportional to the output voltage, a second positive input terminal, a negative input terminal for receiving the reference voltage, and an amplified output terminal. . The second buffer circuit is coupled between the amplified output terminal of the auxiliary error amplifier and the gate of the N-channel power transistor. The control circuit is used to compare the voltage value of the feedback voltage proportional to the output voltage with the voltage value of a bias voltage to control the gate of the N-channel power transistor. The auxiliary error amplifier consumes less current than the main error amplifier. The voltage value of the reference voltage is greater than the voltage value of the bias voltage.
100,100’‧‧‧低壓降電壓穩壓器 100,100’‧‧‧‧Low Dropout Voltage Regulator
12‧‧‧第一緩衝電路 12‧‧‧The first buffer circuit
14‧‧‧第二緩衝電路 14‧‧‧Second buffer circuit
144‧‧‧第一輸出級 144‧‧‧first output stage
146‧‧‧第二輸出級 146‧‧‧Second output stage
16,16’‧‧‧控制電路 16,16’‧‧‧Control circuit
162‧‧‧輸出級 162‧‧‧Output stage
18‧‧‧電壓分壓電路 18‧‧‧Voltage Dividing Circuit
CMP‧‧‧比較器 CMP‧‧‧ Comparator
C1,C2‧‧‧電容 C1, C2‧‧‧Capacitors
CL‧‧‧電容 CL‧‧‧Capacitor
I1,I3‧‧‧電流源 I1, I3‧‧‧ current source
M2,M6‧‧‧P通道電晶體 M2, M6‧‧‧P channel transistor
M3,M4,M7‧‧‧N通道電晶體 M3, M4, M7‧‧‧‧N-channel transistors
MN‧‧‧N通道功率電晶體 MN‧‧‧N channel power transistor
OP1‧‧‧主要誤差放大器 OP1‧‧‧Main Error Amplifier
OP2‧‧‧輔助誤差放大器 OP2‧‧‧Auxiliary Error Amplifier
R1,R2‧‧‧電阻 R1, R2‧‧‧Resistance
X2‧‧‧致能元件 X2‧‧‧Enable element
第一圖顯示結合本發明一實施例之一低壓降電壓穩壓器之方塊示意圖。 The first figure shows a block diagram of a low dropout voltage regulator combined with an embodiment of the present invention.
第二圖顯示結合本發明另一實施例之一低壓降電壓穩壓器之電路圖。 The second figure shows a circuit diagram of a low-dropout voltage regulator combined with another embodiment of the present invention.
第三圖顯示結合本發明一實施例之控制電路之電路圖。 The third figure shows a circuit diagram of a control circuit incorporating an embodiment of the present invention.
在說明書及後續的申請專利範圍當中使用了某些詞彙來指稱特定的元件。所屬領域中具有通常知識者應可理解,製造商可能會用不同的名詞來稱呼同樣的元件。本說明書及後續的申請專利範圍並不以名稱的差異來作為區分元件的方式,而是以元件在功能上的差異來作為區分的準則。在通篇說明書及後續的請求項當中所提及的「包含」係為一開放式的用語,故應解釋成「包含但不限定於」。另外,「耦接」一詞在此係包含任何直接及間接的電氣連接手段。因此,若文中描述一第一裝置耦接於一第二裝置,則代表該第一裝置可直接電氣連接於該第二裝置,或透過其他裝置或連接手段間接地電氣連接至該第二裝置。 Certain terms are used in the description and the scope of subsequent patent applications to refer to specific elements. Those of ordinary skill in the art will understand that manufacturers may use different terms to refer to the same components. The scope of this specification and subsequent patent applications does not take the difference in names as a way to distinguish components, but rather uses the difference in functions of components as a criterion for distinguishing components. "Inclusion" mentioned throughout the specification and subsequent claims is an open-ended term and should be interpreted as "including but not limited to." In addition, the term "coupled" includes any direct and indirect means of electrical connection. Therefore, if a first device is described as being coupled to a second device, it means that the first device can be electrically connected directly to the second device or indirectly electrically connected to the second device through other devices or connection means.
第一圖顯示結合本發明一實施例之一低壓降電壓穩壓器100之方塊示意圖。參考第一圖,該低壓降電壓穩壓器100包含一主要誤差放大器OP1、一第一緩衝電路12、一N通道功率電晶體MN和一電壓分壓電路18。 The first figure shows a block diagram of a low-dropout voltage regulator 100 according to an embodiment of the present invention. Referring to the first figure, the low dropout voltage regulator 100 includes a main error amplifier OP1, a first buffer circuit 12, an N-channel power transistor MN, and a voltage divider circuit 18.
參考第一圖,該N通道功率電晶體MN具有耦接至一電源電壓VDD的一汲極和耦接至該電壓分壓器18和一輸出電容CL的一源極。 Referring to the first figure, the N-channel power transistor MN has a drain coupled to a power supply voltage VDD and a source coupled to the voltage divider 18 and an output capacitor CL.
該主要誤差放大器OP1的一負輸入端用以接收一參考電壓VREF。在一實施例中,該參考電壓VREF由一帶隙電路(bandgap circuit,未繪示)所產生,其電壓值約為1.2V。該電壓分壓電路18包含電阻R1和R2。該等電阻R1和R2對該低壓降電壓穩壓器100的一輸出電壓OUT進行分壓以產生比例於該輸出電壓OUT的一回授電壓FB。該回授電壓FB傳送至該主要誤差放大器OP1的一正輸入端。該主要誤差放大器OP1用以比較該參考電壓VREF和該回授電壓FB的電壓值,藉以產生一誤差信號N1。該第一緩衝電路12耦接至該主要誤差放大器OP1的一輸出端,其用以位移該誤差信號N1的電壓值以推動該N通道功率電晶體MN。 A negative input terminal of the main error amplifier OP1 is used to receive a reference voltage VREF. In one embodiment, the reference voltage VREF is generated by a bandgap circuit (not shown), and its voltage value is about 1.2V. The voltage dividing circuit 18 includes resistors R1 and R2. The resistors R1 and R2 divide an output voltage OUT of the low-dropout voltage regulator 100 to generate a feedback voltage FB that is proportional to the output voltage OUT. The feedback voltage FB is transmitted to a positive input terminal of the main error amplifier OP1. The main error amplifier OP1 is used to compare the voltage value of the reference voltage VREF and the feedback voltage FB to generate an error signal N1. The first buffer circuit 12 is coupled to an output terminal of the main error amplifier OP1, and is used for shifting the voltage value of the error signal N1 to push the N-channel power transistor MN.
在正常運作時,亦即,當緩啟動結束後,該主要誤差放大器OP1藉由該第一緩衝電路12驅動該N通道功率電晶體MN的一閘極端以提供穩定的輸出電壓OUT。在此狀況下該主要誤差放大器OP1、該第一緩衝電路12和該N通道功率電晶體MN形成一第一負回授路徑。該第一負回授路徑會使該回授電壓FB的電壓值和該參考電壓VREF的電壓值實質上相同。因此,該輸出電壓OUT的電壓值會根據該等電阻R1和R2的阻值比例於該參考電壓VREF的電壓值。 During normal operation, that is, after the slow start, the main error amplifier OP1 drives a gate terminal of the N-channel power transistor MN through the first buffer circuit 12 to provide a stable output voltage OUT. In this situation, the main error amplifier OP1, the first buffer circuit 12 and the N-channel power transistor MN form a first negative feedback path. The first negative feedback path causes the voltage value of the feedback voltage FB and the voltage value of the reference voltage VREF to be substantially the same. Therefore, the voltage value of the output voltage OUT is proportional to the voltage value of the reference voltage VREF according to the resistance values of the resistors R1 and R2.
然而,在緩啟動期間,當電源電壓VDD開始供應時,該第一緩衝電路12會將節點N2的電壓值由接地電位上抬至一電壓值,例如一電晶體的閘極-源極電壓差值VGS。因此,該N通道功率電晶體MN會導通而產生湧浪電流,進而對元件造成損害。為了解決此問題,該低壓降電壓穩壓器100需要另一回授路徑控制N通道功率電晶體MN的導通狀況。 However, during the slow start period, when the power supply voltage VDD starts to be supplied, the first buffer circuit 12 will raise the voltage value of the node N2 from the ground potential to a voltage value, such as the gate-source voltage difference of a transistor. Value VGS. Therefore, the N-channel power transistor MN is turned on to generate an inrush current, thereby causing damage to the element. In order to solve this problem, the low-dropout voltage regulator 100 needs another feedback path to control the conduction state of the N-channel power transistor MN.
參考第一圖,為了增加另一回授路徑,該低壓降電壓穩壓器100另包含一輔助誤差放大器OP2、一第二緩衝電路14和一控制電路16。該輔助誤差放大器OP2因為不額外進行溫度補償或製程差異化處理或高速運作,會比需要複雜設計的該主要誤差放大器OP1消耗更少的電流。在本發明一實施例中,該輔助誤差放大器OP2消耗的電流小於10μA。 Referring to the first figure, in order to add another feedback path, the low dropout voltage regulator 100 further includes an auxiliary error amplifier OP2, a second buffer circuit 14 and a control circuit 16. The auxiliary error amplifier OP2 consumes less current than the main error amplifier OP1 that requires a complicated design because it does not perform additional temperature compensation or process differentiation or high-speed operation. In an embodiment of the present invention, the current consumed by the auxiliary error amplifier OP2 is less than 10 μA.
參考第一圖,該控制電路16用以比較該回授電壓FB的電壓值和一偏壓電壓VB的電壓值以產生一控制信號FBX。該輔助誤差放大器OP2的一第一正輸入端用以接收該回授電壓FB,一第二正輸入端用以接收該控制信號FBX,且一負輸入端用以接收該參考電壓VREF。該第二緩衝電路14的一輸入端耦接至該輔助誤差放大器OP2的輸出端,其用以位移一誤差信號N3的電壓值。該第二緩衝電路14的一輸出端耦接至該N通道功率電晶體MN的該閘極。 Referring to the first figure, the control circuit 16 compares the voltage value of the feedback voltage FB with the voltage value of a bias voltage VB to generate a control signal FBX. A first positive input terminal of the auxiliary error amplifier OP2 is used to receive the feedback voltage FB, a second positive input terminal is used to receive the control signal FBX, and a negative input terminal is used to receive the reference voltage VREF. An input terminal of the second buffer circuit 14 is coupled to an output terminal of the auxiliary error amplifier OP2, and is used to shift a voltage value of the error signal N3. An output terminal of the second buffer circuit 14 is coupled to the gate of the N-channel power transistor MN.
第二圖顯示結合本發明另一實施例之一低壓降電壓穩壓器100’之電路圖。參考第二圖,該第一緩衝電路12 包含一P通道電晶體M2和一電流源I1,其中,該P通道電晶體M2具有耦接至一地端的一汲極端,耦接至該主要誤差放大器OP1的該輸出端的一閘極端,和耦接至該電流源I1的一源極端。 The second figure shows a circuit diagram of a low-dropout voltage regulator 100 'combined with another embodiment of the present invention. Referring to the second figure, the first buffer circuit 12 includes a P-channel transistor M2 and a current source I1, wherein the P-channel transistor M2 has a drain terminal coupled to a ground terminal and coupled to the main error amplifier. A gate terminal of the output terminal of OP1 and a source terminal coupled to the current source I1.
該第二緩衝電路14包含一第一輸出級144和一第二輸出級146。該第一輸出級144具有耦接至該輔助誤差放大器OP2的該輸出端的一輸入端,和耦接至該第二輸出級146的一輸出端。該第二輸出級146具有耦接至該N通道功率電晶體MN的該閘極端的一輸出端。 The second buffer circuit 14 includes a first output stage 144 and a second output stage 146. The first output stage 144 has an input terminal coupled to the output terminal of the auxiliary error amplifier OP2, and an output terminal coupled to the second output stage 146. The second output stage 146 has an output terminal coupled to the gate terminal of the N-channel power transistor MN.
在一實施例中,該第一輸出級144包含一N通道電晶體M4。該N通道電晶體M4具有耦接至該主要誤差放大器OP1的該輸出端的一汲極,用以接收該誤差信號N3的一閘極,和耦接至該地端的一源極。 In one embodiment, the first output stage 144 includes an N-channel transistor M4. The N-channel transistor M4 has a drain coupled to the output terminal of the main error amplifier OP1, a gate for receiving the error signal N3, and a source coupled to the ground.
在一實施例中,該第二輸出級146包含一N通道電晶體M3和一電容C1。該N通道電晶體M3具有用以接收該誤差信號N3的一閘極,耦接至該N通道功率電晶體MN的該閘極的一汲極,和耦接至該地端的一源極。該電容C1耦接於該N通道功率電晶體MN的該閘極和該N通道電晶體M3的該閘極之間。 In one embodiment, the second output stage 146 includes an N-channel transistor M3 and a capacitor C1. The N-channel transistor M3 has a gate for receiving the error signal N3, a drain coupled to the gate of the N-channel power transistor MN, and a source coupled to the ground. The capacitor C1 is coupled between the gate of the N-channel power transistor MN and the gate of the N-channel transistor M3.
參考第二圖,該控制電路16包含一比較器CMP和一輸出級162。該比較器CMP用以比較該回授電壓FB的電壓值和該偏壓電壓VB的電壓值以產生一比較信號CMPX。該 比較器CMP的一輸出端耦接至該輸出級162的一輸入端。 Referring to the second figure, the control circuit 16 includes a comparator CMP and an output stage 162. The comparator CMP is used to compare the voltage value of the feedback voltage FB and the voltage value of the bias voltage VB to generate a comparison signal CMPX. An output terminal of the comparator CMP is coupled to an input terminal of the output stage 162.
在一實施例中,該輸出級162包含一N通道電晶體M7、一致能元件X2、一電流源I3和一電容C2。該N通道電晶體M7具有用以接收該比較信號CMPX的一閘極,耦接至該致能元件X2的一汲極,和耦接至該電流源I3的一源極。在一實施例中,該致能元件X2由一P通道電晶體M6所組成,如第三圖所示。該P通道電晶體M6具有用以接收該電源電壓VDD的一源極,用以接收一致能信號EN的一閘極,和耦接至該N通道電晶體M7的該汲極的一汲極。 In one embodiment, the output stage 162 includes an N-channel transistor M7, a uniform energy element X2, a current source I3, and a capacitor C2. The N-channel transistor M7 has a gate for receiving the comparison signal CMPX, a drain coupled to the enabling element X2, and a source coupled to the current source I3. In one embodiment, the enabling element X2 is composed of a P-channel transistor M6, as shown in the third figure. The P-channel transistor M6 has a source for receiving the power voltage VDD, a gate for receiving the uniform energy signal EN, and a drain coupled to the drain of the N-channel transistor M7.
參考第二圖,在緩啟動期間,當該電源電壓VDD開始供應時,該低壓降電壓穩壓器100’中的該參考電壓VREF的電壓值首先會重設為0V(地端電壓值)。此時,該回授電壓FB的電壓值小於該偏壓電壓VB的電壓值(約0.3V),因此該比較器CMP輸出邏輯0的信號CMPX,而使該N通道電晶體M7截止。當該N通道電晶體M7截止時,該致能元件X2會將該控制信號FBX快速上拉至該電源電壓VDD的電壓值,而使該控制信號FBX的電壓值大於該回授信號FB的電壓值。此時該參考電壓VREF的電壓值很小,故該輔助誤差放大器OP2輸出邏輯1的誤差信號N3。 Referring to the second figure, during the slow start period, when the power supply voltage VDD starts to be supplied, the voltage value of the reference voltage VREF in the low dropout voltage regulator 100 'is first reset to 0V (ground voltage value). At this time, the voltage value of the feedback voltage FB is smaller than the voltage value of the bias voltage VB (about 0.3V). Therefore, the comparator CMP outputs a logic 0 signal CMPX, and the N-channel transistor M7 is turned off. When the N-channel transistor M7 is turned off, the enabling element X2 will quickly pull up the control signal FBX to the voltage value of the power supply voltage VDD, so that the voltage value of the control signal FBX is greater than the voltage of the feedback signal FB. value. At this time, the voltage value of the reference voltage VREF is very small, so the auxiliary error amplifier OP2 outputs an error signal N3 of logic 1.
當該輔助誤差放大器OP2輸出邏輯1的誤差信號N3後,該電晶體M4導通,使得該節點N1的電壓值會下拉至接地電位。同時,該電晶體M3導通,使得該節點N2的電壓值會 下拉至接地電位。因此,該N通道功率電晶體MN截止。由於該N通道功率電晶體MN截止,該輸出電壓OUT在電源電壓VDD開始供應時會保持下拉至接地電位。 When the auxiliary error amplifier OP2 outputs an error signal N3 of logic 1, the transistor M4 is turned on, so that the voltage value of the node N1 will be pulled down to the ground potential. At the same time, the transistor M3 is turned on, so that the voltage value of the node N2 will be pulled down to the ground potential. Therefore, the N-channel power transistor MN is turned off. Since the N-channel power transistor MN is turned off, the output voltage OUT will remain pulled down to the ground potential when the power supply voltage VDD starts to be supplied.
接著,該參考電壓VREF以一固定斜率開始上升。當該回授信號FB的電壓值小於該偏壓電壓VB的電壓值時,該輔助誤差放大器OP2、該第二緩衝電路14中的該N通道電晶體M3、該電容C1和該N通道功率電晶體MN形成一第二負回授路徑。該第二負回授路徑會使該回授電壓FB的電壓值和該參考電壓VREF的電壓值實質上相同。 Then, the reference voltage VREF starts to rise with a fixed slope. When the voltage value of the feedback signal FB is less than the voltage value of the bias voltage VB, the auxiliary error amplifier OP2, the N-channel transistor M3, the capacitor C1, and the N-channel power circuit in the second buffer circuit 14 Crystal MN forms a second negative feedback path. The second negative feedback path causes the voltage value of the feedback voltage FB and the voltage value of the reference voltage VREF to be substantially the same.
當該回授信號FB的電壓值上升至接近於該偏壓電壓VB的電壓值時,該比較器CMP輸出邏輯1的信號CMPX,而使該N通道電晶體M7導通。當該N通道電晶體M7導通時,該電流源I3對該電容C2進行放電,因此該控制信號FBX的電壓值以一固定斜率開始下降。當該控制信號FBX的電壓值小於該回授信號FB的電壓值時,該輔助誤差放大器OP2輸出邏輯0的誤差信號N3,而使該等電晶體M3和M4截止。因此,該N通道功率電晶體MN改由該第一負回授路徑推動,而該第二負回授路徑不啟動。 When the voltage value of the feedback signal FB rises to a voltage value close to the bias voltage VB, the comparator CMP outputs a signal CMPX of logic 1 to turn on the N-channel transistor M7. When the N-channel transistor M7 is turned on, the current source I3 discharges the capacitor C2, so the voltage value of the control signal FBX starts to decrease with a fixed slope. When the voltage value of the control signal FBX is less than the voltage value of the feedback signal FB, the auxiliary error amplifier OP2 outputs an error signal N3 of logic 0, so that the transistors M3 and M4 are turned off. Therefore, the N-channel power transistor MN is instead driven by the first negative feedback path, and the second negative feedback path is not activated.
綜上所述,藉由該第一負回授路徑和該第二負回授路徑的輪流啟動,本發明所揭示之低壓降電壓穩壓器因為具有可控制的緩啟動機制而可避免湧浪電流和電壓過衝現象造成的損害。 In summary, with the alternate start of the first negative feedback path and the second negative feedback path, the low-dropout voltage regulator disclosed by the present invention can avoid surges because it has a controllable slow-start mechanism. Damage caused by current and voltage overshoot.
本發明之技術內容及技術特點已揭示如上,然而熟悉本項技術之人士仍可能基於本發明之教示及揭示而作種種不背離本發明精神之替換及修飾。因此,本發明之保護範圍應不限於實施例所揭示者,而應包括各種不背離本發明之替換及修飾,並為隨後之申請專利範圍所涵蓋。 The technical content and technical features of the present invention have been disclosed as above. However, those skilled in the art may still make various substitutions and modifications based on the teaching and disclosure of the present invention without departing from the spirit of the present invention. Therefore, the protection scope of the present invention should not be limited to those disclosed in the embodiments, but should include various substitutions and modifications that do not depart from the present invention, and should be covered by the scope of subsequent patent applications.
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