TW201401655A - Circularly and linearly polarized planar phased array antennae and network systems employing such - Google Patents

Abstract

A high-gain circularly polarized antenna system comprising a passive antenna structure including at least one 3 db quadrature coupler; and a chip set including Tx, Rx and DLO (Distributed Local Oscillator) circuits, interfacing the passive antenna structure, thereby to generate a transceiver. The system (including the chip-set, antenna...) typically operates over an instantaneous bandwidth of 12% centered around 60GHz.

Description

Circular and linearly polarized planar phase array antennas and networks utilizing the antennas Road system

The present invention relates to a communication network, and more particularly to an indoor wireless network.

Conventional techniques relating to certain embodiments of the present invention are described in the following publications: Cho, Jeong-Hoon, "A Design Of Wideband 3-Db Coupler With N-Section Microstrip Tandem Structure", IEEE Microwave And Wireless Components Letters, 15(2), February 2005, p. 113.

Bauer R. L. and Schuss, J. J., "Axial ratio of balanced and unbalanced fed circularly polarized patch radiator arrays", in: Antennas and Propagation Society International Symposium, June 1987, pages: 286-289, which are available for download from the Internet.

References for the double push oscillator include:

‧ Pavio, A. M and M. A. Smith, “Push-Push dielectric resonator Oscillator”, 1985 IEEE MTT-S Digest, p. 266-269.

‧ Winch, R. G., "Wide-Band Varactor-Tuned Oscillators"; IEEE Journal of Solid-State Circuits, vol. SC-17, No. 6, Dec. 1982: pp. 1214-1219.

‧ Pavio A.M and M.A. Smith, "A 20-40-GHz Push-Push Dielectric Resonator oscillator"; IEEE Transactions on Microwave Theory and Techniques, vol. MTT-33, No. 12 Dec. 1985; pp. 1346-1349.

‧ Plessas, F. and Kalivas, G., “Locking Techniques for RF Oscillators at 5-6 GHz Frequency Range”; ICECS-2003; pp. 986-989.

‧ Jeiewski, M. T., “An Approach to the Analysis of Injection-Locked Oscillators”; IEEE communication on Circuits And Systems, vol. CAS-21, No. 3, May 1974; pp. 395-401.

‧ Kurorawa, K., "Injection Locking of Microwave Solid-State Oscillators"; Proceedings of the IEEE, vol. 61, No. 10, Oct. 1973; pp. 1386-1413.

‧ Sinnesbichler et al. "A 38-GHz Push-Push Oscillator Based on 25-GHz fT BJT's", IEEE Microwave and Guided Wave Letters, vol. 9, No. 4. Apr. 1999; pp. 151-153.

‧ Dussopt, L. et al. “A Low Phase Noise Silicon 9 GHz VCO and an 18 GHz Push-Push Oscillator”, 2002 IEEE MTT-S Digest; pp. 695-698.

‧ Ramirez, F. et al, “Nonlinear simulation techniques for the optimized design of pushpush oscillators”, 2003 IEEE MTT-S Digest; pp. 2157-2160.

‧ Xiao, H. et al, “A Low Phase Noise Ku-Band Push-Push Oscillator Using Slot Ring Resonator”, 2004 IEEE MTT-S Digest; pp. 1333-1336.

‧ Sinnesbichler, F. X. "Hybrid Millimeter-Wave Push-Push Osciliators Using Silicon-Germanium HBTs"; IEEE Transactions on Microwave Theory and Techniques, vol. 51, No. 2, Feb. 2003; pp. 422-430.

‧ Yoon, S. W., et al. “A Compact GAAS MESFET-Based Push-Push With Low Phase-Noise Performance Oscillator MMIC Using Differential Topology”, 2001 IEEE GaAs Digest pp. 45-48.

All publications or patents disclosed in this specification are hereby incorporated by reference.

The invention includes at least the following embodiments:

Embodiment 1. A high gain circularly polarized antenna system comprising: a passive antenna structure including at least one 3 db quadrature coupler; and a chip set including Tx, Rx, and DLO (Distributed Area Oscillator) circuits The passive antenna structure is used as an interface to generate a transceiver.

Embodiment 2. A system according to embodiment 1, wherein the passive antenna structure is placed on a multilayer printed circuit board.

Embodiment 3. A system according to Embodiment 2, wherein the multilayer printed circuit board comprises a flexible multilayer printed circuit board.

Embodiment 4. A system according to Embodiment 2, wherein the multilayer printed circuit board is formed of LCP (Liquid Crystal Polymer).

Embodiment 5. A system according to embodiment 1, wherein the wafer set has an active area, wherein the active area is surrounded by the passive antenna structure to serve as a package medium to protect the wafer set.

Embodiment 6. A system according to Embodiment 1, wherein the system covers a bandwidth centered at 55-65 GHz.

Embodiment 7. A system according to embodiment 1 or embodiment 6, wherein the bandwidth is between 5% and 2%.

Embodiment 8. A system according to embodiment 6, wherein the bandwidth is a value centered at 60 GHz.

Embodiment 9. A system according to embodiment 7, wherein the bandwidth is 10%.

Embodiment 10. A system according to embodiment 6, wherein the system covers a bandwidth of 57-64 GHz.

Embodiment 11. A communication network system comprising: A plurality of nodes, at least one of which includes a transceiver, interfacing with an antenna as described in any of the preceding embodiments, which can transmit and receive an electronically steerable focused electromagnetic beam.

Embodiment 12. A system according to Embodiment 11, wherein the electromagnetic beam is controllable by a phase shift injection double push oscillator (PSIPPO) or a phase shift function of a phase shifter.

Embodiment 13. A system according to Embodiment 11 wherein the antenna is circularly polarized such that the electromagnetic beam can be transmitted and received in a spatial position regardless of the transceiver of the transmitting and receiving.

Embodiment 14. A system according to embodiment 11, wherein the antenna has a bandwidth having a center frequency of about 12% to about 57-64 GHz.

Embodiment 15. A system according to embodiment 11, wherein the plurality of nodes comprises at least one pair of nodes comprising first and second nodes, non-line of sight between each other, and for each pair of nodes, the first and second nodes Both are located within the line of sight of at least one repeater node.

Embodiment 16. A system according to embodiment 15, wherein the at least one repeater node comprises at least one repeater node that can serve more than one pair of nodes in a range of non-line of sight between each other.

Embodiment 17. A system according to Embodiment 11 further comprising a software management function for enabling simultaneous transmission of more than one pair of the plurality of nodes by distinguishing at least one of the transmitting and receiving resources between the active nodes receive.

Embodiment 18. A system according to embodiment 17, wherein the software management function uses TDMA.

Embodiment 19. A system according to embodiment 17, wherein the software management function uses FDMA.

Embodiment 20. A system according to embodiment 17, wherein the software management function uses CDMA.

Embodiment 21. A system according to embodiment 11 wherein the focused electromagnetic beam is manipulated using AESA technology.

Embodiment 22. A system according to Embodiment 16, wherein a sequence of repeater nodes within a line of sight and spaced apart from each other by less than a predetermined distance will serve each pair of nodes that are spaced apart from each other by the predetermined distance.

Embodiment 23. A system according to Embodiment 1, wherein the at least one quadrature coupler comprises a plurality of interconnected 3 db quadrature couplers.

Embodiment 24. A system according to embodiment 13, wherein the predetermined distance is at least 10 meters.

Embodiment 25. A system according to embodiment 11, wherein the antenna has a bandwidth of approximately 57-64 GHz.

Embodiment 26. A system according to embodiment 14, wherein the plurality of nodes comprises at least one pair of nodes comprising first and second nodes, non-line of sight between each other, and for each pair of nodes, the first and second nodes Both are located within the line of sight of at least one repeater node.

Embodiment 27. A method for providing a high gain circularly polarized antenna system, the method comprising: Providing a passive antenna structure including at least one 3 db quadrature coupler; and providing a chip set including Tx, Rx, and DLO (Distributed Area Oscillator) chips with the passive antenna structure as an interface to generate a transceiver .

Embodiment 28. A method according to embodiment 27, further comprising operating the transceiver.

Embodiment 29. A method according to embodiment 28, further comprising transmitting with the transceiver.

Embodiment 30. A method according to embodiment 28, further comprising receiving with the transceiver.

Certain embodiments of the invention include planar phased array antennas and associated manifolds for circular and linear polarization.

The "multilayer stripline" technique may include a suitable network of Wilkinson power splitters, a 90 degree power splitter and a 180 degree power splitter.

The 90 degree and 180 degree power splitters have a multi-block structure dispersed across multiple layers of media.

The phase array antenna includes several independent transmitters. Each transmitter receives an RF signal at a given power and a particular phase. Traditional phase array In the system, the signals for each transmitter are generated by a dedicated T/R module. All T/R modules receive the same input signal at the same frequency, same power, and same phase. Among several other functions, the T/R module can set the phase of the output signal delivered to the transmitter to the desired phase. The RF manifold is a device for transmitting signals to each T/R module.

In a conventional phased array system, each individual T/R module is located between the associated transmitter and the associated output port of the manifold.

Some conventional phase array systems do not use conventional T/R modules, but rather conventional hardware based on the novel "distributed area oscillator" subsystem, as described in the co-proprietary patents: Milano and Weinstein. U.S. Patent No. 7,852,265 to Alberto Milano, entitled "Apparatus and methods for radar imaging based on injected push-push oscillators".

An antenna with "N" and "M" column emitters and a phase array system based on the "Distributed Area Oscillator" subsystem, containing two new RF blocks: the first will have "M" appropriate phases The signal is passed to the transmitter in the "M" column for azimuth manipulation, while the second passes the "N" appropriate phase signals to the transmitter in the "N" column for high degree of maneuvering. Therefore, each array of transmitters will receive two signals of the appropriate phase for manipulating the orientation and height of the antenna. The two signals entering the same transmitter should be properly isolated.

The manifold includes a network of various power splitters depending on the functionality of the system.

The Wilkinson power splitter is sufficient for a planar linearly polarized transmitter with only one feed, and for a plane linear with two feeds A polarized transmitter can be added to a 180 degree power splitter; for a circularly polarized transmitter, a 90 degree power splitter can be added.

To operate at high frequencies, the power splitter is implemented as a "dispersive component," which can be a waveguide, a microstrip line, a stripline, a coplanar waveguide, or a slot line.

The design of the strip and microstrip is based on a transmission line that is coupled with its thin edge or its wide side.

The coupling coefficient of the directional coupler is set by the distance between the coupled lines.

In some cases, the value of the geometry may be impractical for a particular physical medium and/or a particular operating frequency. In order to overcome its difficulties, one solution is to set two or more coupling blocks to be parallel; this allows the coupling coefficient and geometry of each single block to be relieved, making the physical application of the multi-block coupler Possible, for example, the so-called "Kevin" solution of the RF Association. Large couplers also use the same structure.

In some cases, in order to reduce the production cost of the coupler, a multi-layer product of a plastic laminate is used. Due to the physical and several characteristics of those materials, it is easy to occur that two coupling blocks of light are insufficient and more blocks need to be used.

In a multi-block coupler microstrip application, two pairs of contiguous blocks can be used, such as shown in FIG. Those lines can damage the phase of the overall coupler and limit the effectiveness of the Kevin solution.

Thus, for any coupler with a multi-block directional coupler with a phase difference of 90 or 180 degrees between the signals of the coupler output for electronic and/or geometric suppression, a multi-layer edge-coupled multi-block directional coupler can be used. .

Each block can be placed on the strip structure and overlapped with the previous and succeeding blocks. Each block forms a stacked structure, that is, all the blocks are arranged in the direction of "z".

Each block is connected to an adjacent one through a plated hole.

A proposed multi-layer application can reduce the length of the electrical connection between two consecutive blocks to a minimum possible, so that the output signal phase accuracy can achieve minimal damage.

The 3 dB/90 degree directional coupler described here can be used as a basic component of the 3 dB/180 degree "Marchand" power splitter and enjoys the same advantages as the basic block.

The antenna described herein can be a composite device. It can use conventional phased array antenna transceiver technology and uses a large number of expensive and cumbersome T/R modules in order to generate all the signals for the antenna. In this case, system power consumption, system production cost, system heat sink size, system weight and size may eliminate the need to apply the antenna to the transceiver. One way to avoid all of the aforementioned system limitations is the "Distributed Area Oscillator" (DLO) embodiment described herein.

The DLO is a subsystem (shown in Figure 20) that receives a reference signal injected into a PSIPPO array at 15 GHz (or any other suitable input frequency), such as the Milano patent referred to herein. The signal transmitted by each PSIPPO in the array and locked with the reference input signal has a frequency of 30 GHz (or twice the input frequency used) and the phase of its input signal can be multiplied by a factor of two. Each PSIPPO can change the phase of the generated signal and change the voltage of the varactor diode embedded in the BRFPO's BRF.

Signals from the first PSIPPO array are injected into a second PSIPPO array. The elements of each of the second array operate in the same manner as the first array, except that their corresponding frequencies are twice as large as before.

The signal output by the DLO can be the pump of the mixer array. The role of the mixer array is to upconvert the baseband signals radiated by the antenna array elements.

When the traditional AESA technology is used in the same binary structure as that used by DLO, in order to feed the same signal at the same frequency and phase, the emitter of the 2×n linear sub-array in the overall antenna array is generally used 2^n. T/R module. Conversely, using the DLO method, a 2×n linear sub-emitter array of the same number of monolithic antennas can be fed by a single DLO.

This case provides at least the following examples:

1. "Dispersed 90 and 180 degree directional couplers", comprising "n" coupling blocks in the strip line, connected together by plated holes, so that the integral coupler can comprise several parallel stacked blocks .

2. Apply the technique to a 90 degree directional coupler starting with 3 dB coupling.

3. Apply the technology to a 180 degree directional coupler with both output signals grounded.

4. The specific configuration of the 180 degree coupler is to reduce the length of the strip line connecting the two blocks of the "Marchand" balance unbalancer so that the input and output ports can be located in the same layer in the multilayer stack.

5. The technique according to any of the preceding embodiments may make the coupler less susceptible to possible misalignment of its numerous masks.

6. The RF manifold includes a mesh Wilkinson 90 degree and 180 degree power splitter.

7. The manifold of embodiment 6 is applied to a linear emitter array and a planar emitter array.

8. Apply the manifold of Embodiment 6 to a conventional and "new" phase array system.

9. Apply the manifold of Embodiment 6 to a linearly polarized and circularly polarized planar antenna.

10. Antenna feed for isolated azimuth and altitude control signals.

11. Patch antennas having two or four feed points, each receiving an isolated ground signal for manipulating the orientation and height.

12. The Wilkinson Power Combiner acts as a connection between the planar emitter and the multilayer manifold to provide antenna-isolated feed for linear and circular polarization for simultaneous azimuth and altitude manipulation.

13. A Decentralized Area Oscillator (DLO) device is an affordable solution that allows the antenna to be applied to a transceiver.

14. The DLO device of Example 13 comprises a PSIPPO of an "n" array. Each array can contain any number of independent PSIPPOs.

15. The DLO device of Embodiment 13 can be implemented in any of the possible frequencies in the entire available spectrum.

16. The DLO device of Embodiment 13 can be used as a subsystem to signal at the frequency and phase of a "K" transmitter of a linear sub-array of a 2"n emitter array of the same rectangular array of "K*2^n" emitters Feed in.

17. Phase array antenna (including the "n" column and the "m" column of the transmitter), which only manipulates the orientation by the "n+m" TR modules of the conventional technology instead of the "n * m" TR modules. And height.

18. The DLO device as a subsystem can pass (2**n) output signals, characterized in that each phase can be specifically defined without the use of a phase shifter.

19. The DLO device as a subsystem can receive a low frequency reference signal with low noise and high stability at the f0 frequency, and transmit the frequency (2**n)*f0 with the stability of the input reference signal and (2**n) signal of spectral purity.

20. The DLO device as a subsystem comprises a series of networked PSIPPO n linear arrays, each array containing an appropriate number of PSIPPOs operating at the appropriate frequency.

21. The DLO device as a subsystem can change the phase of the local processing signal as required.

22. The DLO device as a subsystem enhances the frequency of the input signal by a factor of (2**n).

23. The DLO device as a subsystem enhances the phase of the input signal by a factor of (2**n).

24. The DLO device as a subsystem is locked with the input signal at frequency f0, and can transmit the 2**n output signal at the frequency (2**n)*f0 and has the same spectrum as the reference input signal at f0. Purity and stability characteristics.

25. The DLO device as a subsystem can be cascaded with an appropriate number of PSIPPO linear arrays to avoid the PLL subsystem in the communication device when the input reference signal of the DLO is the XTALO signal.

26. Phase array antennas (including "n" and "m" columns), which consist of only two DLOs instead of "n+m" TR modules or "n * m" TRs as in the conventional technique. The module controls the position and height.

27. Any suitable combination of any of the systems described herein with any of the systems described or illustrated in at least one of the following patents: U.S. Patent No. 7,852,265 to Milano and Weinstein, and U.S. Patent No. 7,800,453 to Alberto Milano, entitled "Apparatus and methods for radar imaging based on injected push-push oscillators".

28. Any suitable combination of any of the methods described or illustrated herein with at least one of the following listed patents: U.S. Patent No. 7,852,265 to Milano and Weinstein, and U.S. Patent No. 7,800,453 to Alberto Milano.

The present invention also provides a method for making any of the systems shown and described herein, including providing a suitable subset of all or any of the system components shown and described herein, using any suitable conventional method, and utilizing any and all of the obvious A method of the system and its components that can be inferred from the structures and functions described herein.

The present invention also provides a computer program product comprising a computer usable medium or a computer readable storage medium, generally tangible, having a built-in computer readable code, the computer readable code executable or Manage any or all of the methods displayed and described here. Any or all of the steps shown and described herein can be made by a computer. The operation taught here This can be achieved by a computer that is specially assembled for the intended purpose or by a computer program that is stored in a general computer readable storage medium and intended for the intended purpose.

Any suitable processor, display and input means for processing, displaying on a computer screen or other computer output device, storing, and receiving information used or generated by any of the methods and devices shown and described herein; The display, and the input means including the computer program, are in accordance with some or all of the embodiments of the present invention. Any or all of the inventive functions shown and described herein can be achieved by conventional personal computer processors, workstations or other programmable devices or computers or electronic computing devices, whether for general purpose or special assembly; Computer monitor screens and/or printers and/or amplifiers for display; machine readable memory such as optical discs, CDROMs, magneto-optical discs or other discs; RAM, ROM, EPROM, EEPROM, magnetic or for storage Optical or other card, and keyboard or mouse for acceptance. The above-mentioned "processing" includes any form of calculation or operation or conversion of data that may occur in the form of an electronic or a phenomenon or that exists in a register and/or memory in a computer.

The above devices can communicate via any conventional wired or wireless digital communication means, such as via a wired or mobile telephone network or a computer network such as the Internet.

In accordance with some embodiments of the present invention, a device of the present invention can include a machine readable memory having a program with instructions stored thereon, which when executed by a machine, can be displayed and described herein as part of the present invention or All devices, methods, features and functions. Alternatively or additionally, according to the invention In some embodiments, the apparatus of the present invention may comprise a program as described above, which may be written in any conventional programming language, and may alternatively be a machine for executing the program, such as but not limited to being selectively compliant with the present invention. A general computer that teaches planning or startup. Any revelation covered here can be applied to signals representing physical objects or substances.

The above-mentioned embodiments and other embodiments will be described in more detail later.

Any trademarks shown in this specification or the drawings are owned by their respective owners and are merely used to explain or demonstrate how to implement the embodiments of the present invention.

To clearly describe the present invention, it uses some general terminology relating to a particular programming language, operating system, browser, system version, personal product, and the like. However, it should be understood that the terminology is used to convey a generic operational concept for clarity and simplicity, and is not intended to limit the scope of the invention to any particular programming language, operating system, browser, system version, or personal product. .

Figure 1 shows a "Kevin" dual block directional coupler. The device of Figure 1 may contain some or all of the requirements listed below:

100: The first block of the coupled line.

101: Cable

102: connecting line

103: Input 埠

104: Output 埠

105: Idle 埠

106: Output 埠

The output signal has a phase difference of 90 degrees at the center frequency. The phase difference receives an error calculated based on the lengths of the connecting lines 101 and 102.

Figure 2 shows a "Kevin" coupler with two blocks connected to two transfer lines. A multi-stage directional power splitter/combiner configured on the same plane has two undesired features: the performance is degraded by the connecting line as the operating frequency increases, and the connecting line also degrades the multi-stage directional coupling An empty bridge connected to the external environment. Certain embodiments of the invention may overcome some or all of these limitations.

Figure 3 shows a linear array of patch emitters that are fed by the manifold in such a way that the radiated MW power is circularly polarized.

In order to radiate a circularly polarized EM field, each transmitter will receive four signals at the same frequency but at different phases: 0/90/180/270 degrees.

The device of Figure 3 may contain some or all of the requirements listed below:

300: A 180 degree power splitter that provides signals to the two 90 degree power splitters 301 and 302.

301: A 90 degree power splitter that transmits a signal to the Wilkinson power splitter 305.

302: A 90 degree power splitter that transmits a signal to the Wilkinson power splitter 306.

303: Wilkinson power distribution for transmitting signal to power splitter 305 Device.

304: A Wilkinson power splitter that transmits a signal to the power splitter 306.

305: The Wilkinson power splitter feeds a signal with phase 0 & 90 degrees to the transmitter.

306: The Wilkinson power splitter feeds a signal having a phase of 180 & 270 degrees to the transmitter.

307: A transmitter that radiates a circularly polarized EM field.

Figure 4 shows a section of a stripline manifold comprising Wilkinson power splitters 401 & 402. It includes a meshed serial Wilkinson power splitter. The medium of the sub-network is a strip line substrate 400. Figure 4 shows the mechanical structure of 303+305 and 304+306 in Figure 3. The device of Figure 4 may contain some or all of the requirements listed below:

400: strip line substrate

401: Wilkinson Power Splitter

402: Wilkinson power splitter

403: 埠1

404: 埠 2

405: 埠 3

406: 埠 4

407: 埠 5

Figure 5 is a schematic illustration of a 90 degree directional power splitter for four blocks. Each block 500 is connected to an adjacent one via a connecting element 501. The connecting element is minimized to its possible physical limit: it can be achieved by placing four strip lines The blocks are achieved with a multi-layer structure overlap such that the connecting elements between two adjacent blocks can pass through the holes between the two overlapping strip line structures. As such, the directional power splitter can form a distributed directional coupler in each layer of the stripline multilayer environment.

Figure 6 shows a 3D mechanical block diagram (top view) of the four blocks of a 90 degree distributed directional power splitter. The device of Figure 6 may contain some or all of the requirements listed below:

600: A separate block on the top stripline medium.

601: Enter 埠.

602: The first output is 埠.

Figure 7 shows a 3D mechanical block diagram (bottom view) of the four blocks of a 90 degree distributed directional power splitter as shown. The independent coupling blocks 700 are coupled together with FIG. The device of Figure 7 may contain some or all of the requirements listed below:

700: A separate block on the bottom stripline medium.

701: Idle.

702: The second output is 埠.

Figure 8 is a schematic illustration of the Marchand power splitter at 180 degrees. The device of Figure 8 may contain some or all of the requirements listed below:

800: Enter 埠.

The first block of the 801:3 dB directional coupler.

The second block of the 802:3 dB directional coupler.

803: The first output 埠.

804: Second output 埠.

805: Open the road.

Figure 9 is a 3D diagram of a 180 degree power splitter ratio in accordance with some embodiments of the present invention. The device of Figure 9 may contain some or all of the requirements listed below:

900: Input 埠, corresponding to 800 of FIG.

The first block of the 901:3 dB distributed 90 degree directional coupler corresponds to 801 of FIG.

The second block of the 902:3 dB distributed 90 degree directional coupler corresponds to 802 of FIG.

903: The first output 埠 corresponds to 803 of FIG.

904: The second output 埠 corresponds to 804 of FIG.

905: Open circuit, corresponding to 805 of FIG.

Figure 10 shows the bottom side of a 180 degree power splitter. The device of Figure 10 may contain some or all of the requirements listed below:

The first block of the 1001:3 dB distributed 90 degree directional coupler corresponds to 801 of FIG.

The second block of the 1002:3 dB distributed 90 degree directional coupler corresponds to 802 of FIG.

1003: The shortest possible transmission line connecting two 3 dB distributed 90 degree directional couplers 1001 and 1002.

Figure 11 depicts a separate manifold for passing signals to a separate vertical linear array transmitter of a circularly polarized planar antenna array. It corresponds to Figure 3. The device of Figure 11 may contain some or all of the requirements listed below:

1100: Enter 埠.

1101:180 degree power splitter.

1102: 90 degree power splitter.

1103: 90 degree power splitter.

1104: The network of the Wilkinson power splitter.

1105: The network of the Wilkinson power splitter.

1106: The network of the Wilkinson power splitter.

1107: The network of the Wilkinson power splitter.

1108: Transmitter feed for a linear array of four emitters.

Figure 12 shows the performance of a 90 degree directional power splitter; its component symbols are as follows:

1200: Comparison of four crickets.

1201: Coupling power of two output turns.

1202: The phase of the output signal.

1203: The phase difference between the two output signals.

Figure 13 shows a configuration for sixteen transmitter linearly polarized planar antennas, the manifold comprising eight Wilkinson networks each comprising three Wilkinson splitters and four 180 degree power splitters. The device of Figure 13 may contain some or all of the requirements listed below:

1300: Transmitter.

1301: The network of the Wilkinson power splitter transmits the signal at 0 degrees.

1302: The Wilkinson power splitter network transmits signals at 180 degrees.

1303: 180 degree power splitter.

Figure 14 depicts a planar array for manipulating azimuth and highly linearly polarized phased array antennas. The device of Figure 14 may comprise the following or all of the following Departmental requirements:

1400: Transmitter.

1401: The Wilkinson power splitter network transmits signal/orientation at 0 degrees.

1402: Wilkinson power splitter network that transmits signal/orientation at 180 degrees.

1403: Wilkinson power splitter network, transmitting signal/orientation at 0 degrees.

1404: The Wilkinson power splitter network transmits signal/azimuth control at 180 degrees.

1405: 90 degree power splitter / height control.

1406: 180 degree power splitter / azimuth control.

Figure 15 depicts a planar array that is only used for azimuth steering circularly polarized phased array antennas. The device of Figure 15 may contain some or all of the requirements listed below:

1500: Transmitter.

1501: The network of the Wilkinson power splitter transmits the signal at 0 degrees.

1502: The network of the Wilkinson power splitter transmits the signal at 90 degrees.

1503: The network of the Wilkinson power splitter transmits the signal at 180 degrees.

1504: The network of the Wilkinson power splitter transmits the signal at 270 degrees.

1505: 90 degree power splitter.

1506: 80 degree power splitter.

Figure 16 depicts a planar array of circularly polarized phased array antennas for steering orientation and height. The device of Figure 16 may comprise the parts listed below or All the requirements:

1600: Transmitter.

1601: The Wilkinson power splitter network transmits signal/orientation at 0 degrees.

1602: Wilkinson power splitter network that transmits signal/orientation at 90 degrees.

1603: Wilkinson power splitter network that transmits signal/orientation at 180 degrees.

1604: The Wilkinson power splitter network transmits signal/azimuth control at 270 degrees.

1605: Wilkinson power splitter network, transmitting signal/height control at 0 degrees.

1606: Wilkinson power splitter network that transmits signal/height control at 90 degrees.

1607: The network of the Wilkinson power splitter transmits signal/height control at 180 degrees.

1608: The network of the Wilkinson power splitter delivers signal/height control at 270 degrees.

1609: 90 degree power splitter.

1610: 180 degree power splitter.

Figure 17 shows a standalone transmitter suitable for a linearly polarized radiating antenna array. The phase difference between the signals fed between 1707 and 1708 is always 180 degrees, so that the transmitter can propagate a linearly polarized EM wave. The device of Figure 17 may contain some or all of the requirements listed below:

1700: Transmitter.

1701: A Wilkinson power splitter that combines the signals transmitted to 埠1705 and 1703 independently.

1702: A Wilkinson power splitter that combines the signals transmitted to the ports 1704 and 1706 independently.

1703: The Wilkinson power splitter 1701 is configured to receive a signal at a reference phase of 0 degrees as an input port for azimuth steering.

1704: The Wilkinson power splitter 1702 is configured to receive a signal at a reference phase of 180 degrees as an input port for azimuth steering.

1705: The Wilkinson power splitter 1701 is configured to receive a signal at a reference phase of 0 degrees as a highly manipulated input port.

1706: The Wilkinson power splitter 1702 is configured to receive a signal at a reference phase of 180 degrees as a highly manipulated input port.

1707: A transmitter having a reference phase of 0 degrees and receiving an independent signal for steering azimuth and altitude.

1708: A transmitter feed having a 180 degree reference phase and receiving an independent signal for steering azimuth and altitude.

Although the signal phase fed into the 1707 as the azimuth control is 180 degrees different from the feed 1708 as the highly manipulated signal phase, the transmitter can propagate an azimuth and highly steerable linearly polarized EM wave in the feed 1707. The signal reference phase can be changed to achieve azimuth and altitude control; the signal reference phase fed to 1708 can be changed to achieve azimuth and altitude manipulation.

A circle with a circle that can be inserted into the Wilkinson Power Combiner The location of the Ohm resistor.

Figure 18 shows the independent transmitter suitable for a linearly polarized radiating antenna array. The phase difference between the signals fed between 1801/a-b-c-d is always 90 degrees, so that the transmitter can propagate a circularly polarized EM wave. The device of Figure 18 may contain some or all of the requirements listed below:

1800: Transmitter.

1801/a: Signal 埠 @ 0 degrees.

1801/b: Signal 埠 @ 270 degrees.

1801/c: Signal 埠 @ 180 degrees.

1801/d: Signal 埠 @ 90 degrees.

1802: The 埠 1802/a & b is used to control the azimuth and altitude signals for the summed power combiner.

1803: The 埠1803/a & b is used to control the azimuth and altitude signals for the summed power combiner.

1804: The 埠1804/a & b is used to control the azimuth and altitude signals for the summed power combiner.

1805: The 埠1805/a & b is used to control the azimuth and altitude signals for the summed power combiner.

The position of the 100 Ohm resistor that can be inserted into the Wilkinson power combiner is indicated by a circle in the figure.

Figure 19 is a 3D view of the transmitter of Figure 17, including a portion of the manifold.

Figure 20 shows an example of the RX portion of the transceiver and the DLO as part of it.

2000: TX of the transceiver.

2001: DLO.

2002: Power splitter @ 15 GHz.

2003-2004: PSIPPO array 15-30 GHz.

2005-2006: Power splitter @ 30 GHz.

2007-2008-2009-2010: Buffer Amplifier Array @ 30 GHz.

2011-2012-2013-2014: PSIPPO second array 30-60 GHz.

2015-2016-2017-2018: Buffer Amplifier Array @ 60 GHz.

2019-2020-2021-2022: Upconverter mixer array.

2023-2024-2025-2026: Buffer Amplifier Array @ 60 GHz.

2027-2028-2029-2030: Linear sub-emitter array.

2031: Baseband signal generator.

Referring to Figure 21, the PSIPPO is a core component of the DLO. Subsequent descriptions will be made for a suitable DLO, for example with reference to FIG.

Figure 22 shows a cross section of a waveguide that is fed as a circularly polarized antenna. The EM field and the vertical EM field entering the horizontal direction of the antenna are generated by two different transmitters and propagated by the antenna connected to the feed. The two vertical EM fields are produced by different mechanical devices. The device of Figure 22 may contain some or all of the requirements listed below:

2200: A section of the waveguide into which the antenna is fed.

2210: The direction of the electric field of the vertically polarized EM wave.

2220: The direction of the electric field of the horizontally polarized EM wave.

Figure 23 shows how an independent signal entering the 180 degree power splitter 2370 is passed to the planar antenna 2300 of the linear array 2341. Entry 2310, 2320, 2330, 2340. The device of Figure 23 may contain some or all of the requirements listed below:

2300: Planar antenna

2310: Feeding 埠.

2320: Feeding 埠.

2330: Feeding 埠.

2340: Feeding 埠.

2341: Linear array of planar antennas.

2311: 0 degree power splitter, passing four signals @ 0 degrees.

2312: 0 degree power splitter, passing four signals @ 180 degrees.

2313: 0 degree power splitter, passing four signals @ 90 degrees.

2314: 0 degree power splitter, passing four signals @ 270 degrees.

2315: Planar antenna.

2316: Planar antenna.

2317: Planar antenna.

2318: Planar antenna.

2350: 90 degree power splitter.

2360: 90 degree power splitter.

2370: 180 degree power splitter.

2371: Input signal for a linear array antenna.

A distributed area oscillator (DLO) for constructing and operating certain embodiments of the present invention will be described in detail herein. Typically, this area oscillator is used to provide signal frequency conversion in a communication system. It typically contains a low frequency crystal oscillator (XTALO) as a reference for frequency and phase, a high A frequency controlled oscillator (VCO), and a phase locked loop (PLL) for transmitting the frequency stability and spectral purity of the XTALO to the VCO.

As long as the XTALO and the VCO have different frequencies, in order to compare the signals from the two devices, the frequency divider reduces the VCO signal frequency to the level of the XTALO frequency.

In an Active Electronic Scanning Antenna System (AESA) system, the signals processed by the various transmitters are frequently converted by a dedicated LO signal. The LO signal can come from the same basic subsystem and is distributed to the system through a suitable decentralized network (manifold) having one input port and the same number of output ports as the antenna elements. The LO allocation signal has the same frequency and phase as the LO. Therefore, in order for the AESA to function properly, each signal output by the manifold and entering the frequency converter is set to a different phase. In traditional AESA systems, this function is achieved by the same number of phase shifters in the array.

In the ALOA based on the DLO subsystem, there is no need to use a phase shifter to set each output signal to a specific phase. In addition, the appropriate phase signals used to convert the information-containing signals are from the same source.

Figure 24 shows a block diagram of a linear array of a DLO-based AESA transmitter. The device of Figure 24 may contain some or all of the requirements listed below:

2000: Block diagram of the Distributed Area Oscillator (DLO) 2020.

2010: Reference signal at f0.

2020: The first linear array of PSIPPOs that transmit signals at 2*f0.

2030: Buffer amplifier array at 2*f0.

2040: A second linear array of PSIPPOs that transmit signals at 4*f0.

2050: Buffer amplifier array at 4*f0.

2060: Upconverter mixer array.

2070: Power amplifier array.

2080: A transmitter array at 4*f0 and with a specific phase-reflected signal.

A wireless area network compatible system using a phased array antenna is described herein, with reference to the system shown in Figs. 1-25, the architecture and operation of which is taught in part by the teachings of U.S. Patent No. 7,852,265, the entire disclosure of which is incorporated herein by reference. For the following examples, please refer to the system with reference to Figure 1-25:

A wireless local area network communication system comprising: at least one phase array antenna frame coupled to a phase array antenna circuit of the at least one phase array antenna frame, wherein the phase array circuit and the at least one phase array antenna frame are operable The wireless area network compatible signal is transmitted to the wireless local area network device or receives the wireless local area network compatible signal from the wireless local area network device; and the phase array antenna circuit includes a plurality of phase shift injection double push oscillators (PSIPPO) ).

2. System 1, wherein the at least one phased array antenna frame transmits or receives radiation.

3. System 1, wherein the phase array antenna circuit is for driving and controlling the at least one phase array antenna frame.

4. System 1, wherein the wireless local area network is a wireless personal area network.

5. System 1, wherein the at least one phased array antenna frame comprises at least two transmitter groups.

6. System 5, wherein one of the at least two transmitter groups is defined as a reference group.

7. The system of embodiment 6 wherein one of the at least two transmitter groups is controlled by the phase array circuit and transmitted or received with a phase offset relative to the reference group.

8. The system of embodiment 7, wherein the phase offset is programmable or written in the code.

9. System 1, wherein the at least one phased array antenna frame comprises at least two substantially linear one-dimensional emitter arrays.

10. System 1, wherein the at least one phased array antenna frame comprises an even number of substantially linear one-dimensional emitter arrays, wherein each substantially linear one-dimensional emitter array comprises two N-th power emitters, and N is greater than An integer of 1.

11. System 1, wherein the at least one phased array antenna frame comprises a substantially hexagonal emitter.

12. System 5, wherein the system selectively switches between different radiation modes with each emitter group.

13. System 12, wherein the radiation pattern is determined by the number of transmitter groups that can be transmitted and received at different phase offsets, and based on the programmable phase offset.

14. System 1, wherein the phase array circuit controls the phase array antenna frame to radiate with a horizontal beam aperture.

15. System 14, wherein the horizontal beam aperture width is substantially between 3 and 15 degrees.

16. System 1, wherein the system is operable to communicate with a plurality of wireless local area network devices.

17. System 1, wherein the system can be used to communicate with a personal computer.

18. System 1, wherein the system is operative to communicate with at least one television device.

19. System 8, wherein the programmable phase offset is +/- 180 degrees.

20. System 8, wherein the programmable phase offset is +/- 180 degrees, and wherein the programmable phase offset is created by a transmission line to reverse the signal phase.

21. System 1, wherein the wireless local area network compatible signal is transmitted in a band of about 57 to 64 GHz.

22. System 12, wherein the system selectively switches between two radiation modes.

23. System 12, wherein the system selectively switches between two radiation modes, and wherein the at least one phase array antenna frame comprises two linear one-dimensional emitter arrays.

24. System 12, wherein selectively switching between different radiation modes depends on the level of signals received in the different phase modes.

25. System 14, wherein the horizontal beam aperture is horizontally controllable according to a programmable mode.

26. System 1, wherein transmitting and receiving wireless local area network compatible signals comes from or can be selectively implemented by the wireless local area network device through the building wall.

27. System 5, wherein the phase array antenna circuit comprises: a. an oscillator circuit for providing a reference signal; b. at least two stages for operation Controlling a phase shift injection locked double push oscillator created by the phase array antenna frame; c. an upconverter for upscaling a signal transmitted by the phase array antenna and for using the phase array antenna a received frequency downconverter; and d. a transmission line for selectively providing a phase offset to a reference signal supplied to the up or downconverter.

28. A method of wireless communication of a phased array antenna, comprising the steps of: providing at least one phase array antenna frame and a phase array antenna circuit coupled to the at least one phase array antenna frame; and controlling the at least by the phase array antenna circuit A phased array antenna frame transmits or receives wireless personal area network compatible signals from the wireless local area network device, wherein the phase array antenna circuit includes a plurality of phase shift injection double push oscillators (PSIPPOs).

29. A circuit for driving a phased array antenna wireless communication system, comprising: a. an oscillator circuit for providing a reference signal; b. at least two stages for manipulating the phase array antenna frame created by the phase array antenna frame a beam phase shift injection locked double push oscillator (PSIPPO); c. an upconverter for upscaling a signal transmitted by the phase array antenna and for downsampling a signal received by the phase array antenna And a d. a transmission line for selectively providing a phase offset to a reference signal supplied to the up or downconverter.

30. The circuit for driving a phased array antenna wireless communication system as described in system 29 above, wherein at least one of the at least two phase phase shift injection locked double push oscillators is used for horizontal steering by the phase array a beam created by the antenna frame, and the phase shift injection lock of the at least two stages At least one of the dual push-push oscillators is used to vertically manipulate a beam created by the phased array antenna frame.

With the rapid increase in the number of wireless accessories in homes and businesses, the need for broadband wireless access solutions has increased.

For example, IEEE 802.15 is a standard used to standardize these communication domains, which are divided into five subgroups 802.15.1-802.15.5. Among these standards, 802.15.3 for handling high-speed wireless personal area networks (WPANs) is particularly important for indoor wireless communications.

IEEE 802.15.3 Task Group 3c (TG3c) was formed in March 2005. For the existing 802.15.3 Wireless Personal Area Network (WPAN) standard 802.15.3-2003, TG3c is developing a millimeter-wave alternating physical layer (PHY).

The millimeter wave WPAN operates in a fresh frequency band and includes the 57-64 GHz unlicensed band as defined by FCC 47 CFR 15.255. The millimeter wave WPAN will have high coexistence (close physical separation) with all other microwave systems in the 802.15 family of WPAN.

In addition, the millimeter-wave WPAN allows high data rate applications over 1 Gbit such as: high-speed Internet access, streaming content download (video on demand, HDTV, home theater, etc.), instant streaming and wireless data sinking To replace the cable. It provides a selective data rate of over 3 Gbits.

It is technically difficult to install communication systems in this frequency range to have broadband capabilities while at the same time meeting commercial low-cost requirements.

Multiple Input Output (MIMO) is one of the ways to install this communication domain. However, there are several reasons (such as: analog calculations and mechanical factors) that will allow MIMO is considered unsuitable for the aforementioned requirements. There is an urgent need for novel technologies to provide a cost effective system that meets the needs of high frequency, high frequency and low cost. The indispensable technical system performance to achieve this benefit is the enhancement of antenna beam focus and the wideband beam steering capability of the antenna. One possible solution is the use of a phased array antenna system.

A method and system for installing a WPAN by a phased array antenna device will be described herein.

A wireless area network communication system is provided, comprising: at least one phase array antenna frame coupled to a phase array antenna circuit of the at least one phase array antenna frame, wherein the phase array circuit and the at least one phase array antenna frame are The wireless local area network compatible signal is transmitted to the wireless local area network device or receives the wireless local area network compatible signal from the wireless local area network device.

In an exemplary embodiment of some systems, the phased array antenna frame transmits or receives radiation. In an exemplary embodiment of some systems, the phased array antenna circuit is used to drive and control the at least one phased array antenna frame.

In an exemplary embodiment of some systems, the wireless local area network is a wireless personal area network. In an exemplary embodiment of some systems, the phased array antenna frame includes at least two transmitter groups, wherein one of the transmitter groups is defined as a reference group.

In some exemplary embodiments of the system, one of the transmitter groups is controlled by the phase array circuit and transmitted or received with a phase offset relative to the reference group. In some exemplary embodiments of the system, the phase offset is programmable or written in the code. Demonstration in some systems In an embodiment, the phased array antenna frame includes at least two substantially linear one-dimensional emitter arrays. In an exemplary embodiment of some systems, the phased array antenna frame includes an even number of substantially linear one-dimensional emitter arrays, wherein each substantially linear one-dimensional emitter array includes two N-th power emitters, and N Is an integer greater than 1.

In an exemplary embodiment of some systems, the phased array antenna frame includes a substantially hexagonal emitter. In an exemplary embodiment of some systems, the system selectively switches between different modes of radiation with each group of transmitters. In some exemplary embodiments of the system, the radiation pattern is determined by the number of transmitter groups that can be transmitted and received at different phase offsets, and based on the programmable phase offset. In an exemplary embodiment of some systems, the phase array circuit controls the phased array antenna frame to radiate with a horizontal beam aperture. In an exemplary embodiment of some systems, the horizontal beam aperture width is substantially between 3 and 15 degrees. In some exemplary embodiments of the system, the system can be used to communicate with a plurality of wireless local area network devices. In some exemplary embodiments of the system, the system can be used to communicate with a personal computer.

In some exemplary embodiments of the system, the system can be used to communicate with at least one television device. In some exemplary embodiments of the system, the programmable phase offset is +/- 180 degrees. In some exemplary embodiments of the system, the programmable phase offset is +/- 180 degrees and the programmable phase offset can be created by reversing the signal phase by a transmission line. In an exemplary embodiment of some systems, the wireless local area network compatible signal is transmitted in a band of about 57 to 64 GHz. In an exemplary embodiment of some systems, the system is selected Switch between the two radiation modes selectively. In an exemplary embodiment of some systems, the system selectively switches between two radiation modes, and wherein the at least one phase array antenna frame includes two linear one-dimensional emitter arrays.

In an exemplary embodiment of some systems, the system selectively switching between different radiation modes depends on the level of signals received in the different phase modes. In some exemplary embodiments of the system, the horizontal beam aperture can be horizontally manipulated in accordance with a programmable mode. In some exemplary embodiments of the system, transmitting and receiving wireless local area network compatible signals comes from or can be selectively implemented by the wireless local area network device through the building wall. According to a preferred embodiment of the present invention, a method of installing a wireless communication is provided, comprising the steps of: providing at least one phase array antenna frame and a phase array antenna circuit coupled to the at least one phase array antenna frame; and by using the phase An array antenna circuit controls the at least one phase array antenna frame to transmit or receive wireless personal area network compatible signals to and from the wireless local area network device.

In accordance with an exemplary embodiment of the present invention, a room having two fixed phase array antenna systems and two personal computers having phase array antenna systems is provided.

In accordance with an exemplary embodiment of the present invention, a room having a fixed phase array antenna system and a plurality of personal computers having phase array antenna systems is provided.

According to an exemplary embodiment of the present invention, a personal computer having two fixed phase array antenna frames and two phase array antenna systems is provided The room is in the first radiation mode.

In accordance with an exemplary embodiment of the present invention, a room having two fixed phase array antenna frames and two personal computers and a television having a phased array antenna system is provided and in a second radiation mode.

In accordance with an exemplary embodiment of the present invention, signal dispersion may exist in various rooms of the same floor.

In accordance with an exemplary embodiment of the present invention, a phased array antenna frame is provided.

In accordance with an exemplary embodiment of the present invention, a phased array antenna frame is provided that includes different units for receiving and transmitting.

In accordance with an exemplary embodiment of the present invention, in a first mode of operation, a phased array antenna frame suitable for a radiation pattern is provided.

In accordance with an exemplary embodiment of the present invention, in a second mode of operation, a phased array antenna frame suitable for the radiation pattern is provided.

In accordance with an exemplary embodiment of the present invention, a circuit for installing a phased array antenna circuit that supports a combination of two modes of operation is provided.

In the PCT application PCT/IL2006/001144, filed on Oct. 3, 2006, and PCT/IL2006/001039, filed on Sep. 6, 2006, the disclosure of And lightweight and decentralized T/R multi-module components and circuit design. The circuits described in these publications can be mounted as low cost and small size circuits or as integrated wafers to generate and control signals transmitted and detected by the phase array antenna. Any or all of the teachings of these publications can be referenced to provide a suitable phased array antenna for mounting the invention as will be described below.

It provides a phase array antenna system configuration 3100A. It contains a living room 3101 and has two personal computers 3130, 3140 located in different locations in the room. Each personal computer has a phase array antenna system 3117, 3122, respectively. Each phase array antenna system includes a phase array antenna frame 3115, 3120, and a phase array antenna for controlling and driving circuits 3116 and 3121 (referred to herein as "phase array antenna circuits").

In an exemplary embodiment of the invention, there are two fixed phase array antenna systems 3107, 3112 located at different corners of the room. Each of the systems 3107 and 3112 also includes a phase array antenna frame 3105, 3110, and a phase array antenna circuit 3106 and 3111, respectively.

Each phase array antenna frame is used to transmit and/or receive data. 3150, 3160, 3155, and 3165 are radiation patterns of the phase array antenna frames 3105, 3115, 3110, and 3120, respectively.

In an exemplary embodiment of the invention, a phased array antenna system 3107 will horizontally manipulate its beam 3150 (azimuth steering) until it reaches an optimal receiving phase from the phased array antenna system 3117. The same procedure can also be applied to phase array antenna system 3117, which will horizontally manipulate its beam 3160 until it reaches an optimal reception phase from the phase array antenna system 3107.

The same procedure can be applied to phase array antenna systems 3112 and 3122. In accordance with the present invention, the narrow horizontal beam aperture and low side lobes of the phased array antenna system are designed to prevent side lobes from occurring.

Once the optimal level of signal reception is reached, the phase array antenna system The orientation can be selectively memorized to enable rapid initialization upon subsequent reopening. The entire area of a rectangular room can be covered with just two systems.

In another exemplary embodiment of the present invention, an independent phase array antenna system 3107 can communicate with three phase array antenna systems 3117, 3122, and 3172, and phase array antenna systems 3117 and 3122 are connected to personal computer devices 3130 and 3140, respectively. The phase array antenna system 3172 is connected to a television device 3169.

The ability of the system to function independently is taken from the beam steering of all antennas, which will be further described. In order to transmit and receive data from a plurality of phase array systems, the phase array system 3107 can be directionally manipulated and electronically rotated to an ellipse 3150 pointing to the personal computer 130, an ellipse 3152 pointing to the personal computer 3140, and an ellipse 3153 pointing to the television 3169. Between locations. After a short lock between the fixed system and the PC/TV/mobile phone, the communication with the PC device will be two-way, and the communication with the TV will be one-way, ie the TV phase array antenna system will only Can receive data.

The antenna can be manipulated by the phased array antenna system very quickly, typically switching from the first beam direction 3150 to the second beam direction 3152 or 3153 typically takes only a few milliseconds.

The independent phase array antenna system can simultaneously communicate with multiple WPAN devices based on time sharing, and the number of devices is limited by the bandwidth requirements of the device and the bandwidth capability of the phase array antenna system. When a phase array antenna system 107 and three phase array antenna systems 3117 and 3122 The phase array antenna system 107 may also communicate with any other WPAN compatible device other than the phase array antenna system during communication.

With respect to the phase array antenna beam, there is a primary radiation lobes in the first radiation mode, such as: 3150, 3155, 3160, and 3165, the lobes having an aperture of about 30 degrees in the vertical direction, which can be between the two communication devices. Provide a good coverage when you have a clear line of sight. However, in a dynamic environment, when an obstacle such as a person passes through a room, the line of sight between the devices in the communication will be obscured, and thus other methods are required.

For the same room 3101 where the line of sight between the two phase array antenna systems 3112 and 3122 is obstructed by the person 3180, when the system detects that the signal level reception is weak, it will switch to the second radiation mode. That is, each of the single main valves 3165 and 3155 will be divided into two main lobes, that is, 3155 will be divided into 3155A and 3155B, and 3165 will be divided into 3165A and 3165B. The two main lobes radiated by the phased array antenna frame transmit and receive radiation via an indirect path to transmit and receive electromagnetic waves that are returned by the environment, primarily from surrounding walls, such as by dashed lines and component symbols 170. The path indicated.

Regarding a signal dispersed in nine rooms 3193 of the same floor 3100E: in the input range, the signal is intercepted by an antenna 3190 and received by a primary phase array antenna 3191. The signal is transmitted and received by a set of phased array antennas 3192a-3192r. The signal can be transmitted and received through the wall of the room, for example, as it passes through the wall array 3194 from the phase array antennas 3192b through 3192e. The relatively low attenuation of high frequency radiation allows it to pass through common rooms such as concrete, plywood, mud bricks, Glass and the like. For example, a 5.8 GHz signal is about 7 dB weak due to a typical concrete wall. Thus, a single primary and a set of phased array antennas provides complete wireless coverage of the entire door. Its output range is symmetrical but opposite.

The phased array antennas 3192a-3192r can also act as transponders to compensate for the degradation of the signal along its path, as the use of a set of transponders to spread the signal is a technique known in the art and will not be described in detail herein.

A radiating portion 3200A of a decentralized active phase array antenna (APAA) (referred to herein as a "phase array antenna frame") is described herein, which includes two one-dimensional arrays of microstrip line emitters (referred to herein as The "transmitters" 3210, 3215 are located on a rectangular housing 205 and comprise a dielectric substrate and associated substrate. The one-dimensional emitter array includes eight emitters, designated A1 through A4, B1 through B4, respectively. Each emitter is a hexagonal patch, for example, emitters A1, 3230. Each transmitter has a supply source (an I/O port for reciprocating electromagnetic waves to the transmitter) 3235, which may be located at the apex of the transmitters (A1 to A4) or at a low point of the transmitter (e.g., B1 to B4). . Hexagonal transmitters, according to analog displays, provide better results than square or circular emitters in terms of transmission gain and/or receive gain and isolation between adjacent emitters at the same distance from each other. .

In an exemplary embodiment of the invention, the sources of the transmitters are arranged in a symmetrical configuration. In the first one-dimensional emitter array, the source of the emitter is located at the apex of the hexagonal patch, while in the second one-dimensional emitter array, the source of the emitter is located at the lower of the hexagonal patch. point. It should be understood that the symmetric arrangement of the source of the emitter can selectively increase the symmetry of the radiation pattern. Contribution.

The size of the antenna depends on the frequency of the wave and the dielectric constant of the substrate. For example, at 60 GHz, a WPAN emitter mounted on a substrate having a dielectric constant of 6 has dimensions on the order of millimeters. Such a small structure allows the phased array antenna described in the present invention to be included in various handheld devices such as a palmtop computer, a personal data integration device (Blackberry), a mobile phone, a notebook computer, and the like.

In an exemplary embodiment of the invention, the same physical emitter array produces different radiation patterns (referred to herein as "radiation modes" in order to maintain high power density and achieve a wider coverage angle to communicate with the devices described above. ).

Alternatively, the plurality of radiation patterns generated by antenna 3200 can be defined by a relative phase offset to a signal between two one-dimensional emitter arrays 3210, 3215.

In an exemplary embodiment of the invention, a first radiation pattern is defined by providing the required phase to the two one-dimensional emitter arrays 3210 and 3215, such that the elements in each of the first one-dimensional arrays" There will be no phase difference between the corresponding element "B" in A" and the second one-dimensional array. A second radiation pattern is defined by providing the required phase to the two one-dimensional emitter arrays 3210 and 3215, such that element "A" and the second one-dimensional array in each first one-dimensional array There will be a 180 degree phase difference between the corresponding elements "B".

It is possible to transmit and receive via the same transmitter and sometimes it is a more efficient architecture. However, in an exemplary embodiment of the invention, its transmission and reception are performed by the transmitting transmitter and the receiving transmitter, respectively. use The scheduling of different transmitters to transmit and receive can be implemented using various topologies, such as spreading functions into two different phase array frames or alternatively defining sub-groups of transmitters in a phase array frame to Complementary subgroups are used for transmission when receiving.

In order to establish the above two radiation modes and when using phase array antenna control and drive circuits to be further described later, the phase array antenna frames should be horizontally aligned.

In accordance with an exemplary embodiment of the present invention, a phased array antenna transceiver can be provided where transmission and reception are performed by two different units. As will be further described later, separating the receiving unit and the transmitting unit will provide technical and economic benefits when the radiation frequency is high.

The receiving and transmitting units basically have the same structure. For example, the transmission unit on the left side may have transmission transmitters A1T-A4T and B1T-B4T. For example, the receiving transmitters shown on the right are labeled A1R-A4R and B1R-B4R. The supply sources of the transmission unit are labeled 3261a-3264a and 3261b-3264b, and the supply sources of the receiving unit are labeled 3265a-3268a and 3265b-3268b.

A connection is provided between germanium wafers 3270-3279 comprising electronic circuitry (referred to herein as phased array circuitry) that provides antenna control.

The defined length microstrip lines 3261a-3268a and 3261b-2368b are sources of the emitter and are located on the upper surface of the dielectric substrate (not shown). The hexagonal patch is located on the upper surface of the second substrate (not shown), covering the previous one, so that there is efficient energy electromagnetic conversion between the supply source and the patch.

In the transmitting unit, the supply sources 3261a-3264a and 3261b-3264b are used to transfer the carriers generated and processed by the circuits 3270-3274 to the transmitter. A1T-A4T and B1T-B4T, when in the receiving unit, receive signals transmitted by the transmitters A1R-A4R, B1R-B4R, and down-convert the signals generated and processed by the circuits 3275-3279 to the baseband.

Circuitry defined as 3270-3274 and 3265-3279 are described in detail in the cited prior specification.

The radiation pattern is created by the first radiation pattern. The radiation pattern 3310 has a vertical aperture 3312 of about 30 degrees that is wide enough to cover a stationary device at a standard table height in a typical room of a home or office. The electromagnetic beam cannot be manipulated at a high altitude.

The radiation pattern 3320 is created by the first radiation pattern. The radiation pattern has a horizontal aperture 3325 of about 5 degrees. A narrow horizontal beam aperture allows power to be concentrated at a narrow angle and has a low side lobes rating. The orientation of the electromagnetic beam can be manipulated to allow it to scan a wide azimuth.

The radiation pattern is created by the second radiation pattern. The radiation pattern has two main lobes 3330A and 3330B. In an exemplary embodiment of the invention, the power radiated by the second radiation mode is equal to the first mode, but the gain of each of the lobes is half of the gain of the first mode. However, this mode allows for a wider dispersion of radiation data (along with the wide angle of data reception) to allow for indirect communication. The two main lobes created in the second radiation mode are facing the floor and ceiling, and part of the radiation is reflected from the ceiling and the floor (or from other items in the room) to the target antenna.

The electromagnetic beam cannot be manipulated at a high altitude.

The radiation pattern is created by the second radiation pattern. However, in the horizontal plane, the radiation patterns of the first and second radiation modes have the same holes. Electricity The orientation of the magnetic beam can be manipulated to allow it to scan a wide azimuth.

The first radiation mode is generated when the signals of the transmitters A1-A4 and the corresponding B1-B4 have a phase difference of 0 degrees.

The second radiation mode is generated when the signals of the transmitters A1-A4 and the corresponding B1-B4 have a phase difference of 180 degrees.

In accordance with an exemplary embodiment of the present invention, the base of the circuit provides a carrier signal to the transmitter array.

Although it is effective to use the same antenna as a receiving (R/X) unit and a transmitting (T/X) unit at a relatively low frequency, a circuit connected to this function involves a transmitter at a high frequency such as 60 GHz. The small size of the array is incompatible with semiconductor real estate, so it is best to separate the functions of T/X and R/X into two different subsystems. As will be further described later, the physical structure difference between the transmitting unit and the receiving unit is extremely small, and the different functions are only the UP converter for the T/X 3491i-3491p and the DOWN conversion for the R/X 3491a-3491h. Device. It's basically the same circuit, just different ways of using it. The UP converter is located at the input of the T/X power amplifier, while the DOWN converter is located at the output of the R/X low noise amplifier.

The circuit uses an oscillator unit 3405 that outputs to two distribution units 3409, 3410. The power splitter 3409 provides the reference signal to the R/X unit, and the power splitter 410 provides the reference signal to the T/X unit. Unless there is a substantial difference, the T/X unit will be described as an extension, otherwise the following description will only be for the R/X unit. This signal will arrive at the first stage of the PSIPPO (Phase Offset Double Push Oscillator) 3420-3421. In PSIPPO this The phase offset determined in each phase will be used to manipulate the electromagnetic beam.

The signal then passes through another stage of distribution elements 3430-3431 (power splitter) and proceeds to the second stage of PSIPPO 3435a-3435d. Those skilled in the art will appreciate that the phase offset determined at this stage of PSIPPO contributes to manipulating the electromagnetic beam. Applying a zero degree phase shift in the first phase 3420, 3421 and the second phase 3435a-3435d of PSIPPO will result in a substantially vertical beam, i.e., its axis of symmetry being perpendicular to the surface of the antenna.

In the next phase, the signal is passed to four power splitters 3440-3443 and handed over to the multi-function block 3450-3453. As long as the above blocks have the same structure, only one phase shift unit 3450 will be described.

In general, a block 3450 includes two branches, each connected to transmitters 3495a and 3495b. The transmitter is represented by A1 and B1. Branch 3284a will pass the carrier signal to the connected mixer at a particular phase. The second branch 3480a-3482a will pass the same signal to the connected mixer at a phase equivalent to branch 3484a, or offset by 180 degrees, depending on the position of switches 3480a and 3482a. As such, the emitter array will produce the two radiation patterns described above. Alternatively, the transmission line 3481a is subjected to a phase shift greater than or less than 180 degrees. The down-converter mixers 3491a and 3491b receive signals amplified by the low noise amplifiers 3492a and 3492b from the antenna patches 3495a and 3495b, respectively, and generate input signals 3490a and 3490b, respectively.

The difference between the T/X path and the R/X path is that the mixer is an upconverter mixer 3491i-3491p that receives the data signal 3490i-3490p and generates The amplified signal is amplified by the amplifier 3495i-3495p and transmitted to the output signal of the antenna patch 3495i-3495p.

In theory, the phase difference between the two branches can be achieved by adding an additional phase of PSIPPO to each mixer. This method will require more components.

Delay elements 3481a-3481h are a simple, low cost transmission line, like electronic switches 3480a-3480h and 3482a-3482h. Compared to solutions with additional stages of PSIPPO, the use of electronic switches and delay elements can simultaneously reduce price and size.

In another exemplary embodiment, the path from the distributor 3440 to the down-converter 490a (and all equal paths) also includes a selective phase offset path that allows the circuit to be programmed for more Phase offset combination.

In some embodiments of the invention, a WPAN phased array antenna system may switch between more than two radiation modes with an equal or different number of linear emitter arrays.

In some embodiments of the invention, the WPAN phased array antenna system provides a phase offset greater than or less than 180 degrees to the one-dimensional emitter array.

In some embodiments of the invention, the WPAN phased array antenna system includes more or less than two linear emitter arrays.

In some embodiments of the invention, the WPAN phased array antenna system includes various transmitter combinations that are different from the linear transmitter array, ie, any subset of transmitters reference any reference subgroup and a programmable phase offset Make a combination.

In some embodiments of the invention, the WPAN phase array antenna system package A radiation pattern containing an azimuth beam that is narrower or wider than previously described.

In some embodiments of the invention, the WPAN phased array antenna system includes a radiation pattern that is narrower or wider than the aforementioned vertical beam aperture, and its vertical beam dispersion is different from the form described herein.

In some embodiments of the invention, the WPAN phased array antenna system can implement a periodic horizontal antenna steering to search for a transmitting device that can communicate with the system.

The above methods and systems can be varied in many ways, including deleting or adding steps, changing the order of the steps and the type of device used. Therefore, different features can be combined in different ways.

A device based on a dual-push oscillator for radar imaging will be described herein, which can be used in conjunction with the system shown in Figures 1-24, and in accordance with the architecture and operation taught by U.S. Patent No. 7,800,453 to Alberto Milano. The device is related to radar imaging and phase array antennas. The device is also associated with a transmit/receive module, a dual push oscillator, and an injection-locked push-push oscillator for a phased array antenna.

The following embodiments based on an apparatus for injecting a double push oscillator for radar imaging may be coupled with the system shown in Figures 1-24:

A reference signal generator comprising: a quartz oscillator; and at least one phase phase shift injection locked double push oscillator connected in series with a quartz oscillator; wherein the phase shift injection locked double push oscillator comprises one or A plurality of push-push oscillators are capable of receiving an injection signal of a specific frequency and phase, and generating a signal having a frequency that is greater than an even multiple of the input frequency and having a phase offset from the injection signal.

2. Reference signal generator 1, wherein the reference signal generator comprises only two stages of phase shift injection locked double push oscillator.

3. Reference signal generator 1, wherein the reference signal generator comprises at least first and second phase phase shift injection locked double push oscillators.

4. Reference signal generator 3, wherein at least one single stage double push oscillator comprises more than one phase shift injection locked double push oscillator.

5. The reference signal generator 1 further includes a plurality of phase shift injection locked double push oscillators that form a tree structure.

6. A transmission/reception module comprising: at least one phase of a phase shift injection locked double push oscillator; and a receiving function for receiving radiation radiated from a phase shift injection locked double push oscillator for transmission/reception Sampling power; wherein the phase shift injection locked double push oscillator comprises one or more double push oscillators that can receive an injection signal of a specific frequency and phase and generate a frequency having an integer multiple of an even multiple of the input frequency. Signal and phase offset from the injected signal.

7. A transmit/receive module 6, wherein the transmit/receive module includes a plurality of phase shift injection locked double push oscillators.

8. A transmit/receive module 6, wherein the receive function comprises a direct balance downconverter.

9. The transmit/receive module 6, further comprising a plurality of phase shift injection locked double push oscillators forming a tree structure.

10. A radar imaging apparatus comprising: a reference signal generator according to embodiment 1; a phased array antenna comprising at least one transmission/reception module having a phase shift injection locked double push oscillator; and a reference signal generator and at least An additional device in series with a transmit/receive module to generate a radar image.

11. Imaging radar device 10, wherein the transmit/receive module includes at least one phase of a phase shift injection locked double push oscillator.

12. An imaging radar device comprising: a reference signal generator; at least one transmit/receive module 6; and additional means in series with the reference signal generator and the at least one transmit/receive module to generate a radar image.

13. A method for generating a reference signal for radar imaging, the method comprising: concatenating a quartz oscillator with a phase shift injection locked double push oscillator having at least one stage, wherein the phase shift injection lock double push oscillation The device includes one or more push-push oscillators that receive an injection signal of a particular frequency and phase and produce a signal having a frequency that is greater than an even multiple of the input frequency and phase shifted from the injected signal.

14. Method 13, wherein the quartz oscillator is coupled in series with a plurality of stages of phase shift injection locked double push oscillators.

15. The method of claim 13, wherein the phase shift injection locked double push oscillator of the at least one stage comprises only two stages of phase shift injection locked double push oscillators.

16. The method of claim 13, wherein the at least one single phase phase shift injection locked double push oscillator comprises more than one phase shift injection locked double push oscillator.

17. A method for generating a radar transmit/receive module of a phased array antenna, comprising: providing at least one phase of phase shift injection locked double push oscillator; and a receiving function for receiving phase shift injection locked double push oscillation The sampled power radiated by the device; and the phase shift injection locked double push oscillator includes one or more double push oscillators that receive an injection signal of a particular frequency and phase and produce an even number than the input frequency Integer multiple frequency The signal is phase shifted from the injected signal.

18. The method of claim 17, further comprising concatenating the reference signal generator and the additional device with the at least one phase of the phase shift injection locked double push oscillator to generate a radar imaging pattern.

19. A method of radar imaging, comprising: serially coupled to a reference signal generator comprising at least one phase of a phase shift injection locked double push oscillator, a phase array antenna including at least one transmit/receive module, and An additional device for generating a radar imaging image; and wherein the phase shift injection locked double push oscillator includes one or more double push oscillators that receive an injection signal of a particular frequency and phase and produce a ratio of input frequencies An even integer multiple of the frequency of the signal and phase offset from the injected signal.

20. Method 19, wherein the transmit/receive module includes at least one phase of a phase shift injection locked double push oscillator.

21. The method of claim 19, further comprising: at least the first phase and the second phase of the phase shift injection locked double push oscillator.

22. The method of claim 19, further comprising: concatenating a phased array antenna including a reference signal generator, including at least one transmit/receive module, a phase shift injection locked double push oscillator including at least one stage, and a broadcast device Generate a radar image.

23. Method 19, wherein the reference signal generator comprises a quartz oscillator.

A T/R (transmit/receive) module for a phased array antenna and an imaging radar is described herein.

Double push oscillators are known in the art. Injection locking oscillators are known in the art. Pre-packages associated with double push oscillators and injection-locked single-ended oscillators Contains the following publicly available materials: Yoon, SW, etal. "A compact GaAs MESFET-based push-push oscillator MMIC using . . . " IEEE 2001 GaAs Digest, p. 45 onward; Sinnesbichler, FX "Hybrid millimeter-wave push -push oscillators . . . ", IEEE Transactions on Microwave Theory and Techniques, Vol. 51(2), February 2003, p. 422 onward; Xiao, H. et al, "A low phase noise Ku-band push push oscillator. . . 2004 IEEE MTT-S Digest, p. 1333 onward; Ramirez, F. et al, "Nonlinear simulation techniques for the optimized design of push-push oscillators . . .", 2003 IEEE MTT-S Digest, p. 2157 onward; Dussopt, L. et al, "A low phase noise silicon 9 GHz VCO and an 18 GHz push-push oscillator", 2002 IEEE MTT-S Digest, p. 695 onward; Sinnesbichler et al, "A 38-GHz Push-push oscillator . . . " IEEE Microwave and Guided Wave Letters, Vol. 9(4), April 1999, p. 151 onward; Kurokawa, K., "Injection locking of microwave solid-state oscillators", Proceedings of the IEEE , 61(10), October 1973, p. 1386 onward; Jezew Ski, MT, "An approach to the analysis of injection-locked oscillators", IEEE Transactions on Circuits and Systems, CAS-21(3), May 1974, p. 395 onward; Plessas, F. and Kalivas, G., "Locking Techniques for RF oscillators . . . ", ICECS-2003, p. 986 onward; Pavio. AM and MA Smith. "Push-push dielectric resonator oscillator", 1985 IEEE MTT-S Digest, p. 266 onward; Pavio, A. M and M. A. Smith, "A 20-40-GHz push-push dielectric resonator oscillator", IEEE Transactions on Microwave Theory and Techniques, MTT-33(12), December 1985, pp. 1346 onward; and Winch, RG, "Wide- Band varactor-tuned oscillators", IEEE Journal of Solid-State Circuits, Vol. SC-17(6), December 1982.

The present invention provides an improved phased array antenna that includes a T/R module based on an injection locked double push oscillator.

The present invention provides a method for simplifying the receive path of a T/R module by using a direct conversion mixer to demodulate the received signal immediately after the antenna. Each receive path can include a receive antenna and a receive protector, a single stage low noise amplifier (LNA), and a direct downconverter. Conversely, in conventional high resolution systems such as aerospace radar systems, in general, the receive path includes the above components, three switches, a multi-stage media power amplifier, and a phase shifter.

Reducing the production cost, size and weight of the radar main frame is the goal of this case.

Reducing the complexity and production cost of the T/R module is the goal of this case.

Reducing the loss caused by the phase shifter on the transmission path of the T/R module is also the goal of the present invention.

Improving the linearity of the phase offset of the operating frequency to the operating frequency is also a further goal to be achieved in this case.

Improved by limiting the size of the LNA (low noise amplifier) amplification chain The third harmonic intercept point (IP3) of the RX (receiver) is also the target of this case.

By providing a double push oscillator circuit embedded in a chain of T/R modules constructed and operated in accordance with an embodiment of the present invention, an embodiment can achieve all of the above advantages, one, some or all of the following features And complete the direct down frequency: The traditional phase shifter can be completely eliminated.

The reference signal generated by the radar main frame has a lower frequency than its radiation signal, making it less susceptible to power consumption.

The total phase offset of the signal is preferably divided between the independent push-push oscillator circuits, for example, into three PS-IPPO stages, each having a phase shift of 120 degrees, with a total phase offset of 360 degrees. The phase sweep result can be improved by increasing the frequency of the double push oscillator.

The structure of the radar main frame is composed of simpler, cheaper and smaller components than conventional components.

The signal power delivered to each new T/R module can be even lower than that required by traditional T/R modules, resulting in improved overall system efficiency.

The mechanical structure of a high-resolution phased array antenna based on the T/R module shown and described herein and suitable for aviation radar applications can be the same as the conventional antenna of this type, that is, the TX and RX modules are integrated in the same mechanical shell. In the body.

Therefore, according to an embodiment, the present invention provides a reference signal generator comprising a quartz oscillator; and at least one stage of the double push oscillator connected in series with the quartz oscillator.

According to an embodiment, the present invention also provides a transmitting/receiving module, including At least one stage of the double push oscillator; and a receive function for receiving a sampled power radiated by the double push oscillator. The power radiated by the double push oscillator is sampled and the sampled result is received by the receive function.

According to an embodiment, the present disclosure further provides a radar imaging apparatus including a reference signal generator and a phase array antenna as described above, including at least one transmitting/receiving module and the transmitting device and the reference generator, and at least one transmitting/receiving The modules are connected in series.

Further in accordance with an embodiment, the transmit/receive module includes a plurality of stages of push-push oscillators.

According to an embodiment, the present invention also provides an injection-locked double-push oscillator device including a 0 degree power splitter. The 0 degree power splitter can divide the reference signal received with high stability and low noise characteristics into a first part and a second part, and the second part has an odd multiple of 180 degrees with respect to the first part. These two signal sections will enter the two reflection amplifiers of the double push oscillator and lock the signals already generated by the double push oscillator. The lock signal has the same stability and noise characteristics as the reference signal.

According to an embodiment, the present disclosure further provides an imaging radar apparatus including a reference signal generator, at least one transmission/reception module as described above, and a string string including a reference generator and at least one transmission/reception module Connected broadcast device.

Further in accordance with an embodiment, the transmit/receive module includes a push-push oscillator of at least one stage.

Further in accordance with an embodiment of the invention, the receiving function includes a direct balance downconverter.

Still further in accordance with an embodiment, the reference signal generator includes only two stages of double push oscillators.

Further in accordance with an embodiment, the reference signal generator includes at least first and second stages of double push oscillators.

According to an embodiment, the present invention also provides a method for generating a reference signal for radar imaging, the method comprising serially connecting a quartz oscillator to at least one stage of the double push oscillator.

According to an embodiment, the present invention also provides a method for generating a radar transmit/receive module of a phased array antenna, comprising providing at least one stage of a double push oscillator and a receiving function.

According to an embodiment, the present disclosure further provides a method for radar imaging, comprising: serially connected to a reference signal generator, comprising a quartz oscillator and at least first and second stage double push oscillators, including at least one transmit/receive A phase array antenna of the module, and a broadcast device.

Further in accordance with an embodiment, the quartz oscillator is coupled in series with a plurality of stages of double push oscillators.

According to an embodiment, the present invention further provides a method for injecting a locked double-push oscillator, comprising: separating a reference signal received with stability and noise characteristics into a first portion and a second portion, wherein the second portion is relative to the second portion The first portion has an odd multiple of 180 degrees; and a dual push oscillator is used to receive the first and second portions and generate a lock signal having stability and noise characteristics of the reference signal.

Further in accordance with an embodiment, the method also includes concatenating a reference signal generator and the broadcast device with the push-push oscillator of at least one stage.

Further in accordance with an embodiment, the transmit/receive module includes a push-push oscillator of at least one stage.

Further in accordance with an embodiment, the double push oscillator of at least one stage includes more than one double push oscillator.

Still further in accordance with an embodiment, the push-push oscillator of at least one stage includes only two stages of double push oscillators.

Further in accordance with an embodiment, the at least one single stage dual push oscillator comprises more than one double push oscillator.

According to an embodiment, a method for radar imaging is also provided, comprising: using a reference signal generator comprising a quartz oscillator and at least first and second stages of a double push oscillator, including at least one transmit/receive module A phase array antenna, and a cascade of broadcast devices to produce a radar image.

According to an embodiment, the present invention also provides a method for radar imaging, comprising using a phased array antenna including a reference signal generator, including at least one transmitting/receiving module, a double push oscillator including at least one stage, and a transmitting device The cascade is used to generate a radar image.

The present invention provides a dual push oscillator based transmit/receive module suitable for high resolution radar imaging applications.

The present invention provides a high resolution imaging radar apparatus based on an active phase array antenna that includes an array of transmit/receive modules such as, but not limited to, a transmit/receive module.

This case provides a conventional high-resolution transmission/reception module.

The present invention provides a transmitter subsystem based on an injection-locked double-push oscillator suitable for commercial applications such as, but not limited to, autonomous driving, The orientation and height of the leading wave of the bit array antenna can be manipulated.

Each of the transfer units based on the injection-locked double-push oscillator can perform azimuth manipulation in commercial applications such as, but not limited to, automatic driving.

The present invention provides a receiver subsystem that cooperates with a reference transmitter circuit to form an imaging radar system suitable for commercial applications such as, but not limited to, autonomous driving.

There is provided a phase scan injection-locked double-push oscillator (PS-IPPO) that is architecture and operational and is suitable for phase scan IPPO in accordance with an embodiment of the present invention.

There is provided a composite band reject filter (BRF) that is constructed and operated in accordance with an embodiment of the present invention.

There is provided a reference signal generator constructed and operative in accordance with an embodiment of the present invention, comprising one or more fixed phase injection locked double push oscillators.

An implantable double push oscillator is provided herein.

A transmission/reception module based on a push-push oscillator for a high-resolution imaging radar is provided herein. The so-called "high resolution" herein refers to devices suitable for aerospace radar applications and other applications requiring considerable accuracy. The apparatus includes a reference signal generator 10, at least one (three of the illustrated embodiments) injected into a cascade of locked double-push oscillators 15, each receiving a signal at a given frequency, and injecting The even multiple of the signal frequency passes the signal (the embodiment shown is twice the input frequency), and each has a specific phase depending on the system requirements, as will be described in detail herein; a digital adjustment attenuator 40, a power Amplifier 50, a coupler 55 for partial transmission The power is sampled for use by a mixer 90 as a regional oscillator, also referred to herein as a "balanced direct frequency downconverter", a circulator 60, a transmitter 65, a receive protector 75 and a low noise. Amplifier 70. In general, the mixer 90 outputs to a conventional digital signal processor (not shown).

The T/R module forms part of the phased array antenna for high resolution imaging radar. Among several other advantages, it is possible to reduce the losses caused by conventional T/R modules by phase shifting. According to an embodiment of the invention, the transmission path of the T/R module includes a chain consisting of three injection-locked double-push oscillators 15, 20 and 30; a digital adjustment attenuator 40, a power amplifier 50, and a coupling The device 55, a circulator 60 and a transmitting transmitter 65. Conversely, in general, the transmission path of a conventional high-resolution system includes three switches (300, 310, 320), a digital adjustment attenuator 360, a multi-stage medium power amplifier 370, a phase shifter, and a power. An amplifier, a circulator 355 and a transmitter 365. In general, three switches, phase shifters, multi-stage media power amplifiers, and digital adjustment attenuators are common transmission and reception paths in conventional systems.

In general, when the system completes a full phase scan, each oscillator operates within a much smaller range than the drawstring that produces the safe lock operating conditions.

At the output of the injection locked phase offset double-push oscillator chain, a transmitter 65 is coupled to radiate the RF signal with an appropriate phase offset.

In accordance with a first embodiment of the present invention suitable for high resolution applications, in general, an RX transmitter has one and the same as a TX transmitter (both represented by component symbol 65) from which the integrated transmitter is The circulator 60 operates and can be appropriately switched between TX and RX. Suitable for the present invention In a second embodiment of the commercial application, in general, the TX antenna of the transmission subsystem is adjacent to the RX antenna of the receiving subsystem, and the distance between the two is similar to the transmitter without significantly affecting the receiver.

There is provided an apparatus for imaging radar comprising a radar main frame 100, a manifold 110, and a phase array antenna 180, generally comprising a transmit/receive module array 120, 130, 140 and 150 . Each T/R module can be constructed and operated as described below, or can be a conventional T/R module. The leading wave of the above device is indicated by element symbol 170. The steering angle ALPHA is indicated by the symbol 160.

There is provided a conventional transmission/reception module comprising first, second and third switches 300, 310 and 320 having selectable transmission paths or reception paths. It is known from the specific positions of the three switches that they are selected as the receiving path. The receiving path includes a transmitter 365, a circulator 355, a receiving protector 340, a multi-stage low noise amplifier 350, a third switch 320, a digital adjustment attenuator 360, a multi-stage medium power amplifier 370, a phase The offset 380, the switch 310 and the switch 300. The transmission path includes a first switch 300, a second switch 320, a digital adjustment attenuator 360, a multi-stage media power amplifier 370, a phase shifter 380, a second switch 310, a typical multi-stage power amplifier 360, and a circulator 355. And transmitter 365.

In general, a phased array antenna includes an array of emitters, each coupled to a T/R module, radiating a signal with a particular phase associated with a given phase reference. In a conventional T/R module, the component that changes the phase of the radiated signal is a circuit called a "phase shifter." Although there are several types of phase shifter components, they are expensive to manufacture, especially for MMIC technology. In conventional systems, the signal input to the T/R module has the same frequency as the radiated signal. In the other shortcomings of the traditional T/R module as described below, the significant power loss of the "managation" (signal to the decentralized network of each T/R module) has a negative impact on it, which is often the operating frequency. Added features. The size and weight of the manifold are also one of the shortcomings of the high-resolution phased array antenna used in conventional aviation.

High-frequency signals transmitted to conventional T/R modules can cause the main frame of conventional radar systems to be forced into integrating expensive and relatively high DC power consumption circuits, such as PLL-controlled high-frequency oscillators, prescalers And power amplifiers. In addition to the phase shift operation, each T/R module also has the function of increasing the received signal power at the input port.

In conventional T/R modules, due to the use of phase shifters, it is necessary to compensate for the loss of the phase shifter, typically about 5-7 dB, so that efficiency is reduced.

In radar "frequency agility" operation, the beam focus of the antenna radiation pattern (used to determine the ability of the system to properly track the target) is negatively affected by the phase shifter's frequency nonlinearity. For high frequency and MMIC technologies, the screening of components reduces the yield of the product and thus increases its production costs. When switching to the receive path, the power consumption of the phase shifter reduces the system's third harmonic intercept point (IP3). When switching to the receive path, the power consumption of the manifold reduces the efficiency of the system.

The present invention provides a transmitter subsystem based on an injection-locked double-push oscillator for manipulating the orientation and height of a phased array antenna leading wave and applying it to commercial applications such as, but not limited to, autonomous driving. The circuit includes a reference signal generator 400 and a multi-module transmission unit 430 and 435. The unit 435 receives an input signal with the transmission unit 435 at the same power and frequency by a phase shift of 180 degrees by the 180 degree delay unit 420. The DSP 610, which is effectively coupled to the transmitter subsystem and the receiver subsystem, provides azimuth manipulation information obtained by the transmission units 430 and 435 and calculates altitude manipulation information.

There is provided a complete phased array antenna system for an imaging radar suitable for commercial applications such as, but not limited to, autonomous driving applications.

Separating the TX module and antenna from the RX module and antenna is believed to be the most cost-effective solution for commercial systems such as the FMCW (Frequency Modulated Continuous Wave) system for autonomous driving.

The device described herein simplifies the reception path of the T/R module by immediately demodulating the received signal after the transmitter by using a direct conversion mixer. In accordance with a first embodiment of the present invention suitable for commercial applications, each receive path includes a receive antenna and a direct downconverter.

Transmitting units 430 and 435 can receive signals having the same power level and frequency but having phases of 0 and 180 degrees, respectively. Each includes a transmitter based on an injection-locked double-push oscillator, which is generally only manoeuvrable in commercial applications such as autonomous driving. As shown, a plurality of stages of double push oscillators can be used, with at least one stage comprising more than one double push oscillator. In the illustrated embodiment, a three-stage dual push oscillator is provided, the first comprising a single oscillator 510, the second comprising two oscillators 530 and 540 and the third comprising four oscillators 570, 580, 585 And 590.

In general, all injection-locked double-push oscillators (IPPOs) in the device are phase scanned (PS) and can include phase scan IPPO. Produced by the present invention The phase offsets are all similar. Therefore, it can be affected by phase shift or temperature fluctuation caused by component aging. In order to ensure the focused radiation field beam of the TX antenna, based on the injection-locked double push oscillator (IPPO), the phase of the last circuit in each of the TX modules (eg, modules 570, 580, 585, and 590) can be A phase detector is periodically used to compare and correct a reference phase (eg, the signal phase of the module 590). For example, the phase of the signal radiated by the PS-IPPO 585 can be compared and corrected by the phase detector 587 with the reference signal of the PS-IPPO 590. Next, the signal phase radiated by the PS-IPPO 580 can be compared and corrected by the phase detector 582 with the new reference (i.e., the phase of the PS-IPPO 585). Next, the signal phase radiated by the PS-IPPO 570 can be compared and corrected by the phase detector 575 with the latest reference (ie, the phase of the PS-IPPO 580). In general, the results can be returned periodically and/or on demand, for example, once a minute to re-storage the focus of the radiation beam.

Phase detectors 575, 582, and 587 can have the same basic structure as the balanced direct downconverter described herein. However, in general, the way it is adjusted is different. The converter described below is adjusted by converting the RF signal into a baseband signal. The phase detector is adjusted to detect the phase between two RF input signals having the same frequency. Each phase detector receives a set of RF signals with the same power and frequency but different phases.

The receiver subsystem utilizes a partial sampling of the signal generated by a homogenous transmitter as a pump for the corresponding mixer of the transmitter.

In general, each of the receivers 640, 650, 660, and 670 includes a receive protector 680 coupled to a low noise amplifier (LNA) 685 and a The direct conversion mixer 690 is balanced. Suitable circuits for balancing the direct conversion mixer 690 in accordance with two different embodiments of the present invention are described separately below.

In general, the pumps used for each RX module are sampled by the corresponding (same) TX module. The so-called "LO signal" refers to the regional oscillator signal corresponding to the receiver (640, 650, 660 or 670). The output of the RX module is directly baseband and transmitted to a digital signal processor (DSP) 610.

The DSP analyzes the data from the radar echo and produces information for image manipulation. A screen display (not shown) will typically display an image of the target.

A phase scan injection-locked double push oscillator (PS-IPPO) has features that are specific to the functionality of the T/R module. In particular, various phase offset injection-locked double-push oscillators (e.g., oscillators 15, 20, and 30; oscillators 510, 530, 540, 570, 580, 585, and 590) of the present invention typically receive an injected RF signal and frequency thereof. Magnified by a multiple of 2*N, N is an integer, and its phase is changed to increase the phase sweep of the system. In general, the stability of the output signal is the same as the stability of the injected signal, and the noise spectrum of the output signal is generally only slightly reduced due to the increase in frequency.

There is provided a composite BRF for injecting block 710 that is constructed and operated in accordance with an embodiment of the present invention.

There is provided a reference signal generator constructed and operative in accordance with an embodiment of the present invention, comprising one or more fixed phase injection locked double push oscillators (CP-IPPO) 910...920. The output of the final CP-IPPO 920 is injected into a T/R module that is constructed and operated in accordance with an embodiment of the present invention. An embodiment of the invention includes two sets of dual architectures and operations in accordance with an embodiment of the present invention. Push the oscillator chain, such as phase shifted IPPOs 15, 20, and 30 and fixed phase IPPOs 1...M. Alternatively, only one of the chain links may be used.

The primary reference signal is generated by a quartz oscillator 900. The reference signal is characterized by high stability and low noise. The M double push series phase 910....920 of the first set of chain links is used as a fixed phase frequency multiplier to multiply the frequency of the main signal to a maximum factor (2*N)**M, as described below, N is an integer.

In commercial applications, the quartz of the T/R module can operate at ultra-high frequencies (UHF) such as 150.39 MHz: the reference signal input to the T/R module is multiplied by the first string of double-push circuits. After the frequency, the frequency can be 9.625 GHz. The radiated signal frequency can reach the desired level of 77 GHz after multiplying its frequency by the second set of strings of the PS-IPPO. In order to achieve this result, the parameters of the first group may be N=4 and M=2, and the parameters of the second group of chains may be N=1 and M=3, (multiplication factor={(2*N)** M}).

If the above exemplary parameters are used in the first and second sets of chain links of the high-resolution T/R module constructed and operated according to an embodiment of the present invention, the radiation frequency is, for example, 10 GHz, and then input to the T/R. The module's reference signal is 1.250 GHz and the quartz main oscillator has a frequency of 19.53 MHz.

The extremely low operating frequency of all of the above circuits saves the production cost of high-resolution imaging radars and has higher system reliability than traditional T/R modules. The double push oscillator constructed and operated in accordance with an embodiment of the present invention facilitates cascading, so that a circulator is not required to isolate the stages as in the case of a conventional frequency multiplier. The first set of chain links of the double push oscillator 910....920 constitutes the radar main frame The RF part of the rack.

The fixed phase injection locked double push oscillator includes a power splitter 1200 to directly inject half of the received power into a band rejection filter (BRF) 1210 and inject the other half of the received power into the 180 degree delay unit 1270. Reject filter 1210. A pair of reflective amplifiers 1230 and 1240 are injected into a power integrator 1250 and a filter 1260. The filter can be adjusted at 2*N*f0, where N is an integer such as 4.

The direct downconverter 90 or 690 generally includes a rat-ring power splitter 1300 (microstrip magic tee), two biasing diodes 1310 and 1320, and a filter 1330 injected into an output DSP (digital signal processing). Device).

Another option is provided herein, an in-phase quadrature phase mixer (I/Q mixer) being an embodiment of balanced direct frequency downconverter 90 or 690. The device includes a 90 degree power splitter 1400, a pair of balanced direct downconverters 1410 and 1420 and a zero degree power splitter 1430.

A layout suitable for transmitter array 595 and/or transmitter array 675 and/or 675A is provided herein. In order to present only the azimuth control of the transmitted beam, the signal to the connection terminals A-H have the following phases: 0, gamma, 2*gamma, 3*gamma, 180, 180+gamma, 180+2*gamma, 180+3*gamma. In order to present only a high degree of manipulation, the signals to the same connection A-H have the following phases: 0, 0, 0, 0, beta, beta, beta, beta. In order to present any combination of manipulations, the phase combinations described above are used. If the radiation pattern of the very low side lobes is desired, gamma and beta are antenna correlation coefficients; in the example shown, gamma can be between -125 degrees and 125 degrees, and beta can be between -90 degrees and Between 90 degrees. If gamma For +/- 125 degrees and beta is +/- 90 degrees, the orientation will be +/- 32 degrees and the elevation angle will be +/- 3 degrees.

The phase shifting function of the injection-locked double-push oscillator will be described here: Given a general-purpose injection-locked oscillator locked at f0, if the frequency of the injected lock signal changes, the reference signal will pull the output frequency back. When outside the locked band, the circuit is degraded to a self-excited oscillator. Similarly, given a general-purpose injection-locked oscillator, locked at the alignment frequency f0, if the BRF of the circuit is adjusted to pull back different frequencies within the bandwidth, the frequency of the output signal will remain the same, but the phase of the output signal Will change.

The circuit-based injection-locked double-push oscillator embodiment outperforms the single-ended oscillator in that it multiplies the natural frequency and phase of the signal, thereby making the system as small and cheaper as possible.

The doubling of the natural frequency makes the radar main frame cheaper, smaller, and lighter, and phase multiplication will enhance the system scan phase and eliminate expensive phase shift circuitry from the system.

The embodiment based on the push-push oscillator described herein is highly economical even when compared to a novel T/R module based on a single-ended oscillator. In order to enhance the phase sweep of a general injection-locked single-ended oscillator, it should be connected in series with a frequency multiplier. Because of the high level of hazard involved in circuit failure, this operation requires a circulator, which is a bulky and expensive component.

A layout suitable for an implantable double push oscillator such as PS-IPPO 30 is provided herein. The circuits of all PS-IPPO and CP-IPPO described herein may be based on the MMIC and may depend on the width and length of the transmission line of each individual IPPO. A layout suitable for balancing the downconverter is provided herein. T/R module The technology of the component is generally an MMIC on an indium phosphate or gallium arsenide substrate. In general, the MMIC components are assembled in an LTCC environment, meaning that the RF and DC connections are embedded on the outside with the printed antenna.

One of the great advantages of this case is to reduce the production cost of the phased array antenna system, which includes a T/R module and a reference signal generator for a given frequency of any radiation signal.

In general, the output signals of the first series of double-push oscillators are characterized by high stability, low noise, and the frequency is lower than the signal frequency radiated by the T/R module. The output of the last IPPO in the chain is injected into a T/R module that is constructed and operated in accordance with an embodiment of the present invention. The T/R module preferably includes a set of at least one stage of injection-locked phase-shifted double-push oscillator strings. The frequency of the signal injected into the T/R module is multiplied by the injection-locked double-push oscillator at each stage until the desired radiation frequency is reached. The phase of the processed signal is scanned by each stage according to system requirements. In general, the phase of the signal generated by each of the injection-locked double-push oscillators of the T/R module constructed and operated in accordance with an embodiment of the present invention is appropriately offset so that the radiation signal can have a 360 degree. Potential phase scan.

Figure 25 shows a wireless network using a 60 GHz AESA transceiver, where each computer on each desk has a dedicated transceiver, typically embedded in a laptop or desktop computer, and forwarded The fixtures are mounted to the ceiling of an indoor environment, in accordance with certain embodiments of the present invention.

According to any embodiment of the present invention, a communication network system includes a plurality of nodes, at least one of which includes a transceiver and an antenna To transmit and receive an electronically controllable focused electromagnetic beam. In general, the electromagnetic beam can be manipulated by a phase shifting function of a phase shift injection double push oscillator (PSIPPO). A group or group of nodes is also referred to herein as a "cluster." Each of the transceivers can be based on known transceiver technology, for example, as shown and described in U.S. Patent No. 7,852,265, the entire disclosure of which is incorporated herein by reference.

Suitable transceiver technologies are also described in PCT/IL06/01144, entitled "Phased shifted oscilator and antenna", PCT/IL06/01039, entitled "Apparatus and methods for radar imaging based on injected push-push oscillators", U.S. Patent No. 7,911,373, entitled "Compact active phased array antenna for radars", U.S. Patent Publication No. 20080272962, entitled "Wireless area network compatible system and method using a phase array antenna", and U.S. Patent Publication No. 20100188289, the invention name is "Communication system and method using an active phased array antenna".

In general, antennas known or described herein are circularly polarized so that the electromagnetic beam can be transmitted and received in a spatial position regardless of the transceiver of the transmitting and receiving transceivers. In general, the antenna has a bandwidth of approximately 12% with a reference point of approximately 60 GHz, such as a bandwidth of approximately 57-64 GHz.

In general, the plurality of nodes includes at least one pair of nodes including first and second nodes, which are non-line of sight between each other, and for each pair of nodes, the first and second nodes are located at the line of sight of at least one repeater node range Inside. At least one repeater node includes at least one repeater node that can serve more than one pair of nodes in a non-line of sight range from each other. A sequence of repeater nodes located within the line of sight and spaced apart from each other by less than a predetermined distance may serve pairs of nodes that are spaced apart by more than the predetermined distance (eg, 10 meters).

In general, the software management function can simultaneously transmit and receive more than one pair of the plurality of nodes by distinguishing at least one of the transceiving resources between the active nodes.

The software management function can include any suitable technology, such as CDMA, TDMA or FDMA.

Certain embodiments of the present invention include a wireless personal area network architecture and associated devices (such as shown in FIG. 1). The network includes transceivers embedded in laptops or desktops and transceivers that act as transponders on indoor open space ceilings. The network allows many users in a home environment to establish a two-way radio connection to each other. The components of the network include an active electronically operated antenna (AESA) transceiver. When using AESA technology, the RF connection between the two network elements will only be used when the transceiver is in line of sight.

In a home environment with many users, it is difficult for two users to be in the line of sight of each other because the user is an obstacle in the line of sight; as is well known, the human body will completely let the 60 GHz signal eliminate. To this end, a transponder can be used to establish an RF connection through an obstacle; for this purpose, the 60 GHz signal in the network is transmitted vertically between the computer-embedded transceiver and the ceiling-mounted transponder and receive.

According to some embodiments, the vertical direction of the RF connection requires the user's The RX and TX directional antennas are parallel to the floor to guide to the ceiling; and the directional antenna of the transponder also needs to be parallel to the ceiling and directed to the floor. The floor is usually parallel to the ceiling, but even in the opposite case, the network can operate successfully; AESA technology can take advantage of the beam's handling capabilities to overcome this problem.

In general, the parallel position of the computer's in-line transceiver and ceiling-mounted transponder is not sufficient to ensure the implementation of RF connections between various network components; instead, the system can handle circularly polarized EM waves. Therefore, linearly polarized transceivers ensure connectivity only when all transceivers are in the same direction as linearly polarized EM waves are transmitted and received. Any possible different azimuths of the network element may eventually result in a weak reception signal.

A signal received by a linearly polarized computer in-line component and transmitted by a linearly polarized transponder in a +/- 90 degree opposite orientation may be ineffective. The same is true for ceiling-mounted transponders that transmit to computer-mounted components with a +/- 90 degree opposite orientation.

Therefore, in order to allow the user to adjust the direction of the computer antenna as desired, all network components should support circular polarization operation.

In general, when each user can transmit/receive to any other network user, each user can also transmit/receive itself using the network. This feature is quite useful when the various functions of the computer are separated and have separate mechanical enclosures, such as for wireless connection. Using this network structure, each user can transmit/receive any individual block in other user computers.

A two-way communication network including a wired or wireless transceiver can be connected to each other Connected system. A specific example is a broadband 60 GHz wireless indoor network for high speed data transfer.

The wireless transceiver can be based on Multiple Input Output (MIMO) or Active Electronically Controlled Antenna (AESA). AESA transceiver based networks, and those based on coherent down-conversion, will be described herein by way of example.

Coherent down-conversion is a "direct" operation; that is, the frequency of the regional oscillator (LO) of the receiver (R/X) and the frequency of the transmitter (T/X) carrier will be the same. In addition, in general, the above signals have a phase difference of 90 degrees. In these cases, information can be “coherently” and “directly” converted to baseband.

To establish a coherent conversion between a single T/X and a single R/X, the frequency and phase of the T/X carrier can be a locked reference.

In order for several T/X and as many R/X networks to work, all network components should be coherent.

The repeater transceiver does not have a digital baseband subsystem; in fact, its repeated operation skips the baseband demodulation and modulation process.

For example, the embodiments shown and described herein can be used for transmission and reception at 57-64 GHz, plus or minus 3 GHz from each side. More specifically, any suitable bandwidth included in the 57-64 GHz bandwidth, or any part or all of the following values plus or minus 1, 2, 3, 5 or 10 or 12 or 15 from one or both sides GHz bandwidth: 57 GHz, 58 GHz, 59 GHz, 60 GHz, 61 GHz, 62 GHz, 63 GHz, 64 GHz, all available.

Figure 25 shows a wireless network using a 60 GHz AESA transceiver. Each computer on the desk has a dedicated transceiver. The transponder is mounted on the ceiling of an indoor environment. Every user can work with any other The user establishes a radio connection through the first available transponder. Additional transponders can be installed on the upper border of the indoor environment divider wall.

The term "commercial" as used herein, with respect to "high resolution", refers to non-military radar applications such as, but not limited to, autonomous driving.

Features of the invention described in the various embodiments may also be provided in a single embodiment. Rather, the features of the invention are to be construed as a singular description of the embodiments of the invention, which are described in a single embodiment or in a particular order or in any suitable combination or in a different order.

The present invention also provides a method for making any of the systems shown and described herein, including providing a suitable subset of all or any of the system components shown and described herein, using any suitable conventional method, and utilizing any and all of the obvious A method of the system and its components that can be inferred from the structures and functions described herein.

It should be understood that the use of phrases such as "command," "required," "required," and "required" is used merely to describe a particular implementation and application, and is merely an option for implementing the application, and is not limited thereto. In alternative implementations, the same elements may be considered non-command and non-required or even completely excluded.

It should be understood that the software component of the present invention includes programs and materials, and if desired, can be implemented in a read only memory (ROM) format, including: CD-ROM, EPROM, and EEPROM, or can be stored in any other suitable computer readable form. Take media such as, but not limited to, various optical discs, various cards, and RAM. The components described herein, such as software, may alternatively be mounted in whole or in part on the hardware, and conventional techniques may be used if desired. Conversely, the components described herein, such as hardware, may alternatively be wholly or partially mounted in the software, Traditional techniques can also be used if desired.

Any calculation or other form of analysis described herein can be achieved by suitable arithmetic methods. Any of the steps described herein can be accomplished by a computer. The invention shown and described herein may include a solution for determining any problem using an arithmetic method for any purpose described herein, the solution optionally including at least one decision, action, product, service, or any other description herein. Process the problem positively or reach information describing the purpose for this; and output its solution.

Features of the invention described in the various embodiments may also be provided in a single embodiment. Rather, the features of the invention are to be construed as a singular description of the embodiments of the invention, which are described in a single embodiment or in a particular order or in any suitable combination or in a different order. "Example" is used herein to mean a specific example, but is not limited thereto.

The devices, devices, or systems shown in any of the figures may be integrated on a single platform in some embodiments or may be coupled together via any suitable wired or wireless integration, such as, but not limited to, fiber optics, Ethernet, wireless LAN, home PNA, power line communication, cell phone, PDA, BlackBerry GPRS, satellite with GPS, or other mobile delivery. It is to be understood that the description and the drawings, the drawings, the description, or the functions of the system and its sub-units herein may also be presented as a method and a And its subunits are presented. The proportions of the elements in the various figures are used for the purposes of illustration and/or explanation and are not intended to be limiting.

100‧‧‧The first block of the coupling line

101‧‧‧Connecting line

102‧‧‧Connecting line

103‧‧‧ Input 埠

104‧‧‧ Output埠

105‧‧‧ idle time

106‧‧‧ Output埠

300‧‧‧ Signals to 180-degree power splitters for two 90-degree power splitters 301 and 302

301‧‧‧Transfer signal to the Wilkinson Power Splitter 305 90-degree power splitter

302‧‧‧Transfer signal to Wilkinson power splitter 306 90 degree power splitter

303‧‧‧Wilkinson power splitter that transmits signals to power splitter 305

304‧‧‧Wilkinson power splitter that transmits signal to power splitter 306

305‧‧‧Wilkinson power splitter feeds signals with phase 0 & 90 degrees to the transmitter

306‧‧Wilkinson power splitter feeds signals with phase 180 & 270 degrees to the transmitter

307‧‧‧A transmitter that radiates a circularly polarized EM field

400‧‧‧ Strip line substrate

401‧‧‧Wilkinson Power Splitter

402‧‧‧Wilkinson Power Splitter

500‧‧‧ blocks

501‧‧‧Connecting components

600‧‧‧Independent blocks on the top strip line medium

601‧‧‧ Input 埠

602‧‧‧First output埠

700‧‧‧Independent blocks on the bottom stripline medium

701‧‧‧ idle time

702‧‧‧Second output埠

800‧‧‧ Input埠

First block of the 801‧‧3 dB directional coupler

Second block of the 802‧‧3 dB directional coupler

803‧‧‧First output埠

804‧‧‧second output埠

805‧‧‧Open road

900‧‧‧ input 埠, corresponding to 800 of Figure 8

The first block of the 901‧‧‧3 dB decentralized 90-degree directional coupler corresponds to the 801 of Figure 8.

The second block of the 902‧‧‧3 dB decentralized 90 degree directional coupler, corresponding to the 802 of Figure 8

903‧‧‧ first output 埠, corresponding to 803 of Figure 8

904‧‧‧Second output 埠, corresponding to 804 of Figure 8

905‧‧‧ open circuit, corresponding to 805 of Figure 8

The first block of the 1001‧‧3 dB decentralized 90 degree directional coupler, corresponding to the 801 of Figure 8

The second block of the 1002‧‧3 dB decentralized 90 degree directional coupler, corresponding to the 802 of Figure 8

1003‧‧‧The shortest possible transmission line connecting two 3 dB distributed 90 degree directional couplers 1001 and 1002

1100‧‧‧ Input埠

1101‧‧‧180 degree power splitter

1102‧‧90 degree power splitter

1103‧‧90 degree power splitter

1104‧‧‧Wilkinson Power Splitter Network

1105‧‧‧Wilkinson Power Splitter Network

1106‧‧‧Wilkinson Power Splitter Network

1107‧‧ Wilkinson Power Splitter Network

1108‧‧‧Transmitter feed for a linear array of four transmitters

Comparison of 1200‧‧‧ four 埠

1201‧‧‧Coupling power of two output ports

1202‧‧‧ Phase of output signal

1203‧‧‧ phase difference between two output signals

1300‧‧‧transmitter

1301‧‧‧Wilkinson power splitter network, transmitting signals at 0 degrees

1302‧‧‧Wilkinson power splitter network, transmitting signals at 180 degrees

1303‧‧‧180 degree power splitter

1400‧‧‧transmitter

1401‧‧‧Wilkinson power splitter network, transmitting signal/orientation at 0 degrees

1402‧‧‧Wilkinson power splitter network, transmitting signal/orientation at 180 degrees

1403‧‧‧Wilkinson power splitter network, transmitting signal/orientation at 0 degrees

1404‧‧‧Wilkinson power splitter network, transmitting signal/orientation at 180 degrees

1405‧‧90 degree power splitter / height control

1406‧‧‧180 degree power splitter/azimuth control

1500‧‧‧transmitter

1501‧‧‧Wilkinson power splitter network, transmitting signals at 0 degrees

1502‧‧‧Wilkinson power splitter network, transmitting signals at 90 degrees

1503‧‧‧Wilkinson power splitter network, transmitting signals at 180 degrees

1504‧‧‧Wilkinson power splitter network, transmitting signals at 270 degrees

1505‧‧90 degree power splitter

1506‧‧80 degree power splitter

1600‧‧‧transmitter

1601‧‧‧Wilkinson power splitter network, transmitting signal/orientation at 0 degrees

1602‧‧Wilkinson power splitter network, transmitting signal/orientation at 90 degrees

1603‧‧‧Wilkinson power splitter network, transmitting signal/orientation at 180 degrees

1604‧‧‧Wilkinson power splitter network, transmitting signal/azimuth control at 270 degrees

1605‧‧‧Wilkinson power splitter network, transmitting signal/height control at 0 degrees

1606‧‧‧Wilkinson power splitter network, transmitting signal/height control at 90 degrees

1607‧‧‧Wilkinson power splitter network, transmitting signal/height control at 180 degrees

1608‧‧‧Wilkinson power splitter network, transmitting signal/height control at 270 degrees

1609‧‧90 degree power splitter

1610‧‧‧180 degree power splitter

1700‧‧‧transmitter

1701‧‧‧Wilkinson power splitter that combines the signals transmitted on 埠1705 and 1703

1702‧‧‧ Wilkinson Power Splitter with independent signals from 埠1704 and 1706

1703‧‧Wilkinson power splitter 1701 is used to receive a signal at a reference phase of 0 degrees as an input for azimuth manipulation埠

1704‧‧Wilkinson power splitter 1702 is used to receive a signal at a reference phase of 180 degrees as an input for azimuth manipulation埠

1705‧‧ Wilkinson Power Splitter 1701 is used to receive a signal at the reference phase of 0 degrees as a highly manipulated input埠

1706‧‧‧Wilkinson power splitter 1702 for receiving at reference phase 180 Degree signal as a highly manipulated input埠

1707‧‧‧ transmitter feed with 0 degree reference phase and receiving independent signals for maneuvering azimuth and altitude

1708‧‧‧Transmitter feed with 180 degree reference phase and receiving independent signals for maneuvering azimuth and altitude

1800‧‧‧transmitter

1801/a‧‧‧ signal 埠 @ 0 degrees

1801/b‧‧‧ signal 埠@270 degrees

1801/c‧‧‧ signal 埠 @180 degrees

1801/d‧‧‧ signal 埠 @ 90 degrees

1802‧‧‧ Use 埠1802/a & b to control the azimuth and altitude signals for the summed power combiner

1803‧‧‧ Use 埠1803/a & b to control the azimuth and altitude signals for the summed power combiner

1804‧‧‧ Use 埠1804/a & b to control the azimuth and altitude signals for the summed power combiner

1805‧‧‧ Use 埠1805/a & b to control the azimuth and altitude signals for the summed power combiner

2000‧‧‧Transceiver TX

2001‧‧‧DLO

2002‧‧‧Power splitter @ 15 GHz

2003-2004‧‧‧PSIPPO array 15-30 GHz

2005-2006‧‧‧Power splitter @ 30 GHz

2007-2008-2009-2010‧‧‧Buffer Amplifier Array @ 30 GHz

2011-2012-2013-2014‧‧‧PSIPPO second array 30-60 GHz

2015-2016-2017-2018‧‧‧Buffer Amplifier Array @ 60 GHz

2019-2020-2021-2022‧‧‧Upconverter Mixer Array

2023-2024-2025-2026‧‧‧Buffer Amplifier Array @ 60 GHz

2027-2028-2029-2030‧‧‧ Linear Sub-Emitter Array

2031‧‧‧Baseband signal generator

2200‧‧‧A section of the waveguide fed by the antenna

2210‧‧‧Electrical field direction of vertically polarized EM waves

2220‧‧‧ electric field direction of horizontally polarized EM waves

2300‧‧‧ planar antenna

2310‧‧‧Feeding

2320‧‧‧Feeding

2330‧‧‧Feeding

2340‧‧‧Feeding

2341‧‧‧Linear array of planar antennas

2311‧‧0 degree power splitter, transmitting four signals @ 0 degrees

2312‧‧0 degree power splitter, transmitting four signals @180 degrees

2313‧‧0 degree power splitter, transmitting four signals @90 degrees

2314‧‧0 degree power splitter, transmitting four signals @270 degrees

2315‧‧‧ planar antenna

2316‧‧‧ planar antenna

2317‧‧‧ planar antenna

2318‧‧‧ planar antenna

2350‧‧90 degree power splitter

2360‧‧90 degree power splitter

2370‧‧‧180 degree power splitter

2371‧‧‧Input signals for linear array antennas

Block diagram of the 2000‧‧‧ Distributed Area Oscillator (DLO) 2020

2010‧‧‧ reference signal at f0

2020‧‧‧ First linear array of PSIPPOs transmitting signals with 2*f0

2030‧‧‧Amplifier amplifier array in 2*f0

2040‧‧‧Second linear array of PSIPPOs transmitting signals with 4*f0

2050‧‧‧Amplifier amplifier array in 4*f0

2060‧‧‧Upconverter Mixer Array

2070‧‧‧Power Amplifier Array

2080‧‧‧4*f0 and transmitter arrays with unique phase-reflected signals

Certain embodiments of the present invention are shown in the following figures: Figure 1 shows a multi-stage "Kevin" 90 degree directional coupler constructed and operated in accordance with an embodiment of the present invention.

2 shows an "Kevin" 90 degree coupler of all architectures and operations in accordance with an embodiment of the present invention, which is an example of a connection that would degrade performance.

3 is a simplified block diagram depicting a basic configuration of a manifold for a linear transmitter array and architecture and operation in accordance with an embodiment of the present invention.

4 shows an architecture and operational 0 degree directional coupler network, such as may be used in the manifold of FIG. 3, in accordance with an embodiment of the present invention.

5 is a schematic diagram of a 90 degree directional power splitter architecture and operation in accordance with an embodiment of the present invention.

6 is a top plan view of a 90 degree multilayer directional coupler of architecture and operation in accordance with an embodiment of the present invention.

7 is a bottom plan view of the architecture and operation of a 90 degree multilayer directional coupler in accordance with an embodiment of the present invention.

Figure 8 shows a "Marchand" 180 degree directional power splitter architecture and operation in accordance with an embodiment of the present invention.

9 is a top plan view of a 180 degree multilayer directional coupler of architecture and operation in accordance with an embodiment of the present invention.

10 is a bottom plan view of the architecture and operation of a 180 degree multilayer directional coupler in accordance with an embodiment of the present invention.

Figure 11 is a diagram of a linear emitter array and in accordance with the present invention Schematic diagram of the basic structure of the structure and operation of the application.

Figure 12 shows the performance of a 90 degree coupler in accordance with an embodiment of the present invention.

Figure 13 shows a phased array antenna with architecture and operation and linear polarization and azimuth steering in accordance with an embodiment of the present invention.

Figure 14 shows a phased array antenna with architecture and operation and linear polarization and azimuth and altitude control in accordance with an embodiment of the present invention.

Figure 15 shows a phased array antenna with architecture and operation and circular polarization and azimuth manipulation in accordance with an embodiment of the present invention.

Figure 16 shows a phased array antenna with architecture and operation and having circular polarization and azimuth and altitude control in accordance with an embodiment of the present invention.

17 shows a phased array antenna of all architectures and operations having linear polarization, azimuth and altitude steering, and isolated feeds in accordance with an embodiment of the present invention.

Figure 18 shows a phased array antenna of all architectures and operations having circular polarization, azimuth and altitude steering, and an isolated feed transmitter in accordance with an embodiment of the present invention.

19 is a 3D diagram of a cut-off ground plane depicting a phased array antenna of all architectures and operations having linear polarization, azimuth and height steering, and isolated feeds in accordance with an embodiment of the present invention.

Figure 20 shows an example of a distributed area oscillator of all architectures and operations in a transmitter in accordance with an embodiment of the present invention.

Figure 21 shows a PSIPPO that is architecture and operation in accordance with an embodiment of the present invention and that effectively cooperates with the above apparatus.

Figure 22 shows a feed of a conventional circularly polarized antenna that may be used by certain embodiments of the present invention.

Figure 23 shows a circular polarization feed of a planar antenna in accordance with an embodiment of the present invention.

Figure 24 is a block diagram depicting a architecture and operation of a distributed area oscillator (DLO) that effectively cooperates with the above-described apparatus in accordance with an embodiment of the present invention.

Figure 25 shows a wireless network using a 60 GHz AESA transceiver, where each computer on each desk has a dedicated transceiver, typically embedded in a laptop or desktop computer, and forwarded The fixtures are mounted to the ceiling of an indoor environment, in accordance with certain embodiments of the present invention.

100‧‧‧The first block of the coupling line

101‧‧‧Connecting line

102‧‧‧Connecting line

103‧‧‧ Input 埠

104‧‧‧ Output埠

105‧‧‧ idle time

106‧‧‧ Output埠

Claims (31)

A high gain circularly polarized antenna system comprising: a passive antenna structure comprising at least one 3 db quadrature coupler; and a chip set comprising Tx, Rx and DLO (Distributed Area Oscillator) circuits with the passive The antenna structure acts as an interface to create a transceiver. The system of claim 1, wherein the passive antenna structure is placed on a multilayer printed circuit board. The system of claim 2, wherein the multilayer printed circuit board comprises a flexible multilayer printed circuit board. The system of claim 2, wherein the multilayer printed circuit board is formed of LCP (liquid crystal polymer). The system of claim 1, wherein the chip set has an active area, wherein the active area is surrounded by the passive antenna structure to serve as a package medium to protect the wafer set. The system of claim 1, wherein the system covers a bandwidth centered at 55-65 GHz. The system of claim 1 or 6, wherein the bandwidth is between 5% and 15%. The system of claim 6, wherein the bandwidth is a value centered at 60 GHz. The system of claim 7, wherein the bandwidth is 10%. The system of claim 6, wherein the system covers 57-64 GHz bandwidth. A communication network system comprising: a plurality of nodes, at least one of which includes a transceiver, interfacing with an antenna as claimed in any of the preceding claims, which can transmit and receive an electronically steerable focused electromagnetic beam. The system of claim 11, wherein the electromagnetic beam is controllable by a phase shifting function of a phase shift injection double push oscillator (PSIPPO). The system of claim 11, wherein the antenna is circularly polarized so that the electromagnetic beam can be transmitted and received in a spatial position regardless of the transmitting and receiving transceivers. The system of claim 11, wherein the antenna has a bandwidth having a center frequency of about 10% to about 57-64 GHz. The system of claim 11, wherein the plurality of nodes comprises at least one pair of nodes including first and second nodes, within a non-line of sight of each other, and for each pair of nodes, the first and second nodes Both are located within the line of sight of at least one repeater node. The system of claim 15 wherein the at least one repeater node comprises at least one repeater node that can serve more than one pair of nodes in a range of non-line of sight between each other. The system of claim 11, further comprising a software management function, wherein at least one of the plurality of nodes can be simultaneously transmitted by distinguishing at least one of the transmitting and receiving resources between the active nodes. receive. The system of claim 17, wherein the software management function uses TDMA. The system of claim 17, wherein the software management function uses FDMA. The system of claim 17, wherein the software management function uses CDMA. The system of claim 11, wherein the focused electromagnetic beam is manipulated using AESA technology. The system of claim 11, wherein the plurality of nodes also includes at least one MIMO node. The system of claim 16, wherein a sequence of repeater nodes within the line of sight and spaced apart from each other by less than a predetermined distance will serve each pair of nodes that are spaced apart from each other by the predetermined distance. The system of claim 13, wherein the predetermined distance is at least 10 meters. The system of claim 11, wherein the antenna has a bandwidth of approximately 57-64 GHz. The system of claim 14, wherein the plurality of nodes comprises at least one pair of nodes including first and second nodes, within a non-line of sight of each other, and for each pair of nodes, the first and second nodes Both are located within the line of sight of at least one repeater node. A method for providing a high gain circularly polarized antenna system, the method comprising: providing a passive antenna junction comprising at least one 3 db quadrature coupler And providing a chip set including Tx, Rx, and DLO (Distributed Area Oscillator) chips with the passive antenna structure as an interface to generate a transceiver. The method of claim 27, further comprising operating the transceiver. The method of claim 28, further comprising transmitting using the transceiver. The method of claim 28, further comprising receiving the transceiver. The system of claim 1, wherein the at least one orthogonal coupler comprises a plurality of interconnected 3 db quadrature couplers.