201228105 六、發明說明： 【發明所屬之技術領域】 本發明有關於一種天線，且特別是一種複合弋夕 線系統以及使用此複合式多天線系統的無線通訊穿1 【先前技術】 ~ 目前，無線通訊技術蓬勃發展，因此人們可以常常 透過無線通訊裝置連接上網或進行通話。不管是何種無 線通訊裝置’都需要天線來收發特定頻率之無線作號。 舉例來說’室外與室内的無線存取裝置(ACCess PQintU， AP)都具有天線，以作為無線通訊裝置連接上網的橋接 點。 平板天線（patch antenna)或微帶天線（micr〇stHp antenna)的天線輻射場型（radiation pattern)具有較高的 指向性與較高的增益值，因此室外的無線存取裝置通常 會使用平板天線或微帶天線。 請參照中華民國公告第]VB55472號專利，此相關 前案揭露一種雙極化陣列天線，且雙極化陣列天線包括 饋入網路與複數個天線單元。雙極化陣列天線利用饋入 網路產生相位差，以使其天線輻射場型在空間中可以達 到雙極化之效果。同時，因為複數個天線單元以陣列方 式配置於同一反射板之上，因此可以提升雙極化陣列天 線之天線輻射場型的指向性與增益值。 然而’上述相關前案所揭露的雙極化陣列天線需要 使用複雜的饋入網路，且為了提升天線增益值，雙極化 陣列天線還必須搭配複數個天線單元來使用。又加上’ 一般平板天線或微帶天線的共振長度約為特定頻率之 201228105 二分之一波長，使得上述雙極化陣列天線之天線面積與 尺寸都較為龐大，而不適合用多輸入多輸出（Multiple Input Multiple Output，ΜΙΜΟ)之多天線通訊系統。 在複數個天線單元中，為了降低天線系統所使用的 空間’收發天線與天線之間必須緊密擺放。然而，因為 X、線與天線之間緊密擺放的原故，天線與天線之間在收 發時的信號將會彼此相互干擾，且特別是在每一天線操 目同或相近的頻帶時，天線與天線之間的信號將會 月”、、員的相互搞合（mutual coupling)，而導致天線收訊 έ #同頻干擾的問題。除此之外，因為天線與天線之間 白勺千会*" ρ201228105 VI. Description of the Invention: [Technical Field] The present invention relates to an antenna, and more particularly to a composite antenna system and a wireless communication using the composite multi-antenna system. [Prior Art] ~ Currently, wireless Communication technology is booming, so people can often connect to the Internet or make calls through wireless communication devices. Regardless of the wireless communication device, an antenna is required to transmit and receive wireless signals of a particular frequency. For example, both the outdoor and indoor wireless access devices (ACCess PQintU, AP) have antennas that serve as bridges for wireless communication devices to connect to the Internet. The antenna radiation pattern of a patch antenna or a microstrip antenna has a high directivity and a high gain value, so an outdoor wireless access device usually uses a patch antenna. Or a microstrip antenna. Please refer to the Republic of China Announcement No. VB55472, which discloses a dual-polarized array antenna comprising a feed network and a plurality of antenna elements. The dual-polarized array antenna uses the feed network to create a phase difference so that its antenna radiation pattern can achieve dual polarization in space. At the same time, since a plurality of antenna elements are arranged in an array on the same reflector, the directivity and gain values of the antenna radiation pattern of the dual-polarized array antenna can be improved. However, the dual-polarized array antenna disclosed in the above related prior art requires a complicated feed network, and in order to increase the antenna gain value, the dual-polarized array antenna must also be used with a plurality of antenna elements. In addition, the resonance length of a general flat panel antenna or a microstrip antenna is about one-half wavelength of 201228105 at a specific frequency, so that the antenna area and size of the above dual-polarized array antenna are relatively large, and it is not suitable for multi-input and multi-output ( Multiple Input Multiple Output (ΜΙΜΟ) multi-antenna communication system. In a plurality of antenna elements, in order to reduce the space used by the antenna system, the transmitting and receiving antennas and the antenna must be closely arranged. However, because the X, the line and the antenna are closely arranged, the signals transmitted and received between the antenna and the antenna will interfere with each other, and especially when each antenna operates in the same or similar frequency band, the antenna and The signal between the antennas will be “mutually coupled”, which will cause the antenna to receive the same frequency interference. In addition, because of the interaction between the antenna and the antenna* " ρ
观相互耦合的原因，系統資料吞吐量（throughout) :因此降低。以兩個平行擺放的偶極天線為例，偶極 無線輿偶極天線之間的間距通常需要大於操作頻率（即 2#彳§號的特定頻率）之波長的0.65倍，才能降低彼此 八的干擾’以確保天線隔離度（isolation)可以小於-15 二、（dB) ’而避免天線之間彼此干擾的問題。但是，由 體 ^夕天線系統中天線之間的間距有所限制，使得整 内^寸過大，而不易置放於輕薄短小的無線通訊裝置的 ,因另外，由於平板與微帶天線常是採用探針饋入方式 绩山系、、先電路板上的射頻訊號輸出端的位置與天線的 二置义、需互相配合，此亦代表無法任意替換其它 银來搭配同一片系統電路板。 【發明内容】 式多本發明實施例提供一種複合式多天線系統，此複合 線系统包括系統電路板、天線基板、以及兩項緊 5/20 201228105 鄰擺放的至少-偶極天線與至少—單極槽孔 電路板上具有至卜系統接地面，且系統接地面用：： 為複合式多天線純的天線反射面。天線基板與 地面具有第-間距。偶極天線提供第—操作頻帶且 第-信號饋人源’而單極槽孔天線提供第二操作頻 具有第二信號饋人源。偶極天線與單極槽孔天線皆位於 天線基板的表面上’單極槽孔天線位於偶極天線附近 單極槽孔天線與偶極天線之間具有第二間距，且第一信 號饋入源與第二信號饋入源的信號饋入方向互相垂直 ，信號相位差90度。 本發明實施例提供一種無線通訊裝置，其中無線通 訊裝置的收發晶片位於上述系統電路板，且電氣連接複 合式多天線系統。 綜上所述’本發明實施例所提供的複合式多天線系 統具有天線結構簡單、尺寸小、製作容易、成本低、易 内藏並整合在無線通訊裝置之中等優點。 為使能更進一步瞭解本發明之特徵及技術内容，請 參閱以下有關本發明之詳細說明與附圖，但是此等說明 =所附圖式僅係用來說明本發明，而非對本發明的權利 範圍作任何的限制。 【實施方式】 式夕天線系統的實施例〕 天線照圖1，圖1是本發明實施例提供的複合式多 天線1、1先的。立體結構圖。複合式多天線系統1包括偶極 14。^纟單極槽孔天線12、天線基板13與系統電路板 '、统電路板14具有系統接地面M1 ’系統接地面 6/20 201228105 141為導體材料。天線基板13位於系統電路板μ之上 ’系統接地面丨4〗可以作為複合❹天㈣統丨的天線 反射面。因為系統接地面Ml作為複合式多天線系統1 的天線反射面’因此系統接地面141範圍必須涵蓋偶極 天線^與單㈣孔天線12之垂直投影面積。偶極天線 11與單極槽孔天線12以平面印刷方式製作在天線基板 13上。 複合式多天㈣、統1的天線基板13置放在無線通The reason for the mutual coupling, the system data throughput (through): therefore reduced. Taking two parallel dipole antennas as an example, the spacing between dipole wireless 舆 dipole antennas usually needs to be greater than 0.65 times the wavelength of the operating frequency (ie, the specific frequency of 2#彳§) to reduce each other. The interference 'to ensure that the antenna isolation can be less than -15 bis (dB)' to avoid interference between the antennas. However, the spacing between the antennas in the antenna system is limited, so that the whole internal size is too large, and it is not easy to be placed in a light and short wireless communication device, because the flat panel and the microstrip antenna are often used. The probe feeding method is the position of the RF signal output on the circuit board and the first board. It needs to match each other. This means that other silver cannot be replaced with the same system board. SUMMARY OF THE INVENTION Many embodiments of the present invention provide a composite multi-antenna system including a system circuit board, an antenna substrate, and two at least a dipole antenna placed at least 5/20 201228105 adjacent to each other and at least The single-pole slot circuit board has a grounding plane for the system, and the system ground plane uses:: The composite multi-antenna pure antenna reflection surface. The antenna substrate has a first pitch from the ground. The dipole antenna provides a first operational band and the first signal feeds the source' and the monopole slot antenna provides a second operational frequency with a second signal feed source. Both the dipole antenna and the monopole slot antenna are located on the surface of the antenna substrate. The monopole slot antenna is located at a second spacing between the monopole slot antenna and the dipole antenna near the dipole antenna, and the first signal feed source The signal feeding direction with the second signal feeding source is perpendicular to each other, and the signal phase difference is 90 degrees. Embodiments of the present invention provide a wireless communication device in which a transceiver chip of a wireless communication device is located on the system circuit board and electrically connected to a composite multi-antenna system. In summary, the composite multi-antenna system provided by the embodiment of the present invention has the advantages of simple antenna structure, small size, easy fabrication, low cost, easy integration and integration in a wireless communication device. For a better understanding of the features and technical aspects of the present invention, reference should be made to the accompanying drawings The scope is subject to any restrictions. [Embodiment] Embodiment of the antenna antenna system] The antenna is shown in Fig. 1. Fig. 1 is a composite multi-antenna 1, 1 according to an embodiment of the present invention. Three-dimensional structure diagram. The composite multi-antenna system 1 includes a dipole 14. ^纟Unipolar slot antenna 12, antenna substrate 13 and system board ', system board 14 has system ground plane M1 'system ground plane 6/20 201228105 141 is a conductor material. The antenna substrate 13 is located above the system board μ. The system ground plane 丨4 can be used as the antenna reflection surface of the composite 四天(四). Since the system ground plane M1 serves as the antenna reflection surface of the composite multi-antenna system 1, the range of the system ground plane 141 must cover the vertical projected area of the dipole antenna ^ and the single (four) aperture antenna 12. The dipole antenna 11 and the monopole slot antenna 12 are formed on the antenna substrate 13 by planar printing. The composite multi-day (four), unified 1 antenna substrate 13 is placed in the wireless pass
訊裝置之系統電路板14(系統接地面141)上方，且彼此 之間距離有間距，故天線基板13與系統電路板Μ之間 為相互獨立之結構。系統電路板14之系統接地面i4i 作為天線反射面’故可以使天線㈣能量較為集中在天 線基板13之法線方向上，進而使複合式多天線系統】 具有較高的指向性與天線增益，並可有效提升無線信號 的傳輸距離。 在此實施例t，系統接地面141至天線基板13下 表面的間距為6.4髮米，系統接地面141可為多邊形、 圓形或橢圓形金屬板，且系統接地面】41至天線基板 13下表面之間是用以空氣作為區隔。另外，系統^路 板Μ與天線基板13都可以是16釐米的FR4基板，因 此，系統電路板14之上表面與天線基板13之上表面的 間距為8釐米。要說明的是，上述間距大小、基板材質 、系統接地面141的形狀與材質都僅是用以說明本發明 的其中一個實施例，其並非用以限定本發明。 偶極天線II用以提供第一操作頻帶且具有第一信 唬饋入源】】0，單極槽孔天線12用以提供第二操作頻 7/20 201228105 帶且具有第二信號饋入源120。偶極天線11與單極槽 孔天線12皆位於天線基板13的上表面，且第一信號饋 入源110與第二信號饋入源12〇的信號饋入方向互相垂 直，且信號相位差90度。單極槽孔天線丨2位於偶極天 線11附近，且單極槽孔天線12與偶極天線n之間具 有微小的間距。 偶極天線11具有第一信號饋入源11〇、輻射單元 111與112,其中第一信號饋入源11〇的信號饋入點u〇a 與ii〇b分、別設置於輻射單元lu與112相對的兩個邊 上。第一仏號饋入源110白勺兩端（亦即信號饋入點⑽ 與110b)分別電氣連接輻射單元lu與⑴。輻射單元 111與112彼此往相反方向延伸，且輕射單a⑴鱼a] 的長度總和約為第-操作頻帶之中心頻率的二分之_ 早極槽孔天線12具有信號饋人源m、韓 :二1:槽孔122，其中第二信號饋入源120的信號饋 ”，占120a與i2〇b分別設置於槽 : 邊上㈣後述的第一長邊與第孔=相二 =個長 ⑵例如為輕射金屬片，d)。輪射導體片 ⑴且垂直對稱於令心線^:聰近輕射單元 孔開口第—長邊與相對於第 槽孔開口位於相對於第—相弟—長邊’其中 長度（第-或第二長邊的 ^二側邊，槽孔⑵的 心頻率的四分之一波長。信二' ·、’、、 一知作頻帶之中 信號饋入點12〇a與12〇]^八〜貝入源120的兩端（亦即 二長邊。 ”別電氣連接至第-長邊與第 8/20 201228105 在圖1的實施例中，為了使第一信號饋入源uo與 第一彳§ 5虎饋入源12 0的信號饋入方向互相垂直。信號饋 入點110a與110b的連線方向會與信號饋入點12〇a與 120b的連線方向互相垂直。Above the system board 14 (system ground plane 141) of the device, there is a distance between them, so that the antenna substrate 13 and the system board 为 are independent structures. The system ground plane i4i of the system circuit board 14 serves as an antenna reflection surface, so that the energy of the antenna (4) can be concentrated in the normal direction of the antenna substrate 13, thereby making the composite multi-antenna system have higher directivity and antenna gain. And can effectively improve the transmission distance of wireless signals. In this embodiment t, the distance between the system ground plane 141 and the lower surface of the antenna substrate 13 is 6.4 meters, and the system ground plane 141 can be a polygonal, circular or elliptical metal plate, and the system ground plane 41 to the antenna substrate 13 The surface is separated by air. Further, both the system board and the antenna substrate 13 may be 16 cm FR4 substrates, and therefore, the distance between the upper surface of the system board 14 and the upper surface of the antenna substrate 13 is 8 cm. It should be noted that the above-mentioned pitch size, substrate material, and the shape and material of the system ground plane 141 are only used to illustrate one embodiment of the present invention, and are not intended to limit the present invention. The dipole antenna II is configured to provide a first operating frequency band and has a first signal feed source, wherein the monopole slot antenna 12 is configured to provide a second operating frequency 7/20 201228105 band and has a second signal feed source. 120. The dipole antenna 11 and the monopole slot antenna 12 are both located on the upper surface of the antenna substrate 13, and the signal feeding directions of the first signal feeding source 110 and the second signal feeding source 12 are perpendicular to each other, and the signal phase difference is 90. degree. The monopole slot antenna 丨 2 is located near the dipole antenna 11 and has a slight spacing between the monopole slot antenna 12 and the dipole antenna n. The dipole antenna 11 has a first signal feeding source 11〇, and radiating units 111 and 112, wherein the first signal feeding source 11〇 is fed to the points u〇a and ii〇b, and is disposed in the radiating unit lu and 112 opposite the two sides. The two ends of the first 馈 feed source 110 (ie, the signal feed points (10) and 110b) are electrically connected to the radiating elements lu and (1), respectively. The radiating elements 111 and 112 extend in opposite directions to each other, and the sum of the lengths of the light-emitting single a(1) fish a] is about two-half of the center frequency of the first operating band. The early-polar slot antenna 12 has a signal feeding source m, Han: Two 1: slot 122, wherein the second signal is fed to the signal source of the source 120, and 120a and i2〇b are respectively disposed in the slot: on the side (four), the first long side and the second hole, which are described later, are two = one long (2) For example, a light-emitting metal sheet, d). The conductor piece (1) is vertically symmetrical with respect to the core line ^: the light-emitting unit aperture opening - the long side and the opening relative to the first slot hole are located relative to the first phase - The length of the long side 'the length of the second side of the first or second long side, the quarter frequency of the heart frequency of the slot (2). The letter 'two', ',, a known as the signal feed point 12 〇a and 12〇]^8~Before the two ends of the source 120 (that is, the two long sides.) Do not electrically connect to the first long side and the eighth side 20/20 201228105 In the embodiment of Fig. 1, in order to make the first The signal feeding source uo is perpendicular to the signal feeding direction of the first 彳5 tiger feeding source 120. The signal feeding point 110a and 110b are connected with the signal feed direction. 12〇a connecting point and a direction 120b perpendicular to each other.
此外，偶極天線11為電流激發的天線，且單極槽 孔天線12則為磁流激發的天線，當偶極天線11的第一 k號饋入源110與單極槽孔天線〗2的第二信號饋入源 no的信號饋入方向互相垂直，且信號相位差9〇度時 ’偶極天線11與單極槽孔天線丨2在空間中的輻射極化 ，具^正交之特性，因此能有效降低兩相鄰天線之間的 福合里，解決天線之間因過靠近而產生隔離度差的問題 二換言之，若將偶極天線n的長邊延伸方向轉動9〇度 设，後，則複合式多天線系統丨將可能無法獲得良好的 效能。據此，本發明實施例的複合式多天線系統1的偶 極天線11與單極槽孔天線12之間的間距可以縮小至2 釐米’且隔離度可以保持在.分貝以下。相較之下， 傳、’、充的夕天線系統的兩個偶極天線之間仍必須要有較 大的間距，才能夠具有較好的隔離度。 另外’為了達到較好的隔離度，偶極天線η與單 =孔天線12之間的相對位置可以擺放如下。偶極天 摇中1Λ早極槽孔天線12大致對稱於天線基板13的對 線12 ^ ,ΥΜ』ΙΝΕ，而且偶極天、線11與單極槽孔天 此。1排心同—軸向°然而’本發明卻不限定於 在其他的實施例中， 12可能僅排列於同—軸向 偶極天線11與單極槽孔天線 ’而未對稱於天線基板13的 9/20 201228105 對稱中心線SYM—LINE ’或者，偶極天線u與單極槽 孔天線12不排列於同—軸向且也不對稱於天線基板13 的對稱中心線S YMJLINE。 總而§之，本發明的偶極天線u與單極槽孔天線 12的擺放。位置並不限^ ’卩要偶極天線u翁號饋入 源110與單極槽孔天線12的信號饋入源的信號饋 入方向互相垂直，且彳§號相位差度，即可以達到良 好的隔離度。 、請參照圖2與圖3,圖2是本發明實施例提供的複 合式多天線系統的上視圖，而圖3是本發明實施例提供 的複合式乡m狀偶極天線u與單簡孔天線12 之詳細上視圖。 ^於圖2中，天線基板13與系統電路板14的長度與 見度相等’天線基板13的長度與寬度分別& 11〇釐米 與7〇釐米。偶極天線U與單極槽孔天線12的總長度 為27釐米，且偶極天線u與單極槽孔天線12位於天 線基板13的中^。換言之，第二側邊與天線基板13之 底邊之間的間距為41.5釐米，且輻射單元ln之頂邊 與天線基板13之頂邊之間的間距也同樣為41.5釐米。 在圖3中，輻射單元111與112的長度為6.25釐 f，且輻射單元丨丨丨與112之間的間距為2釐米。輻射 單7L 112與第一側邊之間的間距為2釐米，槽孔開口的 寬度為2釐米。輻射導體片121的寬度為1〇·5釐米， 輻射導體片121的長度為12·5釐米。第一側邊與槽孔 122之間的間距為！釐米，槽孔122的長度為95釐米 ，且信號饋入源120中心點與槽孔122之間的間距為 10/20 201228105 4·5釐米。圖2與圖3所述各種間距、寬度與長度僅是 用以舉例說明，其並非用以限定本發明。 請參照圖4與圖5，圖4是圖〗之偶極天線u操 作於5490MHz的輻射場型示意圖，而圖5是圖！之單 極槽孔天線12操作於5490MHz的輻射場型示意圖。由 圖4與圖5中，可以得知圖〗之偶極天線u與單極槽 孔天線12之天線輻射能量將會集中在天線基板〗3之法 線方向上（即正X方向）。前面所述，偶極天線n與單 極槽孔天線12在空間中的輻射極化會具有正交之特性 ，因此能降低偶極天線】1與單極槽孔天線12之間的耦 合效應。 接著’請參照圖6 ’圖6是圖1之複合式多天線系 統在不同中心頻率下的S參數之曲線圖。圖6之各反射 麥數之曲線C61〜C63是在電壓駐波比（V〇ltageIn addition, the dipole antenna 11 is an antenna excited by current, and the monopole slot antenna 12 is an antenna excited by magnetic current, when the first k-th feed source 110 and the monopole slot antenna of the dipole antenna 11 are When the signal feeding direction of the second signal feeding source no is perpendicular to each other, and the signal phase difference is 9 〇 degrees, the radiation polarization of the dipole antenna 11 and the monopole slot antenna 丨2 in space is orthogonal. Therefore, the problem of the difference between the two adjacent antennas can be effectively reduced, and the problem that the isolation between the antennas is too close is solved. In other words, if the long side of the dipole antenna n is rotated by 9 degrees, After that, the composite multi-antenna system will probably not achieve good performance. Accordingly, the spacing between the dipole antenna 11 and the monopole slot antenna 12 of the composite multi-antenna system 1 of the embodiment of the present invention can be reduced to 2 cm' and the isolation can be kept below .decibel. In contrast, the two dipole antennas of the transmitting, transmitting, and antenna systems must still have a large spacing to provide better isolation. In addition, in order to achieve better isolation, the relative position between the dipole antenna η and the single-hole antenna 12 can be placed as follows. The dipole antenna shakes 1 Λ the early pole slot antenna 12 is substantially symmetrical with respect to the alignment 12 ^ of the antenna substrate 13, and the dipole antenna, the line 11 and the monopole slot. 1 row of the same - axial ° However, the present invention is not limited to the other embodiments, 12 may be arranged only in the same-axial dipole antenna 11 and the monopole slot antenna 'not symmetric to the antenna substrate 13 9/20 201228105 Symmetrical center line SYM_LINE 'Alternatively, the dipole antenna u and the monopole slot antenna 12 are not arranged in the same axial direction and are also asymmetric with respect to the symmetrical center line S YMJLINE of the antenna substrate 13. In general, §, the dipole antenna u of the present invention and the monopole slot antenna 12 are placed. The position is not limited to ^ ' The dim antenna is not perpendicular to the signal feeding direction of the source feeding source 110 and the signal feeding source of the monopole slot antenna 12, and the phase difference of the 彳§ is good. Isolation. Referring to FIG. 2 and FIG. 3, FIG. 2 is a top view of a composite multi-antenna system according to an embodiment of the present invention, and FIG. 3 is a composite m-type dipole antenna u and a single hole provided by an embodiment of the present invention. Detailed top view of antenna 12. In Fig. 2, the length and visibility of the antenna substrate 13 and the system board 14 are equal. The length and width of the antenna substrate 13 are & 11 cm and 7 cm, respectively. The total length of the dipole antenna U and the monopole slot antenna 12 is 27 cm, and the dipole antenna u and the monopole slot antenna 12 are located in the middle of the antenna substrate 13. In other words, the distance between the second side and the bottom side of the antenna substrate 13 is 41.5 cm, and the distance between the top side of the radiating element ln and the top side of the antenna substrate 13 is also 41.5 cm. In Fig. 3, the length of the radiating elements 111 and 112 is 6.25 PCT, and the spacing between the radiating elements 丨丨丨 and 112 is 2 cm. The distance between the single 7L 112 and the first side is 2 cm, and the width of the slot opening is 2 cm. The width of the radiation conductor piece 121 is 1 〇 5 cm, and the length of the radiation conductor piece 121 is 12 · 5 cm. The spacing between the first side and the slot 122 is! The centimeter, the length of the slot 122 is 95 cm, and the distance between the center point of the signal feed source 120 and the slot 122 is 10/20 201228105 4·5 cm. The various spacings, widths, and lengths described in Figures 2 and 3 are for illustrative purposes only and are not intended to limit the invention. Please refer to FIG. 4 and FIG. 5. FIG. 4 is a schematic diagram of the radiation field pattern of the dipole antenna u operating at 5490 MHz, and FIG. 5 is a diagram! The single-pole slot antenna 12 operates on a 5490 MHz radiation pattern. From Fig. 4 and Fig. 5, it can be seen that the antenna radiant energy of the dipole antenna u and the monopole slot antenna 12 of the figure will be concentrated in the normal direction of the antenna substrate (i.e., the positive X direction). As described above, the radiated polarization of the dipole antenna n and the monopole slot antenna 12 in the space has orthogonal characteristics, so that the coupling effect between the dipole antenna 1 and the monopole slot antenna 12 can be reduced. Next, please refer to Fig. 6. Fig. 6 is a graph of S parameters of the composite multi-antenna system of Fig. 1 at different center frequencies. Figure 6 shows the reflection of the wheat number C61 ~ C63 is the voltage standing wave ratio (V〇ltage
Standing Wave Ratio，VSWR)為 1.5:1 的情況下所獲得 ，曲線C61表示S射參數S22(第2埠的輸入訊號與反射 訊號之比值），曲線C62表示S參數Sn(第]埠的輸入 訊號與反射訊號之比值），曲線C63表示S參數S21(第1 埠的輸入訊號與第2埠接收訊號的比值）。由圖6可知 ’圖1之複合式多天線系統1可以操作於5GHz的頻帶 内，且特別是5.15GHz〜5.825GHz的頻帶内。 請參照圖7與圖8，圖7是圖1之偶極天線η的 天線增益與輻射效率之曲線圖，而圖8是圖1之單極槽 孔天線12的天線增益與轉射效率之曲線圖。曲線C71 與C81分別表示圖1之偶極天線Π與單極槽孔天線12 的各中心頻率之天線增益，曲線C72與C82分別表示 11/20 201228105 圖1之偶極天線11與單極槽孔天線12的各中心頻率之 輻射效率。 由圖7與圖8可知，圖丨之偶極天線u與單極槽 孔天線12在5GHz的頻帶内，天線增益最高皆可達到8 分貝（dBi) ’且其輻射效率皆在6〇0/〇以上。 〔袓合式多天線糸統的其他實施例〕 在前面實施例中，單極槽孔天線12的槽孔形狀為 矩形（長條形），且單極槽孔天線12的槽孔開口位於輕 射導體# 121的第二側邊。然而，要說明的是，單極^ 孔天線I2的槽孔形狀與槽關口位置並非用以限定本 發明。在以下的實施例中，偶極天線u的第一信妒 入源U〇與單極槽孔天、線12的第二信號饋入源1°2〇^ 信號饋入方向互相垂直，且信號相位差90度。 一 圖ΓΤ: 9C, 1 9A〜圖9C皆是本發明另 μ例㈣5心天I㈣的立騎 :複合式多天線系統2的單極槽孔天線22之二二 孔接° ® 9Β的複合式多天線系統3的單極槽孔 線孚统3:二：322為Τ形槽孔。圖％的複合式多天 線糸統3的早極槽孔天線％之矩 夕大 於韓射導體片421的第—側邊。8 開口位 另外，在前面實施例中，偶極 形輻射導體片，作要乂裏的幸田射早兀為矩 . dfcm 要5兄明的是，偶極天線的輻射單元f 形狀並非用以限定本發 钿耵早兀之 元之形狀也未必要相间 °線的兩個輻射單 單元可以為兩個長條之，偶極天線的兩個輕射 導體片。在以下的^^絲、橢圓形或勾形的輕射 下的化财，偶極天線的信號饋入源與 12/20 201228105 單極槽孔天線的信號饋入源的信號饋入方向互相垂直 ’且信號相位差90度。 請參照圖10A〜圖10C，圖10A〜圖10C皆是本發 明另一實施例的複合式多天線系統的立體結構圖。圖 1 〇 A中的複合式多天線系統5的偶極天線51之輻射單 元511與512為三角形輻射單元。圖1〇b中的複合式多 天線糸統6的偶極天線61之輻射單元611與612也為 二角形幸虽射單元，但是與圖10A的差異在於其三角形The Standing Wave Ratio (VSWR) is obtained in the case of 1.5:1, the curve C61 represents the S-radiation parameter S22 (the ratio of the input signal of the second signal to the reflected signal), and the curve C62 represents the input signal of the S-parameter Sn (the first). The ratio of the signal to the reflected signal, curve C63 represents the S parameter S21 (the ratio of the input signal of the first 与 to the received signal of the second )). As can be seen from Fig. 6, the composite multi-antenna system 1 of Fig. 1 can operate in a frequency band of 5 GHz, and particularly in a frequency band of 5.15 GHz to 5.825 GHz. Please refer to FIG. 7 and FIG. 8. FIG. 7 is a graph of antenna gain and radiation efficiency of the dipole antenna η of FIG. 1, and FIG. 8 is a graph of antenna gain and conversion efficiency of the monopole slot antenna 12 of FIG. Figure. Curves C71 and C81 represent the antenna gains of the center frequencies of the dipole antenna Π and the monopole slot antenna 12 of Fig. 1, respectively, and curves C72 and C82 represent 11/20 201228105, respectively, of the dipole antenna 11 and the monopole slot of Fig. 1. Radiation efficiency of each center frequency of the antenna 12. As can be seen from FIG. 7 and FIG. 8, the dipole antenna u and the monopole slot antenna 12 of the figure have a maximum antenna gain of 8 decibels (dBi) in the 5 GHz band and the radiation efficiency is 6 〇 0 / 〇 Above. [Other Embodiments of Cascade Multi-Antenna System] In the foregoing embodiment, the slot shape of the monopole slot antenna 12 is rectangular (long strip shape), and the slot opening of the monopole slot antenna 12 is located at a light shot. The second side of conductor #121. However, it is to be noted that the shape of the slot of the monopole antenna I2 and the position of the slot are not intended to limit the present invention. In the following embodiments, the first signal input source U〇 of the dipole antenna u and the second signal feeding source of the monopole slot and the line 12 are perpendicular to each other, and the signal is fed in a direction perpendicular to each other. The phase difference is 90 degrees. A picture: 9C, 1 9A to 9C are all other examples of the present invention (4) 5 heart days I (four) of the vertical ride: composite multi-antenna system 2 single-pole slot antenna 22 two holes connection ° ® 9 Β composite The multi-antenna system 3 has a monopole slot line 3: 2: 322 is a serpentine slot. The % of the early-pole slot antenna of the composite multi-day line 3 of Fig. 3 is larger than the first side of the Korean conductor piece 421. 8 Opening position In addition, in the previous embodiment, the dipole-shaped radiating conductor piece is used as a moment for the Koda field in the shovel. dfcm To be 5 brothers, the shape of the radiating element f of the dipole antenna is not limited. The shape of the element of this hairpin is also not necessary. The two radiation single cells of the phase line can be two strips, two light-emitting conductor pieces of the dipole antenna. The signal feeding source of the dipole antenna and the signal feeding direction of the signal feeding source of the 12/20 201228105 single-pole slot antenna are perpendicular to each other under the light of the following wire, ellipse or hook light. 'And the signal phase difference is 90 degrees. 10A to 10C, FIGS. 10A to 10C are perspective structural views of a composite multi-antenna system according to another embodiment of the present invention. The radiating elements 511 and 512 of the dipole antenna 51 of the composite multi-antenna system 5 in Fig. 1A are triangular radiating elements. The radiating elements 611 and 612 of the dipole antenna 61 of the composite multi-antenna system 6 in Fig. 1〇b are also dihedral, but the difference from Fig. 10A lies in the triangle.
輻射單元的頂點位置不同。圖10C的複合式多天線系統 7的偶極天線71之輪射單元711與712為勾形輕射導體 片° 在前面實施例中，單極槽孔天線與偶極天線排列於 同一軸向且對稱於對稱中心線，但如同前面所述的，單 極槽孔天線與偶極天線的位置與排列方式並非用以限 定^發明。在以下的實施例中，偶極天線的信號饋入源 與單極槽孔天線的信號饋入源的信號饋入方向互相垂 直’且信號相位差90度。 Μ參照圖11A與圖11B，圖11A與圖UB皆是本 發明另-實施例的複合式多天線系統的立體結構圖。圖 UA中的複合式多天線系統8的偶極天線8ι與單極样 ^天線82並未排财同—軸向且也未對稱於對稱中: 線，同樣地’圖】i B中的複合式多天線系統9的 ^ 91與單極槽孔天線92也同樣未排列在同-轴向且也 未對稱於對稱中心線。 也 f前面實施例中，複合式多天線系統是以_ 天線與料魏天料構成，但在本發料他實施例中 13/20 201228105 ，複合式多天線系統更可以包括至少一組以上的偶極天 線與單極槽孔天線。在以下的實施例中，偶極天線的信 號饋入源與單極槽孔天線的信號饋入源的信號饋入方 向互相垂直，且信號相位差90度。 請參照圖12，圖12是本發明另一實施例的複合式 多天線系統的立體結構圖。複合式多天線系統10包括 兩組偶極天線與單極槽孔天線。偶極天線101、103與 單極槽孔天線102、104彼此交錯排列排列於同一軸向 且對稱於中心對稱線S YM_LINE。 總之，由於單極天線槽孔天線的面積與間距較小， 因此，複合式多天線系統可以具有至少一組以上的偶極 天線與單極槽孔天線。如此，可以藉由增加偶極天線與 單極槽孔天線的組數，來增加系統資料吞吐量。 〔使用複合式多天線系統之無線通訊裝置的實施例〕 上述各實施例所提供的複合式多天線系統皆可以 應用於無線通訊裝置，且可以將此複合式多天線系統整 合於無線通訊裝置内，其中無線通訊裝置的收發晶片可 位於系統電路板，且可以透過小型同軸線電氣連接複合 式多天線系統的信號饋入源。在先前的實施例中，無線 通訊裝置更可以是無線接取裝置。 〔實施例的可能功效〕 综合上述之說明，本發明實施例所提供複合式多天 線系統的可以具有天線結構簡單、尺寸小、製作容易、 成本低、易内藏並整合在無線通訊裝置之中等優點。除 此之外，本發明實施例所提供複合式多天線系統還可以 擁有較高天線增益與輻射效率。 14/20 201228105 以上所述僅為本發明之實施例，其並非用以揭 發明之專利範圍。 【圖式簡單說明】 圖1是本發明實施例提供的複合式多天線系統的 立體結構圖。 、圖2 {本發明實施例提供的複合式多天線系統的 上視圖。The apex positions of the radiating elements are different. The firing units 711 and 712 of the dipole antenna 71 of the composite multi-antenna system 7 of FIG. 10C are hook-shaped light-emitting conductor sheets. In the foregoing embodiment, the monopole slot antenna and the dipole antenna are arranged in the same axial direction. Symmetrical to the centerline of symmetry, but as previously described, the position and arrangement of the monopole slot antenna and the dipole antenna are not intended to limit the invention. In the following embodiments, the signal feeding source of the dipole antenna and the signal feeding direction of the signal feeding source of the monopole slot antenna are perpendicular to each other' and the signal phase is 90 degrees out of phase. Referring to Fig. 11A and Fig. 11B, Fig. 11A and Fig. UB are perspective structural views of a composite multi-antenna system according to another embodiment of the present invention. The dipole antenna 8ι of the composite multi-antenna system 8 in Figure UA is not the same as the monopole-like antenna 82. The axial direction is also not symmetric with respect to the symmetry: the line, the same as the 'picture', the composite in i B The 91 and the monopole slot antennas 92 of the multi-antenna system 9 are also not aligned in the same-axis direction and are also not symmetric to the center line of symmetry. Also in the previous embodiment, the composite multi-antenna system is composed of _ antenna and material Wei Tian material, but in the embodiment of the present invention 13/20 201228105, the composite multi-antenna system may further include at least one group or more. Dipole antenna and monopole slot antenna. In the following embodiments, the signal feeding source of the dipole antenna and the signal feeding direction of the signal feeding source of the monopole slot antenna are perpendicular to each other, and the signals are out of phase by 90 degrees. Referring to Figure 12, there is shown a perspective view of a composite multi-antenna system in accordance with another embodiment of the present invention. The composite multi-antenna system 10 includes two sets of dipole antennas and a monopole slot antenna. The dipole antennas 101, 103 and the monopole slot antennas 102, 104 are arranged in a staggered arrangement in the same axial direction and symmetrically to the central symmetry line S YM_LINE. In summary, since the area and spacing of the monopole antenna slot antennas are small, the composite multi-antenna system can have at least one set of dipole antennas and monopole slot antennas. Thus, the system data throughput can be increased by increasing the number of groups of dipole antennas and monopole slot antennas. [Embodiment of Wireless Communication Device Using Composite Multi-Antenna System] The composite multi-antenna system provided by each of the above embodiments can be applied to a wireless communication device, and the composite multi-antenna system can be integrated into a wireless communication device. The transceiver chip of the wireless communication device can be located on the system circuit board, and can be electrically connected to the signal feeding source of the composite multi-antenna system through a small coaxial line. In the previous embodiment, the wireless communication device may more be a wireless access device. [Possible Efficacy of the Embodiments] In summary, the composite multi-antenna system provided by the embodiments of the present invention can have the advantages of simple antenna structure, small size, easy fabrication, low cost, easy integration, and integration in a wireless communication device. advantage. In addition, the composite multi-antenna system provided by the embodiments of the present invention can also have higher antenna gain and radiation efficiency. 14/20 201228105 The above description is only an embodiment of the present invention, and is not intended to disclose the scope of the invention. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a perspective structural view of a composite multi-antenna system according to an embodiment of the present invention. FIG. 2 is a top view of the composite multi-antenna system provided by the embodiment of the present invention.
圖3是本發明實施例提供的複合式多天線系統之 偶極天線與單極槽孔天線之詳細上視圖。 圖4是圖】之偶極天線操作於549〇MHz的輻射場 型示意圖。 圖5是圖1之單極槽孔天線操作於549〇mHz的輻 射場型示意圖。 圖6是圖1之複合式多天線系統在不同頻率下的s 參數之曲線圖。 圖7疋圖1之偶極天線的天線增益與輻射效率之曲 線圖。 圖8是圖1之單極槽孔天線的天線增益與輻射效率 之曲線圖。 圖9A〜圖12皆是本發明另一實施例的複合式多天 線系統的立體結構圖。 【主要元件符號說明】 1〜10 :複合式多天線系統 11、51、61、71、81、91、101、103 :偶極天線 110 :第一信號饋入源 u〇a、ll〇b、120a、120b :信號饋入點 15/20 201228105 m、112、511、512、611、612、711、712 :輻射 Χ3Ό — 早兀 12、22、32、42、82、92、102、104 :單極槽孔天 線 120 :第二信號饋入源 121、 421 :輻射導體片 122、 222、322、422 :槽孔 13 :天線基板 14 :系統電路板 141 :系統接地面 C61 〜C63、C71、C72、C81、C82 :曲線3 is a detailed top view of a dipole antenna and a monopole slot antenna of a composite multi-antenna system according to an embodiment of the present invention. Fig. 4 is a schematic view showing the radiation pattern of the dipole antenna operating at 549 〇 MHz. Figure 5 is a schematic illustration of the radiant field pattern of the monopole slot antenna of Figure 1 operating at 549 〇mHz. Figure 6 is a graph of the s-parameters of the composite multi-antenna system of Figure 1 at different frequencies. Figure 7 is a graph showing the antenna gain and radiation efficiency of the dipole antenna of Figure 1. Figure 8 is a graph of antenna gain and radiation efficiency for the monopole slot antenna of Figure 1. 9A to 12 are perspective structural views of a composite multi-antenna system according to another embodiment of the present invention. [Description of main component symbols] 1 to 10: Composite multi-antenna system 11, 51, 61, 71, 81, 91, 101, 103: dipole antenna 110: first signal feed source u〇a, ll〇b, 120a, 120b: signal feed point 15/20 201228105 m, 112, 511, 512, 611, 612, 711, 712: radiation Χ 3 Ό - early 兀 12, 22, 32, 42, 82, 92, 102, 104: single Pole slot antenna 120: second signal feed source 121, 421: radiating conductor piece 122, 222, 322, 422: slot 13: antenna substrate 14: system circuit board 141: system ground plane C61 ~ C63, C71, C72 , C81, C82: Curve
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