201216603 /1 w j>4864twf.doc/n 六、發明說明： 【發明所屬之技術領域】 本發明是有關於一種電壓轉換裝置，且特別是有關於 一種交流轉直流電壓轉換裝置的驅動電流調整機制。 【先前技術】 請參照圖1A及圖1B所分別繚示習知的電阻式及電容 式交流直流電壓轉換器110、120的電路圖。其中，在交流 直流電壓轉換器110中’交流輸入電壓ACIN經過二極體 D1整流後，經過電阻R1及作為穩壓功用的齊納二極體 ZD1 (zener diode)與電容C1後’產生直流輸出電壓來驅動 負載111。而在交流直流電壓轉換器120中，交流輸入電 壓ACIN則是先通過交流耦合電容C1後，再分別經過用 來穩壓以及整流的齊納二極體ZD1、電容C1以及二極體 D1 ’並藉以產生直流輸出電壓來驅動負載12ι。 而在上述的兩種交流直流電壓轉換器1丨〇、12〇中， 不論是在負載111及121在工作模式下或是在待機模式下 時’都不會對應改變交流直流電壓轉換器U〇、12〇所輸出 的驅動電流I。而當在負載11丨及121在待機模式下時， 其所需要的驅動電流顯然會比交流直流電壓轉換器11〇、 120所固定輸出的驅動電流丨來得小。在此情況下，在負 載111及121在待機模式下時，多餘的電流就會由齊納二 極體ZD1流出而被浪費掉。 34864twf.doc/n 201216603 3y/j 【發明内容】 本發明提供一種電壓轉換裝置，依據所驅動的負載裝 置的電流需求狀態，來改變電壓轉換裝置所提供的電流大 小，以有效節省電力的消耗。 本發明提出一種電壓轉換裝置，用以接收交流輸入電 壓’並依據轉換交流輸入電壓來產生直流輸出電壓以驅動 負載裝置。電壓轉換裝置包括整流器、電流路徑選擇器以 及負載狀態偵測器。整流器接收交流輸入電壓並據以產生 直流輸入電壓。電流路徑選擇器具有輸入端與輸出端，其 輸入端接收直流輸入電壓，其輸出端產生直流輪出電壓。 電=路徑選擇器包括串接在電流路徑選擇器的輪入端與輸 出^0間的第一及第一電流傳輸路徑。電流路徑選墟 襲信號來選擇藉由第-及第二電流傳輸路徑的至^其中 之-來傳送直流輸人電壓至電流路徑選擇器的輸出端 =變電流路徑選擇器的輸人端與輸出端間的等效阻 ^載=_轉接電流路徑選擇㈣輸出端以及 置’，據偵測負載裝置的電流需求狀絲產生選擇信號。、 控制軍本發月之0 Λ;^例中’上述之負載狀態彳貞測器包括 “晋二控制單元耦接電流路徑選擇器的輸出端以及負 號:：料元接收並依據模式設定信號來產生選擇信 在本發明之一實施例中，上+ 一 設定信號來產生㈣am 控制早70更依據模式 κ—Μ產生負載錢域°控制單it接收並依據模式 δ又疋㈣來控制該負絲置的該電流需求狀態。式 5 201216603 /1 w jn864twf. doc/n 在本發明之-實施例中，上述之負載狀態侦測器包括 U貞測電路、控制單元以及邏輯運算電路^電流偵測電 ，搞接電流路㈣擇H的輪出端，用則貞測電流路徑選擇 ，的輸出電W ’並依據輸出電流產生偵測結果信號。控制 :7L輕接電流細電路以及貞載裝置，接傾式設定信號 2產，模式設定結果。邏輯運算電路耦接電流彳貞測電路、 工制早7〇m電流路徑獅器，接收並依據制結果信號 以及模式设定結果進行邏輯運算以產生選擇信號。 产。。在本發明之一實施例中，上述之電流偵測電路包括比 車乂 1感測電阻以及臨界電壓源。比較器的輸出端產生偵 測^果信號。感測電阻串接在比較器的第—輸人端及電流 路控選擇㈣輸出賴。臨界電獅财接在比較器的第 一輸入端及電流路徑選擇器的輸出端間，用以提供臨界 麼。 ％ 在本發明之一實施例中，上述之邏輯運算單元為哎 閘。或閘的輸入端接收偵測結果信號以及模式設定結果一， 並在其輪出端產生選擇信號。 、° 在本發明之一實施例中，上述之負載狀態偵測器包括 電流偵測電路。電流偵測電路耦接電流路徑選擇器的輸出 端’用以偵測電流路徑選擇器的輸出電流，並依據輪^ 流產生選擇信號。 月'電 在本發明之一實施例中，上述之負載狀態偵測器更包 括控制單元。控制單元耦接電流偵測電路以及負栽裝置匕 接收並依據模式設定信號來控制負載裝置的電流需求狀 201216603 jy/i w 34864twf.doc/n201216603 /1 w j>4864twf.doc/n VI. Description of the Invention: [Technical Field] The present invention relates to a voltage conversion device, and more particularly to a drive current adjustment mechanism for an AC-to-DC voltage conversion device . [Prior Art] A circuit diagram of a conventional resistive and capacitive AC DC voltage converter 110, 120 will be shown with reference to Figs. 1A and 1B, respectively. Wherein, in the AC-DC voltage converter 110, the AC input voltage ACIN is rectified by the diode D1, and the DC output is generated after the resistor R1 and the Zener diode ZD1 (zener diode) and the capacitor C1 function as a voltage regulator. The voltage drives the load 111. In the AC DC voltage converter 120, the AC input voltage ACIN is first passed through the AC coupling capacitor C1, and then passed through the Zener diode ZD1, the capacitor C1, and the diode D1' for voltage regulation and rectification, respectively. The DC output voltage is generated to drive the load 12ι. In the above two kinds of AC DC voltage converters 1丨〇, 12〇, no matter when the loads 111 and 121 are in the working mode or in the standby mode, the AC voltage converter U〇 does not change correspondingly. The drive current I output at 12 。. When the loads 11 丨 and 121 are in the standby mode, the required driving current is obviously smaller than the driving current 固定 of the fixed output of the AC dc voltage converters 11 〇 120. In this case, when the loads 111 and 121 are in the standby mode, excess current is discharged from the Zener diode ZD1 and was wasted. 34864twf.doc/n 201216603 3y/j SUMMARY OF THE INVENTION The present invention provides a voltage conversion device that changes the current supplied by a voltage conversion device in accordance with the current demand state of the driven load device to effectively save power consumption. The present invention provides a voltage conversion device for receiving an AC input voltage ' and generating a DC output voltage in accordance with a converted AC input voltage to drive a load device. The voltage conversion device includes a rectifier, a current path selector, and a load state detector. The rectifier receives the AC input voltage and generates a DC input voltage accordingly. The current path selector has an input end and an output end, the input end of which receives a DC input voltage, and the output end of which generates a DC output voltage. The electric = path selector includes first and first current transfer paths connected in series between the turn-in end of the current path selector and the output ^0. The current path selects the signal to select the DC input voltage to the output of the current path selector by the first and second current transmission paths to the output of the current path selector = the input and output of the variable current path selector The equivalent resistance between the terminals = _ current path selection (four) output and set ', according to the current demand of the detection device to generate a selection signal. The control load state detector includes the output of the Jin 2 control unit coupled to the current path selector and the minus sign: the material element receives and is based on the mode setting signal. In the embodiment of the present invention, the upper + a set signal is generated to generate (4) the am control is early 70. According to the mode κ - Μ generates the load money domain ° control unit it receives and controls the negative filament according to the mode δ 疋 (4) The current demand state is set. Equation 5 201216603 /1 w jn864twf. doc/n In the embodiment of the present invention, the load state detector includes the U test circuit, the control unit, and the logic operation circuit ^ current detection Electric, make the current path (4) select the round end of H, use the current path selection, the output power W ' and generate the detection result signal according to the output current. Control: 7L light current circuit and load device, connect Tilt setting signal 2 production, mode setting result. The logic operation circuit is coupled with the current measurement circuit, the industrial 7 〇m current path lion, receiving and logicizing according to the result signal and the mode setting result. In one embodiment of the invention, the current detecting circuit includes a sensing resistor and a threshold voltage source than the rudder 1. The output of the comparator generates a detection signal. The resistor is connected in series with the first input terminal of the comparator and the current path selection (four) output. The critical electric lion is connected between the first input of the comparator and the output of the current path selector to provide a critical value. In one embodiment of the present invention, the logic operation unit is a gate, or the input end of the gate receives the detection result signal and the mode setting result one, and generates a selection signal at the wheel end thereof. In one embodiment, the load state detector includes a current detecting circuit coupled to the output of the current path selector to detect an output current of the current path selector, and according to the current The selection signal is generated. In one embodiment of the present invention, the load state detector further includes a control unit, and the control unit is coupled to the current detecting circuit and the receiving device to receive and Control the current demand of the load device according to the mode setting signal 201216603 jy/i w 34864twf.doc/n
在本發明之-實施例中，其中更包括穩壓電路。 電路耦接電流路徑選擇H的輪出端，用_定直流‘雷 壓的電壓值。 ％ 在本發明之-實施例中，上述之穩壓電路包括齊納二 極體以及穩壓f容。齊納二極體串接在電流路徑選擇器的 輪出端與接地電壓間。穩壓電容則與齊納二極體並連耦接。 在本發明之一實施例中，上述之電流路徑選擇器更包 括選擇開關。選擇開關的-端接收直流輸人電壓以及第一 電流傳輸路徑的第一端，其另一端耦接第二電流傳輪路徑 的第一端。選擇開關接收選擇信號以導通或斷開。其中， 第一及第二電流傳輸路徑的第二端耦接至電流路徑選擇器 的輸出端。 ° b在本發明之一實施例中，上述之第一電流傳輸路徑所 ，供的等效阻抗大於第二電流傳輸路徑所提供的等效阻 抗。 在本發明之一實施例中’上述冬電流路徑選擇器更包 t選擇開關。選擇開關的一端接收直流輸入電壓，其另— 端依據選擇信號選擇耦接第一電流傳輸路徑的第一端或第 =電流傳輪路徑的第一端。其中，第一及第二電流傳輸路 2的第二端耦接至電流路徑選擇器的輸出端’且第一電流 輪路徑所提供的等效阻抗大於第二電流傳輸路徑所提供 的等效阻抗。 在本發明之一實施例中，上述之電流需求狀態為負載 201216603 jy /1 w j*t864twf.doc/n 裝置啟動或關閉時，負載裝置所消耗的電流。 -基於上述’本發明藉由提供不同同阻抗的電流傳輸路 徑，來傳輸經整流器整流後的直流輸入電壓，並藉以產生 具有不同驅動能力的直流輸出電壓，來驅動不同電流需求 狀態下的負載裝置。如此一來，可以有效的提升效率，達 到綠色能源的需求。 為讓本發明之上述特徵和優點能更明顯易懂，下文特 舉實施例’並配合所附圖式作詳細說明如下。 【實施方式】 以下請參照圖2，圖2繪示本發明的一實施例的電壓 轉換裝置200的示意圖。電壓轉換裝置2〇〇包括整流器 210、電流路徑選擇器220、負載狀態偵測器230以及穩壓 電路240。其中，電壓轉換裝置2〇〇接收交流輸入電壓 ACVIN，並依據轉換交流輸入電壓ACVIN來產生直流輸 出電壓DCVOUT以驅動負載裝置250。 整流器210接收交流輸入電壓ACVIN，整流器210 並針對交流輸入電壓ACVIN進行整流以產生直流輸入電 壓DCVIN。在本實施例中，整流器210為利用二極體所建 構的半波整流器。也就是說，在本實施例中，直流輸入電 壓DCVIN則是整流器210藉由濾除交流輸入電壓ACVIN 的負半週的電壓所產生的。 電流路徑選擇器220具有輸入端P1以及輸出端P2。 電流路徑選擇器220的輸入端P1耦接至整流器210以接 201216603 / 1 YV 34864twf.doc/n 收直流輸入電壓DCVIN，而電流路徑選擇器220的輸出端 P2則產生直流輸出電壓DCVOUT。電流路徑選擇器220 中則包括兩個電流傳輸路徑221及222。電流傳輸路控221 及222串連耦接在電流路徑選擇器220的輸入端P1與輸 出端P2間。電流路徑選擇器220另接收選擇信號SEL， 並依據選擇信號SEL來選擇藉由電流傳輸路徑221及222 的至少其中之一來傳送直流輸入電壓DCVIN至電流路徑 選擇器220的輸出端P2並藉以產生直流輸出電壓 DCVOUT。其中，在電流路徑選擇器220依據選擇信號SEL 來改變直流輸入電壓DCVIN的傳輸路徑時，電流路徑選 擇器220的輸入端P1與輸出端P2間的等效阻抗也隨之改 變0 在本實施例中，電流路徑選擇器220中另包括選擇開 關SWH。選擇開關SW1受控於選擇信號SEL來導通或斷 開。選擇開關SW1的一端耦接電流路徑選擇器22〇的輸入 端P1以接收直流輸入電壓DCVIN，另一端則耦接到電流 傳輸路徑222。而電流傳輸路徑22:[則跨接在電流路徑選 擇器220的輸入端pi及電流傳輸路徑222的第二端間。 當在選擇開關SW1依據選擇信號SEL斷開時，直流輸入 電壓DCVIN由電流傳輸路徑奶接收並傳輸至電流路徑 選擇器22〇的輸出端P2並產生直流輸出電壓DCV〇UT。 當選擇開關swi依據選擇錢SEL導通時，直流輸入電 壓DCVIN貝|!會同時由電流傳輸路徑221及222進行傳輸。 在此請注意，電流傳輸路徑221及222分別提供一等 201216603 /1 yv j4864twf.doc/n 效阻抗，並且，電流傳輸路經221所提供 電流傳輸路徑222所提供的等效阻抗。當直流輪i = =僅由電流傳輸路徑221進行傳輸時(選擇開關謂 電流路徑選擇器22()的輪入端？1及輸出端以 間的專效阻抗等於電流傳輸路徑221所提供的等效阻抗。 而當直流輸入電壓DCVIN㈤時由電流傳輸路徑功及切 進行傳輸時(選擇開關SW1導通時），電流路徑選擇器22〇 的輸入端P1及輸出端P2間的等效阻抗等於電流傳輸路徑 221及222所提供的等效阻抗並連的阻抗值。也就是說， 選擇開關swi斷開時的電流路徑選擇器，的輸入端ρι 及輸出端1>2 _等效阻抗大於麵關SW1導通時的電 抓路稜選擇器220的輸入端pi及輸出端p2間的等效阻抗。 負載狀態偵測器230耦接電流路徑選擇器22〇的輸出 端P2以及負載裝置25〇。負載狀態偵測器23〇偵測負載裝 置250的電流需求狀態並據以產生選擇信號SEL。在本實 施例中，負載狀態偵測器230包括控制單元231。控制單 元231接收模式設定信號M〇DSET，並依據模式設定信號 MODSET來獲知負載裝置25G的電流需求狀態。模式設定 “5虎MODSET是由外部輸入的信號，用來指示設定負載 裝置250進入工作模式或是待機模式。而當模式設定信號 MODSET指示負載裝置250進入工作模式時，表示負载裝 置250的電流需求狀態為需要較大的驅動電流。此時，控 制單元231依據模式設定信號MODSET產生選擇信號SEL 來導通選擇開關SW1，以選擇較小的等效阻抗的傳輸路徑 201216603 麵一 來傳輸直流輸入電壓DCVIN。並且’控制單元231依據模 式設定信號MODSET產生負載設定信號LS以啟動負載裝 置250 ’使負載裝置250進入工作模式。 相對的’當模式設定信號MODSET指示負載裝置250 進入待機模式時’表示負載裝置250的電流需求狀態為需 要較小的驅動電流。此時，控制單元231依據模式設定信 號MODSET產生選擇信號SEL來斷開選擇開關SW1，以 選擇較大的等效阻抗的傳輸路徑來傳輸直流輸入電壓In an embodiment of the invention, a voltage stabilizing circuit is further included. The circuit is coupled to the wheel path of the current path selection H, and the voltage value of the dc voltage is determined by _. % In the embodiment of the invention, the above-mentioned voltage stabilizing circuit comprises a Zener diode and a regulated voltage. The Zener diode is connected in series between the wheel terminal of the current path selector and the ground voltage. The Zener capacitor is coupled in parallel with the Zener diode. In an embodiment of the invention, the current path selector further includes a selection switch. The - terminal of the selection switch receives the DC input voltage and the first end of the first current transmission path, and the other end of the switch is coupled to the first end of the second current transfer path. The selector switch receives the selection signal to turn on or off. The second ends of the first and second current transmission paths are coupled to the output of the current path selector. In one embodiment of the invention, the first current transmission path provides an equivalent impedance greater than the equivalent impedance provided by the second current transmission path. In one embodiment of the invention, the winter current path selector described above further includes a t-selection switch. One end of the selection switch receives the DC input voltage, and the other end selectively couples the first end of the first current transmission path or the first end of the = current carrying path according to the selection signal. The second end of the first and second current transmission paths 2 is coupled to the output end of the current path selector and the equivalent impedance provided by the first current path is greater than the equivalent impedance provided by the second current transmission path. . In an embodiment of the invention, the current demand state is the load 201216603 jy /1 w j*t864twf.doc/n The current consumed by the load device when the device is started or turned off. - Based on the above, the present invention transmits a DC input voltage rectified by a rectifier by providing current transmission paths of different impedances, and thereby generates DC output voltages having different driving capacities to drive load devices in different current demand states. . In this way, efficiency can be effectively improved and the demand for green energy can be achieved. The above described features and advantages of the present invention will become more apparent from the description of the appended claims. [Embodiment] Referring now to Figure 2, there is shown a schematic diagram of a voltage conversion device 200 in accordance with an embodiment of the present invention. The voltage conversion device 2A includes a rectifier 210, a current path selector 220, a load state detector 230, and a voltage stabilizing circuit 240. The voltage conversion device 2 receives the AC input voltage ACVIN and generates a DC output voltage DCVOUT according to the converted AC input voltage ACVIN to drive the load device 250. The rectifier 210 receives the AC input voltage ACVIN, and the rectifier 210 rectifies the AC input voltage ACVIN to produce a DC input voltage DCVIN. In the present embodiment, the rectifier 210 is a half-wave rectifier constructed using a diode. That is, in the present embodiment, the DC input voltage DCVIN is generated by the rectifier 210 by filtering out the voltage of the negative half cycle of the AC input voltage ACVIN. The current path selector 220 has an input terminal P1 and an output terminal P2. The input terminal P1 of the current path selector 220 is coupled to the rectifier 210 to receive the DC input voltage DCVIN of 201216603 / 1 YV 34864twf.doc / n, and the output terminal P2 of the current path selector 220 generates the DC output voltage DCVOUT. The current path selector 220 includes two current transmission paths 221 and 222. The current transmission paths 221 and 222 are coupled in series between the input terminal P1 and the output terminal P2 of the current path selector 220. The current path selector 220 further receives the selection signal SEL, and selects at least one of the current transmission paths 221 and 222 to transmit the DC input voltage DCVIN to the output terminal P2 of the current path selector 220 according to the selection signal SEL and thereby generate DC output voltage DCVOUT. In the embodiment, when the current path selector 220 changes the transmission path of the DC input voltage DCVIN according to the selection signal SEL, the equivalent impedance between the input terminal P1 and the output terminal P2 of the current path selector 220 also changes. The current path selector 220 further includes a selection switch SWH. The selection switch SW1 is controlled to be turned on or off by the selection signal SEL. One end of the selection switch SW1 is coupled to the input terminal P1 of the current path selector 22A to receive the DC input voltage DCVIN, and the other end is coupled to the current transmission path 222. The current transmission path 22: [crosses" between the input terminal pi of the current path selector 220 and the second terminal of the current transmission path 222. When the selection switch SW1 is turned off in accordance with the selection signal SEL, the DC input voltage DCVIN is received by the current transmission path milk and transmitted to the output terminal P2 of the current path selector 22A to generate a DC output voltage DCV〇UT. When the selection switch swi is turned on according to the selection money SEL, the DC input voltage DCVINB|! is simultaneously transmitted by the current transmission paths 221 and 222. It should be noted here that the current transmission paths 221 and 222 respectively provide a first-order 201216603 /1 yv j4864twf.doc/n effect impedance, and the current transmission path provides an equivalent impedance provided by the current transmission path 222. When the DC wheel i = = is only transmitted by the current transmission path 221 (the selection switch refers to the rounding end of the current path selector 22 () and the output impedance of the output terminal is equal to that provided by the current transmission path 221, etc. When the DC input voltage DCVIN (5) is transmitted by the current transmission path and cut (when the selection switch SW1 is turned on), the equivalent impedance between the input terminal P1 and the output terminal P2 of the current path selector 22 is equal to the current transmission. The impedance values of the equivalent impedances provided by paths 221 and 222 are connected. That is, the input path ρι and the output terminal 1> 2 _ equivalent impedance of the current path selector when the selection switch swi is turned off is greater than the face SW1 The equivalent impedance between the input terminal pi and the output terminal p2 of the electric grabbing edge selector 220 during the conduction. The load state detector 230 is coupled to the output terminal P2 of the current path selector 22A and the load device 25A. The detector 23 detects the current demand state of the load device 250 and generates a selection signal SEL accordingly. In the present embodiment, the load state detector 230 includes a control unit 231. The control unit 231 receives the mode setting signal M. DSET, and according to the mode setting signal MODSET to know the current demand state of the load device 25G. The mode setting "5 tiger MODSET is a signal input from the outside to indicate that the set load device 250 enters the working mode or the standby mode. When the mode is set When the signal MODSET indicates that the load device 250 enters the working mode, it indicates that the current demand state of the load device 250 is a large driving current. At this time, the control unit 231 generates a selection signal SEL according to the mode setting signal MODSET to turn on the selection switch SW1 to select The smaller equivalent impedance transmission path 201216603 transmits the DC input voltage DCVIN, and the 'control unit 231 generates the load setting signal LS according to the mode setting signal MODSET to activate the load device 250' to bring the load device 250 into the operating mode. 'When the mode setting signal MODSET indicates that the load device 250 enters the standby mode' indicates that the current demand state of the load device 250 is that a smaller drive current is required. At this time, the control unit 231 generates a selection signal SEL according to the mode setting signal MODSET to disconnect the selection. Switch SW1 to select Large equivalent impedance transmission path to transmit DC input voltage
# DCVIN。並且，控制單元231依據模式設定信號M〇DSET 產生負載设疋號LS以關閉負载裝置250，使負載裝置 250進入待機模式。 穩壓電路240耦接在電流路徑選擇器22〇的輸出端p2 上，用以穩定電流路徑選擇器220的輸出端p2上的直流 輸出電壓DCVOUT的電壓值。在本實施例中，穩壓電路 240包括齊納二極體ZD1以及穩壓電容C2。齊納二極體 ZD1串接在電流路徑選擇器220的輸出端p2與接地電壓 • GND間’而穩壓電容C2則與齊納二極體ZD1並連耦接。 齊納二極體ZD1用來使直流輸出電壓dcv㈤τ被前置在 二定的電壓(齊納二極體ZD1的崩潰電壓）以下，而穩壓電 容C2則可以有效降低直流輸出電壓dcv〇ut的紋波 (ripple)程度。 接著叫參照圖3 ’圖3綠示本發明的另一實施例的電 壓轉換裝置300的示意圖。電壓轉換裂置3〇〇包括整流器 310、電流路徑選擇器320、負栽狀態_器330以及穩壓 11 201216603 397TW 34864twf.doc/n 電路340。電壓轉換裝f _接收交流輸入電壓人⑺取， 並依據轉換交流輸人電壓ACVIN來產生直流輸出 DCVOUT以驅動負载裝置35〇。 與則-實，例不同的，本實施例中的負載狀態该測器 33〇包括控制單元331以及電流偵測電路332。電流偵測電 路3—32輕接電流路經選擇器32〇的輸出端，用以偵測電流 路徑選擇器320的輪出電流，並依據所_出的輸出電= 來產生選擇信號S E L。控制單元3 3丨耦接電流偵測電路3 3 2 以及負載裝置350，用以接收並依據模式設定信號 MODSET來啟動或關閉負載裝置35〇。 請注意，在本實施例中，選擇信號SEL是由電流偵測 電路332來偵測實際流至負載裝置350的電流大小，來獲 知負載裝置350的電流需求狀態。並依據實際的負载裝置 350的電流需求狀態來產生選擇信號sel，以改變電壓轉 換裝置300所提供的驅動電流大小。也就是說，電壓轉換 裝置300可以主動的偵知負載裝置350處於待機模式或工 作模式’並據以調整其所產生的直流輸入電壓的傳輸選擇 路徑’來進以調整電壓轉換裝置3〇〇所提供的驅動電流大 /】、〇 以下再請參照圖4A，圖4A繪示本發明的再一實施例 的電壓轉換裝置400的示意圖。電壓轉換裝置400包括整 流器410、電流路徑選擇器420、負載狀態偵測器430以及 穩壓電路440。電壓轉換裝置400接收交流輸入電壓 ACVIN ’並依據轉換交流輸入電壓ACVIN來產生直流輸 12 201216603 1 w 34864twf.doc/n 出電壓DCVOUT以驅動負載裝置450。 與前述實施例不同的，本實施例中的負載狀態偵測器 430包括控制單元43卜電流偵測電路432以及由或閘〇Rl 建構的邏輯運算單元。電流偵測電路432耦接電流路徑選 擇器420的輸出端，用以偵測電流路徑選擇器420的輸出 電流，並依據所偵測出的輸出電流來產生偵測結果信號 DR。控制單元431耦接電流偵測電路432以及負載農置 435，並接收模式設定信號MODSET來產生模式設定結果 MR。作為邏輯運算單元的或閘OR1的輸入端則接收偵測 結果信號DR以及模式設定結果MR，並針對偵測結果信 號DR以及模式設定結果MR進行邏輯運算來產生選擇信 號 SEL。 也就是說，在圖4A的實施例中，負載狀態偵測器430 除了可以藉由電流偵測電路432主動偵知的負載裝置450 的電流需求狀態所獲得的偵測結果信號DR來設定選擇信 號SEL外’還可以藉由控制單元431依據模式設定信號 MODSET所產生的模式設定結果MR來設定選擇信號 SEL。舉一個實際的實施範例來說明，在負載裝置450進 入工作模式時，電流偵測電路432會偵測出負載裝置450 需要較大的驅動電流並產生邏輯高準位的偵測結果信號 DR。而或閘OR1則會依據邏輯高準位的偵測結果信號dr 來產生邏輯高準位的選擇信號SEL使選擇開關SW1導 通’並使電壓轉換裝置400提供較高的驅動電流。或者， 在負載裝置450進入工作模式時，控制單元431依據設定 13 201216603 〜，…，^ ^864twf.doc/n 負載裝置450進入工作模式的模式設定信號m〇dset所 產生的邏輯高準位的模式設定結果MR，來透過或閘〇iu 產生邏輯高準位的選擇信號SEL使選擇開關swi導通， 並使電壓轉換裝置400提供較高的驅動電流。 相反的，當負載裝置450進入待機模式時，控制單元 431以及電流偵測電路432都不會產生邏輯高準位的模式 設定結果MR以及偵測結果信號dr。因此，或閘〇R1會 提供邏輯低準位的選擇信號SEL使選擇開關簡關閉。 並有效降低電壓轉換裝置400提供的驅動電流。 鲁 附帶一提的，上述實施範例中的模式設定結果MR、 ，測結果信號DR以及選擇信號SEL的邏輯高低準位的設 定僅只是一個範例，並不用來限制本發明的範疇。 另請參照圖4B，圖4B繪示本發明圖4A繪示的實施 例的實％方式。其中，在本實施方式的電流路徑選擇器 46〇中的選擇開關SW1的一端接收直流輸入電壓 DCVIN’其另-端依據選擇信號SEL選擇輕接電流傳輸路 徑461的第一端或電流傳輸路徑462的第一端。其中，電 "IL傳輸路徑461及462的第二端耗接至電流路徑選擇器 鲁 460的輸出端，且電流傳輸路徑461所提供的等效阻抗大 於/電流傳輸路徑462所提供的等效阻抗。簡單來說，電流 路徑選擇器楊是利用選擇開關SW1來選擇電流傳輸路徑 或的其中之一來進行傳送直流輸入電壓DCVIN。 並错由電流傳輸路徑461及462所提供的等效阻抗的不 同，來調整電壓轉換裝置400所提供的驅動電流。 14 34864twf.doc/n 201216603 jy/l w 請參照圖5，圖5繪示本發明圖4A實施例的另一實 施方式。其中，電壓轉換裝置500為電阻式電壓轉換裝置。 其中的電流路徑選擇器520中利用電阻RA來形成提供較 高阻抗的電流傳輸路徑，並利用開關SW1來形成提供較低 阻抗的電流傳輸路徑。# DCVIN. Further, the control unit 231 generates a load setting number LS according to the mode setting signal M〇DSET to turn off the load device 250, and causes the load device 250 to enter the standby mode. The voltage stabilizing circuit 240 is coupled to the output terminal p2 of the current path selector 22A for stabilizing the voltage value of the DC output voltage DCVOUT at the output terminal p2 of the current path selector 220. In the present embodiment, the voltage stabilizing circuit 240 includes a Zener diode ZD1 and a voltage stabilizing capacitor C2. The Zener diode ZD1 is connected in series between the output terminal p2 of the current path selector 220 and the ground voltage • GND, and the voltage stabilizing capacitor C2 is coupled in parallel with the Zener diode ZD1. The Zener diode ZD1 is used to make the DC output voltage dcv(5)τ be pre-set at a certain voltage (the breakdown voltage of the Zener diode ZD1), and the Zener capacitor C2 can effectively reduce the DC output voltage dcv〇ut. The degree of ripple. Next, a schematic diagram of a voltage converting device 300 according to another embodiment of the present invention will be described with reference to Fig. 3'. The voltage conversion split 3 includes a rectifier 310, a current path selector 320, a load state_stater 330, and a voltage regulator 11 201216603 397TW 34864twf.doc/n circuit 340. The voltage conversion device f_ receives the AC input voltage (7), and generates a DC output DCVOUT according to the converted AC input voltage ACVIN to drive the load device 35A. The load state detector 33 of the present embodiment includes a control unit 331 and a current detecting circuit 332, which are different from the actual case. The current detecting circuit 3 - 32 is connected to the output terminal of the current selector 32 轻 to detect the current of the current path selector 320 and generate the selection signal S E L according to the output power =. The control unit 3 3 is coupled to the current detecting circuit 3 3 2 and the load device 350 for receiving and turning on or off the load device 35 according to the mode setting signal MODSET. Please note that in the present embodiment, the selection signal SEL is used by the current detecting circuit 332 to detect the current flowing to the load device 350 to know the current demand state of the load device 350. The selection signal sel is generated in accordance with the actual current demand state of the load device 350 to change the magnitude of the drive current provided by the voltage conversion device 300. That is, the voltage conversion device 300 can actively detect that the load device 350 is in the standby mode or the operating mode 'and adjusts the transmission selection path of the DC input voltage generated by it to adjust the voltage conversion device 3 The drive current provided is large. Please refer to FIG. 4A below. FIG. 4A is a schematic diagram of a voltage conversion device 400 according to still another embodiment of the present invention. The voltage conversion device 400 includes a rectifier 410, a current path selector 420, a load state detector 430, and a voltage stabilization circuit 440. The voltage conversion device 400 receives the AC input voltage ACVIN' and generates a DC input according to the converted AC input voltage ACVIN. 12 201216603 1 w 34864twf.doc/n The output voltage DCVOUT is used to drive the load device 450. Different from the foregoing embodiment, the load state detector 430 in this embodiment includes a control unit 43 and a current detecting circuit 432 and a logical operation unit constructed by the OR gate R1. The current detecting circuit 432 is coupled to the output of the current path selector 420 for detecting the output current of the current path selector 420, and generating the detection result signal DR according to the detected output current. The control unit 431 is coupled to the current detecting circuit 432 and the load farm 435, and receives the mode setting signal MODSET to generate the mode setting result MR. The input terminal of the OR gate OR1 of the logic operation unit receives the detection result signal DR and the mode setting result MR, and performs a logic operation on the detection result signal DR and the mode setting result MR to generate the selection signal SEL. That is, in the embodiment of FIG. 4A, the load state detector 430 sets the selection signal in addition to the detection result signal DR obtained by the current demand state of the load device 450 actively detected by the current detecting circuit 432. The selection signal SEL can also be set by the control unit 431 according to the mode setting result MR generated by the mode setting signal MODSET. As a practical example, when the load device 450 enters the operating mode, the current detecting circuit 432 detects that the load device 450 requires a large driving current and generates a logic high level detection result signal DR. The OR gate OR1 generates a logic high level selection signal SEL according to the logic high level detection result signal dr to turn on the selection switch SW1 and causes the voltage conversion device 400 to provide a higher driving current. Alternatively, when the load device 450 enters the working mode, the control unit 431 enters the logic high level generated by the mode setting signal m〇dset of the working mode according to the setting 13 201216603 〜, . . , ^ ^ 864 twf.doc/n The mode setting result MR is such that the selection switch swi is turned on by the gate iu generating a logic high level selection signal SEL, and the voltage conversion device 400 is supplied with a higher driving current. Conversely, when the load device 450 enters the standby mode, neither the control unit 431 nor the current detecting circuit 432 generates the mode setting result MR of the logic high level and the detection result signal dr. Therefore, OR gate R1 will provide a logic low level select signal SEL to turn the select switch off. The driving current supplied from the voltage conversion device 400 is effectively reduced. Inc., the setting of the mode setting result MR, the measurement result signal DR, and the logic high and low level of the selection signal SEL in the above embodiment is merely an example and is not intended to limit the scope of the present invention. Please refer to FIG. 4B. FIG. 4B illustrates a real % mode of the embodiment of FIG. 4A of the present invention. The one end of the selection switch SW1 in the current path selector 46A of the present embodiment receives the DC input voltage DCVIN', and the other end selects the first end of the lightly connected current transmission path 461 or the current transmission path 462 according to the selection signal SEL. The first end. Wherein, the second ends of the electrical "IL transmission paths 461 and 462 are drained to the output of the current path selector 460, and the equivalent impedance provided by the current transmission path 461 is greater than the equivalent provided by the current transmission path 462. impedance. Briefly, the current path selector Yang uses the selection switch SW1 to select one of the current transmission paths or to transmit the DC input voltage DCVIN. The drive current supplied from the voltage conversion device 400 is adjusted by the difference in equivalent impedances provided by the current transmission paths 461 and 462. 14 34864twf.doc/n 201216603 jy/l w Please refer to FIG. 5, which illustrates another embodiment of the embodiment of FIG. 4A of the present invention. The voltage conversion device 500 is a resistive voltage conversion device. The current path selector 520 utilizes a resistor RA to form a current transmission path that provides a higher impedance, and utilizes the switch SW1 to form a current transmission path that provides a lower impedance.
另外’負載狀態偵測器530中的電流偵測電路532則 包括比較器CMP卜感測電阻R2以及臨界電壓源v〇。感 測電阻R2串接在比較器CMP 1的第一輸入端及電流路徑 選擇器520的輸出端間。臨界電壓源v〇串接在比較器 CMP1的第二輸入端及電流路徑選擇器52〇的輸出端間， 用以提供臨界電壓。比較器CMP1則依據其兩輸入端所接 收的信號來進行比較，並在其輸出端產生偵測結果信號 DR。附帶一提的，電容〇及〇4為穩壓電容。 =下並請參照圖6，圖6緣示本發明圖4A實施例的 ；5咨式。電愿轉換裝置6〇0包括電流路徑選擇器620 測器630。與圖5繪示的實施方式不相同的， 發電容式電壓轉換裝置。也就是說，本 法，不但可實二袁路：來提供不同的驅動電流的作 電容式電㈣換裝置。且式電壓轉換襄置，也可以實施於 載骏置處二乍電壓轉換裝置所驅動的 :上的等效阻抗，二傳輸路徑來調 大小。達到有效針對負載；3置所輪出的驅動電 、裝置的電流需求狀態來動態調 201216603 々· l ” -^4864twf.doc/n 電壓轉換裝置所輸出的驅動電 耗，增加能源的使用效率。 減低驅動電流的虛 雖然本發明已以實施例揭露如 本發明，任何所屬技術領域中具有通非用以限定 本發明之精神和範_，t j ’在不脫離 發明之保護範圍當視後附之為;本 【圖式簡單說明】 電容式交流 置200的示 圖1A及圖1B所分別繪示習知的電阻式及 直々IL電壓轉換器110、丨2〇的電路圖。 圖2繪示本發明的一實施例的電壓轉換裝 意圖。In addition, the current detecting circuit 532 in the load state detector 530 includes a comparator CMP sensing resistor R2 and a threshold voltage source v. The sense resistor R2 is connected in series between the first input of the comparator CMP 1 and the output of the current path selector 520. A threshold voltage source v is connected in series between the second input of the comparator CMP1 and the output of the current path selector 52A to provide a threshold voltage. The comparator CMP1 compares the signals received by the two inputs and generates a detection result signal DR at its output. Incidentally, the capacitors 〇 and 〇4 are voltage regulator capacitors. = Please refer to FIG. 6, which shows the embodiment of FIG. 4A of the present invention; The electric power conversion device 6〇0 includes a current path selector 620 detector 630. Unlike the embodiment illustrated in FIG. 5, the capacitive voltage conversion device. In other words, this method can not only be used to provide two different types of drive currents for capacitive electric (four) converters. The voltage conversion device can also be implemented by the equivalent impedance on the second voltage conversion device of the relay device and the two transmission paths to adjust the size. To achieve effective load; 3 sets the driving power of the device and the current demand state of the device to dynamically adjust the driving power consumption of the 201216603 々· l ” -^4864twf.doc/n voltage conversion device to increase the energy efficiency. Having reduced the driving current, although the present invention has been disclosed in the embodiments as a matter of the present invention, it is not intended to limit the spirit and scope of the present invention, and tj' is attached thereto without departing from the scope of the invention. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1A and FIG. 1B are schematic diagrams showing a conventional resistive and direct-turn IL voltage converter 110, FIG. 2B. FIG. 2 is a circuit diagram of the present invention. The voltage conversion of one embodiment is intended.
一立圖3繪示本發明的另一實施例的電壓轉換裝置3㈧ 不意圖。 、J 一圖4Λ繪示本發明的再一實施例的電壓轉換裝置4 的示意圖。 圖4B繪示本發明圖4A繪示的實施例的—實施方弋 圖5繪示本發明圖4A實施例的另一實施方式。 圖6繪示本發明圖4A實施例的再一實施方式。 【主要元件符號說明】 110、 120、200、300、400、500、600 :電壓轉換器An elevational view of Figure 3 illustrates a voltage conversion device 3 (eight) of another embodiment of the present invention. FIG. 4 is a schematic diagram showing a voltage conversion device 4 according to still another embodiment of the present invention. FIG. 4B illustrates an embodiment of the embodiment of FIG. 4A of the present invention. FIG. 5 illustrates another embodiment of the embodiment of FIG. 4A of the present invention. FIG. 6 illustrates still another embodiment of the embodiment of FIG. 4A of the present invention. [Main component symbol description] 110, 120, 200, 300, 400, 500, 600: voltage converter
111、 121 :負載 、Q 210、310、410 :整流器 220、320、420、460、520、620 :電流路徑選擇器 16 201216603 397TW 34864twf.doc/n 230、 330、430、530、630 :負載狀態偵測器 240、340、440 :穩壓電路 250、350、450 :負載裝置 221、222、321、322、421、422、461、462 :電流傳 輸路徑 231、 33卜431 :控制單元 332、432、532、632 :電流偵測電路 CMP1 :比較器 OR1 :或閘 VO :臨界電壓源 DR :偵測結果信號 MR :模式設定結果 ACVIN :交流輸入電壓 DCVIN :直流輸入電壓 PI、P2 :端點 DCVOUT :直流輸出電壓 SEL :選擇信·號 SW1 :選擇開關 MODSET :模式設定信號 C2、C3、C4 :穩壓電容 D1 :二極體 ZD1 :齊納二極體111, 121: load, Q 210, 310, 410: rectifier 220, 320, 420, 460, 520, 620: current path selector 16 201216603 397TW 34864twf.doc / n 230, 330, 430, 530, 630: load status Detectors 240, 340, 440: voltage stabilizing circuits 250, 350, 450: load devices 221, 222, 321, 322, 421, 422, 461, 462: current transmission paths 231, 33 431: control units 332, 432 532, 632: current detection circuit CMP1: comparator OR1: or gate VO: threshold voltage source DR: detection result signal MR: mode setting result ACVIN: AC input voltage DCVIN: DC input voltage PI, P2: endpoint DCVOUT : DC output voltage SEL : Select signal · No. SW1 : Select switch MODSET : Mode setting signal C2 , C3 , C4 : Stabilizing capacitor D1 : Diode ZD1 : Zener diode
Rl、R2、RA :電阻 C1 :電容 LS :負載設定信號 17Rl, R2, RA: Resistor C1: Capacitor LS: Load setting signal 17