TW201212553A - Portable computing device with a SAW-less transceiver - Google Patents

Abstract

A portable computing device includes an FEM, a SAW-less receiver, a SAW-less transmitter, and a baseband processing unit. The FEM isolates one or more outbound RF signals from one or more inbound RF signals. The SAW-less receiver converts the one or more inbound RF signals into one or more inbound intermediate frequency (IF) signals by frequency translating a baseband filter response to an IF filter response and/or an RF filter response. The SAW-less receiver filters the inbound RF signal(s) in accordance with the RF filter response and/or filters the inbound IF signal(s) in accordance with the IF filter response. The SAW-less transceiver then converts the inbound IF signals(s) into inbound symbol stream(s). The SAW-less transmitter converts outbound symbol streams(s) into the outbound RF signal(s). The baseband processing unit converts outbound data into the outbound symbol stream(s) and convert the inbound symbol stream(s) into inbound data.

Description

201212553 VI. Description of the Invention: TECHNICAL FIELD OF THE INVENTION The present invention relates to the field of wireless communications, and more particularly to a wireless transceiver. [Prior Art] Communication systems are known to support wireless and wired communication between wireless and/or wired connected communication devices. These communication systems range from national and/or international beephone systems to the Internet and even to point-to-point home wireless networks. Various types of communication systems can be created separately' and operate in accordance with one or more communication standards. For example, a wireless communication system can operate in accordance with one or more standards including, but not limited to, IEEE 802. 11. Bluetooth, advanced mobile phone service (personal Mps), digital AMPS, Global System for Mobile Communications (GSm), Code Division Multiple Access (CDMa), Local Multipoint Distributed System (LMDS), Multi-channel Multi-point Decentralized System ( MMDS), Radio Frequency Identification (RFE), Enhanced Packet Radio Communications (EDGE), General Packet Radio Service (GPRS), WCDMA, Long Term Evolution (LTE), Worldwide Interoperability for Microwave Access (WiMAX), and/or variations thereof. Depending on the type of wireless communication system, wireless communication devices (such as cellular phones, two-way radios, personal digital assistants (PDAs), personal computers, laptops, home entertainment devices, RpID card readers, ie, 1-inch tags, etc.) communicate with other wireless devices. The device communicates directly or indirectly. For direct communication (also known as peer-to-peer communication), the participating recordings will transfer their receivers and transmitters to the same channel (for example, wireless communication systems, multiple RF commands) = some systems Specific RF frequencies) and communicate through these channels. For indirect = line communication 'Every wireless communication device and associated base station (for example, for bee-off service, 4 201212553 to communicate and/or pass points to mines and side-point points (such as hiding in the home or in the building) _路) Straight letter. In order to complete the communication link of the no-faceted miscellaneous room, 'the relevant base station and/or related access point through the system controller, through the public switched telephone network, through the Internet and/or through - others The wide area network is mutually independent for each wireless communication device participating in wireless communication, including a built-in radio transceiver (ie, receiver and transmitter) or connected to an associated radio transceiver (eg, for home and/or intra-building wireless communication networks (10) Base station, data modem, etc.) The receiver is known to be connected to the antenna and includes a low noise amplifier, one or more intermediate frequency stages, a filtering stage, and a data recovery stage. The low noise amplifier receives the human station RF through the antenna.彳5 then zoom in. One or more towel frequency levels mix the amplified RF signal with one or more local oscillations to convert the amplified shrimp signal to ribbon or towel _ number. A signal or intermediate frequency signal is used to attenuate unwanted out-of-band money, thereby generating money for the wave reduction. The data recovery stage recovers the data in the filtered signal according to a particular wireless communication standard. The known transmitter includes a data modulation level, one or A plurality of intermediate frequency stages and a power amplifier. The f-modulation stage converts the body into a baseband signal according to the mosquito-free signal. One or more intermediate frequency stages mix the baseband signal with one or more local oscillations to generate an RF signal. The amplifier amplifies the signal and then transmits it through the antenna. To implement the radio transceiver, the wireless communication device includes a plurality of integrated circuits and a plurality of discrete components. Figure 1 illustrates a wireless communication device supporting 2G and 3G cellular telephone protocols. As an example, as shown, the wireless communication device includes a baseband processing 1C, a power management 1C, a radio transceiver IC, a transmit/receive (T/R) 201212553, an antenna, and a plurality of discrete trees. The discrete components include surface acoustic waves. Eagle), power amplifier, dual I, inductor and capacitor. These separate tillages increase the cost of material inspection (4), but it is not necessary to achieve the precise performance requirements of the 2G and 3G agreements. With the development of integrated circuit technology, wireless communication device manufacturers hope that wireless transceiver 1C manufacturers will update their 1C according to the progress of IC system. For example, changes in the manufacturing process (such as the use of smaller transistor models) are aimed at the new design of the four-chip IC. Because of the large-scale digital digital series, the 1C manufacturing 1 art touches the secret, and the IC digital part is re-four-one relatively simple process. However, since most analog circuits (such as inductors, materials) do not shrink with the Ic process, the redesign of the analog part is not a simple task. As a result, wireless transceiver IC manufacturers have put a lot of effort into producing ICs that use the updated Ic manufacturing process. SUMMARY OF THE INVENTION The present invention is provided with a device and a method of operation, and further description is provided in the following description of the drawings and the specific embodiments and claims. According to an aspect of the present invention, a portable computing device is provided, comprising: a front end module 'for connecting to an antenna portion and for separating one or more out from one or more inbound radio frequency signals Station RF signal; a surfaceless acoustic wave (less-SAW) receiver for: converting the one or more inbound RF signals into one or more inbound IF signals by: Responding to at least one of an intermediate frequency filter response and a 201212553 frequency filter response; when the base wave n is responsive to the RF filter response, according to the RF device response, the one or more An inbound radio frequency signal; and filtering the one or more inbound intermediate frequency signals according to the intermediate frequency filter response when the baseband filter responds to the intermediate frequency filter response; and Or converting multiple inbound IF signals into one or more inbound symbol streams; no surface acoustic wave transmitter for converting one or more outbound symbol streams into the one or more outbound RFs Number; and a baseband processing unit, configured to: convert outbound negative material of the one or more outbound symbol stream; and the one or more inbound symbol stream into inbound data. Preferably, the portable computing device further includes: the front end module further configured to separate one or more second outbound radio frequency signals from the one or more second inbound radio frequency signals, wherein the one Or a plurality of inbound and outbound radio frequency signals are located in a first frequency band, and the one or more second inbound radio frequency signals are located in a second frequency band; the surface acoustic wave receiver is further configured to: Converting the plurality of second inbound radio frequency signals into one or more second inbound intermediate frequency signals, wherein: converting the second baseband filter response to at least one of a second intermediate frequency filter response and a second RF filter response 201212553 when the second baseband II is responsive to the second radio frequency filter, the second radio frequency signal is filtered according to the second radio frequency; and the second Baseband filter response frequency conversion for said second intermediate frequency filter response according to said second middle waver response, said one or more second person station intermediate frequency signals; and said one or more The second person station IF signal is converted into one Or a second inbound symbol stream; the surfaceless acoustic wave transmitter is further configured to convert the one or more (four) two outbound symbol streams into the one or more second outbound radio frequency signals; and the baseband processing unit Also for: converting the second outbound data to the one or more second outbound symbol streams; and converting the one or more second inbound symbol streams to the second inbound material. Preferably, the front end module comprises: an antenna tuning unit coupled to the antenna portion and tuned for providing an impedance matching the impedance of the antenna portion; one or more power amplifiers for amplifying the Decoding one or more outbound radio frequency signals to generate one or more amplified outbound radio frequency signals; a separation module coupled to the surfaceless wave receiver, the antenna tuning unit, and the one or more power amplifiers The separation module is configured to: output the one or more amplified outbound radio frequency signals to the antenna tuning unit; and 8 201212553 attenuate in the connection between the separation module and the surfaceless wave receiver The one or more amplified outbound radio frequency signals thereby separating the one or more inbound radio frequency signals from the one or more outbound radio frequency signals. Preferably, the baseband processing unit is further configured to generate at least one of: an antenna tuning unit control signal for impedance of the antenna tuning unit according to an impedance variation of the antenna portion; separating a control signal for adjusting Attenuation of the one or more outbound Rp signals; and power amplifier control signal 'for adjusting one or more parameters of the one or more power amplifiers. Preferably, the surface-free wave transmitter comprises: an up-conversion mixing module, configured to convert the one or more outbound symbol streams into one or more up-converted signals; and transmit a variable-frequency band-pass filter And for: converting the second baseband filter response to a second RF bandpass filter response; and filtering the one or more upconverted signals according to the second RF bandpass filter response to generate one or more a filtered upconverted signal; and an output module 'for adjusting the one or more filtered upconverted signals to produce one or more adjusted upconverted signals; and a power amplifier driver for amplifying The one or more adjusted upset cheeks to generate the one or more outbound radio frequency signals. 201212553 Preferably, the baseband processing unit is further configured to: generate a transmitter control signal, where the transmitter control signal is used to adjust at least one of: the second baseband filter response, the second radio frequency bandpass filtering The device responds with parameters of the power amplifier driver. Preferably the 'surfaceless wave receiver' comprises: a radio frequency-intermediate frequency receiver section comprising: a low noise amplifier for amplifying the one or more inbound radio frequency signals to generate one or more amplified inbound stations a radio frequency signal; an intermediate frequency down conversion module for converting the one or more amplified inbound radio frequency numbers into the one or more inbound intermediate frequency signals; and having the radio frequency band pass filter response a variable frequency band pass filter for filtering the one or more inbound radio frequency signals or filtering the one or more inbound intermediate frequency signals; and an intermediate frequency-baseband receiver portion for using the one or more The inbound IF signals are converted to one or more inbound symbol streams. Preferably, the baseband processing unit is further configured to: generate a receiver control signal, where the receiver control signal is used to adjust at least one of the following. The baseband filter responds, the RF bandpass filter responds to, and the parameters of the low noise amplifier. Preferably, the portable computing device further includes: a first integrated circuit for supporting the baseband processing unit, the surfaceless wave receiver and the surfaceless wave transmitter; and a second integrated circuit For supporting the front end module. Preferably, the portable computing device further includes at least one of the following: 10 201212553 processing module, configured to: execute one or more portable computing materials; and work to generate the outbound function processing Performing the one or more portable computing input data; and setting one or more power management units 'for performing the portable computing to install a power management function. According to another aspect, a portable computing device is provided, including: a front end module, wherein the front end module includes: a power amplifier, wherein a power amplifier of the plurality of power amplifiers amplifies a plurality of outbound RF signals a first-outlet RF signal of the towel; a plurality of separate modules, wherein the separation module of the plurality of separation modules separates the first of the plurality of inbound RF signals from the first outbound RF signal a station radio frequency signal; and at least one antenna tuning unit for providing an impedance matching the impedance of the antenna portion according to the control signal, wherein the antenna tuning unit receives the first inbound radio frequency signal from the antenna portion, and The antenna portion outputs the first outbound radio frequency signal; a surface acoustic wave receiver for converting the plurality of inbound radio frequency signals into a plurality of inbound symbol streams; no surface acoustic wave transmitter for more Converting the outbound symbol stream into the plurality of outbound radio frequency signals; and baseband processing unit, configured to: generate the control signal according to the impedance change of the antenna portion; 201212553 a plurality of outbound (four) converting the extracted outbound symbol streams; and converting the plurality of inbound symbol streams into a plurality of inbound data. Preferably, the portable computing device further comprises: a second power amplifier of the plurality of power amplifiers amplifying a second outbound radio frequency signal of the plurality of outbound radio frequency signals, wherein the first outbound station is located at In the frequency band, the second outbound station number is located in the second frequency band. The second split mode of the plurality of split cells - the second outbound radio frequency signal separates the second person station radio frequency signal of the plurality of human station radio frequency signals.  a band switcher connected to the antenna portion and the at least one antenna tone spectrum; and the second antenna antenna unit of the at least one antenna tuning unit for providing impedance to the antenna portion according to the second control signal The second antenna element receives the first-person station radio frequency signal through the band switch, and outputs the second out-end radio frequency signal to the line unit through the fresh switch. Preferably, the separation module is further configured to: output the first-outbound number to the at least one day-of-the-cell; and, in the face-to-face group, describe a continuous wave of the surface wave receiver The first-out station shoots the number so as to separate the first-person station radio frequency from the outbound radio frequency signal. Preferably, the portable computing device further comprises: the baseband processing module generating a separation control signal; and the sub-group adjusting the attenuation of the outbound radio frequency signal. 201212553 Preferably, the surfaceless wave transmitter comprises: an upconversion mixing module for converting the one or more outbound symbol streams into one or more upconverted signals; transmitting a variable frequency bandpass filter, For: converting a second baseband filter response to a second RF bandpass filter response; and filtering the one or more upconverted signals according to the second RF bandpass filter response to generate one or more filters And an output module for conditioning the one or more filtered upconverted signals to generate one or more adjusted upconverted signals; and a power amplifier driver for amplifying the one Or a plurality of adjusted upconverting # numbers to generate the one or more outbound radio frequency signals. Preferably, the baseband processing unit is further configured to: generate a transmitter control signal, the transmitter control signal for adjusting at least one of: the second base; f filter response, the second radio frequency bandpass The filter responds with the parameters of the power amplifier driver. Preferably, the surface waveless receiver comprises:  The RF-IF receiver section includes: a low noise amplifier section 'for amplifying the plurality of inbound radio frequency signals to generate a plurality of amplified inbound radio frequency signals; an intermediate frequency down conversion module 'for Converting a plurality of amplified inbound radio frequency signals into a plurality of inbound intermediate frequency signals; and a variable frequency band pass filter having the RF band pass filter response, filtering the plurality of inbound radio frequency signals or filtering with 13 201212553 The plurality of inbound intermediate frequency signals; and the intermediate frequency-baseband receiver portion 'for converting the plurality of inbound intermediate frequency signals into a plurality of inbound symbol streams. Preferably, the baseband processing unit is further configured to: generate a receiver control signal, where the receiver control signal is used to adjust at least the following: the baseband chopper response, the radio frequency bandpass chopper response, and The parameters of the low noise amplifier. Preferably, the portable computing device further comprises: =-integrated circuit 'for supporting the first baseband processing unit, the surfaceless wave receiver and the surfaceless wave transmitter; and a second product a body circuit for supporting the front end module. The portable computing device further includes at least one of the following: a processing module, configured to: data execution and one or more portable computing device functions to generate the outbound input The plurality of portable computing device functions process the power management unit for a power management function. Details of the various advantages of one or more of the present inventions for binding the portable computing device will be made in the following (d) daily rectification aspects and innovative features, as well as specific embodiments [embodiments] 5 and _ Detailed introduction. Figure 2疋 is a schematic block diagram of the real-time connection of the portable 4 arithmetic and miscellaneous 1G of the system-on-chip (soc) 12 and the front-end module (job) 201212553, the towel s〇cl2 ^ΡΈΜ 14 in a separate integrated circuit Implemented on. The portable computing communication device 1 can carry any device that can be carried by an individual, at least partially powered by a battery, including a radio transceiver H (eg, radio frequency and/or meter wave (should perform one or two soft details. For example) The portable computing communication device 1G can be a cellular, portable!: &, personal number_hand, video gamer, video game player, personal entertainment unit, desktop computer, etc. SOC12 includes no surface acoustic wave (four) 18. A surface acoustic wave transmitter unit 2, a baseband processing unit 22, a processing module 24 and a power management unit 26. The surface acoustic wave receiver 18 includes a receiver (RX) radio frequency (RF)-intermediate frequency (IF) «Ρ 28 and receiver (10)) IF_baseband (10)) section 3〇. The shape _ positive % also includes one or more variable frequency band pass filters (FTBpF) 32. The processing module 24 and the wire material a can be a single mineral processing device, a sub-processing device or a plurality of processing devices. The processing device can be a microprocessor, a microcontroller, a digital signal processor, a microcomputer, a central processing unit, a field programmable gate array, a heterogeneous logic device, a state machine, a logic circuit, an analog circuit, a digital bit path, and/or A device that processes hard signals and/or wires to process signals (analog and/or digits). The processing template address 24 and/or the baseband processing unit το 22 may have associated memory and/or memory elements, which may be a single recording device, a home device, and/or a processing device. Module 24 is a human-like circuit. The slimming memory, random access memory, volatile memory, non-volatile memory, static memory, dynamic memory, flash memory, cache memory and / Or ^ Any device that stores digital information 4 If you want to process the data or baseband processing single 15 201212553 More: processing equipment, these processing equipment can be arranged centrally (for example, the line bus is directly connected together) or distributed arrangement ( For example, an indirect connection between a left-hand local area network and/or a wide area network (for cloud computing). Further, when the module 24 and/or the baseband processing unit 22 perform its function or functions through a state machine, a class, a bit t-plane, or a logic circuit, the memory and/or memory of the corresponding operation instruction is stored. The memory component can be embedded or externally connected to the circuit including the state machine, the analog circuit, the digital circuit and/or the logic circuit. 2. It should be noted that the memory storage is stored, and the processing module 24 or the baseband processing unit 7L 22 is executed. At least - at least some steps and/or functionally related hard code and/or operational instructions as indicated by the towel. Front End Module (FEM) 14 includes multiple power amplifiers (PA) 34-36, multiple receiver-transmitter (κχ·τχ) separation modules 3, multiple antenna modulation units (ATU) 42-44 And Band_Switch#. Note that the f job* can enclose two paths Pas 34_36 (the camera group 38_4 〇 and the ATU 42·44 are connected to the FB switch 46) or can include a single path. For example, the FEMM may include one path for 2G (second generation) cellular services, - a path for 3G (third generation) cellular services, and a third path for wireless local area network (WLAN) services. Of course, there are many other exemplary path combinations in FEM 14 to support one wireless communication standard (such as IEEE 802. Il, Bluetooth, Global System for Mobile Communications (GSM), Code Division Multiple Access (CDMA), Radio Frequency Identification (RFID), Enhanced Packet Radio Communications (EDGE), General Packet Radio Service (GPRS), WCDMA, High Speed Downlink Packet Incoming (HSDPA), High Speed Uplink Packet Access (HsupA), Long Term Evolution (LTE), WiMAX (Worldwide Interoperability for Microwave Access) and/or variants thereof. 201212553 - In the example of the application, the processing module 24 executes a shirt that requires wireless transmission of data. At this time, the processing module 24 provides the source material (such as voice, text, audio, video, _, etc.) to the baseband processing unit or module 22, and the baseband processing unit or module 22 according to one or more wireless communications. Standards (eg GSM, CDMA, wcdma, _A, hsdpa, WiMAX, EDGE, GPRS, U, Bluetooth Zombie, Universal Mobile Telecommunications, UMTS, Long Term Evolution (LTE), Dirty 8〇2. 16. Capital 2 optimization improvement (EV_D0), etc.) converts outbound (4) into one or more outbound symbol streams. This transformation includes at least the following items: scrambling, puncturing, coding, interleaving, constellation mapping, modulation, spreading, frequency hopping, beamforming, space-time block coding, space-frequency block coding, frequency domain·time Domain conversion and / or digital baseband · IF conversion. Note that the baseband processing unit converts the outbound data into a single stream of simple numbers to achieve single-input single-output (10) (1) communication and/or multiple-input single-output (MSO) communication, and converts outbound data into multiple Outbound symbol stream 'to achieve single-input multiple-output (SIM〇) and multiple-input multiple-output (ΜΙΜΟ) communication. The baseband processing unit το 22 provides the one or known outbound symbol stream to the surfaceless acoustic wave generating portion 2G, and the surface acoustic wave transmitter portion 2() converts the outbound symbol stream into one or more Station RF signals (eg, signals in one or more frequency bands 800 MHz, 1800 MHz, 19 〇〇 MHz, 2 〇〇〇 MHz, 2 4 Gfc, 5 GHz, 60 GHz, etc.). The surface acoustic wave transmitter section 2 includes a >, an up-conversion module, at least one variable frequency bandpass chopper (FTBpF), and an output module; it can be configured as a direct conversion topology (eg, baseband or near baseband symbols) The direct conversion to the RF signal is either a superheteron dyne (201212553 topology) (eg converting a baseband or near baseband symbol stream to a positive signal and then converting the IF signal to an RF signal). For direct conversion, the surface acoustic wave transmitter section 2 can have a Cartesian-based topology, a polarization-based topology, or a hybrid polarization-Cartesian-based topology. In a Cartesian-based topology, the surface acoustic wave transmitter portion 2 同 combines the in-phase and quadrature components of the or each outbound symbol stream (eg, A^cos^bb(1)+Φ丨(9) and AQ(t, respectively) )cos((〇BB(t)+~t)))) is in-phase and quadrature components of one or more lx-radio local oscillations (TX L0) (eg c〇S(〇)RF(t), respectively) And (yes) good (〇) mix to produce a mixed signal. The FTBPF chops the mixed signal, and the output module adjusts (eg, common mode filtering and/or differential to single-ended) to produce one or more output upconverted signals (eg, A(1)cos((〇BB(1)) +〇(t)+ 〇)RF(t))). A power amplifier driver (PAD) module amplifies the outbound upconverted signal to produce a pre-power amplified (pre-PA) outbound RF signal. In a phase polarization based topology, the surfaceless acoustic wave transmitter section 2 includes an oscillation for generating an outbound symbol stream (eg, based on phase information (+/_Δφ[phase shift] and/or Φ(ΐ) [phase modulation] The oscillator that performs the adjustment (7) as the rape (1))). The resulting adjusted oscillations (eg, (10) plus (1) + / _ Λ Φ) or c 〇 s (( 〇 RF (t) ten (9)) can be further derived from the amplitude information of the outbound symbol stream (eg Α (〇 [amplitude modulation]) To adjust to produce one or more upconverted signals (eg AWc〇s(c〇RF(t) +/- ΔΦ) or A(1) coffee(9)叮(1)+Φ(9)). FTBPF filters one or more upconverted signals And the output module conditions (such as common mode filtering and / or differential single-ended conversion). The power amplifier driver (PAD) module amplifies the outbound upconverted signal to generate the pre-power amplified outbound RJ7 signal. 201212553 In a frequency polarization based topology, the surface acoustic wave transmitter portion 20 includes an oscillation for generating an outbound symbol stream (eg, based on frequency information (eg, +/_Δcognition) and/or f(t) [frequency modulation] Perform an adjusted c〇s(_(t))) oscillator. Obtain the adjusted oscillations (eg c〇s(c〇RF(t:) +/_ from or +f_ can be further flowed by the outbound symbol) Amplitude information (such as A (1) [amplitude modulation]) to adjust, To generate a signal that is converted to one or more rainbows (eg, (10) (1) +/- Δί) or Α〇〇 3 (ω κ Ρ ω + f (1)). The FTBPF filters one or more upconverted signals, and the output modules adjust (c〇nditi〇n) (e.g., common mode and/or differential single-ended conversion). The power amplifier driver (pAD) module amplifies the outbound upconverted signal to produce an outbound signal that is preamplified by power. In a hybrid polarization-Cartesian based topology, the surface acoustic wave transmitter portion 20 will phase information of the outbound pay stream (e.g., ε 〇 3 (ω ΒΒ (1) Δ φ) or C 〇 S ((DBB(t) + (I&gt) (t))) and amplitude information (e.g., eight (1)) are separated. The surface acoustic wave transmitter portion 20 combines the in-phase and quadrature components of the one or more outbound symbol streams (e.g., cos(a) BB, respectively). (t) + 〇 ^ t)) and (7) Laqiu (1) + 〇 Q (t))) and one or more transmitter local oscillations (TXL0) in-phase and quadrature components (for example, cos^aKt) As good as (1))) mixing to generate a mixed signal qFtbpf to filter the mixed signal, and the output module adjusts (c〇nditi〇n) (such as common mode filtering and/or differential single-ended conversion) to generate one or more An outbound upconverter # (eg Α(〇α>5(ωΒΒ(ί)+Φ〇ωκρ(ΐ))). The power amplifier driver (PAD) module amplifies the standardized outbound upconverted signal and amplitude information (eg, A(t)) injects a normalized outbound upconverted signal to produce a pre-power amplified (pre-PA) outbound RF signal (eg, a(1) Cagahong (1) Query (9). No Surface Acoustic Wave Transmitter Other examples of section 20 will be described with reference to Figures 23 and 24. 201212553 For superheterodyne topology, the surface acoustic wave transmitter section 20 includes a baseband (BB) intermediate frequency (IF) section and an IF-radio frequency (RF) section. BB_IF section偏振 Polarization-based topology, Cartesian-based topology, hybrid polarization-Cartesian-based topology, or hybrid stage of upconverting outbound symbol streams. In the first three examples, the bb_if section generates an IF domain (eg A(t) C〇s((〇IF(t)+a>(9)),: [F-rf part includes mixing stage, filter stage and power amplifier driver (pad) to generate pre-power amplification station RF signal. When BB-IF part Including the mixing stage, the positive-segment can have a polarization-based topology, a Cartesian-based topology or a hybrid polarization-Cartesian-based topology. In this case, the BB_IF section will have an outbound symbol stream (eg A〇S«) a > BB(t) + a > (t))) is converted into an IF symbol stream (for example, A_S(〇)IF_>(9)). The IF_Rp IF IF is a pre-power amplified outbound RF signal. The H-port 2G is transmitted to the power amplifier module (PA) 34·36 of the front-end module (FEM) 14 to output the pre-power amplified outbound RF. No. PA 34-36 includes one or more power amplifiers connected in series and/or in parallel with amplified pre-power amplified shrimp signals to generate an outbound signal. Note that parameters of pA 34-36 (eg gain, Linearity, bandwidth, efficiency, noise, output dynamic range, slew rate, rise rate, settling time, overshoot, stability factor, etc. can be received from baseband processing unit / and/or processing module % Control (4) to adjust. For example, the processing source of the SOC 12 (eg, the processing unit 22 and/or the processing module 24) monitors changes in transmission conditions due to changes in transmission conditions (eg, corresponding channel changes, distance changes between TX units and RX units, changes in antenna properties, etc.). And adjust the properties of PA 34_36 to optimize performance. It is true that 201212553 is not made independently; for example, it can be made according to other parameters of the front-end module that can be adjusted (such as ATU42-44, Rx-τχ separation module 38_4〇) to optimize the emission of RF signals and receive. The TX knife attenuates the outbound RP signal from the module 38-40 (which may be a duplexer, a CKcuiator or a transformer balun or other separate means for providing a TX signal and an RX signal using a shared antenna). The TX-TX separation module 38_4 can adjust the attenuation of the signal at the outbound according to the control received from the baseband processing unit and/or processing mode, group 24 of the SOC 12. For example, when the transmit power is relatively low, the RX_TX split module 38_4 can be adjusted to reduce its attenuation of the τχ signal. The antenna tuning unit (ATU) 42_44 is tuned to provide the desired impedance that is substantially matched to the antenna 16. After tuning, the ATU 42_44 provides the attenuated τχ signal from the sigma-τ χ = module 38-40 to the day and line 16 贱 emissions. /Thinking, the ATU 42-44 can be adjusted continuously or periodically to track the impedance of the antenna 16. For example, baseband processing unit 22 and/or processing mode 'group % can detect changes in impedance of antenna 16 and provide control signals to ATUs 42-44 based on the detected changes, causing them to change their impedance accordingly. In the 3H example, the 'surfaceless acoustic wave transmitter section 2' has two outputs: one is the first - the other is the second. The above discussion is concerned with the conversion process of outbound data from the outbound data to a single frequency band (eg 850ΜΗζ, 900ΜΗΖ, etc.). The process and outbound data to other frequency bands (eg 1800MHz ^ 1900MHz ^ 2100MHz > 2. 4GHz '5GHz#) Rp signal conversion When she makes an antenna 16th, no surface acoustic wave transmitter 2〇 generates an outbound RJF signal in other frequency bands after other bands. The frequency band (FB) of the FEM14 201212553 switches n % to connect the antenna μ to the appropriate output of the wire-to-sound ejector wheeling path. The FB switch 46 receives control information from the baseband processing unit 22 and/or the processing module 24 for selecting a path to connect to the antenna 16. Antenna 16 also receives one or more inbound signals, and provides them to one of ATUs 42-44 via a frequency band (FB) switch 46. The ATU 22-24 provides the inbound signal to the RX-TX split module 38-40, which routes the signal to the receiver (rx) Rp_IF portion of the SOC 12. The RX RF-IF section 28 converts the inbound RF signal (eg A(t)cos(aDRF(t)+a)(9)) into an inbound IF signal (eg gossip (10) (4) (8) + less) and AQ(t)COS ((〇IF(1)+φρ(9)). Various embodiments of the rx rf_if portion 28 will be illustrated in Figures 15-23 or other figures. The RX IF_BB portion 30 converts the inbound IF signal into one or more inbound symbol streams (e.g. A(t)cos(G)BB(t)+0>(9)). At this time, the 'rxif-bb unit 30 includes a mixing unit and a combination & filter unit. The mixing unit will inbound IF signal and second local oscillation. (For example, L02=IF-BB 'where BB can range from zero to several mhz) to mix to generate I and Q mixing signals. Combining & filtering is combined (for example, adding mixed signals together - including sum The component and the differential component are then filtered to substantially attenuate the sum component and pass the substantially un-attenuated differential component as an inbound symbol stream. The baseband processing unit 22 is based on one or more wireless communication standards (eg, GSM, CDMA) , WCDMA, HSUPA, HSDPA, WiMAX, EDGE, GPRS, IEEE802. 11, Bluetooth, ZigBee, Universal Mobile Telecommunications System (), Long Term Evolution (LTE), IEEE 802. 16. Data optimization improvement (ev_d〇), etc.) Convert inbound symbol streams into inbound data (eg voice, text, audio, video, 22 201212553 graphics, etc.). Such conversion may include at least the following items: digital intermediate frequency _ baseband conversion, time domain-frequency domain conversion, space-time packet decoding, space-frequency packet decoding, demodulation, spread spectrum decoding, frequency hopping decoding, beamforming decoding. , constellation de-mapping, de-interlacing, decoding, de-puncturing, and/or descrambling. Note that the processing module 24 converts a single inbound symbol stream into a human station (4), a single-investment single-lion (s shame) communication and/or a multi-input single-willow (MISQ) job, and the township personal facet is converted into an inbound station. Data to achieve single input multiple output (8 fine) and multiple input multiple output (ΜΙΜΟ) communication. Power Management Unit% City in the SGC U towel tons of various functions. These features include monitoring power connections and battery charging, charging the battery when necessary, controlling power to other components of the SOC 12, generating power supplies, touching unnecessary SOC modules, controlling the sleep mode of the SOC module, and/or providing an instant clock. . In order to facilitate the generation of the power supply voltage, the power management unit % may include one or more switching mode power supplies and/or one or more linear regulators. With this portable computing communication device, expensive and discrete off-chip components (such as ϋ, duplexers, domains, and/or capacitors) can be eliminated and their Wei can be included on a single die. Really depends on the front-end mode & (_) 14 in. In addition, the SAW-free receiver unit facilitates the elimination of discrete off-chip components. 3 is a schematic block diagram of a portable computing communication device 10 including a system on a chip (soc) 52 and a further example (FEM) 50 in accordance with another embodiment of the present invention. The SOC 52 includes an electrical unit 26, a (10) receiver unit I8, a no-transmitting unit 2, a baseband processing unit, 23 201212553 to include a processing module. The FEM 50 includes a plurality of power amplification sets (pA) % 36, a plurality of κ χ τ χ separation modules 38_4 〇, and at least one antenna tone modulation unit (ATU) 54. In the present embodiment, the SOC 52 is used to simultaneously support at least two types of wireless communication (e.g., bee call and WLAN communication and/or babble communication). Thus, the no SAW transmitter 2 generates two (or more) outbound chirp signals of different frequency bands in the manner described with reference to Figure 2 and/or with reference to one or more of the following figures. The first of these different frequency outbound RP signals can be provided to the PAs 34-36 of the ρΕΜ5〇, and the other outbound signals are provided to the other PA 34-36. The function of each of the TX-RX separation modules 38_4 is as described with reference to Figure 2 and will be described with reference to at least one of the following figures. The ATU 54 tuned according to the control signal from the SOC 52 provides the antenna 16 with two outbound signals for transmission. Antenna 16 also receives inbound RF signals of two or more different frequency bands and provides them to ATU 54. The ATU 54 may include a splitter for separating the two inbound RF signals and separating the impedance matching circuits (eg, one or more LC circuits) of each of the separated signals; for separating the signals and separating the impedance matching circuits A balun transformer; or an impedance matching circuit for both signals, wherein the two signals are provided to the RX-TX separation module 38-40.

The RX-TX split modules 38-40 rely on respective frequency bands, respectively, which only pass inbound and outbound RF signals within respective frequency bands (e.g., 850-900_2 and 1800-1900 MHz). Therefore, the 'first TX_RX separation module 38_4〇 provides the first frequency band inbound RF signal to the first input of the no SAW RX unit 18, and the second TX_RX separation module 38_4 provides the second frequency band inbound signal to the no SAW 24 201212553: The second loser of 18. The non-oriented section 18 processes the inbound RFb tiger according to the material at least the data to generate the first inbound data and the second station data.

Figure 2 is a portable computing communication device, in accordance with another embodiment of the present invention, which includes an on-chip secret (9) C) 12 or 52 connected to a front-end module (4) network 6 through an RF connection 70. The S〇c 12 or power management unit 26, the no SAW reception||part 18, and the no SAW baseband processing unit 22 may further include a processing module. That is, the connection 1 = 〇 is: a shaft gauge, an elastic fiber cable, an elastic waveguide, and/or other high frequency electric windings. The FEM network 6G includes a plurality of FEMs 62_68 (eg, two or more) 'where each of the FEMs 62-68 includes a plurality of power amplifier modules (PAs), a plurality of rx_tx split modules, and at least _ antennas The spectroscopy unit (Απ) and the band switcher (SW). The structure of at least one of the FEM 62_68 is as described with reference to FIG. Each of the FEMs 62-68+ may support the same frequency band, different frequency bands, or a combination thereof, respectively. For example, two FEMs can support the same passband (eg 850-900 dirty 2 and 180 (M900MHz), while the other two can support different frequency bands (eg 2.4 GHz, 5 GHz, 60 GHz, etc.). In this case, s〇 c 12 or 52 may be based on at least one of a plurality of RF communication parameters (eg, transmit power level, received signal strength, out-of-band block, signal to noise ratio, signal to interference ratio, operating frequency, interference with other wireless communications, etc.) Select one of the FEMs 62-68 with the same frequency band. For example, the SOC 12 or 52 selects the FEM that provides the best performance level of cellular communication and the WLAN, personal area network, or other wireless that provides the best performance at present. Another FEM for network communication. 25 201212553 Since each of the FEM 62-68 is programmable, s〇c 12 or & can program the selected modules to reduce mutual interference. For example, The FEM supporting cellular communication can be woven to have additional attenuation in rogue communication (eg, 2.4 GHz, 5 GHz, 6 GGHz, etc.). In addition, with conditions (eg, interference, transmit-receive distance, antenna parameters, environmental factors, etc.) The change, the SOC 12 or 52 can adjust the parameters of the selected FEM to substantially compensate for the change. Alternatively, the SOC 12 or 52 can select another FEM to perform at least one of the two communications. The SOC 12 or 52 can select multiple FEMs. 62-68 to support ΜΙΜΟ communication, SIMO communication and/or MS0 communication. For example, in 2*2ΜΙΜ〇 communication, one FEM can be selected for one τχ/κχ ΜΙΜ〇 communication, and another FEM for another tx/rx SOC Communication SOC 12 or 52 may also select one FEM to support transmissions in one frequency band and another FEM to support reception in the same frequency band. For example, SOC 12 or 52 may select the first FEM to support 1800 MHz cellular phones. The first FEM is transmitted and supported by the 1800 MHz cellular phone. For example, the s〇c 12 or 52 can select the first FEM to support the 1800 MHz cellular phone transmission, the second FEM to support the 900 MHz cellular phone transmission, and the third FEM to support the 1800 MHz cellular. Telephone reception, and fourth FEM to support 900MHz cellular phone reception. For another example, SOC 12 or 52 can select the first FEM to support 1800MHz cellular phone transmission, FEM supports 900MHz cellular phone transmission, and the second FEM supports 1800MHz cellular phone reception, and the first FEM supports 900MHZ cellular phone reception. FEM network 60 can be implemented on a single die on a single package substrate 26 201212553 Implemented on multiple dies on a single substrate (eg, each brain on a die) as a separate integrated circuit (5). At least one of the FEMs 62-68 in the rear clearance v may be away from s〇c 12 or %. For example, 'portable computer computing can be sighed to support the wireless femtocell station (f_eell), which is a bit of a miscellaneous material. At least, it is physically distanced from the SOC 12 or 52 - segment distance (for example, greater than i meters). ). In addition, one of the FEMs can be used to communicate with the base station while one or more other FEMs can be used to communicate with other wireless communication (e.g., bee write). For example, the device ίο communicates with a base station (BS) using conventional cellular services, while the device uses a different frequency band with the coffee links of other scale communication devices. The processing module coordinates the signal conversion of other devices _ network and / or cellular access and various keys. For another example, the device 10 is used as a wireless femto-based read for M bees or other handheld devices. A mounted wireless local area link can be compliant with one or more aspects. - Nading is said to be _ quasi (for example, a wireless milliplane-like base station like a BS-like distribution local area radio link). Another protocol enables wireless femtocell station devices to be extended as user interfaces on the Internet Protocol (Ip) channel. The handset's - link is connected to the access point (AP), the _ handcraft is tied to its wire-shaped fine grid, and logically connected to the AP from (4) in other ways. 'For example, the device 10 acts as a wireless femtocell base station (for example, it uses a data call to the beer calling system to wirelessly connect, thereby providing an IP channel to the Internet, which logically connects the AP to the Internet) An application word processor anywhere on the road. For example, the carrier does not have to provide a voice call for the voice call system. 201212553 "The IP channel passes through the Ap to connect the Internet telephony client in the domain to the Internet telephony network. The load and valley 1 of the carrier's data channel determines the number of active handsets supported by the AP. In this example, the link from the AP to the supported wireless device is not in the cellular band' but instead is written using a traditional bee. Standard (ie, the AP is similar to the BS, and the AP performs the converter function when the mobile client is running on the supported wireless device.) The link between the wearer 10 and the supported wireless device is not a write standard. Proprietary-series call step. At this time, the AP runs the device client and the device is a hash extension on the 1p channel. The nano+ device 1G describes itself as Wei. The station of the device. At this time, the device 10 determines whether it satisfies the signal that the quality is not used for the carrier to ride, has better battery life, bit (four) call, etc. If so, then its carrier is registered as a given geographical location. In the femtocell base station. The smart way (60GHz, TVW9 t book will be written by point-to-point wireless such as bee). For its device to the device 'device device (such as carrier (such as they transmit information) strong The BS of the second-line device's carrier is strong. For the mother carrier (for example, the wireless device with weak or no weight, device K), the femtocell base station of the line device actively becomes 10 Become your own femto bee t ... line device wants to shock yourself as a wireless device: micro bee micro high bee =: use, set the dynamic process basis between devices; ^ use. Note that this can be a few picocellular base station APs. If _^ is the other device's milli, ., „ condition change, the other F罟 is from the femto bee that becomes the device, and the bee-high base station AP, and writes as the femto bee 28 201212553 base station The device of the AP becomes a new femto-bee-type base station. For example, a plurality of devices can be combined to form a femto-netw. At this time, the device is used as a relay station for one or more joys. The device is connected to the device as a wireless femto-bee-type base station A/, and the device is used as the host of the device, and they are linked to provide a connection. This is a wireless one. The pico-satellite base station device provides a bee whisper; the connection 'the other provides a cellular data connection, and the third provides a muscle touch connection. For another example, the multiple is placed in the dense field (for example, in a bridge, Determine which device will act as its wireless, picocell base station AP and which services are provided. For example, Jianshe establishes a point-to-point link (60GHz, TVWS, 9dru, 1V, 2.4GHZ, etc.) and then passes Compare, nodes on the mobile site Make sure these links = the duration of the time continues, and whether they move basically together (9) 2 in the same - in a car or train, etc.) if they determine the best overall body from the axis, each or they can be in the same time The signals between the service and the other device are very different. =z is a lot of variables (such as the position in the motor vehicle and the distance from the car body. The best signal is obviously better than the given device can pass through its straight machine.曰4 implements 1, which requests the device with the best signal as the master—(4), and the call will be passed to the other device through the host. 29 201212553 If the carrier signal is lower than ·, the process is repeated and can be mixed Select another - device new = machine. In this special case, all devices know which other devices are performing the test, at least until they are out of range. For example, for the device participating in the network conference, each device is once The user (ie, the device user) provides the user interface. Therefore, each device uses substantially the same carrier-to-one wireless connection. To reduce redundant traffic and reduce the f-plus network capacity of the county, The first device of the road conference becomes a wireless femtocell base station AP of other devices in the same geographical area. If accepted, the first device is registered with the carrier and then serves as its wireless conference at the pico-cell base station. The extension of this scheme can be applied to any type of audio and/or video shot, regardless of the number of given ground_s participating in the conference through the portable computing communication device. Another extension can include ~, he The device shares a 値H-based lang (for example, a device is connected to the Internet-hosted Gu (for example, a (4) library, a dependent micro-bee-base station ΑΡ, and other devices are written by the wireless femto-bee ^= ΑΡ Internet-hosted applications). For example, as a wireless femtocell base station, the touch is based on its ring = for example, in an office, at home, in a wheeled vehicle, in a public place, in a private place, in a dual use, in a private use, etc. ) Configure. The configuration options include frequency usage two, transmit power, secret support unit (four), pin femto bee base station control, decentralized femtocell base station control, allocated capacity, compilation level, symbol and/or interface people. For example, if you are in a public place, the job will be used as a public wireless wireless cellular femtocell. When Cai Cai made a private woven cellular wire division, it chose to be able to ensure the privacy of the communication that it supports in 201212553. 5 is a schematic block diagram of a portable computing communication device 10 including an on-chip system (S0C) 12 coupled to a front end module (/em) network 80 via an RF connection 9 in accordance with another embodiment of the present invention. Or 52. The s〇c 12 or % includes a power management unit το 26, a no-SAW receiver unit 18, a no-saw transmitter unit 20, and a baseband processing unit 22, and may further include a processing module. The connection 9 can be at least one of a coaxial cable, an elastic wire cable, an elastic waveguide, and/or other high frequency. The FEM network 80 includes a plurality of FEMs 62_68 (e.g., two or more) and a frequency conversion module 82. The frequency conversion module 82 includes one or more bypass conversion modules. Each of the FEM 62·68 includes a plurality of power amplifier modules (ΡΑ), a plurality of RX-TX separation modules, at least one antenna tuning unit (), and a band switch (SW). Note that the structure of at least one of the FEMs 62_68 is as described with reference to FIG. The functions of SOC 12 or 52 and FEM 62-68 are similar to s〇c 12 or 52 and FEM 62-68 in FIG. In this embodiment, the inbound or out signal from the FEM and/or the outbound RP signal from the SOC 12 or 52 may be frequency converted prior to routing between s〇c 12 or 52 and the corresponding FEM. For example, s〇c 12 or 52 may form an input and outbound RF signal for processing a carrier frequency of 24 GHz, but with baseband functionality that produces a symbol stream based on a plurality of standardized wireless protocols and/or proprietary protocols. At this point, SOC 12 or 52 generates an outbound symbol stream in accordance with a given radio protocol and upconverts the symbol stream to an RF signal having a 2.4 GHz carrier frequency. RF-RF Inverter Module with Local Oscillator, Mixing Module, and Filtering % Mix the outbound RF signal with local oscillator to produce a mixed signal. The filter section filters the 2012-12553 wave-mixed signal to produce an outbound Rp signal of the desired carrier frequency (eg, 900 MHz, 1800 MHz, 19 〇〇 MHz, 5 GHz, 60 GHz, etc.). Note that the frequency conversion module 82 can include a plurality of RF-RF conversion modules (one or more for the k-South carrier frequency and/or one or more for reducing the carrier frequency). In this regard, the implementation of the general purpose SOC 12 or 52 can be coupled with various implementations of the FEM network 80 (eg, the number of FEM modules 62-68, the number of RF-RF conversion modules, etc.) to form various portable calculations. Communication device. 6 is a schematic block diagram of a portable computing communication device 1A including a plurality of system-on-chips connected to a front end module (FEM;) network 60 via an RF connection 78 (s〇), in accordance with another embodiment of the present invention. C) 12 or 52. Each SOC 12 or 52 includes a power management unit 26, a no-SAW receiver unit 18, a no-SAW transmitter unit 20, a baseband processing unit 22, and a processing module. The Rjp connection 78 can be at least one of a coaxial cable, an elastic fiber cable, a flexible waveguide, and/or other high frequency cable. The FEM network 60 includes a plurality of FEMs 62-68 (eg, two or more) 'where each of the FEMs 62-68 includes a plurality of power amplifier modules (PAs), a plurality of RX-TX split modules, and at least one antenna Tuning unit (ATU) and band switcher (SW). Note that at least one of the FEMs 62-68 has the same structure as described with reference to FIG. In this embodiment 'one SOC 12 or 52 uses at least one of feM 62-68 to support one or more wireless communications (eg, cellular, Wlan, WPAN, etc.) 'Another SOC 12-52 uses one or more other FEMs 62- 68 to support one or more other wireless communications. In order to reduce interference between wireless communications and/or to optimize each wireless communication 'at least one S〇c 12 or 52, a control signal is provided to the FEM 62_68 to adjust its performance. In addition to each s〇c 12 or 52 making 32 201212553 different FEM 62-68-in this example, in another example, two or more SOC 12 "2 can pass the switching module (not shown) in a time division manner Share FEM 62-68. In yet another example, one s 〇 c 丨 2 or 52 may use one path of the FEM 62-68 'the other s 〇 c 12 or 52 may use at least one of the other paths of ρ ΕΜ 62_68. 7 is a block diagram of a portable computing communication device 10, including a plurality of system-on-chips connected to a front end module (FEM) network 80 via an RJP connection 90 (s〇c), in accordance with another embodiment of the present invention. 12 or 52. 3〇 (: 12 or 52 includes power supply unit 26, no SAW receiving H unit 18, no SAW transmitter 4 2〇, baseband processing unit 22' may also include a processing module. It may be at least one of a coaxial Wei, a miscellaneous fiber cable, a hybrid waveguide, and/or other high frequency cable. The FEM network 8G includes a rural FEM 62_68 (eg, two or more) and a variable face group 82. The frequency conversion module 82 Include one or more bypass RF RF conversion modules. Each of FEM 62-68 includes multiple power amplifier modules (PA), rural rx_TX, at least one antenna modulation unit (ATU), and frequency band. Switch (sw). Note that at least one of the FEM 62 68 structures is as described with reference to Figure 3. In this embodiment, one SOC 12 or 52 uses at least one of the FEMs 62_68 to support one or more wireless communications. (eg cellular, WLAN, WPAN, etc.), another SOC 12-52 uses one or more He supports the FEM 62_68 or a variety of other wireless communications. To reduce interference between wireless communications and/or to optimize each wireless communication, at least one SOC 12 or 52 provides control signals to the FEM 62-68. At least one wireless communication can be bribed by Wei Yu 82 to reduce the carrier frequency of the wire communication 33 201212553. Figure 8 is a schematic block diagram of a portable computing communication device 10 including RF via RF according to another embodiment of the present invention. Connected to the system (s〇c) connected to the front-end module (FEM) network 60. The s〇c 1〇〇 includes the power management unit 26 and the plurality of SAW-free receivers 18_丨_18_2 The plurality of non-saw transmitter units 20-1-20-2, one or more baseband processing units 22, may further include a processing module. The RF connection 7〇 may be a coaxial electric coil, an elastic optical fiber, and an elastic waveguide. And/or at least one of the other high frequency electrical windings. The FEM network 6A includes a plurality of fem 62-68 (eg, two or more), wherein each of the FEM 62 68 includes a plurality of power amplifier modules (PA) , multiple RX4X separation modules, at least one antenna adjustment Unit (ATU) and band switcher (sw). Note that the structure of at least one of fem 62_68 is as described with reference to Fig. 3. In this embodiment, 'soc 1〇〇 can utilize at least one of FEM 62_68 for multiple concurrency Wireless communication. For example, a pair of SAW-free transmitters & receivers can be used for WLAN communications, and another pair of SAW-free transmitters & receivers can be used for 850 or 900 MHz cellular telephone communications. As another example, a pair of SAW-free transmitter & receivers can be used for cellular voice communications and another pair of SAw-free transmitters can be used for cellular data communications. Note that these concurrent wireless touches can be in the same frequency band with different carrier frequencies and/or in different frequency bands. 9 is a schematic block diagram of a portable computing communication device 10 including a system on chip (S〇C) 100 connected to a front end module (FEM) network 80 via an RF connection 7 in accordance with another embodiment of the present invention. . The s〇c 1〇〇 includes a power management unit 26, a plurality of SAW-free receiver units 18_Μ8·2, a plurality of SAW-free transmitter units 20-1-20-2, one or more baseband processing units 22, and may also include Department 34 201212553 Management Module. The RF connection 70 can be at least one of a coaxial cable, an elastic fiber optic cable, an elastic waveguide, and/or other frequency-over-frequency cable. The FEM network 80 includes a plurality of FEMs 62-68 (e.g., two or more) and frequency conversion modules. The frequency conversion module 82 includes one or more bypass RF-RF conversion modules. Each of the FEMs 62_68 includes a plurality of power amplifier modules (PAs), a plurality of rx-tx split modules, at least one antenna tuning unit (ATU), and a band switch (sw). Note that the structure of at least one of fem 62-68 is as described with reference to FIG. In the present embodiment, the 'SOC 100 can utilize at least one of the FEMs 62_68 for multiple concurrent wireless communications' and at least one of the carrier frequencies of the wireless communications can be converted by the frequency conversion module 82. For example, a pair of SAW-free transmitters & receivers can be used for WLAN communications, and another pair of SAW-free transmitters & receivers can be used for 850 or 900 hall cellular telephone communications. As another example, a pair of SAW-free transmitter & receivers can be used for cellular voice communications, and another pair of SAW-free transmitter & receivers can be used for cellular data communications. In any of the above examples, the carrier frequency to > one wireless pass # can be increased or decreased by the frequency conversion module 82. 10 is a block diagram of a portable computing communication device 10 in accordance with another embodiment of the present invention, including a system on chip (s〇c) connected to a front end module (FEM) network 120 via an RP connection 122. The 〇s〇c 11〇 includes a power management unit 26, an intermediate frequency (positive) baseband (BB) receiver unit 112, a BB-IF transmitter unit II4, and a baseband processing unit 22, and may further include a processing module. The connection 122 can be at least one of a coaxial Wei, an elastic fiber, a flexible waveguide, and/or other high frequency cable. The FEM network 120 includes a plurality of FEMs 62-68 (e.g., two or more) and a plurality of RF-IF TX and rx pair 124_138. Each of FEM 62·68 is divided into 35 power amplifiers (PA), _ _ χ χ separation module, at least one antenna unit (ATU) and fresh switch (sw) (jTx IF RF132) Each of -138 includes a polarization-based topology, a Cartesian-based topology, a hybrid polarization-based city or mixing, filtering & hybrid module. Each of RX RF-IF and 4-130 includes a low Noise amplifier and downconversion section. Note that at least one structure of the FEM 62_68 is as described with reference to Figure 3. In this embodiment, the baseband processing module 22 converts the outbound data into one according to one or more wireless communication protocols. Or a plurality of outbound symbol streams. The τχ ι_ιρ portion 114 includes a mixing module, and the mixing module mixes the outbound symbol stream with the transmitting positive local vibrating (for example, an oscillation with a frequency of several tens of MHz and ten GHz) One or more outbound IF signals are generated. The SOC 110 provides an outbound IF 4 number to the FEM network 120 via the RF connection 122. Additionally, the SOC 110 provides a representation of which of the rx_tx pair 124-130 and corresponding FEM62-68 will support the selection signal for wireless communication The selected TXIF-RF sections 132-138 mix the IF signal with a second local oscillation (e.g., an RF-IF frequency oscillation) to produce one or more mixed signals. The combined & filter section will have one or more The mixed signal combinations are filtered and filtered to produce a pre-PA outbound RF signal. The pre-PA outbound RF signal will be provided to the corresponding FEM 62-68. For inbound RF signals, with FEM 62- 68 associated antenna receives the signal and provides it to the Band Switch (SW) (if included) or to the ATU (if no switch is included) FEM 62-68 processes the inbound RF signal as described above and will process it The inbound RF signal is provided to the corresponding RXRF-IF section 124-130. 36 201212553 The RXRF-IF section 124-130 mixes the inbound RF signal with a second RX local oscillation (eg, an amplitude of RJF-IF oscillation) to produce One or more inbound IF mixing signals (eg, I and Q mixing signal components or polarization format signals at IF (eg, AOcos^Wt) + Φ(ΐ)). The RXIF-BB portion 112 of the SOC 110 receives one or Multiple inbound IF mixing signals and converting them into one or more inbound symbol streams. Baseband processing module 22 One or more inbound symbol streams are converted to inbound data. Note that S〇c 110 may include multiple RX IF-BB and TX BB-IF sections to support multiple concurrent wireless communications. Figure 11 is in accordance with the present invention. A block diagram of a portable computing communication device 10 of one embodiment 'it includes a system on chip (s〇C) 140 coupled to a front end module (FEM) network 142 via connections 152-154. The S0C 140 includes a power management unit 26, an intermediate frequency (IF)-baseband (BB) receiver unit H4, a BB-IF transmitter unit 146, and a baseband processing unit 22, and may further include a processing module. The RF connections 152-154 can be at least one of coaxial electrical, cable, resilient fiber optic, elastic waveguides, and/or other high frequency cables. The FEM network 142 includes a plurality of FEMs 62_68 (e.g., two or more) and a pair of RF-IF TX and RX sections 148_150. Each of the FEM 62_68 includes a plurality of power amplifier modules (pA), a plurality of split modules, an antenna tuning unit (ATU), and a band switch (sw) qTxif^ »M々50 including polarization based Topology, Cartesian-based topology, hybrid polarization based Kalman topology or mixing, filtering & hybrid modules. The RX RF-IF section includes low noise amplification H and lower variants. Note that the structure of at least one of the distances is as described in Reference 3. 37 201212553 In this embodiment, baseband processing module 22 converts outbound data into one or more outbound symbol streams in accordance with one or more wireless communication protocols.

. The TX BB-IF portion 146 includes a mixing module that mixes the outbound symbol stream with a positive local oscillation (eg, an oscillation having a frequency of tens of MHz to several tens of GHz) to produce one or more outputs. Station IF signal. The SOC 140 provides an outbound IF 5 tiger to the FEM network 142 via RF connections 152-154. The TXIF-RF section 150 mixes the IF signal with a second local oscillation (e.g., an RF-IF oscillation) to produce one or more mixed signals. The combined & filter combines the one or more mixed signals and filters them to produce an outbound RF signal for the pre-PA, which will be provided to the corresponding FEM 62-68. For inbound RF signals, the antenna associated with FEM 62-68 receives the signal and provides it to the Band Switcher (SW) (if included) or to the ATU (if no switch is included) 〇FEM 62-68 as described above The inbound rf signal is processed and the processed inbound RF signal is provided to the RX RF-IF portion 148. The RX RF-IF section 148 mixes the inbound RF signal with a second RX local oscillator | (e.g., frequency oscillation) to produce one or more inbound IF mixing signals (e.g., I and q mixing signal components). Or the RXIF-BB portion 144 of the IF's polarization format signal (eg, A(1)cos(coIF(t;) + Φ(ί)) ° SOC 140 receives one or more inbound IF mixing signals and converts them to one or more Inbound symbol stream. Baseband processing module 22 converts one or more inbound symbol streams into inbound data. Note that SOC 140 may include multiple RX IF-BB 144 and TX BB-IF portions 146 to support multiple concurrent Wireless communication. 38 201212553 FIG. 12 is a schematic block diagram of a portable computing communication device 10 including a system on chip connected to a front end module (FEM) network 162 via an RF connection 176, in accordance with another embodiment of the present invention ( S〇c) 160. The SOC 160 includes a power management unit 26, a no-SAW receiver (RX) downconversion unit 164, a SAW-free transmitter (τχ) up-conversion unit 166, and a baseband processing unit 22, and may further include a processing module. The RF connection 176 can be coaxial electrical winding, elastic fiber electrical winding, flexible waveguide, and/or other At least one of the frequency cables. The FEM network 162 includes a plurality of FEMs 168-174 (eg, two or more) and a pair of RF-IF TX and RX sections. Each of the FEMs 168-174 includes a plurality of power amplifier drivers, respectively. (PAD), multiple low noise amplifiers (lna), multiple power amplifier modules (PA), multiple RX_TX split modules, at least one antenna tuning unit (ATU), and band switcher (sw). Note, fem The structure of at least one of 168-174 is as described with reference to Figure 3. In this embodiment, baseband processing module 22 converts outbound data into one outbound symbol stream according to one or more wireless communication protocols. The saw τ 上 upconversion section 166 converts the outbound symbol stream into one or more outbound upconverted signals, and the no SAW ΤΧ upconversion section 166 can be implemented similarly to the SAW TX upconverter 166 lacking the power amplifier driver. The outbound upconversion domain is provided to the FEM network 162 via the RF connection 176. The SOC 160 can also provide the FEM network 162 with a selection signal. The selected FEM module receives the outbound upconverted signal through the power amplifier driver (pAD). · Zoom out of the station The signal is frequency converted to produce an outbound RF signal of pre-pA, which is then processed by the FEM 168 loss in the manner described above and/or as will be described with reference to at least one of the following figures. 39 201212553 For Inbound RF 彳§号' The antenna associated with FEM 168-174 receives the signal and provides it to the Band Switcher (SW) (if included) or to Ατυ (if no switch is included). The ATU and RX-TX split modules process the inbound RF signals in the manner described above and provide the processed inbound RF signals to lna. LNa amplifies the inbound RF signal to produce an amplified inbound rf signal. The no SAW RX portion 164 (similar to the no SAW reception 5 | implementation lacking the LNA) receives one or more amplified inbound IF mixing signals and converts them into one or more inbound symbol streams. The baseband processing module 22 converts one or more inbound symbol streams into inbound data. Note that the baseband processing unit 22 and/or the processing module can provide control signals to the LNAs and/or PADs of each FEM 168-174 to adjust its performance (eg, gain, linearity, bandwidth, efficiency, noise, output dynamics). Range, slew rate, rate of rise, settling time, overshoot, stability factor, etc.). FIG. 13 is a schematic block diagram of a portable computing communication device including a system on chip (S0C) 180 coupled to a front end module (FEM) 182, in accordance with another embodiment of the present invention. The S0C 180 includes a plurality of SAW-free receiver sections (only the LNA and variable-frequency bandpass filters (FTBpF) of the receiver section are shown), and a plurality of non-saw transmitter sections (only the power amplifier drive is shown!|(PAD) )), a processing module, a baseband processing module (not shown or included in the processing module), and a power management unit (not shown). FEM I82 includes low band (LB) path, high band (10)) way # and band switcher (FB SW> LB path including power amplifier || module (p:), low band impedance level (LB Z), low band Low pass filter (LB LpF), switch (SW), transmit-receive split module (τχ-Rx IS〇) (eg duplexer 201212553)

The second switch (SW) and the antenna tuning unit (ΑΤυ)°ΗΒ path include a power amplifier module (ΡΑ), a high-band impedance stage (ηβ Ζ), a high-band low-pass filter (HB LPF ), and a switch (SW) ), a transmit-receive split module (tx_rx ISO ) (eg, a duplexer), a second switch (SW), and an antenna tuning unit (ATU). Note that low-band paths can be used to support low-band GSM, EDGE, and/or WCDMA wireless communications, and high-band paths can be used to support high-bandwidth GSM, EDGE, and/or WCDMA wireless communications. As described above and/or as will be described with reference to at least one of the following figures, SOC 180 is used to output an outbound Rp signal of a pre-PA and for inputting an inbound RF signal. The FEM 182 receives the outbound RF signals of the pre-PA through the LB path or the HB path and amplifies them through the corresponding PA modules. The impedance level (LB z or HB Z) provides the desired load on the output of the PA module and is connected to a low pass filter (LB LPF or HB LPF). The LPF filters the outbound RF signal, and the outbound Rp signal is provided to the tx-rx 1§〇 module or ATU according to the configuration of the switch (SW). If the switch connects the LPF to the TX-RX ISO module, TX_rx

The modules attenuate the outbound RF signals before providing them to the ATU. The functions of the ATU are as described above and/or will be described with reference to at least one of the following figures. Note that there are no discrete components between the S0C 180 and the FEM 182. In particular, the portable computing communication device* requires a separate SAW filter necessary for the beekeeper to write the telephone to the headset. At least one of the following is to eliminate the SAW filter and / or its

His traditional external components have contributed: the structure without the SAW receiver, the structure without the SAW transmitter, and/or the programmability of the various components of the FEM 182. Figure 14 is a portable version in accordance with another embodiment of the present invention. A schematic block diagram of computing communication device 201212553 includes a system on chip (SOC) 190 coupled to a front end module (FEM) 192. The SOC 190 includes a plurality of SAW-free receiver sections (only the LNA and variable frequency bandpass filters (FTBpF) of the receiver section are shown), and a plurality of SAw-free transmitter sections (only the power amplifier driver is shown (PAD, A processing module, a baseband processing module (not shown or included in the processing module), and a power management unit (not shown). The FEM 192 includes a low band (LB) path, a high band (HB) path, and a band switcher. (FB SW). The LB path includes a power amplifier module (pA), a low-band impedance stage (LB Z), a switch (Sw), a low-band low-pass filter (LB LPF), and a transmit-receive separation module (tx). -rx IS〇;) (for example, duplexer), second switch (SW), and antenna tuning unit (atu). The path includes power amplifier module (ΡΑ), high-band impedance level (ηβ ζ), switching (SW), high-band low-pass chopper (HB LPF), transmit-receive split module (τχ-Rx iso ;) (eg duplexer), second switch (SW) and antenna tuning unit (ATU) Note that low-band paths can be used to support low-band GSM, EDGE, and/or WCDMA wireless communications. The path supports high-bandwidth GSM, EDGE, and/or WCDMA wireless communications. In various embodiments of the SOC 190, the variable frequency bandpass filter in the receiver section of the sC 190 provides adequate filtering of the out-of-band block (far- 〇utblocker) and filtering the image signal that has a non-negligible effect on the desired signal. This will reduce the dynamic range of the analog-to-digital converter (ADC) of the receiver section (the input of the baseband processing module or the input of the RXBB-IF section). Requirement. The superheterodyne structure of the receiver portion of the receiver portion is advantageous for reducing power consumption and deadband compared to comparable direction conversion. 42 201212553 Figure 15 is a s〇c according to an embodiment of the present invention. 2〇〇的处_11? The schematic block diagram of the receiver unit 204 'It includes the FEM module (including the transformer τι, the adjustable capacitor network C1 and / or the low noise amplifier module (LNA) 206), mixing Module 208, mixing registers 210-212, variable frequency bandpass filter (FTBPF) circuit modules (including FTBPF 222 and/or other registers 214_220), and receiver IF-BB portion 224. SOC 200 also includes No SAW transmitter portion 202, and may also include a baseband Unit, processing module, and power management unit. In an operational example, an inbound signal is received through an antenna. The inbound RF signal includes a desired signal component of the RF and an undesired component at a frequency above or below the frequency (shown The higher than the component). About the local oscillation of the part 204 (for example, 4〇) 'If the jg number is in the rRF-2fIF', an image signal will appear. Note that the RF used here and throughout the text includes frequencies in the radio band up to 3 GHz and frequencies in the 3 GHz-300 GHz millimeter wave (or microwave) band. The antenna provides an inbound RF signal to the FEM. The FEM processes the signal in the manner described above and/or as will be described with reference to at least one of the following figures. Transformer T1 receives the FEM processed inbound RF signal and converts it into a differential signal 'adjustable valley network C1 (eg, a plurality of series connected switches and capacitors, wherein the plurality of parallel connections) filters the differential signal . The tunable capacitor network C1 receives control signals from the baseband processing unit and/or processing module (e.g., s〇c processing resources) to enable the required capacitance. A low noise amplification module (LNA) 206 comprising one or more low noise amplifiers connected in series and / or in parallel amplifies the inbound RF signal to produce an amplified inbound RF signal. The LNA 206 can receive a control signal from the SOC processing resource, wherein the control 彳5 refers to a setting that does not include at least one of the following: benefit, linearity, band 43 201212553 width, efficiency, noise, output dynamic range, swing rate, rate of rise, Establish time, overshoot and stability factor. The mixing module 208 receives the amplified inbound signal and converts it into an in-phase (I) signal component and a quadrature (Q) signal using a conversion module (eg, a π/2 phase shifter or other type of phase control circuit). Component. A mixer of the mixing module 2〇8 mixes the I signal component with a local oscillator (eg, sink) signal component to generate an I-mixed money 'other-mixing|| The locally vibrated Q signal component is mixed and shouted. Note that the mixer of the mixing module 208 can be a balanced mixer, a double balanced mixer, a passive switching mixer, a Gilberte mixer (Gilberteellmixe or other types of two sinusoidal numbers). Multiply and generate a "frequency and" signal component and a "frequency difference, the circuit of the signal component. Also note that the Ϊ and Q mixed signals are differential or single-ended signals; the differential signal is shown. Save II 210-212 filtered and / or buffered and Q mixed signals, which will then be provided to the FTBPF, structure (such as register 214_22 〇 and variable frequency band pass test (FTBPF) 222). Note that mixed The signals of the frequency include the components of the IF form, and can also be used in the form of mirrors.

Like a signal component. It should also be noted that the mixing module or the mixing register 2 may include a button to attenuate an undesired amount of signaling, so that it has little effect on the if signal component. FTBPF 222 (various embodiments will be described with reference to the following figures) by attenuating the mirrored IF domain score 4 and filtering the IF money by the substantially unobserved IF signal component. For example, 'Assume that FTBpF converts the baseband band pass filter response frequency into an IF (for example, 〇) ferrite response. For this 201212553 example, it is also assumed that RF is 2 GHz, L02 is 1900 GHz, and RFimage is 1800 GHz. Based on these assumptions, the mixing module 208 will generate an I-mixed signal and a Q-mixed signal, the resulting signal being a combination of the desired signal and the image signal. In a nutshell, the I-mixed signal (eg cos(RF)*cos(L02)) includes l/2cos (2000-1900) +l/2cos (2000+1900) of the desired signal component and l/ of the image signal component. 2cos (1800-1900) +l/2cos ( 1800+1900), Q mixed signal (eg sin(RF)*sin(LO)) including l/2cos (2000-1900) -l/2cos of the desired signal component (2000+1900) and l/2cos (1800-1900) -1/2COS (1800+1900) of the image signal component. Note that the frequency component of 2000+1900 is filtered by the register after the mixer. The narrowband of the FTBPF filters out (1800-1900) the image frequency and the undesired signal component' leaving the desired signal component at a frequency of (2000-1900). Specifically, 1/2C0S (2000-1900) of the I-mixed signal and l/2cos (2000-1900) from the Q-mixed signal are left. The FTBPF 222 uses these two inputs to achieve addition of the terms of the desired signal component (eg, 1/2C0S (2000-1900) +l/2cos (2000-1900) =cos (2000-1900)), and implements the image signal component. Addition of terms (eg l/2cos (1800-1900) _l/2cos (1800-1900) = 〇 (ideally)). Therefore, the image signal component is attenuated while the signal component is expected to pass substantially without attenuation. To enhance the filtering of the FTBPF 222, it can receive one or more control signals from the s〇c processing resource. The control signal can cause the FTBPF 222 to adjust the mid-rate of the baseband filter response (changing the center frequency of the high q IF filter) to change the quality factor of the chopper to change the gain to change the bandwidth and the like. 45 201212553 Receiver IF-ΒΒ section 224 includes a mixing section and a combination & chop section. The mixing section transmits the inbound 彳s number and the second local oscillating frequency to generate I and 卩 mixed signals. The combined hopping section combines the I and Q mixed signals to produce a combined check' and then the hybrid semaphore to generate one or more human station symbol streams. The RF_IF section 204, which is currently not available, is connected to a single antenna for SIS〇 (single input and single output) through L. 'But this scheme can also be applied to MIS〇 (multiple input single output) communication and MiM0 (multiple input multiple output) ) Communication. In these cases, multiple antennas (e.g., two or more) are coupled to a corresponding number of FEMs (or a smaller number of FEMs based on the receive path in the FEM). The FEM is connected to a plurality of receiver RF-IF sections (e.g., the same number of antennas), which in turn are coupled to a corresponding number of receiver IF_BB sections 224. The baseband processing unit processes the plurality of symbol streams described above to generate inbound data. The RX RF-IF section 204 has at least one of the following advantages and/or includes at least one of the following features: the superheterodyne receiver structure is superior to the corresponding direct conversion receiver in terms of deadband and power consumption; using complex baseband impedance in the FTBPF 222 The frequency shift of the bandpass filter center frequency, thereby enabling the center frequency of the on-chip high q-mirror band-stop filter to be tuned to the desired frequency; and only the signal local oscillator is required, which can be used for the downconverting mixer and FTBPF 222 . 16 is a schematic block diagram of an RF_IF receiver portion 232 of a SOC 230 including a FEM interface module (including a transformer T1 and/or a tunable capacitor network C1), a variable frequency bandpass filter, in accordance with another embodiment of the present invention. (FTBPF) 234, low noise amplifier module (LNA) 206, mixing section (including mixing module 208 and/or mixing buffer 210-212). The SOC 230 also includes a receiver IF-BB section 224, a SAW-free transmitter section 202' and may also include a baseband processing unit, a system, and/or a power management unit. In an operational example, the inbound signal is received through the antenna. The inbound RF signal includes the desired signal component of the RF and the undesired component of the frequency above or below 耵 (the higher component is shown). About the local oscillation of the Rp_IF section 232

(eg fL〇) ’ If the signal is at rRF-2fIF, an image signal will appear. The antenna provides an inbound RFj message to the FEM, which is in accordance with the above and/or will refer to at least the following

The RP signal is processed in a manner described in the accompanying drawings. The transformer receives the FEM-processed human station RF signal and converts it into a differential signal. The tunable capacitor network C1 performs chopping according to the control hybrid squad from the SQC processing lion. The FTBPF 234 (various embodiments will be described with reference to the following figures) filters the inbound signal by attenuating the image signal component and the undesired signal component and by substantially unsuppressed RF k number separation. For example, assume that the FTBPF converts the narrowband baseband bandpass chopper response to (e.g., the carrier frequency of the desired signal component) to produce a high q RF filter response. At the narrowband high Q, the filter bypasses the image signal component and the undesired signal component and passes through the substantially un-attenuated desired signal component. The low-impedance amplifier module (LNA) 2〇6 amplifies the desired inbound signal in the knife to produce an amplified desired inbound signal. Lna can receive control signals from 230 processing resources, wherein the control signals indicate none of the following: gain, linearity, bandwidth, efficiency, noise, output dynamic range, swing, rate, rise rate, settling time, super Adjustment and stability factor. The frequency mode, group 208 receives the amplified inbound or out signal and converts it into an in-phase (1) signal component and an in-phase (Q) apostrophe component using a π/2 phase shifter or a two-phase phase-inducing circuit. A mixer of the mixing module 2〇8 mixes the signal 201212553 with the j signal component of the local oscillation (eg, sink) to generate a j-mixed signal. Another mixer uses the Q signal. The component is mixed with the local oscillating Q signal component to produce a Q corpse. Note that the signals mixed by χ and Q can be differential signals or single-ended signals; differential signals are shown. Mix register cache! Signals mixed with Q, which are then supplied to a filter (such as a bandpass filter). Filters 236 and 238 filter the I and Q mixed signals, respectively, which are then supplied to the IF BB portion 224. The receiver IF-BB section 224 includes a mixing section and a combination & filter section. The mixing unit will station IF彳. The 5 tiger mixes with the first local oscillation to produce a signal of I and q mixing. Combination & Chop Department will! The signals mixed with q are combined to produce a combined signal' and then the Weihexin Weibo domain generates one or more human station symbol streams. Although the currently shown RF_IF section 232 is connected to a single antenna for SIS〇 (single input single output)#, the scheme can also be applied to MjS〇 (multiple input single output) communication and ΜΙΜΟ (multiple input multiple output). Communication. In these cases, multiple antennas (e.g., two or more) are coupled to a corresponding number of FEMs (or a smaller number of FEMs based on the receive path in the FEM). The FEM is connected to a plurality of receiver RF-IF sections (e.g., the same number of antennas), which in turn are coupled to a corresponding number of receiver IF_BB sections 224. The baseband processing unit processes the plurality of symbol streams described above to generate inbound data. 17 is a schematic block diagram of a positive-receiving portion 242 of a s〇c 24〇, including a front-end module interface (including a transformer T1 and/or a tunable capacitor network C1), in accordance with another embodiment of the present invention, - for inverting (four) low noise amplifier module (LNA) 244-246, mixing module 248 and a pair of transimpedance amplifier modules (including transimpedance amplifier (TIA) 48 201212553 250-252, respectively Impedance (Z) 254-256 and / or temporary n 258 · 260). The SOC 240 also includes a receiver IF-BB section 224, a SAW-free transmitter section 2〇2, and may also include a baseband processing unit, a processing module, and a power management unit. In an operational example, an inbound signal is received through the antenna. The inbound RF signal includes the desired signal component of the RF and the undesired component of the frequency above or below 卯 (the higher component is shown). Regarding the local vibration of the F department (for example, fL0), if the signal is at rRF-2fIF, an image signal will appear. The antenna provides an inbound RF signal to the fem that processes the RF signal as described above and/or with reference to at least the following figures. The transformer receives the fem-treated human station RF money and converts it into differential money. The tunable capacitor network C1 filters the differential signal according to the control signal from the S0C 240 processing resource. The LN 244 amplifies the positive term of the inbound rf signal (p 〇 s s s s s s s s s s s s s s s s s s s s s s s s s s s s s s s s s s s s s s The lna 244-246 can receive control signals from the S0C 24 processing resource, respectively, wherein the control signal indicates at least the following settings: gain, linearity, bandwidth, efficiency, noise, output dynamic range, swing rate, rate of rise, Set up time, overshoot and stability factor. The mixing module 248 receives the positive current rf signal and the negative current current, and converts them into in-phase (1) current signals and quadrature (Q) current signals by using a π/2 phase shifter or other type of phase control circuit. . The mixer mode and the 2 sen mixer mix the I current signal with a local oscillator (eg, rib) #! current signal to generate an I-mixed current signal (eg, "), and the current is 49 201212553 The local current I's Q current letter ship generates a Q-heavy current signal (eg 1BB-Q). Note that the 'I and Q mixed current signals can be differential or single-ended signals; the differential signal is shown. It is noted that the current signals of the J and Q mixing include an image component and a desired component, respectively. TIA 250-252 (one or more embodiments of which will be described with reference to at least one of the following figures) receive I and q mixing The current signals are converted to (iv)f by impedance (z) such that the resulting 丨 and q voltage mixed signals have an attenuated image component and a substantially un-attenuated desired component. ΉΑ 25〇_252 combined with impedance (z) a structure that provides a low impedance path between their inputs and a reference potential (eg, Vdd or ground) for less than positive frequencies and a low impedance between their respective inputs for higher than positive frequencies & Path. For frequencies close to IF, TIA 250-252 They are amplified and converted into voltage signals. The register provides I and q voltage signal components to the RXIF-BB section 224, which converts them into an inbound symbol stream. The RX RF-IF section 224 provides at least one of the following advantages and And/or include at least one of the following features: the superheterodyne receiver structure outperforms the corresponding direct conversion receiver in terms of deadband and power consumption; and substantially eliminates the offset and flicker noise problems present in the superheterodyne receiver Figure 18 is a schematic block diagram of an RF-IF receiver portion 271 of a s〇c 270, including an FEM interface module (including a transformer T1 and/or a tunable capacitor network C1), in accordance with another embodiment of the present invention, RF variable frequency bandpass filter (FTBPF) 272, a pair of inverter-based low noise amplifier module (LNA) 274-276, mixing module 278, and a pair of transimpedance amplifier modules (included separately Transimpedance Amplifier (TIA) 280-282, Impedance (Z) 284-286 and/or Register 50 201212553

280-286) and IF FTBPF 288. The SOC 270 also includes a receiver IF-BB section 224, a no-SAW transmitter section 202' and may also include a baseband processing unit, a processing module, and a power management unit. In the present embodiment, the function of the RF FTBPF 272 is as described with reference to Fig. 17 as described with reference to Fig. 16. The bandwidth of the IFFTBpF 288 synchronized with the RF clock and its center frequency in the Shengzheng Town is such that the image signal is attenuated and the thief signal component is passed through without attenuation. Therefore, the filtered, wave mirrored signal is three times: by Rp FTBPF 272, by TIA 280-282 and then by IF FTBPF 288. The RX RF-IF section 271 provides at least one of the following advantages and/or includes at least one of the following features: two clocks are used (eg, and L〇2); the superheterodyne receiver structure is superior to the corresponding in terms of deadband and power consumption. Direct conversion of the receiver; flicker noise is not important' so the baseband circuit can be small; the inductorless LNA274-276 can be used (for example, the LNA can be implemented as an inverter); no DC offset occurs, so eliminated Large footprint offset cancellation circuit; receiver architecture with frequency planning flexibility comparable to direct conversion receivers; includes advanced bandpass filtering stages across RX chains; and can be easily integrated into S〇c 270 . 19 is a schematic block diagram of an RF-IF receiver portion 292 of a s〇c 290 including an FEM interface module (including a transformer τι and/or a tunable capacitor network 匸丨), in accordance with another embodiment of the present invention, ^Inverter bandpass filter (FTBpF) 272, a pair of inverter-based low noise amplifier module (LNA) 274_276, mixing module 278, and a pair of transimpedance amplifier modules (including mutual resistance) Amplifier (TIA) 280-282, impedance (Z) 284-286 and/or register 51 201212553

280-286) and IF FTBPF 294. The SOC 290 also includes a receiver IF-BB section 224, a no-SAW transmitter section 202, and may also include a baseband processing unit, a processing module, and a power management unit. The function of the 'IF FTBPF 294' in this embodiment is as described with reference to Fig. 15, and the function of the TIA is as described with reference to Fig. 17. The RFFTBpF272 is synchronized with the 1^〇 clock and has a center frequency of 117. 1^17. 81) 17272 has a bandwidth such that the mirror signal is substantially attenuated (four) and the signal component passes through substantially un-attenuated. Therefore, the filter and wave image signals are three times: by Rp FTBPF 272, by TIA 28〇-282 and then by IF FTBPF 294. The RX RF-IF portion 292 provides at least one of the following advantages and/or includes at least one of the following features: using one clock (eg, U32); the superheterodyne receiver structure is superior to the corresponding direct conversion receiver in terms of deadband and power consumption; Flicker noise is not important, so the baseband circuitry can be small; non-inductive LNA 274-276 can be used (for example, LNA can be implemented as an inverter); no DC offset occurs' thus eliminating the large footprint offset Elimination of circuitry; receiver architecture with frequency planning flexibility comparable to direct conversion receivers; advanced bandpass filtering stages including spanning chains; and easy integration into S〇C29〇. 20 is a schematic block diagram of a dual band RF-IF receiver section 302 of a s〇c 3〇〇, including a FEM interface module (including a transformer T1 and/or a tunable capacitor network, in accordance with another embodiment of the present invention). Ci), variable frequency bandpass filter (FTBPF) 304, a pair of low noise amplifier modules (LNA) 3〇6_3〇8 and mixing section (including a pair of mixing modules 310-312, mixing register) 314-320 and / or chopper 322-328). The SOC 300 also includes a receiver IF-BB section 224, a SAW-free transmitter section 202' and may also include a baseband processing unit, a processing module, and a 52201212553/or power management unit. ^-A running example towel that receives signals from the person station through the antenna. The inbound RF signal includes one or more desired signal components (eg, one at the "and the other is an undesired component above and below the frequency (showing a higher component). About the RF-IF portion The local seam (one for the first desired shrimp signal, the other for the second desired + RF signal _w and "), if the signal is at rRFr2fIF 々 / or at rRpr2fiF2, one or more image signal components will appear. The antenna provides an inbound rf signal to the FEM, which processes the signal in accordance with the above and/or will be described with reference to at least one of the following figures. Transformer T1 receives the FEM processed inbound rf signal and converts it to a differential The signal, tunable capacitor network C1 filters the differential signal based on control signals from the SOC processing resources. ° FTBPF 〇4 (various embodiments will be described with reference to the following figures) by attenuating the image signal component and undesired The signal component and the inbound or out signal are filtered by the substantially un-attenuated desired RF signal component. For example, suppose the FTBPF converts the narrowband baseband bandpass waver to muscle and 2 (eg carrier of the desired signal component) Rate) to generate two high QRP filters. The narrowband high q RF filter filters out the image signal component and the undesired signal component and passes the substantially un-attenuated desired signal component. The first low noise amplifier module (LNA) Amplifying the desired inbound rpi signal component (when included in the inbound RF signal) to produce an amplified desired inbound ##, and the second low noise amplifier module (LNA) amplifies the desired inbound RP2 signal component (when The inbound RF signal is included to generate an amplified inbound RF2 signal. Each LNA can receive a control signal from the SOC processing resource 53 201212553 'where the control signal indicates the following $ small ^ : gain, linearity, six plus squares, swing rate, rate of rise, settling time, overshoot and stability factor. The first mixing module of the mixing section receives the expected inbound muscle signal of the rose and uses = The phase shifting circuit of phase shifter Wei_ converts it into in-phase (four) apostrophe 77 and positive (Q) signal components. The mixer of the first-mixed group =, the number component is mixed with the _ component of the local oscillation (eg ') Frequency production The first-to-one mixed-domain, the Q-signal component of the local oscillator, the Q-subtractive component of the local oscillator, and the first-Q and the Q-mixed signals can be recorded in a differential or single-ended domain; The differential signal is shown. The first mixing module of the 'band frequency section receives the amplified desired inbound signal and converts it to in-phase with a =2 phase shifter or other type of phase control circuit (1) 仏 component and positive Crossing the (Q) signal component. The mixer of the second mixed group mixes the I domain component with the local vibrating (eg, the U i signal component of U to generate the second 1st domain) and subtracts the Q signal age The locally oscillated Q signal components are mixed to produce a second Q-mixed signal. Note that the first J and Q mixing 1 tongues can be differential or single-ended; Each mixer buffers their respective I and Q mixed signals, which are then provided to filters, filters (such as bandpasses). Honesty! The signals mixed with Q are then supplied to the IF BB portion 224. Although the currently shown RF-IF section 302 is connected to a single antenna for SIS0 (single-input single-output) communication, the scheme can also be applied to MJSOC multi-input single-output communication and MIMO (multi-input multiple-output) communication. In these cases, multiple antennas (e.g., two or more) are coupled to a corresponding number of FEMs (or roots 54 201212553 based on a smaller number of FEMs in the receive path in the FEM). The fem is connected to a plurality of receiver RF_IF sections (e.g., the same number of antennas), and these receiver sections are in turn connected to a corresponding number of receiver IF_BB sections. The baseband processing unit processes the plurality of symbol streams described above to generate human station data. The RXRF-IF section 3〇2 provides at least one of the following advantages and/or includes at least one of the following clocks (eg, L〇2); capable of receiving two inbound RF signals using a single input; Two additional SAW choppers are needed again - one FTBPF 304 effectively filters the two channels (eg muscle and off-signal); the center frequency of the two high QRFs is controlled by the local oscillator 1 clock; and can be easily Integrated in the SOC 300. 21 is a schematic block diagram of a positive receiver portion 332 of a s〇c 33〇, including an FEM interface module (including a transformer T1 and/or a tunable capacitor network C1), with a EM 〇 33 〇 according to another embodiment of the present invention. Variable band pass filter (4) bPF) 338 low noise amplifier module (LNA), negative resistance band-pass bandpass filter (FTBPF) 334 and mixing section (including mixing module 34〇, mixing temporary storage) The 342-344 and/or the filter 346_348>s〇c 33〇 further includes a receiver IF-BB section 224, a SAW-free transmitter section 202, and may further include a baseband processing unit, a processing module, and/or a power management unit In this embodiment, the parasitic resistance (Rp) is shown to be associated with the FEM interface module to represent switching losses (eg, FTBPF) and/or inductance losses. The inductance loss is primarily due to the ohmic resistance of the transformer coil (eg, on the substrate). The metal loss) and/or the substrate loss under the transformer, the inductance loss is the main component of the RF segment impedance due to the modulation of the capacitor C1. The lower parasitic resistance will reduce the quality factor of the filter and reduce the frequency outside the RF. Out-of-band attenuation. 55 2012125 in FTBPF334 53 effectively increases the parasitic resistance, which increases the quality factor and band reduction. ▲ In an operational example, the RF signal is inbound through the antenna. The inbound RF\ number includes the expected signal component of the RF and the frequency is higher or lower. The undesired component (showing the higher component). The local vibration (for example, fL〇) about the purchased F portion 332 'If the signal is at rRF_2flF', the image signal component will be reflected. The antenna provides the inbound rf to the FEM. Signal, the FEM processes the RF signal in accordance with the above and/or will be described with reference to at least one of the following figures. Transformer: Π Receives the FEM processed inbound signal, and converts it into a differential signal, The network C1 filters the differential signal according to a control signal from the SOC 33G processing resource. The FTBPF 334 (various embodiments will be described with reference to the following figures) by attenuating the signal component of the money segment f and the non-thief and passing substantially Attenuating the desired RP signal component to filter the inbound liver signal. For example, suppose the FTBPF office converts the narrowband baseband bandpass chopper to a location (eg, the carrier frequency in the desired signal knife) The high-order q Rp filter. The narrow-band high q Μ filter filters out the image signal component and the undesired signal component, respectively, and passes through the substantially un-attenuated desired signal component. In addition, the FTBPF 334 includes a negative resistance, which is similar to parasitic The resistor (Rp) compensates for the loss represented by the parasitic resistance (eg, effectively increases the quality factor of the filter and increases the out-of-band attenuation). The negative resistance can be dynamically adjusted based on the change in parasitic resistance by a control signal from the SOC 330 processing resource. .

A low noise amplifier module (LNA) 336 amplifies the desired inbound RF signal component to produce an amplified desired inbound RF signal. The LNA 336 can receive a control signal from the SOC 56 201212553 33〇 processing resource, wherein the control signal indicates a setting of at least one of: gain, linearity, bandwidth, efficiency, noise, output dynamic range, swing rate, rate of rise, establishment Time, overshoot and stability factor. In addition, LNA 336 may include RF fTBPf 338, which functions similarly to RF FTBPF 334 described above to further attenuate the image signal component. Mixing module 340 receives the amplified desired inbound signal and uses a π/2 phase shifter or other type of bet to control it to convert the binary phase (1) signal and positive (Q) signal components. The mixer of the mixing module 34〇 combines the 〗 signal component with the local oscillator S (eg fLQ)! The signal components are mixed to produce a chirped k-number and the Q-signal component is mixed with the locally oscillating q signal component to produce a Q-mixed signal. Note that the mixed signal of j and q can be a differential signal or a single-ended signal; a differential signal is shown. The mixing buffer buffers the I and Q mixed signals, which are then supplied to the chopping H (e.g., with a home wave). The reduced wave Η Η mixed signals are then supplied to the RXIF-BB section 224. Although the currently shown RF_IF section 332 is connected to a single antenna for SISO (single input single output) overnight, the scheme can also be applied to MjS〇 (multiple input single output) communication and M!M〇 (multiple input multiple Output) communication. In these cases, multiple antennas (e.g., two or more) are coupled to a corresponding number of FEMs (or a smaller number of FEMs based on the receive path in the FEM). The FEM is connected to a plurality of receiver RF_IF sections (e.g., the same number of antennas), and these receivers RF IF α卩 are connected to the corresponding number of receiver if_bb sections. The baseband processing unit processes the plurality of symbol streams described above to generate inbound data. The RX RF-IF section 332 provides at least one of the following advantages and/or includes the following to 57 201212553. One feature is that the off-chip SAW filter and matching components are no longer needed; the negative resistance increases the quality of the FTBPF 334; the sense of loss can be compensated, Therefore, the inductor has lower tolerances; the need for a thick metal layer is reduced, thereby reducing the manufacturing cost of the die; the center frequency of the two high QRP filters is controlled by the local oscillation clock; and can be easily integrated into the s〇c 330 in. 22 is a schematic block diagram of a receiver portion 352 of a s〇c 35A, including an FEM interface module (including a transformer τι and/or a tunable capacitor network (1), in accordance with another embodiment of the present invention, Variable frequency bandpass filter (FTBPF) 354 with complex baseband (BB) impedance, low noise amplifier module (LNA) 356, and mixing section (including mixing module 34〇 and/or mixing register 342_344) The s〇c 350 further includes a receiver IF_BB section 224, a no-SAW transmitter section 2〇2, and may further include a baseband processing unit, a processing module, and/or a power management unit. In an example of operation, an antenna is used. Receive inbound signal. Inbound RF signal, including RP_Wang component and undesired component above or below the word (showing higher component). Local oscillation (eg fLO) about RP_IF part The image signal component appears if the signal is known. The antenna provides the inbound rf signal to the FEM, which processes the victim signal in the manner described above and/or described in at least one of the figures. Receiving the inbound rf signal after FEM processing and converting it into a differential number, adjustable The capacitance network α filters and waves the differential signal according to the control signal from the SOC 35 〇 processing resource. FTBRP354 (various embodiments will be described with reference to the following _) by attenuating the image of the age-sensitive amount of money and passing the basic The un-attenuated desired RF signal component is filtered to inbound 15. For example, assume that 58 201212553 FTBPF 354 converts the narrowband baseband bandpass filter to Rp (e.g., the carrier frequency of the desired signal component) to produce a high Q RJF filter. The filter at high q filters out the image signal component and the undesired signal component, respectively, and passes through the substantially un-attenuated desired signal component. By using the complex baseband impedance 354, the center frequency of the narrow-band baseband BPF can be adjusted. For example, according to the complex BB The adjustment of impedance 354 can cause the bandpass region to become higher or lower in frequency. A low noise amplifier module (LNA) 356 amplifies the desired inbound Rp signal magnitude to produce an amplified desired inbound signal. The LNA 356 can receive a control signal from 35 〇 processing resources, wherein the control signal indicates a setting of at least one of: gain, linearity, bandwidth Efficiency, noise, output dynamic range, swing rate, rise rate, build amount, and stability factor. The mixing module 34G of the mixing section receives the amplified desired inbound RF signal and controls the ==n or other _ (4) The road converts it into the same phase (1) ^ knife and positive X (Q) # component. Lai module's unique mixer mixes the ^ knife with the local button (such as U) to generate ^ 2 彳. No. 'and the Q signal component and the local vibration q signal component eight kernel = generate Q five-frequency signal. Note that the '1 and Q mixed lying signal can be a differential knife face single-ended signal; Differential signal. The mixing registers 342·344 will be provided with traces (4) ο Q, pain signals, which follow the waves I and Ο, (such as bandpass choppers). The choppers 346-348 filter ^ signals' these signals are then provided to the leg F-BB portion 224. Out) Communication S's field 1 is not out of your department 352 and is used for SIS〇 (single-input single-input single-antenna connection, but the program can also be applied to swollen (early early round-out) communication and _〇 ( Multiple input and multiple rounds of communication. In these cases, the number of antennas (for example, 2 or more) is connected with the corresponding number of FEMs (or a smaller number of FEMs according to the receiving path in the FEM). FEM and more The receiver RF-IF sections are connected (e.g., the same number of antennas), and the receiver RF-IF sections are in turn coupled to a corresponding number of receiver IF_BB sections. The baseband processing unit processes the plurality of symbol streams to generate inbound data. The RX RF-IF portion 352 provides at least one of the following advantages and/or includes at least one of the following features: a superheterodyne receiver has advantages over a similar direct conversion receiver in minimum area and power; the use of complex baseband impedance in the FTBPF 354 enables the band The center frequency of the pass filter is changed; the complex baseband impedance 354 can be realized by the switch and the capacitor, and its core is controlled by the LO clock; the same LO clock used by the (4) mixing || Device FTBpF) is tuned to the desired frequency; RF_IF section 352 uses a signal phase locked loop (pLL); and can be easily integrated into SOC 350. Figure 23 is a schematic illustration of a transmitter section of s〇c 36〇, in accordance with one embodiment of the present invention. Block diagram 'It includes upper _ mixed face group, Wei Wei local vibration module (LO) 364, variable frequency band pass filter (FTBpF) application, output module (including capacitor _ 368_370 and / or transformer n n1) And a power amplifier driver (PAD) 372. The PAD 372 includes a transistor φ_〇2, a resistor R1, and a junction C1 as shown in the figure. Note that the capacitance C1 and/or the resistance illusion can be realized by using one or a solar body Q1_Q2. The s〇c 36() also includes a non-SAw receiver unit 364 and may also include a baseband processing unit, a processing module, and/or a power management unit. In an example, the upconversion mixing module 362 receives the baseband. (BB) I and Q money (for example, the output ship _ ratio and the positive wire). The up-conversion hybrid 201212553 frequency module 362 can convert the bb z and 卩 signals into up-converted signals using a direct conversion topology or a super-heterodyne topology, the latter The carrier frequency is at the desired RF. FTBPF 366 (various embodiments will be The following figures are described by attenuating the out-of-band signal component and factoring up the up-converted 彳§ by a substantially un-attenuated up-converted signal. For example, suppose the FTBPF 366 converts the narrow-band baseband bandpass filter to RF (eg Upconverting the carrier frequency of the signal to produce a high Q filter. The narrowband high QRF filter filters out the out-of-band signal and passes the substantially un-attenuated up-converted signal. Capacitor array 368·370 provides an adjustable low-wave n, Wei The filter filters common mode noise and/or linear noise. Transformer T1 converts the differential upconverted signal to a single-ended ##' which is then amplified by PAD 372. The PAD 372 provides an extended upconversion k number to the FEM, which is further amplified by the FEM to separate it from the inbound liver signal and provide it to the antenna for transmission. The TX portion provides at least one of the following advantages and/or includes at least one of the following features: a superheterodyne receiver has advantages over a similar direct conversion receiver in minimum area and power; uses a TXLO 364 with a transmitter upconverting mixer LC load The synchronous FTBPF 366 reduces transmitter noise and other out-of-band noise at the rx frequency, but has little effect on the desired TX signal; the baseband impedance of the high QFTBPF 366 can be achieved using a capacitor' and its center frequency is controlled by TX LO 364 control; eliminated TXSAW filter; and easy to integrate into S〇C36〇. 24 is a schematic block diagram of a transmitter portion 382 of a s〇c 380, which includes an upconversion mixing module 362, a transmitter local oscillation module (LO), and a variable frequency bandpass filter, in accordance with another embodiment of the present invention. (FTBPF), output module (including capacitor array 368-370 and/or transformer T1), and power amplifier driver 201212553 (PAD) 372. The PAD 372 includes transistors, resistors, and capacitors as shown in the figure. Solemnly, the capacitance and/or resistance can be achieved using one or more transistors. The s〇c 380 also includes a SAW-free receiver unit 364 and may also include a baseband processing unit, a processing module, and/or a power management unit. In this embodiment, the upconversion mixing module includes a passive mixing structure as shown in the figure, and the passive mixing structure can employ a 5〇% duty cycle L〇 clock. In an operational example, the L〇 and Q signal components are mixed by the circuit on the left side of the figure, and the roi and q signal components are mixed by the circuit on the right side of the figure. The mixed LO signal component is then mixed with the mixed BB signal component to produce an upconverted signal. For example, LO-1+ injects energy into its corresponding capacitance and LOj—extracts energy from the union (and vice versa), thereby producing a change at the rate corresponding to L〇 across the capacitor. LQ-Q+ and l〇_Q· are similarly processed for their capacitances. By adding (five) points (four), the capacitance of the (four) change is superimposed on the amount of L-〇-age of the mixed-mixing. _ hard to occur on the baseband side of the mixer. TX portion 382 provides at least one of the following advantages and/or includes at least one of the following features: Vbl and Vb2 driven transistors are high voltage transistors (e.g., her voltage >2.5V); and the TX, structure provides low power high The efficiency region is designed and uses a passive mixer driven by a 50% duty cycle LO clock, which reduces power consumption compared to a mixer driven by a 25% duty cycle clock. Figure 25 is a schematic block diagram of a portion of an egg-positive receiver portion including a single-ended FTBPF (Frequency Variable Bandpass Ship) 394, in accordance with one embodiment of the present invention. This portion of the RF-IF portion includes a transformer Ή, a variable capacitance network ci, and an na 392. The FTBPF 394 includes a plurality of transistors (e.g., a switching network) and a plurality of bases 62 201212553 with impedance (Zbb(s)) 396-402. In one operational example, the front end module (FEM) 390 receives the inbound RF signal through the antenna 'processes the RF signal' and processes the FEm 390 as described above and/or with reference to at least one of the following figures. The inbound signal is provided to transformer T1. Transformer T1 raises or lowers the voltage level of the inbound rf signal, which is then filtered by variable capacitance network C1. Note that the transformer τι can be omitted if the voltage level of the inbound RF signal is not required to be adjusted and/or the separation provided by the transformer T1 is not required. The FTBPF 394 provides a high Q (quality factor) Rjp filter that chops the inbound RF signal such that the desired signal component of the inbound RF signal is substantially un-attenuated to the LNA 392 and undesired signal components (eg, block, Mirror, etc.) Attenuation. To implement the filter, the baseband impedance (Zbb汹) 396_4〇2 together provide a low q baseband filter with a corresponding filter response, where each baseband impedance can be a capacitor, a switched capacitor filter, a switched capacitor resistor, and/or Complex impedance. Note that the impedance of each baseband impedance can be the same, different, or a combination thereof. Also note that the impedance of each baseband impedance can be adjusted by control signals from the SOC processing resources to adjust the performance of the low Q baseband filter (e.g., bandwidth, attenuation rate, quality factor, etc.). The low Q baseband filter is frequency converted to the desired RF frequency by a clock signal provided by clock generator 404 to produce a high QRp filter. Figure 27 shows the frequency conversion of the low Q baseband filter in response to the high Q RF filter, and Figure 26 illustrates one embodiment of the clock generator 404. As shown in Figure 26, the clock generator (which various embodiments will be described with reference to at least one of the following figures) produces four clock signals, each clock signal having 63 201212553 having a 25/〇 duty cycle and sequentially phase shifting 9〇. . The frequency of the clock signal corresponds to the carrier frequency of the inbound or signal and can be adjusted to better track the carrier frequency. The clock generator 404 can also generate a local oscillator clock signal (not shown) for downconverting the inbound RF signal to an inbound IF signal. Returning to the discussion of Figure 25, the FTBPF 394 receives clock signals that are coupled to the transistors to sequentially connect their respective baseband impedances to the inbound RF signals. Since the clock rate is at RF (e.g., the carrier frequency of the desired component of the signal at the inbound), the baseband impedance response (the low Q bandpass filter is commonly) is transferred to the RP to achieve a high QRP bandpass filter. Figure 28 is a schematic block diagram of a single-ended FTBPF 410 comprising four transistors and four capacitors, wherein the transistors and capacitors provide baseband impedance, in accordance with one embodiment of the present invention. Four capacitors provide a concentrated baseband impedance, which provides a low Q baseband bandpass filter as shown in Figure 29. Specifically, the impedance of one capacitor (or four in parallel) is 1/sC, where s is 2πί*. Therefore, as the frequency (f) approaches zero, the impedance of the valley is near infinity, and as the frequency (f) increases, the impedance of the capacitor decreases. In addition, the phase of the capacitor is from 90 at zero frequency. Change to -90. . Returning to the discussion of Figure 28, the valley is connected to the common node of the FTBPF 410 (e.g., the input of the FTBpF) due to the application of the clock signal to the transistor. In this way, the performance of the capacitor can be frequency shifted to the rate of the clock signal as shown in Figure 3 (e.g., fL〇). Specifically, the impedance of the capacitor (and the four capacitors in parallel) is moved to the frequency of the clock. Since L〇 is close to infinite impedance, ftbpf 410 has a high impedance at LO, so the effect on the carrier frequency is comparable to that of the signal component. As the frequency deviates from L0, the impedance of FTBpF 41〇 decreases, so FTBPF 410 effectively "attenuates" the carrier frequency with a signal component that is not equivalent to 64 201212553. Figure 31 is a diagram of another embodiment of the present invention. A schematic block diagram of a portion of the _117 receiver section, which includes a differential FTBPF 412 (frequency bandpass filter). This portion of the RXRF-IF section includes a transformer τι, a variable capacitance network ci, and an na 393. The FTBPFization includes Multiple transistors and multiple baseband impedances (Zbb(8)) 414-420. In one operating example, the front end module (FEM) 39〇 receives the inbound RF nickname through the antenna 'according to the above and/or will refer to at least one of the following The RF signal is processed in the manner described in the accompanying drawings and the inbound RF signal processed by the FEM 39〇 is supplied to the transformer T1. The transformer T1 converts the single-ended inbound signal into a differential inbound RF signal. A high Q (quality factor) RP filter that filters the differential inbound RF signal such that the desired signal of the inbound or out signal is transmitted to the LNA 393 undesirably and undesired (eg, stagnation, mirroring, etc.) attenuation In order to realize the filter and wave, the baseband impedance (ζ_ 414-420 provides a low-turn baseband tear waver with a response of the wave H, each of which can be a capacitor, a capacitor, a second switch, and a resistor. / or complex impedance. Note that the impedance of each strap impedance can be the same different or a combination thereof. Also note that the impedance of each baseband impedance can be controlled by the self-SOC processing, so that the performance of the wave (eg bandwidth, attenuation rate, product f factor, etc.) (d) The clock generated by the clock generation || 422 will be converted to the desired KP frequency to produce a high Q (qua) wave. Figure Q wire chopper responds to high Q RF遽The frequency converter responds to the frequency conversion, Figure 32 (f) 65 201212553. One embodiment of the clock generator 422. As shown in Figure 32, the clock generator 422 (the various embodiments of which will be described with reference to the following at least - amplitude) produces 4 clocks. Signal, each clock signal has a 25% duty cycle and phase shift by %. The frequency of the clock signal corresponds to the carrier frequency of the inbound RF signal and can be adjusted to better match the vertical carrier frequency. Clock generation H 42 2 A local oscillating clock signal (not shown) can also be generated, which is used to downconvert the inbound RF signal to the inbound IF signal. Returning to the discussion of Figure 31, the FTBPF 412 receives the clock signals, which are coupled to the transistor. Connected to sequentially connect their respective baseband impedances to the two-station RF domain. Since the clock rate is at RP (eg, inbound, ie, the carrier frequency of the desired component of the signal), the baseband impedance response (low-Q bandpass filter is commonly used) is transferred to the RF. Thus, a high QRF bandpass filter is implemented.Figure 34 is a schematic block of a portion of the inferior receiver portion in accordance with another embodiment of the present invention. 'It includes a single-ended FTBPF 43" (frequency bandpass filter). This portion of the RXRF IF σ卩 includes the transformer II T1, the variable capacitor network a, and the 392. The FTBPF 43G includes a plurality of transistors and a complex baseband filter 432. In an operational example, the front end module (FEM) 390 receives the inbound RF 彳 § via the antenna and processes the signal as described above and/or as described with reference to at least one of the following figures, and the fem 39 The inbound station after the processing is supplied to the transformer T1. Transformer T1 raises or lowers the voltage level of the inbound Rp signal 'P4, which is then waved by the (4) fine path α. Note that right = the voltage level of the inbound RF signal needs to be adjusted and/or the separation of the transformer is not required, then the transformer T1 can be omitted. The FTBPF 430 provides a high q (quality factor) at the chopper, and the filter 66 201212553 chopped the inbound RF signal such that the desired signal component of the inbound Rp signal is substantially un-attenuated to the LNA 392 and undesired signal components (eg, Blocking, mirroring, etc.) attenuation. In order to realize the low frequency q baseband filter and wave filter of the sinus wave filter, the band pass region of the latter can be offset by zero frequency. Note that the performance of the complex baseband (four) poles (e.g., bandwidth, attenuation rate, quality factor, frequency offset, etc.) can be adjusted by control signals from the SOC processing resources.

The low Q baseband chopper of the frequency offset is frequency converted to a desired RF frequency by a clock signal provided by clock generator 434 to produce a frequency shifted high q卯 filter. Figure 36 illustrates frequency conversion of a low frequency band offset low frequency band filter to a frequency shifted high Q RF waver. Figure 35 illustrates an embodiment of a clock generator 434. As shown in FIG. 35, clock generation (four) 434 (which various embodiments will be described with reference to at least the following figures) produces four clock signals, each having a 25/〇 duty cycle and sequentially phase shifting by 9 〇. . . The frequency of the clock signal corresponds to the carrier frequency of the inbound RF signal and can be adjusted to better follow the vertical carrier frequency. The clock generation g 434 can also generate a local flash clock signal (not shown) for downconverting the inbound RF signal to an inbound IF signal. Alternatively, at least one clock signal of the FT erasing can be used as the chirp clock signal. Returning to the discussion of Figure 34, the FTBpF object receives a clock signal that is coupled to the transistor to sequentially connect it to the complex baseband data stream inbound RF signal. Since the clock rate is at (e.g., the carrier frequency of the desired component of the inbound signal), the response of the complex baseband waver 432 is transferred to the shrimp (and/or LO)' to achieve a high QRF bandpass chopper. Figure 37 is a schematic (4) of a portion of the RF-IF receiver portion, in accordance with another embodiment of the present invention, in accordance with an embodiment of the present invention, including an age-based FTBPF 44G (variable solution). This portion of the shape includes a transformer T1, a variable capacitance network α, and a differential knife FTBPF 440 including a plurality of transistors and a complex baseband chopper. In an example of operation, the front end module (FEM) 39 receives the station RF signal through the antenna. The RP signal is processed in accordance with the above and/or will be described with reference to at least one of the following figures, and the fem will be processed. The in-situ liver signal after the 39〇 treatment is provided to the transformers. Transformer T1 converts the single-ended inbound rf signal into a differential inbound RF signal. . The differential FTBPF 440 provides a high q (quality factor) filter that filters the differential inbound RF signal such that the desired signal component 2 of the inbound liver signal is transmitted to the LNA 393 undesirably and undesirably (eg, blocked) Printed image, etc.) Attenuation. To implement the filter, complex baseband chopper 442 provides low Q baseband filtering H, the bandpass region of which can be offset by zero frequency. Note that the performance of the complex baseband filter 442 (e.g., bandwidth, attenuation rate, quality factor, frequency offset, etc.) can be adjusted by control from the SOC processing resources. The low q baseband filter face of the frequency offset is clocked by the clock generator 444 to the desired RF frequency to produce a frequency shifted high Q卯 chopper. Figure 39 shows frequency conversion of a frequency shifted low q baseband ferrite to a frequency shifted 鬲Q RF filter, and Figure 1 shows an embodiment of a clock generator 444. As shown in Fig. 38, the 'clock generators (the various embodiments of which will be described with reference to at least one of the following figures) generate four clock signals, each having a 25% duty cycle and sequentially 姊9G. . The clock money rate corresponds to the carrier frequency of the inbound RF L number and can be adjusted to better match the vertical carrier frequency. The clock generator 444 can also generate a local oscillating clock signal (not shown) for the lower _ station RF money to be the human station IF signal. At least one clock signal of ρτΒρρ 440 can be used as the L〇 clock signal. Returning to the discussion of Figure 37, the FTBPF 440 receives clock signals that are connected to the transistor and connected to their respective complex baseband data and inbound RF signals. Since the clock rate is at rf (e.g., the in-carrier, i.e., the carrier frequency of the desired component of the signal), the response of the complex baseband filter 442 shifts to phantom/(and/or LO), thereby implementing a high QRp bandpass filter. Figure 40 is a schematic block diagram of a portion of an rpjf receiver portion including an FTBPF 440 (inverter (four) waver) in accordance with another embodiment of the present invention. This portion of the RF-IF section includes a transformer 耵, a variable capacitance network α, and an 娜 393. The differential FTBPF 440 includes a plurality of transistors and a complex baseband filter 442. The complex baseband filter 442 includes a plurality of baseband impedances (e.g., Zbb(s)) 45〇_456, a positive gain stage (Gm) 458, and a negative gain stage (_gM) 46〇. In an operational example, the front end module (FEM) 39 receives the inbound RF signal through the antenna 'the RF signal is processed as described above and/or will be described with reference to at least one of the following figures, and the FEM 39〇 The processed inbound RF signal is supplied to the transformer T1. Transformer T1 converts the single-ended inbound Rp signal to a differential inbound RF signal. The differential FTBPF 440 provides a 咼Q (quality factor) filter that filters the differential inbound RF signal such that the desired signal component of the inbound RF signal is substantially un-attenuated to the LNA 393 and undesired signal components (eg, block , mirroring, etc.) clothing reduction. To implement the filter and waver, the complex baseband chopper 442 provides a low Q baseband filter whose bandpass region can be offset by zero frequency, which is based on the ratio between the gain stage and the baseband impedance. Note that each baseband impedance can be a capacitor, a switched capacitor filter, a switched capacitor resistor, and/or a complex impedance, respectively. Also note that the impedance of each baseband impedance can be the same, different, or a combination thereof. It is also noted that the impedance of each baseband impedance and/or the gain of at least one gain stage can be adjusted by the (four) signal from the SGC processing resource to adjust the performance of the low Q baseband filter (eg, bandwidth, attenuation rate, quality factor). Wait). The low Q baseband filter of the frequency offset is frequency converted to the desired RF frequency by the clock signal provided by clock generator 444 to produce a high frequency shift of the frequency shift. Figure 42 shows a high QRp chopper with frequency offset and Figure q shows an embodiment of a clock generator 444. As shown in Figure 41, clock generator 444 (which various embodiments will be described with reference to at least the drawings) produces four clock signals, each clock having a 25/. The duty cycle is sequentially shifted by 9 (). . The clock signal rate corresponds to the carrier frequency of the inbound RP signal and can be adjusted to better match the vertical carrier frequency. The clock generator 444 can also generate a local slot clock signal (not shown) for downconverting the inbound Rp signal to an inbound positive signal. Alternatively, at least one clock signal of the FTBpF paste can be used as the LO clock signal. ▲ Returning to the discussion of Figure 4G, the FTBPF receives the clocks, which are connected to the transistors to connect their respective complex baseband choppers and 2 signals. Since the clock rate is at RF (eg, the carrier frequency of the desired blade of the inbound RF signal), the response of the complex baseband filter 442 is shifted to (ie, and/or (9), thereby achieving a high QRF^ Detector. Figure 43 A schematic block diagram of a portion of 201212553 of the RF-IF receiver section of another embodiment of the invention includes an FTBPF 44〇 (frequency conversion bandpass filter). The portion of the RX Rf-if section includes a transformer T1 and a variable capacitance network. The path Cl and the LNA 393. The differential FTBPF 44A includes a plurality of transistors and a complex baseband filter 442. The complex baseband chopper 442 includes a plurality of capacitors, a positive gain stage (Gm) 458, and a negative gain stage (-GM) 460. In an operational example, the front end module (FEM) 39 receives the inbound RF through the antenna, and processes the RF signal in accordance with the above and/or will be described with reference to at least one of the following figures. The 39 〇 inbound RF signal is supplied to transformer T1. Transformer T1 converts the single-ended inbound signal into a differential inbound RF signal. Differential FTBPF 440 provides a high Q (quality factor) chopper that filters Differential inbound RF signal enables inbound RF signals The desired signal component is transmitted to the LNA 393 substantially un-attenuated and the unwanted signal components (e.g., block, mirror, etc.) are attenuated. To implement the chopper, the complex baseband filter, waver 442 provides a low Q baseband filter 'the latter' The bandpass region can be offset by a zero frequency based on the ratio between the gain level and the capacitance. Note that the capacitance of each capacitor is the same, not _ or a combination thereof. Also note that each capacitor The gain and/or the gain of at least one gain stage can be adjusted by adjusting the control signal from the s〇c processing resource to adjust the performance of the low Q baseband filter (eg, bandwidth, attenuation rate, quality factor, etc.). The frequency offset low Q baseband filter is frequency converted to a desired RF frequency by a clock signal provided by clock generator 444 to produce a high frequency filter of frequency offset. Clock generator 444 as shown in FIG. Various embodiments will be described with reference to at least the following figures to produce four clock signals, each of which has a 25% duty cycle and a phase shift of 9 依次. The frequency of the clock signal corresponds to the inbound RF. Money The ship can be throttled to better follow the vertical carrier frequency. Clock generator 444 can also generate a local oscillator clock signal (not shown) that is used to downconvert the inbound RF signal to an inbound IF signal. At least one clock signal of the FTBPF 440 can be used as the l clock signal. Returning to the discussion of Figure 43, the FTBPF 44 receives the clock signals that are coupled to the transistors to sequentially connect their respective complex baseband filters 442 with Inbound RF signal. Since the clock rate is at (e.g., the carrier frequency of the desired component of the signal at the inbound), the response of the complex baseband filter 442 is shifted to Rp (and/or LO), thereby implementing a high QRF bandpass filter. Figure 45 is a schematic block diagram of a portion of a ready-to-use receiver portion including an FTBPF 440 (frequency conversion band pass filter) in accordance with another embodiment of the present invention. ! 〇 (This portion of the RF-IF section includes a transformer τι, a variable capacitor network C1, a control module 470, and an LNA 393. The differential FTBPF 440 includes a plurality of transistors and a complex baseband filter 442. The complex baseband filter 442 includes multiple Baseband impedance (for example

Zbb(s) ) 450-456, positive gain stage (Gm) 458 and negative gain stage (-GM) 460. In an operational example, a Front End Module (FEM) 39 receives an inbound RF signal through an antenna 'Processing the RF signal ' and processing the FEM 390 as described above and/or with reference to at least one of the following figures; The subsequent inbound RF signal is supplied to the transformer Ή. Transformer T1 converts the single-ended inbound RF signal into a differential inbound RF signal. The differential FTBPF 440 ^ is for a Q (quality factor) chopper that filters the differential inbound RF signal such that the desired signal component of the inbound Rp signal is substantially un-attenuated to the LNA 393 and the undesired signal component ( For example, the resistance 72 201212553 can be mirrored 荨) clothing reduction. To implement the filter, the complex baseband filter 442 provides a low Q baseband filter whose bandpass region can be offset by a zero frequency based on the ratio between the gain level and the baseband impedance, which is provided by the control module alone. The control signal is set. Control module 470 is part of the SOC processing resource that determines the desired low Q bandpass filter response (eg, gain, bandwidth, quality factor, frequency offset, etc.) based on at least one of the following: signal to noise of the inbound RF signal Ratio (SNR), signal to interference ratio (SIR) of the incoming financial signal, strength of the received signal, bit error rate, and the like. 1. According to the expected response, the control module uniquely determines the baseband impedance and/or gain mode settings. Note that the control mode, group can continuously update, periodically update, and/or satisfy the characteristics of the desired shout according to the changes in the various factors it monitors (eg, launching God level changes, checking below the inter-value) , SIR is below the threshold, the strength of the received signal is lower than the threshold, etc.) is updated. Once the frequency response of the low Q baseband filter is asserted (or updated), the low q baseband filter is converted to the desired RF frequency by the clock signal provided by the clock generation H 476 to produce a high Q of the frequency offset. filter. The clock generator 476 (which various embodiments will be described with reference to at least one of the following figures) produces four clocks, each clock signal having a Μ% ratio and a phase shift of 90. . The frequency of the clock signal corresponds to the carrier frequency of the signal at the inbound, and can be used for a good touch. The clock generator 476 can also generate a local oscillator i clock signal (not shown) for downconverting the inbound RF No. 6 into an inbound IF signal. Alternatively, at least one clock signal of the willow can be used as the chirp clock signal. Returning to the discussion of Figure 45, the FTBpF_receives the age number when these are connected. The 201212553 clock signal is connected to the transistor to connect them in turn (4) complex base (four) wave device secret and input money. Since the clock rate is (i.e., the carrier frequency in the desired knife of the inbound RF signal), the response of the complex baseband chopper 442 shifts to (i.e., / or LO)' to achieve a high QRp bandpass chopper. - Figure 47 is a block diagram of a complex baseband (bb) device tearing according to an embodiment of the present invention. b includes a plurality of adjustable baseband impedance gamma-gamma, an adjustable positive gain stage, and an adjustable negative gain stage. thorough. Each tunable baseband impedance can include at least the following: an optional capacitor network 492 (eg, a tunable capacitor), a programmable switched capacitor network 494, and a programmable switched capacitor chopper 496 (i-order to n-th order) And any combination of components (such as honesty, capacitance, resistance) that can provide a drunk response. Adjustable Gain Levels (+Gm and _Gm) The 488-49G can each include an amplifier that is connected to a gain network. The gain network can include at least the following items: resistance, current, variable resistance, variable electrical material. In this regard, the gain of each gain stage can be adjusted to vary the performance of the complex baseband filter 442. Specifically, the low Q-band 赖 阙 frequency offset can be changed by making the variable gain by the adjustable impedance. Additionally or alternatively, the bandwidth, gain, swing rate, factor f, and/or other performance of the complex baseband 442 can be varied by the control signals provided by the control module 47A. Figure 48 is a diagram showing the frequency response of the complex BB filter 442 to a high QRF filter for the frequency response of the BB filter 442, including the tunable complex baseband filter 442 of Figure 47, in accordance with one embodiment of the present invention. 1?1^1>17 440. In this diagram, the bandwidth, swing rate, gain, frequency offset, and/or other performance 201212553 of the low-keyband baseband filter provided by the complex baseband filter 442 can be adjusted. The low Q _ ship 1! can be converted to RF (or LO). In this regard, by adjusting the performance of the low Q baseband detector, the performance of the corresponding high Q baseband filter can be similarly adjusted. Figure 49 is a schematic block diagram of a portion of a receiver portion including an FTBPF 412 (frequency-converting bandpass ferrite) in accordance with another embodiment of the present invention. This portion of the purchased F portion includes ϊ 504 and Q muscle 1]7 mixing system, and a mixing register 502. The FTBPF module includes the FTBPF and other registers. The FTBpF includes a plurality of transistors and a plurality of baseband impedances (e.g., Zbb(s)) 414, 416, 418, and 420. In a running example, the I mixer 5〇4 mixes the j component of the inbound or out signal with the local oscillator (eg, the component is mixed to produce the I-mixed signal. The I mix buffer cache) The frequency signal will be buffered by the frequency ## length: supplied to the FTBPF module 412. Similarly, the Q mixer will combine the Q component of the inbound RFk number with the local oscillation (eg, fL 〇 2 = fRp - heart) The q component is mixed to produce a Q-mixed signal. The q-mixer buffer buffers the Q-mixed signal and provides the buffered Q-mixed signal to the FTBPF module 412. The FTBPF412 provides a high-Q (quality factor) IF filter. The filter filters the inbound IF signal (eg, the I and q mixed signals) such that the desired signal component of the inbound positive signal is transmitted substantially un-attenuated and the undesired signal components (eg, block, mirror, etc.) are attenuated. Implementing the filter, the baseband impedance (Ζββφ) 414, 416, 418, and 420 together provide a low q baseband filter with a baseband filter response. Each of the baseband impedances can be a capacitor, a switched capacitor filter, or a switched capacitor resistor. And / or complex impedance. Note that the impedance of each baseband impedance can be the same, different, or a combination thereof. Also note the impedance of each baseband impedance

The 75 S 201212553 can be adjusted by control signals from the SOC processing resources to adjust the performance of the low Q baseband filter (eg bandwidth, attenuation rate, quality factor, etc.). The low frequency baseband filter of the frequency offset is converted to a desired IF frequency by a clock signal provided by the clock generator 510 to produce a high frequency filter with frequency offset. Fig. 51 shows the frequency conversion of the low-frequency (four-wave) to frequency-shifted high QIF filter, and Fig. 50 shows an example of the clock generator 51. As shown in Fig. 50, the clock The generator 51A (the various embodiments of which will be described with reference to at least one of the following figures) produces four clock signals, each having a 25% duty cycle and sequentially phase shifting by 9 〇. The frequency of the clock signal corresponds to The carrier frequency of the inbound IF signal can be adjusted to better track the carrier frequency. The clock generator 510 can also generate a local oscillator clock signal (not shown) that is used to downconvert the inbound RF signal to the inbound IF. Signal (example *L〇2). Alternatively, at least the -_ clock signal of the 'FTBPF 412 can be used as the L〇 clock signal. Returning to the discussion of Figure 49, the FTBPF 412 receives the clock signals that are connected to the transistors in sequence. Connect their respective baseband impedances to the inbound IF signal. Since the clock rate is at IF (eg carrier frequency of the desired component of the inbound positive signal) 'baseband impedance response (low q bandpass filter common) is transferred to IF (and / Or L02) to achieve high Fig. 52 is a schematic diagram of a portion of an RF-IF receiver section including an IF FTBPF module 530. RX RF-IF section in accordance with another embodiment of the present invention. This part includes the j and q _ positive mixers and the mixing register. The IF FTBPF 530 module includes a differential if FTBPF 530 and other registers. The differential EFFTBPF 530 includes multiple transistors and multiple baseband impedances ( Example 76 201212553 eg ZbB(s). In an operational example, I mixer 522 mixes the I component of the inbound RF signal with the j component of the local oscillation (eg, fL 〇 2 = fRF _ know 52 〇) The frequency is used to generate an I-mixed signal. The I-mix buffer 522 buffers the j-mixed signal and provides the buffered I-mixed signal to the FTBPF 53A module. Similarly, the Q mixer 523 will inbound RP. The q component of the signal is mixed with the Q component of the local oscillation (eg, &=heart-known 521) to produce a Q-mixed signal. The Q-mix register 523 buffers the Q-mixed signal and mixes the buffered Q. The frequency signal is provided to the FTBpF 53〇 module. The FTBPF 530 provides a high Q (quality factor) filter that crosses the inbound IF signal (eg ϊ and q) The mixed signal) makes the expected signal component of the inbound π signal substantially unaffected by the ship and the difficult money component (such as block, mirror, etc.) is attenuated. To achieve _, wave H, baseband impedance ~ kiss) said, 534 536, 538, 540, 542, 544, and 546 together provide a low Q baseband chopper [wherein each baseband impedance can be a capacitor, a switched capacitor, a switched capacitor, and/or a complex impedance, respectively. Note that the impedance of each baseband impedance can be the same, not or a combination thereof. Note that the impedance of each baseband impedance can be adjusted by a control signal from the SOC processing resource to adjust the performance of the low Q baseband ( For example, bandwidth, attenuation rate, product f factor, etc.). The low Q filter of the speech offset is converted to the desired IF frequency by the clock generation ϋ provided clock domain to produce a frequency offset high Q IF data filter. The clock generator 55A shown in FIG. 53 (the various embodiments of which will describe at least the towel) will generate eight clock signals, each clock signal having a duty cycle of 12.5% and phase shifting in sequence. . The frequency of the clock signal corresponds to the carrier frequency of the 77 201212553 inbound IF signal and can be adjusted to better track the carrier frequency. The clock generator 550 can also generate a local oscillator clock signal (not shown) for downconverting the inbound RF signal to an inbound positive signal (e.g., £2). Alternatively, at least one clock signal of the 'FTBPF' can be used as a clock signal. Returning to the discussion of Figure 52, the FTBPF 530 receives clock signals that are coupled to the transistors to sequentially connect their respective baseband impedances to the inbound IF signals. A high-qif bandpass filter is implemented because the clock rate is shifted to IF (and/or L02) at the IF (eg carrier frequency of the desired component of the inbound jitter signal) 'baseband impedance response (low q bandpass filter common) . Figure 54 is a schematic block diagram of a portion of a receiver portion including a single-ended FTBPF 56 (frequency band pass filter) and a single-ended FTBPF 560 including a negative resistance, in accordance with one embodiment of the present invention. This part of the RX RF-IF section includes transformers, variable capacitor networks, and LNAs. The FTBPF 560 includes a plurality of transistors and a plurality of baseband impedances (ZBB(S)) 562, 564, 566, and 568. In an operational example, a front end module (FEM) 39 receives an inbound RF signal through an antenna and processes the RF signal in accordance with the above and/or will be described with reference to at least one of the following figures, and the FEM 39〇 The processed inbound RF signal is provided to the transformer. The voltage level at which the transformer raises or lowers the inbound chirp signal is then followed by the Weirong network. Note that the material needs to be adjusted for the level of the inbound RF signal and/or the separation provided by the transformer is not required. Then the transformer can be omitted. The FTBPF 560 provides a high Q (quality factor) RF filter that causes the desired signal component of the inbound or out signal to be substantially un-attenuated to the LNA 392 and unwanted signal components (eg, block, mirror 78) 201212553, etc.) attenuation. In order to implement the chopper, the baseband impedances (Zbb(8)) 562, 564, 566, and 568 together provide a low q baseband filter, where each baseband impedance can be a capacitor, a switched capacitor, a H, a closed capacitor, or a complex impedance. . = Meaning, the impedance of each baseband impedance can be phase_, different, or a combination thereof. Also note that each baseband impedance response can be adjusted by a control signal from the s〇c processing resource to adjust the performance of the low Q baseband (eg, bandwidth, attenuation rate, quality factor, etc.). In addition, 'FTBPF 560 includes negative resistance (such as _2R) to compensate for inductance loss, compensate for switching secrets and / or improve the selectivity of low q-band servos and / or quality factor negative resistance can be implemented as shown in Figure 56 That includes multiple transistors. The low Q-based (qua) wave is converted to the desired RF frequency by a clock signal provided by the clock generator to produce a high QRp ferrite. A clock generator as shown in FIG. 55 (various embodiments of which will be described with reference to at least one of the following figures) generates a clock city' each clock signal having a 25% null ratio and sequentially phase shifting 90 乂 clock signal The frequency corresponds to the carrier frequency of the signal at the inbound, and can be adjusted (4) to better track the carrier frequency. The clock generator can still generate a local clock signal (not shown) that is used to downconvert the inbound RF signal to an inbound IF signal. ▲ Returning to the discussion of Figure 54, the FTBPF receives the clock signals that are connected to the transistors to sequentially connect their respective baseband impedances to the inbound signals. The high QRF bandpass ferrite is achieved because the clock rate is at (e.g., the carrier frequency of the desired component of the inbound RF signal) ' baseband impedance response (low Q bandpass filter) is transferred to RF'. Figure 57 is a schematic block diagram of a portion of the RF-IF receiver section 79 201212553, which includes a differential FTBPF 580 (frequency bandpass filter), and the differential FTBPF 580 includes a negative resistance, in accordance with an embodiment of the present invention. Rxrpjj: This part of the section includes the transformer, variable capacitor network, and LNA 393. The differential FTBPF 580 includes a plurality of transistors and a plurality of baseband impedances (Zbb(8)). In one operational example, the front end module (FEM) 390 receives the inbound RP signal through the antenna 'processes the RP signal as described above and/or will be described with reference to at least one of the following figures, and processes the FEM 39〇 The inbound k number is provided to the transformer. The voltage level at which the transformer raises or lowers the inbound signal is then chopped by the variable capacitance network. Note that the transformer can be omitted if the voltage level of the inbound RF signal does not need to be adjusted and/or the separation provided by the transformer is not required. The FTBPF 580 provides a high Q (quality factor) RF filter that filters the inbound RF signal such that the desired signal component of the inbound RP signal is substantially un-attenuated to the LNA 393 and undesired signal components (eg, Hysteresis, mirroring, etc.) attenuation. To achieve this filter, the baseband impedance (ZBB(s)) together provides a low Q baseband filter, where each baseband impedance can be a capacitor, a switched capacitor filter H, a switched capacitor resistor, and/or a complex impedance, respectively. Note that the impedance of each baseband resistance = can be the same, not _ or a combination thereof. Note also that the acknowledgment of each base W can be adjusted by the control signal from the SQC processing resource to adjust the performance of the low Q-based (four) wave (eg, bandwidth, attenuation rate, quality factor, etc.). / outside 'F talks include negative resistance (such as at the location) to compensate for inductance losses, _ open_loss and / or improve the selection and / or quality factor of the low Q band. The negative resistance can be implemented as shown in FIG. 201212553 ▲ The low Q baseband filter is frequency converted to the desired RF frequency by a clock signal provided by clock generator 582 to produce a high QRF filter. A clock generator 582, as shown in Figure 58 (which various embodiments will be described with reference to at least the following figures), generates four clock signals, each having a 25% duty cycle and sequentially phase shifted by 90. . The frequency of the clock signal corresponds to the carrier frequency of the signal at the inbound and can be adjusted to better track the carrier frequency. The clock generator 582 can also generate a local oscillator clock signal (not shown) for downconverting the inbound RF signal to an inbound IF signal. Returning to the discussion of Figure 57, the FTBPF 580 receives clock signals that are connected to the transistors to sequentially connect their respective baseband impedances and inbound numbers. Since the clock rate is shifted to RF at the RP (e.g., carrier frequency of the desired component of the signal at the inbound), the baseband impedance response (low q bandpass filter) is transferred to the RF, thereby implementing a high QRF bandpass filter. Figure 59 is a schematic block diagram of a portion of a positive-receiver portion including a dual-band FTBPF (Frequency Bandpass Filter) 5 90 ° RX RF-IF portion including a transformer, in accordance with another embodiment of the present invention Variable capacitance network and LNa 392_1 and 392-2. The FTBPF 590 includes a plurality of transistors and a plurality of baseband impedances (ZBB(s)) 592, 594, 596, and 598. In an operational example, a front end module (FEM) 39A receives dual band inbound RF signals (e.g., 5^ and f^2) through an antenna, as described above and/or with reference to at least one of the following figures. The Rp signal is processed in a manner, and the FEM-processed inbound rf signal is supplied to the transformer. The transformer raises or lowers the voltage level of the inbound RF signal, which is then filtered by the variable capacitor network Ci. Note that the transformer can be omitted if the voltage level of the inbound RJT signal does not need to be adjusted and 201212553 / or the separation provided by the transformer is not required. The FTBPF 590 provides two high-Q (quality factor) RP filters (one with fRF1 as the center frequency and the other with fRF2 as the center frequency). These filters consider the inbound RF signal to make the desired signal for the dual-band inbound RF signal. The components are transmitted to the LNAs 392-1 and 392-2 substantially un-attenuated and the unwanted signal components (e.g., block, mirror, etc.) are attenuated. The two high QRF ferrites are formed by a plurality of baseband impedances (ZBB(s) 592, 594, 596, and 598) and a plurality of transistors, wherein each baseband impedance includes a plurality of additional baseband impedances (eg, Zbb, (8) 592, 594 , 596 and 598) and a plurality of other transistors. A plurality of other baseband impedances (ZBB'(s) 592, 594, 596, and 598) provide a low Q baseband filter, wherein each of the other plurality of baseband impedances may be a capacitor, a switched capacitor filter, a switched capacitor resistor, and/or Or complex impedance. Note that the impedance of each baseband impedance can be the same, different, or a combination thereof. Also note that the impedance of each baseband impedance can be adjusted by control signals from the S〇C processing resources to adjust the performance of low Q baseband ships (eg, bandwidth, attenuation rate, quality factor, etc.). The low Q baseband filter is converted to the desired frequency (e.g., fDK〇2)/2 by the clock generation n _ providing (four) clocks (freshly fD) to produce the 冋QRF test. As shown in FIG. 6G, the clock generator _ (its various implementations (four) are at least __目目) generates 4 clock signals 2 such as L〇wlq'4), and each clock signal has a continental short-sell ratio And subtracting the second frequency band 丨μ of the inbound RF signal (for example, or W) according to the frequency of the clock signal corresponding to the carrier frequency of the first frequency band of the inbound m signal (eg, fj^p丨 or vt, ^ L〇l) The difference is 1/2 and can be adjusted 82 201212553 to better match at least the carrier frequency. = the first plurality of transistors are synchronized with the rate _ 〇 ( 4 (generated by the clock generator), formed by the first plurality of baseband impedances, = the same Q RF filter is converted to a higher desired Rf frequency Among them, 5 61 * city (10) soil was converted to call. Therefore, the response of the 'first-high Q-band pass wave: (f) is the center frequency, and the third-order harmonic is also shown. Referring to the diagram magic, ^ a Q-bandpass filter is frequency converted to fc and fc% to produce two: ^^11 ° ^ +W/2 ^ f〇=(fL01 .fL02)/2 , fc - plant L02 , fc +fD=L01. Therefore, one of the high Q bandpass filters is centered on (10) or %2, and the other high Q bandpass filter is centered on L01 (or fRF1). Therefore, the frequency of the inbound RF signal passing through the inbound RF signal is L02 (or %2), and the frequency of the second high Q bandpass filter passing the inbound RF signal is L01 (or fRpi). Expected signal component. Figure 63 is a block diagram of a portion of a muscle positive receiver portion including a dual band differential FTBPF (Frequency Bandpass Filter) 610°RXRF_IF portion including a transformer, a variable capacitance network, in accordance with another embodiment of the present invention. Road and LNA 393-1 and 393-2. The FTBPF 610 includes a plurality of transistors and a plurality of baseband impedances (ZBB(s)) 612, 614, 616, and 618. In an operational example, a front end module (FEM) 39 receives a dual band inbound RF signal (e.g., and fRF2) through an antenna, and processes the RP in accordance with the above and/or as described with reference to at least one of the following figures. The signal is supplied to the transformer Ή after the FEM processed inbound Rjp signal. The transformer converts the inbound RF signal into a differential inbound rf signal. 83 201212553 FTBPF 610 provides two high Q (quality factor) Rp filters (one with fRF1 as the center frequency and the other with the center frequency). These tear filters filter the inbound RF signal to make the desired signal for the dual band inbound RF signal. The amount of attenuation is transmitted to the LNAs 393_1 and 393-2 without attenuation and unwanted signal components (eg, block, mirror, etc.) are attenuated. The two high QRJF viewers are formed by a plurality of baseband impedances (ZBB(S) 612, 614, 616, and 618) and a plurality of transistors each of which includes a plurality of additional baseband impedances (eg, Zbb, (8) 612, 614 , 616 and 618) and a plurality of other transistors. A further plurality of baseband impedances, (8) 612, 614, 616 and 618) provide a low Q baseband chopper, wherein each of the additional baseband impedances may be a capacitor, a capacitance vessel, a switched capacitor resistor and/or an anti-resistance, respectively. Note that the impedance of each wire impedance can be the same, different, or a combination thereof. Also note that the impedance of each baseband impedance can be adjusted by control signals from the SQC processing resources to adjust the performance of the low q baseband filter (e.g., bandwidth, attenuation rate, quality factor, etc.). " The clock signal (frequency &) provided by the clock generator 6GG converts the low q baseband filter to the desired RF frequency (eg, fD=(WW2), produces a 冋QRF filter. As shown in Figure 6〇 The clock generator _ (its various implementations of the fiber reference at least - the edge of the money) generates 4 clock signals (such as LO to l 〇 '4) 'Each clock signal has a 25% open ratio and phase shift 90 The frequency of the clock signal corresponds to the inbound carrier frequency (eg w, fL.,) minus the input (four) signal: the carrier frequency of the two (eg "or") is 1/2 of the difference and can be adjusted To better track at least one carrier frequency. Since the first plurality of transistors are synchronized with L0]-L04 (generated by the clock generator as shown in Fig. 6〇20122012553) of the rate fc, by the first plurality of basebands The impedance-formed high Q RF filter is frequency converted to a higher desired Rf frequency, where fc = (fLO 丨 + fL 〇 2) / 2. Therefore, one of the high Q bandpass filters is l 〇 2 (or fRF2) Centered on 'another high Q bandpass filter centered around L01 (or heart). Therefore, the first high Q bandpass filter is The frequency of the inbound RF signal is the desired signal component of L02 (or fRF2), and the second high Q bandpass filter passes the desired signal component of the frequency of L01 (or f^pi) through the inbound RF#. Figure 64 is based on A schematic block diagram of a portion of an rf-IF receiver portion of another embodiment of the present invention includes a transformer, a variable capacitance network, a pair of inverter-based LNAs 395, a mixer, and an output register (or Unity Gain Driver) The mixer consists of multiple transistors, a pair of transimpedance amplifiers (TIAs) 622 and 624 and the accompanying impedances (Z) 626 and 628. In one running example the 'LNA 395 is supplied to the mixer. Differential current (iRF and -irf). In the current domain, the mixer mixes the differential current with the local oscillator's differential 1630 component (LOjp and LOnJ to produce an I-mixed current signal. The mixer also The differential current is mixed with the differential Q 632 component (LOqp and LOqn) of the local oscillation to produce a q-mixed current signal. The first TIAs 622 and 624 amplify the I-mixed current signal through the associated impedances (z) 626 and 628, And generate a signal in the voltage domain 丨 mixing. Similarly, the second TIA pass The correlated impedances (z) 626 and 628 amplify the Q-mixed current signal and produce a voltage domain Q-mixed signal. Figure 65 is a clock generator 634 for a local-positive receiver portion in accordance with another embodiment of the present invention. A schematic block diagram of the clock generator (the various embodiments of which will be described with reference to at least one of the following figures) produces four clock signals (example 85 201212553 such as LO[P, LOIN, LOqP and L〇QN), each The clock signals have a 25% duty cycle and are phase shifted by 90 in sequence. . Figure 66 is a schematic block diagram of a transimpedance amplifier (ΉΑ) and corresponding impedances (Z) 640 and 642, in accordance with one embodiment of the present invention. The TIA includes a current source, a frequency dependent amplifier (-A(8)), an IF transistor (TIF), and a low frequency transistor (TLF). The corresponding impedance in each output pin of the TIA includes resistors, capacitors, and transistors. In a running example, the differential input current is received at in_ and in+. Current node analysis of the negative input node (eg KCL-Kirch〇ff current law) shows that the current source current (ib) is equal to the input current (丨,) + the current through the capacitor (ic) + through The current of tif (i0UT) + the current through Tlf. The positive input (out+) KVL (Kirchhoff voltage law) shows that the output voltage (V〇ut+) is equal to Vdd_z*I〇UT (ie, the current through & At two frequencies (e.g., higher than the rRp of the inbound RF signal), the impedance of the capacitor becomes dominant and the input is substantially reduced; therefore, the output current (i〇uT) does not substantially contain the chirp component. At low frequencies (e.g., lower than the rj^ of the inbound Rp signal), the amplifier and low frequency transistors are configured for the TIF, and the low frequency current T [F is essentially open. This can be achieved by changing the size of the transistor and biasing the amplifier so that the impedance of the TLF at low frequencies is much smaller than the frequency of z+T1F 〇 for the desired frequency range (eg fRF), the impedance compared to the corresponding impedance Z 640, 642 Capacitors and TLFs have higher impedance. Therefore, iOuTHb-' and v〇UT=Z*i〇UT. Accordingly, ΉΑ and the corresponding impedance z 64 〇, 642 can be tuned to provide a high Q RF bandpass filter. Note that at least one component of the TIA can be adjusted by the control signal provided by the S0C processing resource to adjust the performance of the high Q bandpass filter. Figure 67 is a schematic block diagram of a low noise amplifier (LNA) 670 that includes FTBPFs 650, 672, 674, and 678, in accordance with one embodiment of the present invention. The LNA 670 includes a current source, a pair of input transistors (T3 and T4), a pair of bias transistors (Τ1 and Τ2), and an output impedance (showing the resistance, but can also be an inductor, a transistor, a capacitor, and/or Combinations. Note that the current source can be replaced by passive devices (such as resistors, inductors, capacitors, and/or combinations thereof) or can be omitted. The FTBPFs 650, 672, 674, and 678 can be located anywhere in the LNA 670 as shown. Figure 68 is a schematic block diagram of a differential 4-phase FTBPF (frequency conversion bandpass; filter) 680 comprising a plurality of transistors and 4 baseband impedances (e.g., ζββ(8)) 682, 684, 686, in accordance with one embodiment of the present invention. And 688. Baseband impedance (zbb(s)) 682, 684, 686, and 688 together provide a low Q baseband filter, where each baseband impedance can be a capacitor, a switched capacitor filter, a switched capacitor resistor, and/or a complex impedance, respectively. Note that the impedance of each baseband impedance can be the same, different, or a combination thereof. Also note that the impedance of each baseband impedance can be adjusted by the control ship from the processing resource, from the low Q baseband chopper of the butterfly performance Such as bandwidth, attenuation rate, quality factor, etc.).

The low Q baseband chopper is frequency converted to the desired RF frequency by a clock signal provided by the clock generator (eg, l〇i_l〇4) to produce a high Q or positive chopper differential two Q RF chopper filter differential or The IF signal causes the desired healthy component of the positive or positive signal to be substantially un-attenuated and the signal component of the complement (eg, block, mirror, etc.) is attenuated. Figure 69 is a diagram showing the response of the frequency of the 4-phase FTBpF _ 87 201212553, which shows the signal feedthrough and the superimposed signal read wave, in accordance with one embodiment of the present invention. The signal feedthrough harmonics 692 are at +/-3, +/·5, +/_7, and 仏9, and the superimposed signal harmonics 69〇 are at -3, -5, -7, and -9. FIG. 70 is another according to the present invention. A schematic block diagram of a 3-phase (frequency-converting bandpass chopper) of one embodiment 'which includes a finned transistor and three baseband impedances (e.g., ZBB(8)) 702, 704, and 7〇6. The baseband impedance (^(9)) 7〇2, 7〇4, and 7〇6 together provide a low-q baseband chopper, where each baseband impedance is divided into a valley, a switched gate, a switched capacitor, and/or Complex impedance. Note that 'each wire impedance _ anti-coherent phase _, not _ or a combination thereof. Also, the impedance of the baseband impedance can be adjusted by the control signal from the s〇c processing resource to adjust the performance of the low Q baseband filter (eg, bandwidth, attenuation rate, quality factor, etc.). The low Q baseband filter is frequency converted to a desired, i.e., frequency, by a clock signal (e.g., LCVLOa) provided by the clock generator as shown in Figure 71 to produce a high QRF or IF filter. The differential high-qrp filter chopping difference, or 圧 signal, makes the thief-receiving of the RF cake money substantially untransferred and the expected signal components (such as block, mirror, etc.) are attenuated. Figure 72 is a schematic illustration of the frequency response of a 3-phase FTBpF 7 , showing signal feedthrough harmonics and superimposed signal harmonics, in accordance with one embodiment of the present invention. The signal feedthrough harmonics 708 are at +/- 5 and +/- 7, and the superimposed signal harmonics 710 are at 5 and 7. Figure 73 is a schematic block diagram of a 4-phase FTBPF (frequency conversion band pass filter) 712 comprising a plurality of transistors and 4 capacitors in accordance with another embodiment of the present invention. These capacitors together provide a low Q baseband filter. Note that the capacitance of each capacitor can be the same, different, or a combination thereof. Also note that the capacitance of each capacitor, S8 201212553, can be adjusted by control signals from the SOC processing resources to adjust the performance of low Q baseband ships (eg, bandwidth, attenuating materials, quality factors, etc.). The wire chopper provided by the clock generation H (e.g., (1) can) converts the wire chopper to a desired frequency, i.e., to produce a high Q or a chopper. The differential high-Q RF chopper is based on the difference or positive signal so that the expected money component of the shrimp or positive signal is transmitted substantially un-attenuated and the desired signal component (e.g., block, mirror, etc.) is attenuated. 74 is a schematic diagram of a 4-phase FTBpF (frequency conversion pass filter) 714 according to another embodiment of the present invention, which includes a multi-crystal crystal and a disc-shaped contact lens as shown in the figure (for example, Zbb(s) ). The substrate (8) 舳 provides a low Q basis. For example, the impedance phase of each wire can be I valley, switched capacitor filter, switched capacitor resistance and/or complex impedance. Note, the baseband impedance hybrid impedance can be _, different or a combination of = meaning, the impedance of each baseband impedance can be adjusted by the control k from the s〇c processing resource, thereby adjusting the low Q Baseband filter performance (example ^, attenuation rate, quality factor, etc.). To see, the clock signal provided by the clock generator (for example, the L〇i baseband chopper is converted to the desired RP frequency to generate a high Q egg or H. The differential high Q RF waver chop difference or IF signal makes 卯The number of the new number of the slogan is basically unsuccessful and is not expected.

Attenuation (eg block, mirror, etc.). H, FIG. 75 is a schematic block diagram of a 4-phase FTB filter 716 according to another embodiment of the present invention, which includes a plurality of transistors and 4 basebands: (for example, zBB(8)). The baseband impedance (Zbb(8)) provides a low q-base wave. The 2012 baseband impedance can be a capacitor, a switched capacitor chopper, a switching capacitor resistor, and/or a complex impedance. Note that the impedance of each baseband impedance can be the same, different, or a combination thereof. Also note that the impedance of each baseband impedance can be adjusted by control signals from the SOC processing resources to adjust the performance of the low Q-based f-chopper (e.g., bandwidth, attenuation rate, quality factor, etc.). The low q baseband filter is frequency converted to the desired RF frequency by a clock signal provided by the clock generator (e.g., L0rL04) to produce a high Q or positive filter. The differential Q RF chopper clamps the differential Rp or ip signal such that the desired signal component of the Rp or positive signal is transmitted substantially un-attenuated and the unwanted signal components (e.g., block, mirror, etc.) are attenuated. Figure 76 is a schematic block diagram of a 4-phase ftbpf (frequency conversion bandpass filter) 720 comprising a plurality of transistors and a plurality of complex baseband impedances (e.g., ZBB, c(co)) 722, in accordance with another embodiment of the present invention. The complex baseband impedance provides a low Q baseband filter, which is offset from zero by w〇C. Note that the complex baseband impedance can be performed by the control _ number from the s〇c processing resource, thus the performance of the low Q baseband chopper (such as bandwidth, attenuation rate, quality factor, frequency offset, etc.). The low Q baseband filter is converted to the desired RF frequency by a clock signal (e.g., 1〇1丄〇4) provided by the clock generator to produce a high Q or positive filter. The differential 咼QRF filter filters the difference or positive signal such that the desired signal component of the positive or positive signal is transmitted substantially un-attenuated and the undesired signal component (e.g., block, mirror, etc.) is attenuated. Figure 77 is a schematic block diagram of the complex baseband impedance of a secret FTBpF (frequency band pass filter) in accordance with an embodiment of the present invention. The complex baseband impedance 726 includes a first baseband impedance (e.g., Zbb (10)), a negative gain stage (e.g., -jGm(co)V1M(co)), a 201212553 second baseband impedance (example #Zbb(0)), and a positive selection (10). Therefore, the multifilament impedance includes real numbers = (yang and imaginary = Μ). The complex baseband impedance is provided as a curve representation with a frequency response as shown in the figure, where the real component is represented by the curve of (4) and the imaginary component is w<0. Figure 78 is a schematic illustration of a 4-phase pulse (frequency bandpass filter) according to one embodiment of the present invention. It includes a complex baseband impedance that is achieved by capacitance. The complex baseband impedance provides a low q-wave ferrite 73〇 which is offset relative to w〇C, which is dependent on the ratio between the gain (Gm) and the capacitive impedance (Cbb). Note that the complex baseband impedance can be used to control the performance of the low-Q baseband n (such as bandwidth, attenuation rate, quality factor 'frequency offset, etc.) by the control signal from the s〇c processing resource. For example, the capacitance and/or gain module can be adjusted. The frequency offset low Q baseband filter is frequency converted to the desired or frequency to produce a high QRF or IF filter by a clock signal provided by the clock generator (e.g., L01_L04). The differential high Q or filter, wave chop differential RF or IF signal attenuates the RF or _ _ 黯 component substantially un-attenuated and undesired signal components (eg, block, mirror, etc.). Figure 79 is a schematic illustration of a melon phase FTBpF (frequency conversion band pass filter) 732 comprising a plurality of transistors and claw capacitors, wherein m - > 2, in accordance with one embodiment of the present invention. Each capacitor together provides a low Q baseband detector. Note that the capacitance of each capacitor can be the same, different, or a combination thereof. It should also be noted that the valley value of each electricity valley can be adjusted from the SC) C processing resource control bank, so that the performance of the low Q base (four) wave | | (such as bandwidth, attenuation rate, product 201212553 quality factor Wait).

The low Q baseband filter is frequency converted to the desired RP frequency by a clock signal (eg, called) provided by the clock generator to produce high q Μ or positive filtering

Device. The chopper filter, wave differential RF or IF signal at the differential high Q causes the desired signal component of the RF or IF signal to pass substantially un-attenuated and the unwanted signal components (e.g., block, mirror, etc.) to decay. Figure 80 is a schematic illustration of a melon phase FtbPF (frequency conversion bandpass chopper) 734 according to the present invention, which includes a plurality of transistors and m baseband impedances (e.g., ZBB(S)). An integer multiple of 4 and greater than $. The baseband impedance (ZBB(s)) together provides a low q baseband ferrite, where each baseband impedance can be electrically coupled to a switching electric chopper, a switched capacitor resistor, and/or a complex impedance. Note that the impedance of each baseband impedance can be the same, different, or a combination thereof. It is also noted that 'each baseband impedance _ resistance can be adjusted by a control signal from s〇c processing resources' to adjust the performance of the low Q baseband chopper (e.g., bandwidth, attenuation rate, quality factor, etc.). The low q baseband chopper is frequency converted to the desired RP frequency by a clock signal (e.g., l〇i_l〇m) provided by the clock generator to produce a high Q or positive filter. The differential number component and the differential Q signal component of the differential high QRF chopper wave IF signal cause the desired domain component of the LF domain to pass substantially un-attenuated and the unwanted signal components (e.g., block, mirror, etc.) to decay. Figure Si is an illustration of an m-phase ftbpf (frequency conversion bandpass filter) 736 according to an embodiment of the present invention, which includes a plurality of transistors and m/2 baseband impedances (e.g., zBB(s)), where m is greater than Equal to 4. The baseband impedance (Μ) provides a low Q baseband filter, where each baseband impedance can be a capacitor, 92 201212553 switched capacitor, n, _ capacitor, and/or complex impedance. Note that the impedance of each baseband impedance can be the same, not _ or a combination thereof. Also note that the impedance of each baseband impedance can be adjusted by the control from s〇c processing Wei' to adjust the performance of the low Q baseband filter (eg, bandwidth, attenuation, quality factor, etc.). The clock signal generated by the clock generation (eg, called) converts the low Q baseband ferrite to the desired RF frequency to produce a high Q or positive filter differential Q RF; the filter filters the differential RP or IF signal such that That is, the expected money component of the positive signal is substantially non-aged and the signal component (eg, block, mirror, etc.) is attenuated. Figure 82 is a schematic block diagram of a m-phase FTBpF (frequency-converting bandpass ferrite) 738, which includes a plurality of transistors and m baseband impedances (e.g., ΖβΒ(8))' where m is greater than or equal to two, in accordance with one embodiment of the present invention. The baseband impedance (Zbb(s)) together provides a low Q wire H', which can be a capacitor, a switched capacitor ship H, a _capacitor resistor, and/or a complex impedance, respectively. Note that the impedance of each baseband impedance can be the same, different, or a combination thereof. Also note that the impedance of each baseband impedance can be adjusted by control signals from the soc processing resources to adjust the performance of the low Q baseband filter (e.g., bandwidth, attenuation, quality factor, etc.). ~ The clock signal provided by the clock generator (eg L0rL04) is used to convert the low Q baseband filter to the desired RF frequency to produce a high Q or IF filter difference is 咼Q see 7 filter, wave 泸, wave differential RF or The IF signal causes the desired signal component of the Rp or if apostrophe to pass substantially un-attenuated and the undesired signal component (eg, block, mirror, etc.) to decay. 93 201212553 FIG. 83 is a schematic block diagram of a single-ended m-phase ftbpf (frequency conversion bandpass filter) 740 including a plurality of transistors and m baseband impedances (eg, ZBB(8)), wherein the jaws are greater than or equal to one, in accordance with an embodiment of the present invention. 2. The baseband impedance (Zbb(8)) together provides a low Q baseband filter, where each baseband impedance can be a capacitor, a switched capacitor filter, a switched capacitor resistor, and/or a complex impedance, respectively. Note that the impedance of each baseband impedance can be the same, different, or a combination thereof. It is also noted that the impedance of each baseband impedance can be adjusted by the control signal from the S〇c processing resource' to adjust the performance of the low q baseband filter (e.g., bandwidth, attenuation rate, quality factor, etc.). The low Q baseband filter is frequency converted to the desired RF frequency by a clock signal provided by the clock generator (e.g., L〇1_l〇4) to produce a high Q or IF filter. The differential high QRF filter filters the differential RF or positive signal such that the desired signal component at or at the positive signal is transmitted substantially un-attenuated and the unwanted signal components (e.g., block, mirror, etc.) are attenuated. Figure 84 is a schematic illustration of the frequency response of the claw phase FTBPF 740, which illustrates the low Q band pass filter being frequency converted to a higher frequency (e.g., fL0), in accordance with one embodiment of the present invention. fLO corresponds to RF frequency, positive frequency, local oscillation or a combination thereof. Figure 85 is a schematic block diagram of a clock generator 750 for m-phase ftbpf, in accordance with one embodiment of the present invention. The clock generator includes a plurality of flip flops (DFF) 752, 754 and 756 and a plurality of pulse narrowers (pulse n_wer) 7S8, 760 and ? 62. The flip-flops 7S2, 754 and 756 are synchronized with a clock signal (elk) of rate m*fRp and a clock gate signal (clkb). The clock pulses obtained from each of the flip-flops 752, 754, and 756 are pulsed by the corresponding pulse constrictor 94 201212553. Pulse narrowers 758, 760 and 762 comprise two pairs of transistors connected as shown. The lower left transistor is smaller than the other transistors, making the rising edge time slower than the falling edge time, thereby narrowing the pulse. Figure 86 is a diagram showing the clock generation H 77G for the melon phase FTBpF in accordance with another embodiment of the present invention. The clock generator includes a plurality of flip flops (DFF) 772, 774, and 776 and a plurality of gates. The flip-flops 772, 774, and 776 are synchronized with a clock signal (dk) of rate (1/2) * m*fRF and a clock signal (clkb). The AND gate receives the non-inverted output from the first flip-flop and receives the inverted output from the lower-trigger H 774 to ensure that successive clock pulses do not overlap. The diagram is a schematic block diagram of a clock generation H 790 for a melon phase FTBpF in accordance with another embodiment of the present invention. The clock generator includes a ring oscillator 792 = and a plurality of circuits. Each logical path includes a rib or a register. The gate value of the ring oscillation H 792 is an odd number at the clock rate, which is equal to or greater than 3). Each logic circuit receives successive pulses from ring oscillator 792 such that successive clock pulses do not overlap. Figure 88 is a schematic block diagram of a clock generator 800$ for a 3-phase FTBpF that includes a ring oscillator 792 and a plurality of circuit circuits, in accordance with one embodiment of the present invention. Each of the circuits includes a combination of off and temporary pulses/or inverters. For example, each logic circuit includes a gate, an inverter, and a register. The gate of the ring oscillator 792 is clocked at 3*fRp. Through the logic circuit, the AND gate is biased to produce a 1/3 duty cycle non-overlapping clock (eg, dku〇2, elk 2 806, and elk 3 804). Figure 89A is a schematic block diagram of a 2012 810 generation H 810 for a 3-phase FTBpF, the clock generator including two ring oscillators 792 and a home gate. Each revolution circuit includes a combination of a register and/or a phase inverter. For example, each logic circuit includes a gate, an inverter, and a register. The gate value of the first-loop vibrator 792 is a clock rate of 3*fRF, and the gate value of the second ring oscillator 792 is inverted (inversi〇n) (for example, -3*ί^) of 3*ί^. In this configuration, as shown in Fig. 88, the clock signals 4-6 818, 820, and 822 are the inversion of the clock signal 丨-3, respectively. Figure 90 is a schematic block diagram of a portion of a front end module (FEM) 810 and a portion of a SOC 812, in accordance with one embodiment of the present invention. This portion of the FEM 81 包括 includes a power amplifier module (PA) 814, a duplexer, a balanced network 818, and a common mode sensing circuit. The duplexer includes a transformer (or other structure, such as a frequency selectable duplexer and/or an electronically balanced duplexer), and the balanced network 818 includes at least one variable resistor and a variable electrical valley. The common mode sensing circuit includes a pair of resistors connected between the secondary of the transformer. This portion of the SOC 812 includes a peak detector 82A, an engine 822, and a low noise amplifier module (LNA). Alternatively, peak detector 82A and/or tuning engine 822 may be located in FEM 810. In one operating example, the PA 814 provides an outbound RF signal to the center tap of the primary double coil of the transformer. Depending on the impedance difference between the antenna and the balanced network 818, the current of the outbound RF signal is shunted between the two coils. If the impedance of the balanced network 8 j 8 substantially matches the impedance of the antenna, the current is substantially evenly split to two coils. With the coil configuration as shown, if the primary coils are substantially equal in current, their magnetic fields in the secondary coils substantially cancel each other out. Therefore, the secondary outbound RF彳§ is basically attenuated. For inbound RF signals, the primary two 96 201212553 coils generate a magnetic field based on the current of the inbound RF signal. At this point, the magnetic field is increased, thus producing twice the current in the secondary relative to the primary (assuming each coil has the same number of turns). Therefore, the transformer amplifies the inbound Rp signal. If the antenna impedance does not match the impedance of the balanced network 818, an outbound RF signal current component (e.g., TX leakage) will appear in the secondary. For example, suppose the current flowing from the coil to the inductor is iP1, and the current flowing from the coil to the balanced network 8丨8 is h, then τχ, the amount can be expressed as iprip2. The common mode of the residual resistance induces the amount of τχ leakage. For example, the voltage at the center node of the resistor is equal to vs_(Hr+hra), where vs is the secondary voltage and 2iR is the current of the received inbound RF signal. Assuming Ri = R2 and ipi = ip2, then the voltage at the center node is equal to 丨/2 of VS. If 1 ipi is not equal to -, the voltage at the center node of the resistor will deviate from 1/2 VS, and the amount of deviation is proportional to the difference. Detector 820 detects that the voltage at the center node of the resistor deviates from the difference of 1/2 ν § and provides an expression of the difference to tuning engine 822. The tuning engine 822 parses the difference and generates a control rib to adjust the flat-off impedance. For example, if iP1 > iP2, the voltage of the common mode sensing circuit (e.g., the center node of the resistor) will be greater than 1/2 VS, which indicates that the impedance of the balanced network 818 is too large. Thus, tuning engine 822 becomes a control signal to reduce the balance network 818 _ resistance. For another example, if ΐρι<ΐΡ2 ’ then the voltage of the common mode sensing circuit will be less than 1/2 VS, which means that the impedance of the balanced network is too small. Thus, the engine 822 domain control signal is added to increase the impedance of the balanced network 818. The metrology engine 822 can resolve the common mode voltage deviation, determine the desired impedance of the balanced network 818, and generate control signals accordingly. Alternatively, the phasing engine illusion 2 can repeatedly generate control signals such as step by step _ 纟 818 818 818 818 818 818 818 818 818 818 818 818 818 818 2012 2012 2012 2012 2012 2012 2012 2012 2012 Using any method, the function of the tempering engine 822 = the drum _ impedance of the balanced network 818 is substantially matched (ik changes in time, usage, and/or environmental conditions) to minimize the amount of leakage. Figure 91 is a schematic block diagram of a portion of a front end module (fem) and a portion of a SOC 832 in accordance with another embodiment of the present invention. This portion of the FEM 83A includes a Power 2 Module (PA) 836, a duplexer 838, a balanced network 842, an antenna tuning single το (ATU) 840, and a common mode sensing circuit. Duplexer 838 includes a variator (or other structure, such as frequency selectable duplexer 838 and/or electronically balanced duplexer 838). The balanced network includes at least one variable resistor and at least one variable capacitor. The common mode sensing circuit includes a pair of resistors connected between the secondary of the transformer. This portion of the S 〇 C 832 includes a peak detection H 848, a tuning engine 850, a look up table (LUT) 844, a processing module 846, and a low noise amplifier module (LNA) 852. Alternatively, peak detector 848 and/or tuning engine 85A may be located in fem 830. In addition to the common mode sensing circuit (ie, resistor), detector 848, tuning engine 85, and balanced network 842 provide the function of balancing the impedance of the balanced network 842 with the antenna impedance (as described with reference to FIG. 9A). In addition, the FEM83〇 also includes the ATU 840. The ATU 840 includes one or more side-by-side passive components and/or one or more variable passive components. For example, the ATU 84 can include variable capacitance-inductor circuits, variable capacitors, variable inductors, and the like. In an operational example, ΡΑ 836 provides an amplified outbound signal to duplexer 838, which includes a transformer having the functionality as described with reference to the figures. The duplexer 838 outputs the amplified outbound signal to the ATU 84A, tuning the ATU 84A through the settings stored in the LUT 844 to provide the desired antenna matching 98 201212553 circuit (eg, impedance matching, quality factor, bandwidth, etc.) . The ATU 84 outputs the outbound RF signal to the antenna for transmission.

For an inbound RF signal, the antenna receives the signal and provides it to the ATU 840 which then provides it to the duplexer 838. The duplexer 838 outputs the inbound RF signal to the LNA 852 and the common mode sensing circuit. The functions of the common mode sensing circuit, the detector (10), the read engine mo, and the balanced network are as described above with reference to FIG. The processing module 846 is used to monitor various parameters of the FEM_. For example, the processing module 846 can monitor antenna impedance, transmit power, performance of the pA836 (eg, gain, linearity, bandwidth, efficiency, noise, output dynamic range, swing rate, rate of rise, build coffee, super woman, 敎Etc.), received signal strength, SNR, SIR, adjustments made by the tuning engine, etc. The processing module 846 parses these parameters to further optimize the performance of the deleted (four). For example, the processing module 846 can determine that adjusting the ATU 84 can improve the performance of the pA 836. At this point, the processing module _ addresses the LUT m to provide the desired setting for Xiao _. If this change in the ATU 840 affects the impedance balance between the thin _ and the 690 network, the modulo engine 85 will make the appropriate paving. In another embodiment, the processing module 846 provides the ability to adjust the balance of the ATU_ and balance network 842 to the performance of the FEM 830. In yet another embodiment, in the example embodiment, the balance network 842 is sturdy, and the ATU 840 provides the desired adjustment in the FEM 830 for the desired balance to obtain the desired impedance. The performance of the FEM 830. Figure 92 is a schematic block diagram of a portion of a front end module (FEM) 860 and a portion s C 862 for use in committing and committing bee writing, 2012-12553, in accordance with another embodiment of the present invention. This part of the FEM860 includes a power amplifier module (pA) 866, a duplexer, a balanced network, and a common mode sensing circuit. The duplexer includes a transformer (or other structure, such as a frequency selective double guard || and/or an electronic balance double guard), the flat path includes a switch, at least one variable resistor, and at least one variable capacitor. The common mode sensing circuit includes a pair of resistors connected between the secondary of the transformer. This portion of the s〇c 862 includes a peak detector 872, an engine 874, a switch, and a low noise amplifier module (LNA) 876. Alternatively, peak detector 872 and/or tuning engine 874 can be located in FEM 860. In this embodiment, the duplexer is best suited for Frequency Division Duplex (FDD), used in 3G cellular telephone applications and the balanced network switch and LNA 876 switch are open. In Time Division Duplex (TDD) for 2G cellular applications, the balance network is crossed by switches. This basically eliminates the 3_dB theoretical insertion loss limit and leaves only the implementation loss (implementati〇n丨〇ss). Note that for 2G transmission, the LNA876 switch is off, and for 2G reception, the LNA876 is turned on when the switch is turned on. Note also that for the 3G mode, the functions of the FEM and s〇c 862 are as described with reference to Figs. 90 and/or 91. Figure 93 is a schematic block diagram of a portion of a front end module (FEM) 860 and a portion of a SOC 862 shown in the 2G τ χ mode, in accordance with one embodiment of the present invention. In this mode, the LNA 876 switch shorts the LNA 876 and the balanced network switch shorts the balanced network. Due to the short circuit across the secondary coil, the primary coil is also substantially shorted. Therefore, the PA866 is efficiently connected directly to the antenna. Figure 94 is a schematic block diagram of a portion of a front end module (FEM) 860 and a portion S 〇c 862 of Figure 92 in an rx mode, in accordance with one embodiment of the present invention. 100 201212553 In this mode, the LNA gate network is shorted. In this: set; open change =, closed, so will be flat balun transformer. The function of the τ 颜 器 is as used for the receiver section. FIG. 95 is a block diagram of the small signal balancing network 880 according to the present invention __ dry dr +1 + ^ example, which includes a plurality of eel body , a resistor and a capacitor. The balance of the net object is called the whistle (9) (four) bit) into the balance _ t packet capacitance can be corrected - (four) bit signal 例如 (for example, 5 bits) for control. For example, if the resistance side of the balanced network includes four resistor-transistor circuits, the common node of the resistor-transistor circuit (c_onnode) is connected to the drain of the next resistor-transistor circuit. In this example, each ridge is also connected to receive a 4-bit bit control signal. For example, the gate of the leftmost resistor_transistor circuit receives the most significant bit, the next leftmost resistor-transistor circuit receives the first most significant bit, and so on. In addition, the resistance of the leftmost resistor-transistor circuit is R4, and the resistance of the next leftmost resistor_transistor circuit is R3, and so on. Thus, for example, when the 4-bit control signal is 〇001, only the rightmost resistor-transistor circuit is turned on, and its resistor R1 provides the final resistance. When the 4-bit control signal is 〇〇11, the two rightmost resistance-transistor circuits are turned on and the final resistance is R1//R2. When the 4-bit control signal is 0111, the three resistor-transistor circuits at the right end are turned on, and the final resistance is R1//R2//R3. When the 4-bit control signal is 1111, all four resistor-transistor circuits are turned on and the final resistance is R1//R2//R3//R4. The capacitive side function of the balanced network is similar. In another embodiment, each of the resistor-transistor circuit and each of the capacitors can be independently controlled by the bits of the respective control signals. The four-resistor-transistor circuit configuration 'control signal 1000' described in the above figures and modified herein produces a resistor R4; the control signal 0100 produces a resistor R3; the control signal 1010 produces a resistor R4//R2; and so on. Figure 96 is a schematic block diagram of a large signal balancing network 882 that includes an RLC (resistor-inductor-capacitor) network and a plurality of transistors, in accordance with one embodiment of the present invention. The transistor is gated on and off to provide a different combination of resistance, inductance and/or capacitance of the RLC network to achieve the desired balanced network impedance. At this point, the transistor has a relatively small voltage swing, so a lower voltage transistor can be used. Figure 97 is a schematic block diagram of a portion of a front end module (fem) and a portion SOC 892, in accordance with another embodiment of the present invention. This part of the FEM 890 includes Power Amplifier Module (PA) 896, Duplexer_, Balanced Network_, and Common Mode Inductor. Duplexer 898 includes a transformer (or other structure, such as frequency selectable duplexer 898 and/or electronically balanced duplexer _), and the balanced network includes at least one variable resistor and at least one variable capacitor. The common mode sensing circuit includes a pair of resistors connected between the secondary of the transformer. This portion includes a peak detector 〇2, a tuning engine 904, a leak detection 906 module, and a low noise amplifier module (LNA) 908. Alternatively, the peak detector 9 〇 2, the module and/or the machine guide (4) He Cong in the leg (four) towel. In addition to the leak detection (4) 9〇6 module, the function of this embodiment is similar to the example. The Leakage Module is used to detect changes in the transistor's on-resistance of the balanced network-circuit based on the PA 896 output. For example, if the output of the willow is increased, the balance network _ transistor's on-resistance will change. This changes the overall impedance of the balanced network_. Corresponding (d) Leakage Detection 9Q6 Module ^ 102 201212553 On-resistance changes and provides a representative signal to tuning engine 904 and/or processing module (as shown in Figure 91). The tuning engine 9〇4 adjusts the impedance of the balancing network 900 based on the input of the leak detection 906 module. Alternatively or in addition, the processing module uses the input from the leak detection 906 module to adjust the ATU settings. Regardless of which particular method is employed, the variation in the on-resistance of the transistor in the balance network 900 and/or in the power amplifier is compensated. Figure 98 is a schematic block diagram of a portion of a front end module (fem) 910 and a portion of a SOC 912, in accordance with another embodiment of the present invention. This portion of the FEM 910 includes a power amplifier module (ΡΑ) 916, a duplexer 918, a balanced network 920, and a common mode mitigation circuit. The duplexer 918 includes a transformer (or other structure, such as a frequency selectable duplexer 918 and/or an electronically balanced duplexer 918) that includes at least one variable resistor and at least one variable capacitor. The common mode sensing circuit includes a pair of resistors connected between the secondary of the transformer. This portion of SOC 912 includes peak detector 922, processing module 926 (which includes the functionality of the tuning engine), and low noise amplifier module (LNA) 924. Alternatively, the peak detector 922 and/or the tuning engine can be located in the FEM 910. For the ability to adjust the chirp attenuation and/or rx gain of duplexer 918, the functionality of this embodiment is similar to the embodiment shown in FIG. For example, when the transmit power is relatively low (eg, the blockage of the inbound RF signal is small and/or the signal strength of the signal at the inbound is relatively high), the processing module 926 provides a signal to the duplexer 918 to enable duplexing. The 918 reduces the enthalpy attenuation, thereby reducing insertion loss. For example, if the duplexer 918 includes a transformer and/or other type of frequency selectable duplexer 918 as shown in Fig. 90, a partial filter can be shorted to increase her by the generation of the 2012. As another example, if the double guard (10) includes an electronic balance duplexer, the separation can balance the separation phase balance of the network. Figure 疋 According to the local Ming and other examples of the front-end module (yang 930 and part of the S0C 932 schematic block diagram. This part of the 93 包括 includes the power amplifier module (PA) 936, duplexer 938 and balance network Road _. Duplexer 938 includes transformer H (or other structure, such as frequency selectable duplexer (10) ^ or electronic balance double 4 (10)), parasitic capacitance and mineral capacitance, the balanced network includes a variable resistance and at least - Variable capacitance. The common mode sensing circuit includes a pair of resistors connected between the transformer secondary. This part of the s〇c 932 includes a peak detector, a processing module (including the function of the tuning engine), and a low noise amplifier. Module (LNA) 940. Only LNA 94 is shown. In this embodiment t, the compensation capacitor is added to compensate for the parasitic capacitance (eg, 卬 and Cp2), which is due to the primary coil (eg, li and ^) Therefore, the compensation capacitor (Ccl and Μ) is selected to make Cpl+CcBu CP2+Ce2. After adding the compensation capacitor, the duplexer's separation bandwidth is larger than the separation bandwidth without the compensation capacitor. 〇〇 is another embodiment in accordance with the present invention A schematic block diagram of a portion of the front end module (FEM) 950 and a portion of the LNA 952. This portion of the FEM includes a power amplifier module (PA) 954, a duplexer 956, and a balanced network 958. The duplexer 956 includes a transformer (or other Structure 'inventory flat thief: please), can (four) Cp4). The LNA 952 includes an input transistor, a bias transistor, an inductor (L3), and a load impedance (Z), wherein the input transistor has a parasitic capacitance (Cp). Since the L3 ’ duplexer 956 and the 952 common mode interval 104 201212553 are included in the LNA 952, the input configuration is improved compared to the traditional LNA 952. Figure 101 is a schematic representation of a portion of the front end module (FEM) and a portion of the LNA _ effect shown in Figure 1 of the present invention. This schematic shows how the common mode spacing is improved. The unbalanced current connected to the secondary coil (L) through the parasitic capacitance (Cp3 and CP4) of the transformer is connected to a different spectral circuit, which is formed by the domain (L3) and the parasitic capacitance of the input transistor. The resonant circuit provides high differential impedance and low common mode impedance. Figure 102 is a schematic block diagram of a portion of a front end module (FEM) 960 and a portion of a SCC %2 in accordance with another embodiment of the present invention. This part of Cong 96〇 includes power amplifier module (PA), duplexer, balanced network 97〇 and common mode sensing circuit. The double includes the marrow|| (or other structure, such as a freshly selectable duplexer and/or an electronically balanced duplexer), and the balanced turn includes at least one variable resistor and a variable electric valley. The common mode sensing circuit includes a pair of resistors connected between the secondary of the transformer. This portion of the SOC 962 includes a peak detector 974, a processing module 976 (which includes the functionality of the tuning engine), and a single-ended low noise amplifier module (LNA) 972. Alternatively, the peak detectors 9-4 and/or the metrology engine can be located in the FEM 960. In this embodiment, the common mode spacing is substantially eliminated by using a single-ended LNA 972. The functions of the FEM 960 and other parts of the SOC 962 shown in the figure are as described above. Figure 103 is a schematic block diagram of a transformer of a duplexer including a primary coil (L1 & L2) and a secondary coil (L2), in accordance with one embodiment of the present invention. The primary coils each have the same number of turns; the secondary coils can have the same number of turns or different turns as the primary coil. The winding of the coil is as shown. 105 201212553 Figure 104 is an illustration of the implementation of the variation (4) implemented on the four thick metal layers of the IC package substrate and/or the integrated circuit on the printed circuit board in accordance with one embodiment of the present invention. The primary coil is on the upper two layers and the secondary coil is on the lower two layers. The first coil of the secondary layer on the - layer can be connected in series or in parallel with other coils on the other layers. Figure 105 is a schematic illustration of an implementation of a transformer on an IC armor substrate and/or three thick metal layers of 1C on a barbed circuit board in accordance with one embodiment of the present invention. The primary coil is located on the top layer and is used under the interconnection ^ at least one primary coil can be rotated 90. . The secondary coil is located on the third layer below. Figure 106 is a schematic block diagram of a portion of a front end module (FEM) 990 and a portion s〇c 992 in accordance with another embodiment of the present invention. This part of Cong 99〇 includes power amplifier module (PA) 994, duplexer 9%, balanced network 1〇〇〇, tone injection module 998 and common mode sensing circuit. The duplexer _ includes a transformer (or other structure such as a frequency selective duplexer 9% 电 or an electronically balanced duplexer 996) that includes at least one variable resistor and at least one variable capacitor. The common mode sensing circuit includes - a pair of resistors connected between the secondary of the transformer. This part of the S0C 962 includes the peak detector biliary, the processing module brain (the quoting element), the baseband alcohol element, and the sounding amplifier module (LNA) 1006. Alternatively, the peak detectors can be located in the FEM 990. In a running example, the functions of the ...., the analog sensing circuit, the engine, the inspection and balancing network 1000 are as described above. In the case of multiple reports, each receiver band is lower than or equal to LNA1__decombination and pieces; small transmitter (τχ) and/or receiver (RX) noise. When τχ~ or 杂 106 201212553 is at or below the noise platform, it is difficult to trace the impedance of the antenna. To enhance tracking of the antenna impedance, the tone module 998 injects a tone into the receiver band (eg, Ac〇s (0r^(9)). The duplexer 996 attenuates the RX tone differently than the TXk number because it is located In the rx band, and the duplexer 996 and the balanced network 1 are tunable for the τ χ band. Therefore, an easily detectable leakage signal is generated on the RX side of the duplexer 996 (e.g., on the secondary of the transformer). The leakage signal based on the RX tone propagates through the receiver section until it is converted to a baseband signal. At baseband, the tone amplitude is a measure of the RX band spacing. Depending on the measured value of the RX band spacing, the impedance of the antenna can be determined. The impedance change 'can adjust the antenna tuning unit and/or the balance network 1000 to track the impedance of the antenna. Note that the tone can be easily removed at the baseband. Figure is a partial front end module (FEM) according to another embodiment of the present invention A schematic block diagram of 1010 and part s〇c 1〇12. This part of FEM1〇1〇 includes power amplifier module (pA) 1〇14, duplexer 1〇16, balanced network 1018 and common mode sensing circuit ( Not shown The duplexer includes a transformer (or other structure, such as frequency selective duplexer 1〇16 and/or electronically balanced duplexer 1016.) The common mode sensing circuit includes a pair of resistors connected between the transformer secondary. This portion of the view includes the peak detector dirty (not shown), the processing module 1020 (which performs the functions of the tuning engine), and the low noise amplifier module (LNA) 1022. Alternatively, the peak detector 1〇〇2 and The tuning engine can be located in the FEM 1010. The balancing network 1018 includes an RLC network having a plurality of 107 201212553 variable resistors, a plurality of variable capacitors, and at least one inductor. In this embodiment, ... The network 1018 is balanced to provide a substantially variable impedance to better match the antenna impedance. FIG. 108 is a schematic block diagram of the impedance of a balanced body (RT) circuit in accordance with an embodiment of the present invention. The capacitance is equivalent to the capacitance of the transistor. Since the RT circuit includes a true passive resistor, it can contribute to the 3dB theoretical limit on the insertion loss. Figure 1-9 is a balanced network in accordance with another embodiment of the present invention. The resistance- A schematic block diagram of the impedance of a transistor (RT) circuit. In this embodiment, the r_t circuit includes an inductively weakened common-source transistor. Therefore, it is an active resistor, not a 3dB theory of insertion loss. The limit contributes. Therefore, the only loss of the balanced network is the implementation loss. Figure 110 is a schematic block diagram of a balanced network 1〇3〇 according to an embodiment of the invention, which includes impedance upconversion H 1G32 and Or multiple baseband impedances (full 1034). The impedance upconverter is synchronized with the desired frequency (eg fL〇 or y. The combination of impedance upconversion H 1G32 and baseband impedance can be implemented in accordance with the above m-phase variable frequency bandpass filter) . Figure 111 is a schematic block diagram of a balanced network in accordance with another embodiment of the present invention, including two impedance upconverter legs, 1044 and corresponding baseband impedances (zbb 1046, 1048). Each impedance upconverter is synchronized to the desired frequency (eg fRF τχ or fRF_RX). Each combination of impedance upconverters 1〇42, 1〇44 and one or more baseband impedances can be implemented in a manner similar to the m-phase variable frequency band-waves described above. Figure 112 is a schematic block diagram of a negative 108 201212553 impedance 1050 for balancing a network, in accordance with one embodiment of the present invention. The circuit includes a baseband negative impedance 1〇5〇 circuit. For example, as shown in Fig. 56, the anti-upconverter 1052 can be implemented in a manner similar to the m-phase variable frequency band pass filter described above. Figure 113 is a schematic block diagram of a polarization receiver 1〇6〇 including a phase-locked loop (PLL) 1068, an analog-to-digital converter (ADC 1064, 1066), and a phase processing module 1〇62, in accordance with one embodiment of the present invention. The peak detector 1〇7〇 and the amplitude processing module 1062. The PLL 1068 includes a phase and frequency detector (pFD), a charge pump, a loop filter, a voltage controlled oscillator (VC0), a frequency divider (which can be a 1:1 divider), a summing module, and a modulator ( Sigma_ddta) module. In one operational example, the antenna receives an inbound signal (e.g., AOOcosCwRFOO+e(9)) and provides it to the PLL 1068 and peak detector 1070 of the receiver section via an FEM (not shown). The peak detector 1〇7〇 (possibly the envelope detector) separates the amplitude term (eg A(1)). The amplitude term is then converted to a digital signal by a£>c 1064, 1066. PLL 1〇68 processes the cos^Rpie+eCt) of the signal at the inbound to extract the phase signal (e.g., θ(1)). Processing module 1062 parses the amplitude and phase signals to recover the transmitted data. Figure U4 is a schematic block diagram of a scratchpad circuit that can be used to connect a local oscillator PLL 1082 to a mixer of a downconversion mixing module and/or an upconversion mixing module, in accordance with one embodiment of the present invention. . The scratchpad circuit includes a differential register and a braided connection 1086. The braided connection 1086 produces an increased inductance (relative to the parallel line)' thereby attenuating undesirable high frequency components to the mixer. In addition, the size and nature of the braided connection 1086 can be selected to achieve the desired inter-line capacitance, resulting in a tuned and distributed L-C circuit. Figure 115 is a schematic illustration of an interleaving connection 11 109 201212553 block diagram 'which includes a first line on a substrate (e.g., die, package substrate, etc.) layer on her substrate (the other layer) -line. This pavement layer is interwoven to increase magnetic compatibility with each other. In addition, at least one line can be looped to increase its honesty. Figure 116 is a schematic block diagram of a receiver including a wheeling section, a downconversion mixing section, and a transimpedance amplifier (TIA 1126, 1128) in accordance with an embodiment of the present invention. The input section includes a MN m2, a gain module, an inductor, and a capacitor. The downconverting mixing section includes a mixer and a local oscillator. The TIA1126 and 1128 respectively include a crystal and a resistor connected as shown in the figure. Note that the positive input can also be used to connect the resistor to the common node on the positive output, and the drain is connected to the common node between the resistor and the transistor on the negative output. As used herein, the term "substantially," or "about," provides an acceptable tolerance to the corresponding term and/or component. This industry-acceptable public is less than 1% to m and is used for, but not limited to, component values, integrated circuit processing fluctuations, temperature fluctuations, rising and falling coffee, and/or thermal noise. The relationship between components varies from a small percentage difference to a large difference. Also possible herein is a operative connection, "connection" and/or "coupling", including through intermediate elements (eg, 'the element includes, but is not limited to, elements, elements, circuits, and/or modes Group) direct and/or indirect connections, where for intermediate connections, the intermediate insertion element does not change the information of the apostrophe, but its current level, voltage level and/or power level can be adjusted. It is also possible in this paper to infer connections (that is, one element is connected to another element according to inference), including direct and indirect connections between dragon elements using the same method as "operably connected." The term "operably connected" means that the element comprises the following one or more: power connection 110 201212553 connection, input, output, etc., for performing one or more corresponding functions at startup and may further include - «Multiple other components _ broken connection. As used herein, the term "associated" as used herein may include a direct and/or indirect connection of a single element and/or an element that is interspersed with another element. It may also be used herein that the term "comparison results are advantageous, as may be used herein, to refer to a comparison between two or more elements, 彳§, etc. to provide a desired relationship. For example, when desired Hidden is that the health of the 丨 _ _ _, when the amplitude of the signal is greater than the amplitude of the signal 2 or the amplitude of the signal 2 is less than the amplitude of the signal ,, can obtain favorable comparison results. The crystal is a field effect transistor (five), but those skilled in the art should understand that the above transistor can be made into any type of crystal structure, including but not limited to, bipolar, metal oxide semiconductor field effect transistor (MOSFET). , N-well transistor, p-well transistor, yaw type, depletion mode, and zero voltage threshold (VT) transistor. The above description helps explain the function of the fingerprint and the method steps of the invention. Miscellaneous, suspending the ship's method of stepping down the county. _. Fine, only dodging functions and relationships are properly implemented, boundaries and order changes are allowed. The boundaries or order of any of the above changes should be considered as the face Within the scope of the system. The present invention has been described with respect to the embodiments of the present invention, which are used to illustrate the aspects, features, concepts and/or examples of the present invention. The machine and / = physical compensation may include at least one of the aspects, features, concepts, examples, etc. described in the description of the present invention. 111 201212553 - The above also means by means of (four) some important Wei's Wei model Saki has made a description of the invention. For the convenience of description, the boundaries of these functional components are defined here. When these important Weis are properly cleared, changing their boundaries is allowed. Similarly, the process The graph module is also specifically defined here to illustrate some important functions. For a wide range of applications, the boundaries and order of the flowchart module can be additionally defined as long as these important functions can still be realized. Variations in the boundaries and order of the functional modules are still considered to be within the scope of the claims. Those skilled in the art are also aware of the functional modules described herein, and other illustrative modules, The group and elements may be combined as an example or by a discrete component, a special function integrated circuit, a processor with appropriate software, and the like. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a schematic diagram of a prior art wireless communication device. 2 is a schematic block diagram of a portable computing communication device in accordance with one embodiment of the present invention; FIG. 3 is a schematic block diagram of a portable computing communication device in accordance with another embodiment of the present invention; A schematic block diagram of a portable computing communication device in accordance with another embodiment of the present invention; FIG. 5 is a schematic block diagram of a portable computing communication device in accordance with another embodiment of the present invention; FIG. 6 is another embodiment of the present invention. A schematic block diagram of a portable computing communication split; 112 201212553 FIG. 7 is a schematic block diagram of a portable computing communication device in accordance with another embodiment of the present invention; FIG. 8 is a portable embodiment in accordance with another embodiment of the present invention. FIG. 9 is a schematic block diagram of a portable computing communication device in accordance with another embodiment of the present invention; FIG. 10 is another embodiment of the present invention. FIG. 11 is a schematic block diagram of a portable computing communication device in accordance with another embodiment of the present invention; FIG. 12 is a portable computing communication in accordance with another embodiment of the present invention. Figure 13 is a schematic block diagram of a portable computing communication device in accordance with another embodiment of the present invention; Figure 14 is a schematic block diagram of a portable computing communication device in accordance with another embodiment of the present invention; 15 is a schematic block diagram of an RF-IF receiver section of a SOC according to an embodiment of the present invention; FIG. 16 is a block diagram of an RF-IF receiver section of a SOC according to another embodiment of the present invention, and FIG. 17 is A schematic block diagram of an RF-IF receiver section of a SOC according to another embodiment of the present invention; FIG. 18 is a schematic block diagram of an RF-IF receiver section of a SOC according to another embodiment of the present invention; 113 201212553 FIG. A schematic block diagram of a sigma receiver portion of a soc according to another embodiment of the present invention; FIG. 20 is a schematic block diagram of an ugly receiver portion of a SOC according to another embodiment of the present invention; Another embodiment of the SO of the invention FIG. 22 is a schematic block diagram of a ^p_IF receiver section of s〇C according to another embodiment of the present invention; FIG. 23 is a transmitter section of a SOC according to an embodiment of the present invention. Figure 24 is a schematic block diagram of a transmitter portion of s〇c in accordance with an embodiment of the present invention; Figure 25 is a diagram including fTBPf (frequency bandpass filter) in accordance with an embodiment of the present invention. A schematic block diagram of a portion of an RF-IF receiver portion; Figure 26 is a schematic block diagram of a clock generator for the rp_iF receiver portion in accordance with an embodiment of the present invention; Figure 27 is an RF diagram in accordance with one embodiment of the present invention. Figure 28 is a schematic block diagram of an FTBPF according to an embodiment of the present invention; Figure 29 is a schematic diagram of phase and frequency response of a baseband component of an FTBPF according to an embodiment of the present invention; 30 is a schematic diagram of phase and frequency response of an RF component of an FTBPF according to an embodiment of the present invention; FIG. 31 is an RF-IF receiving If component including an FTBPF (frequency conversion band 114 201212553 pass filter) according to another embodiment of the present invention; part Figure 32 is a schematic block diagram of a clock generator for aligning receiver components in accordance with another embodiment of the present invention; Figure 33 is a _11? receiver component in accordance with another embodiment of the present invention. FIG. 34 is a schematic block diagram of a portion of a purchase (four) receiver portion including an FTBpF (frequency conversion band pass filter, wave device) according to another embodiment of the present invention; FIG. 35 is another embodiment of the present invention. A schematic block diagram of a clock generator for a _ positive receiver component; . 36 is a schematic diagram of frequency response of a positive receiver component in accordance with another embodiment of the present invention; and FIG. 37 is an RF-IF reception including FTBpF (frequency conversion chopper) in accordance with another embodiment of the present invention. FIG. 38 is a schematic block diagram of a clock generator for a brain F receiver portion according to another embodiment of the present invention; FIG. 39 is a grasping diagram according to another embodiment of the present invention. A schematic diagram of a positive receiver portion rate response; FIG. 4A is a schematic block diagram of a portion of an RF-IF receiving H portion including an FTBPF (frequency conversion band pass; wave filter) according to another embodiment of the present invention; A schematic block diagram of a clock generator for a positive-positive receiver portion in accordance with another embodiment of the present invention; FIG. 42 is a schematic diagram of a rate response of a grab receiver portion in accordance with another embodiment of the present invention; A schematic block diagram of a portion of an RF_IF receiver portion including an FTBpF (frequency band 115 201212553 wanted, wave) in accordance with another embodiment of the present invention; FIG. 44 is a diagram for use in accordance with another embodiment of the present invention. Schematic diagram of the clock generator of the receiver section Figure 45 is a schematic block diagram of a portion of an RF-IF receiver section including an fTBPF (Frequency Variable Bandpass Filter) in accordance with another embodiment of the present invention; Figure 46 is a diagram for use in accordance with another embodiment of the present invention; Figure 47 is a schematic block diagram of a complex baseband (BB) filter in accordance with one embodiment of the present invention; Figure 48 is a plurality of BBs in accordance with one embodiment of the present invention. A schematic diagram of a filter frequency response converted to a high Q RF chopper frequency response; FIG. 49 is a partial (four) frame of an RF_IF connection (four) portion including an FTBpF (frequency bandpass data filter) in accordance with another embodiment of the present invention. Figure 50 is a schematic block diagram of a clock generator for a liver_positive receiver in accordance with another embodiment of the present invention; σ Figure 51 is a schematic diagram of a team positive receiver rate response in accordance with another embodiment of the present invention; 1 Figure 52 is an RP-IF reception including FTBpF (variable filter, waver) in accordance with another embodiment of the present invention. A schematic block diagram of a portion of n; FIG. 53 is a schematic block diagram of a clock generator received according to another embodiment of the present invention; FIG. 54 is a diagram showing an FTBpF according to another embodiment of the present invention. A schematic block diagram of a portion of the F receiver portion of the (variable waver); FIG. 55 is a schematic block diagram of a clock generator for the muscle positive receiver portion 116 201212553 according to another embodiment of the present invention; 56 is a schematic block diagram of a negative resistance according to an embodiment of the present invention; FIG. 57 is a schematic block diagram of a portion of an RF-IF receiver section including an FTBPF (Frequency Variable Bandpass Waver) according to another embodiment of the present invention; Figure 58 is a schematic block diagram of a clock generator for a receiver portion according to another embodiment of the present invention; Figure 59 is a diagram including a ftbpf (frequency band pass filter) according to another embodiment of the present invention. A schematic block diagram of a portion of the RF-IF receiver section; 60 is a schematic block diagram of a clock generator for the _11? receiver section in accordance with another embodiment of the present invention; FIG. 61 is a frequency of the first LO of the receiver portion in accordance with one embodiment of the present invention. Figure 62 is a schematic diagram of the frequency response of the second LO at the positive receiver portion; Figure 63 is a diagram showing the inclusion of an FTBpF (frequency bandpass filter) in accordance with another embodiment of the present invention. Figure 64 is a schematic block diagram of a portion of a f-receiver portion including a mixer; Figure 65 is another embodiment of the present invention, in accordance with another embodiment of the present invention; FIG. 66 is a schematic block diagram of a transimpedance (TIA) amplifier according to an embodiment of the present invention; FIG. 67 is a schematic block diagram of a transimpedance (TIA) amplifier according to an embodiment of the present invention; A schematic block diagram of an embodiment comprising a FTBpF$low noise amplifier (LNA); 201212553 Figure 68 is a schematic block diagram of a 4-phase FTBPF (frequency bandpass chopper) in accordance with one embodiment of the present invention; One embodiment of the present invention FIG. 70 is a schematic block diagram of a 3-phase FTBPF (frequency conversion band pass filter) according to another embodiment of the present invention; FIG. 71 is a 3-phase FTBPF according to an embodiment of the present invention. Figure 72 is a schematic diagram of the frequency response of a 3-phase FTBPF in accordance with one embodiment of the present invention; Figure 73 is a schematic block diagram of a 4-phase FTBPF in accordance with another embodiment of the present invention; Schematic block diagram of a 4-phase FTBPF of one embodiment; FIG. 75 is a schematic block diagram of a 4-phase FTBPF according to another embodiment of the present invention; FIG. 76 is a schematic block diagram of a 4-phase FTBPF according to another embodiment of the present invention; Figure 77 is a block diagram of a complex baseband impedance of an FTBPF in accordance with one embodiment of the present invention; Figure 78 is a schematic illustration of a 4-phase FTBPF in accordance with one embodiment of the present invention, and Figure 79 is a block diagram of a 4-phase FTBPF in accordance with one embodiment of the present invention. Schematic block diagram of a m-phase FTBPF; 118 201212553 FIG. 80 is a schematic block diagram of a phase FTBPF according to an embodiment of the present invention; FIG. 81 is a schematic block diagram of an m-phase FTBPF according to an embodiment of the present invention; A schematic block diagram of an m-phase FTBPF according to an embodiment of the present invention, FIG. 83 is a schematic block diagram of an m-phase FTBPF according to an embodiment of the present invention; and FIG. 84 is a frequency response of an m-phase FTBPF according to an embodiment of the present invention. Figure 85 is a schematic block diagram of clock generation of an m-phase FTBPF according to an embodiment of the present invention; Figure 86 is a schematic block diagram of a clock generator of an m-phase FTBPF according to another embodiment of the present invention; A schematic block diagram of a clock generator of a claw phase FTBPF according to another embodiment of the present invention; FIG. 88 is a schematic block diagram of a clock generator of a 3-phase FTBPF according to an embodiment of the present invention; FIG. 89 is another A schematic block diagram of a clock generator for a 3-phase FTBPF of an embodiment; FIG. 90 is a schematic block diagram of a portion of each of a front-end module (FEM) and a SOC, in accordance with one embodiment of the present invention; A schematic block diagram of a front end module (FEM) and a portion of each of the SOCs of another embodiment;

119 S 201212553 FIG. 92 is a schematic block diagram of a portion of each of a front end module (fem) and a SOC according to another embodiment of the present invention; FIG. 93 is a front end module in a 2G TX mode according to an embodiment of the present invention. A schematic block diagram of a portion of each of (FEM) and SOC; FIG. 94 is a schematic block diagram of a portion of each of the front end module (FEM) and SOC in 2GTX mode, in accordance with one embodiment of the present invention; Is a schematic block diagram of a small signal balancing network in accordance with one embodiment of the present invention; FIG. 96 is a schematic block diagram of a large signal balancing network in accordance with one embodiment of the present invention; FIG. 97 is a front end in accordance with another embodiment of the present invention. A schematic block diagram of a module (FEM) and a portion of a parent in the SOC; FIG. 98 is a schematic block diagram of a front end module (FEM) and a portion of the parent in the SOC according to another embodiment of the present invention; Is a schematic block diagram of a portion of each of a front end module (FEM) and a SOC according to another embodiment of the present invention; FIG. 100 is a diagram of each of a front end module (FEM) and an LNA according to another embodiment of the present invention. of BRIEF DESCRIPTION OF THE DRAWINGS FIG. 101 is a schematic block diagram of an equivalent circuit of a portion of each of a front end module (FEM) and an LNA in accordance with one embodiment of the present invention; FIG. 102 is another embodiment of the present invention A schematic block diagram of a portion of each of a front end module (FEM) and an LNA; FIG. 103 is a schematic block diagram of a transformer balim in accordance with one embodiment of the present invention; 120 201212553 FIG. 104 is a diagram in accordance with the present invention Schematic diagram of a transformer balun of an embodiment; FIG. 105 is a schematic diagram of a transformer balun according to another embodiment of the present invention; FIG. 106 is a front end module (FEM) according to another embodiment of the present invention. Schematic block diagram of a portion of each of the LNAs; and FIG. 107 is a schematic block diagram of a portion of each of a front end module (FEM) and an LNA in accordance with another embodiment of the present invention; FIG. Schematic block diagram of impedance of one embodiment; FIG. 109 is a schematic block diagram of impedance in accordance with another embodiment of the present invention; FIG. Schematic block diagram of a balanced network of an embodiment; Figure 111 is a schematic block diagram of a balanced network in accordance with another embodiment of the present invention; Figure 112 is a schematic block diagram of a negative impedance in accordance with one embodiment of the present invention; A schematic block diagram of a polarization receiver according to an embodiment of the present invention, FIG. 114 is a schematic block diagram of a register circuit according to an embodiment of the present invention; FIG. 115 is a braided connection according to an embodiment of the present invention ( Schematic block diagram of a weaved connection; Figure 116 is a schematic block diagram of a receiver in accordance with one embodiment of the present invention. [Main component symbol description] Portable computing communication device 10 System-on-a-chip (S0C) 12 Front-end module (KEM) 14 Antenna 16

121 S 201212553 Surfaceless Acoustic Receiver Unit 18 Surface Acoustic Wave Transmitter Unit 20 Baseband Processing Unit 22 Processing Module 24 Power Management Unit 26 Receiver (RX) Radio Frequency (RF) - Intermediate Frequency (IF) Section 28 Receiver (RX IF-Baseband (BB) Part 30 1 Variable Frequency Band Filter (FTBPF) 32 Power Amplifier (PA) 34-36 Receiver-Transmitter (RX-TX) Separation Module 38-40 Antenna Tuning Unit (ATU) 42 -44 Band (FB) Switcher 46 Front End Module (FEM) 50 System-on-Chip (SOC) 52 Antenna Tuning Unit (ATU) 54 Front End Module (FEM) Network 60 Front End Module (FEM) 62-68 RF Connection 70 RF Connection 78 Front End Module (FEM) Network 80 Frequency Conversion Module 82 RF-RJF Frequency Conversion Module 86 RF Connection 90 System-on-Chip (SOC) 100 System-on-Chip (SOC) 110 Intermediate Frequency (IF) · Baseband (BB) Receiver Part 112 BB_IF Transmitter Unit 114 Front End Module (FEM) Network 120 RP Connection 122 RXRF-IF Unit 124-130 TXIF-RF Unit 132-138 System on Chip (SOC) 140 Terminal Module (FEM) Network 142 Frequency (IF)-baseband (bb) receiver section 144 BB_IF transmitter section 146 RXRF-IF section 148 TXIF-RJF section 150 RF connection 152-154 on-chip System (s〇c) 160 Front End Module (FEM) Network 162 122 201212553 No SAW Receiver (RX) Downconverter 164 No SAW Transmitter (TX) Upconverter 166 FEM 168-174 RF Connection 176 System on Chip ( SOC) 180 Front End Module (FEM) 182 System-on-Chip (SOC) 190 Front End Module (FEM) 192 System-on-Chip (SOC) 200 No SAW Transmitter Unit 202 RF-IF Receiver Unit 204 Low Noise Amplifier Module (LNA) 206 Mixing Module 208 Mixing Register 210-212 Register 214-220 Variable Frequency Pass Filter (FTBPF) 222 Receiver IF-BB Section 224 System on Chip (SOC) 230 RF-IF Receiver Section 232 Variable Frequency Band Filter (FTBPF) 234 Filter 236, 238 System on Chip (SOC) 240 RF-IF Receiver Unit 242 Low Noise Amplifier Module (LNA) 244-246 Mixing Module 248 Transimpedance Amplifier (TIA) 250-252 Impedance (Z) 254-256 Register 258-260 System on Chip (SOC) 270 RF-IF Receiver Section 271 RF Variable Frequency Bandpass Filter (FTBPF) 272 Low Noise Amplifier Module (LNA) 274- 276 Mixing Module 278 Transimpedance Amplifier (TIA) 280-282 Impedance (Z) 284-286 IF FTBPF 288 System-on-Chip (SOC) 290 RF-IF Connection Unit 292 IF FTBPF 294 System on Chip (SOC) 300 Dual Band RF-IF Receiver Unit 302 Variable Frequency Band Filter (FTBPF) 304 Low Noise Amplifier Module (LNA) 306-308 123 201212553 Mixing Module 310- 312 Mixing Register 314-320 Filter 322·328 System-on-Chip (SOC) 330 RF-IF Receiver Unit 332 RF Variable Frequency Bandpass Filter (FTBPF) 334 Low Noise Amplifier Module (LNA) 336 Variable Frequency Band Filter (FTBPF) 338 Mixing Module 340 Mixing Register 342-344 Filter 346-348 System on Chip (SOC) 350 Variable Frequency Pass Filter (FTBPF) Low Noise Amplifier Module (LNA) System-on-Chip ( SOC) 360 Upconverting Mixing Module 362 Transmitter Local Oscillation Module (LO) Variable Bandpass Filter (FTBPF) RF-IF Receiver Section 352 354 356 364 366 Capacitor Array 368-370 System on Chip (SOC) 380 FEM 390 Single-Ended Frequency Bandpass Filter (FTBPF) Baseband Impedance (Zbb(8)) 396-402 Clock Generator 404 Differential FTBPF 412 Clock Generator 422 Complex Baseband Filter 432 Differential FTBPF 440 Clock Generator 444 Power Amplifier Driver (PAD) 372 Transmit Department 382 LNA 392 394 Single FTBPF 410 baseband impedance (ZBB(8)) 414-420 single-ended FTBPF 430 clock generator 434 complex baseband filter 442 baseband impedance (ZBB(S)) 450-456 124 201212553 positive gain stage (Gm) 458 control module 470 adjustable baseband Impedance 480 Adjustable Negative Gain Stage 490 Programmable Switched Capacitor Network 494 Q RF-IF Mixer 500 I Mixer 504 I Mix Register 522 Negative Gain Stage (-GM) 460 Clock Generator 476 Adjustable Positive gain stage 488 Optional capacitor network 492 Programmable switched capacitor filter 496 Mix register 502 Clock generator 510 Q Mix register 523 IFFTBPF (frequency band pass filter) module 53 〇 baseband impedance ( ZBBz(s)) 532, 534, 536, 538, 540, 542, 544, 546 Clock Generator 550 Single-Ended FTBPF 560 Baseband Impedance (ZBB(8)) 562, 564, 566, 568 Clock Generator 572 Differential FTBPF 580 Clock Generator 582 Dual Band Variable Frequency Bandpass Filter (FTBPF) 590 Baseband Impedance (ZBB(s)) 592, 594, 596, 598 Clock Generator 600 Dual Band Differential Frequency Bandpass Filter (FTBPF) 610 Baseband Impedance (ZBB(s) ) 612 >614 >616 > 618 Transimpedance Amplifier (TIA) 622, 624 Related Impedance (Z) 626, 628 Differential I 630 Differential Q 632 Clock Generator 634 Corresponding Impedance (Z) 640, 642 Low Noise Amplifier (LNA) 670 FTBPF 650, 672, 674, 678 4 Phase FTBPF 680

125 S 201212553 Baseband Impedance ZBB(s) 682, 684, 686, 688 Superimposed 彳 § Harmonic 690 Signal Feedthrough Spectrum 692 3-Phase FTBPF (Frequency Conversion Bandpass Filter) 700 Baseband Impedance ZBB(8) 702, 704, 706 t Feedthrough Wave 708 Superimposed Signal Wave 710 4-phase FTBPF (Frequency Bandpass Filter) 712 4-phase FTBPF (Frequency Bandpass Filter) 714 4-phase FTBPF (Frequency Bandpass Filter) 716 4-phase FTBPF (Frequency Bandpass Filter) 720 Complex baseband impedance ZBBC((〇) 722 Complex baseband impedance 726 Low Q baseband filter 730 m phase FTBPF (frequency conversion bandpass filter) 732 m phase FTBPF (frequency conversion bandpass filter) 734 m phase FTBPF (inverter Bandpass filter) 736 m phase FTBPF (frequency bandpass filter) 738 m phase FTBPF (frequency bandpass filter) 740 clock generator 750 flip flop (DFF) 752, 754, 756 pulse narrower 758, 760, 762

770 790 Ring Oscillator 800 Clock Generator 812, 814, 816 818, 820, 822 830 SOC Duplexer Clock Generator Clock Generator Clock Generator Clock Signal 1·3 Clock Signal 4-6 Front End Module (FEM) Power Amplifier Module (ΡΑ) 836 Trigger (DFF) 772, 774, 776 792 810 832 838 126 201212553 Antenna Tuning Unit (ATU) 840 Balanced Network 842 Lookup Table (LUT) 844 Processing Module 846 Peak Detector 848 Tuning Engine 850 Low Noise Amplifier Module (LNA) 852 Front End Module (FEM) 860 SOC 862 Power Amplifier Module (PA) 866 Peak Detector 872 Tuning Engine 874 Switch and Low Noise Amplifier Module (LNA) 876 Small Signal Balance Network 880 Large Signal Balancing Network 882 Front End Module (FEM) 890 SOC 892 Power Amplifier Module (PA) 896 Duplexer 898 Balanced Network 900 Peak Detector 902 Tuning Engine 904 Leak Detection 906 Module and Low Miscellaneous Amplifier Module (LNA) 908 Front End Module (FEM) 910 SOC 912 Power Amplifier Module (PA) 916 Duplexer 918 Balanced Network 920 Peak Detector 922 Low Miscellaneous Amplifier Module (LNA) 924 Processing Module 926 Front End Module (FEM) 930 SOC 932 Power Amplifier Module (PA) 936 Duplexer 938 Balanced Network 940 Front End Module (FEM) 950 LNA 952 Power Amplifier Module ( PA) 954 Duplexer 956 Balanced Network 958 Front End Module (FEM) 960 SOC 962 Balanced Network 970 127 201212553 Single-Ended Low Noise Amplifier Module (LNA) 972 Peak Detector 974 Processing Module 976 Front End Module ( FEM) 990 S0C 992 Power Amplifier Module (PA) 994 Duplexer 996 tone injection module 99S 1 Balanced Network 1000 Peak Detector 1002 Processing Module 1004 Low Noise Amplifier Module (LNA) 1006 Front End Module (FEM) 1010 SOC 1012 Power Amplifier Module (PA) 1014 Duplexer 1016 Balanced Network 1018 Processing Module 1020 Low Noise Amplifier Module (LNA) 1022 Balanced Network 1030 Impedance Upconverter 1032 Baseband Impedance ( Zbb) 1034 Impedance Upconverter 1042, 1044 Baseband Impedance (Zbb) 1046, 1048 Negative Impedance 1050 Anti-Upconverter 1052 Polarization Receiver 1060 Phase Processing Module 1062 Analog to Digital Converter (ADC) 1064, 1066 Phase-Locked Loop (PLL) 1068 Peak Detector 1070 Amplitude Processing Module 1072 PLL 1082 Braided Connection 1086 Interleaved Connection 1100 MN 1112 Transimpedance Amplifier (TIA) 1126, 1128 128

Claims (1)

201212553 VII. Patent application scope: 1. A portable computing device, comprising: a front end module connected to the antenna portion and configured to separate one or more outbound stations from one or more inbound radio frequency # numbers Radio frequency signal; surface acoustic wave receiver for: converting the one or more inbound radio frequency signals into one or more inbound IF signals by: converting the baseband filter response to an intermediate frequency filter response And at least one of the RF filter responses; filtering the one or more inbound radio frequency signals according to the RF filter response when the baseband filter responds to the RF filter response; and when the baseband filtering Filtering the one or more inbound intermediate frequency signals according to the intermediate frequency filter response when the response is frequency converted to the intermediate frequency filter; and converting the one or more inbound intermediate frequency signals into one Or a plurality of inbound symbol streams; a surface acoustic wave transmitter for converting one or more outbound symbol streams into the one or more outbound radio frequency signals; And a baseband processing unit for: converting the outbound data to the one or more outbound symbol streams; and converting the one or more inbound symbol streams into inbound data. 2. The portable computing device according to claim 1, wherein the package further comprises: <e^ 129 201212553, wherein the m-end module is served by one or more second persons Separating one or more second outbound radio frequency signals from the station radio frequency signal, wherein the one or more inbound and outbound radio frequency signals are located in a first frequency band, and the one or more second inbound radio frequency signals are located In the second frequency band; the surface acoustic wave receiver is further configured to: convert the one or more second human station radio frequency signals into one or more second inbound intermediate frequency signals by the following steps, wherein: a baseband chopper response frequency conversion is at least one of a second intermediate frequency waver response and a second RF filter response; and when the second baseband detector responds to the second RF chopper, the according to the Transmitting, by the second surface wave, the one or more second inbound radio frequency signals; and when the second baseband carrier responds to the second intermediate frequency chopper response IF filter 'wave detector response test - one or more second inbound IF No.: and converting the one or more second person station intermediate frequency signals into one or more second inbound symbol streams; The silk acoustic wave transmission n further converts one or more second outbound symbol streams into the one or more second outbound radio frequency signals; and the baseband processing unit is further configured to: Transmitting the station data into the one or more second outbound symbol streams; and converting the one or more second person station symbol streams into a second inbound 130 201212553 data. · 3, such as the scope of patent application! The portable computing device of the present invention, wherein the front end module comprises: , a day, a material element, and a line material to provide an impedance matching the impedance of the antenna portion; a plurality of power amplifiers for amplifying the one or more outbound radio frequency signals to generate one or more amplified outbound radio frequency signals; a separation module, and the surfaceless wave receiver, the antenna tuning unit And the one or more power amplifiers are connected, the separation module is configured to: output the one or more amplified outbound radio frequency signals to the antenna tuning unit; and in the separation module and the The one or more amplified outbound radio frequency signals are attenuated in the connection without the surface wave receiver to separate the one or more inbound radio frequency signals from the one or more outbound radio frequency signals. 4. The portable computing device of claim 3, wherein the baseband processing unit is further configured to generate at least one of: an antenna tuning unit control signal for changing impedance according to the antenna portion Adjusting an impedance of the antenna tuning unit; separating control signals for adjusting attenuation of the one or more output RF signals; and power amplifier control signals for adjusting one or more of the one or more power amplifiers parameter. 5. The expandable computing device of claim i, wherein the 131 201212553 surface-free wave transmitter comprises: , an up-converting mixed-surface group, wherein the one or more (four) symbol streams are returned Converting to one or more upconverted signals; transmitting a variable frequency bandpass chopper for: converting the second baseband to a second RF bandpass chopper response; and according to the second RF band Resolving one or more upconverted signals to produce one or more filtered upconverted signals; and an output module 'sense adjusting the one or more healthy, wave upconverted signals to produce one or a plurality of adjusted upconverted signals; and a power amplifier driver for amplifying the one or more adjusted upconverted signals to generate the one or more outbound radio frequency signals. 6. The portable computing device of claim 5, wherein the baseband processing unit is further configured to: generate a transmitter control signal, the transmitter control signal, to adjust at least one of the following: A second baseband filter response, the second RF bandpass filter response, and parameters of the power amplifier driver. 7. The portable computing device of claim 1, wherein the surface-free wave receiver comprises: a radio frequency-intermediate frequency receiver unit, comprising: a low noise amplifier 'for amplifying the one Or a plurality of inbound radio frequency signals to generate one or more amplified inbound radio frequency signals; an intermediate frequency down conversion module configured to convert the one or more amplified ingress 132 201212553 station radio frequency signals into the one or a plurality of inbound IF signals; and a variable frequency bandpass filter having the RF bandpass filter response, for filtering the one or more inbound RF signals or filtering the one or more inbounds And an intermediate frequency-baseband receiver section for converting the one or more inbound intermediate frequency signals into one or more inbound symbol streams. 8. The portable computing device of claim 1, further comprising: a first integrated circuit for supporting the first baseband processing unit, the surfaceless wave receiver, and the a surface waveless transmitter; and a second integrated circuit for supporting the front end module. 9. The portable computing device of claim 1, wherein the portable computing device further comprises at least one of the following: a processing module, configured to: execute-deactivate multiple portable computing functions to generate the outbound data And executing the one or more portable computing device functions to process the input; and the power management unit 'for performing one or more power management functions of the portable computing device. A portable computing device, comprising: a front end module, wherein the front end module comprises: · a plurality of power amplifications n 'where the power amplifiers in the plurality of power amplifiers are amplified by a plurality of a first outbound radio frequency signal 133 201212553 in the station radio frequency signal; a plurality of separation modules, wherein the separation module of the plurality of separation modules separates the plurality of inbound radio frequencies from the first outbound radio frequency signal a first inbound radio frequency signal in the signal; and at least one antenna tuning unit for providing an impedance matching the impedance of the antenna portion based on the control signal, wherein the antenna tuning unit receives the first input from the antenna portion a radio frequency signal and outputting the first outbound radio frequency signal to the antenna portion; a surface acoustic wave receiver 'for converting a plurality of human station radio frequency signals into a plurality of inbound symbol streams; no surface acoustic wave transmitter, Converting a plurality of outbound symbol streams into the plurality of outbound radio frequency signals; and a baseband processing unit, configured to: generate the control signal according to an impedance change of the antenna portion; Converting a plurality of outbound data into the fine (four) trickle stream; and converting the plurality of inbound symbol streams into a plurality of inbound materials. 134